TW201939876A - Inverter device and inverter device control method - Google Patents

Inverter device and inverter device control method Download PDF

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TW201939876A
TW201939876A TW108103579A TW108103579A TW201939876A TW 201939876 A TW201939876 A TW 201939876A TW 108103579 A TW108103579 A TW 108103579A TW 108103579 A TW108103579 A TW 108103579A TW 201939876 A TW201939876 A TW 201939876A
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inverter
frequency
resonance
inverter device
output
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TW108103579A
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Chinese (zh)
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TWI721370B (en
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石間勉
田內良男
守上浩市
高田太郎
辻寬樹
伊藤政浩
茂野大作
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日商島田理化工業股份有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/06—Control, e.g. of temperature, of power
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The purpose of the present invention is to prevent displacement of the frequency of the output of an inverter unit from a resonant frequency even if performing output control, and to improve the characteristics of tracking a load of which the resonant frequency varies. An inverter device is a PWM-controlled voltage-type inverter connected to a resonant load and has: an inverter unit connected to the resonant load and driven by an inverter drive signal; and a control means for controlling the operation of the inverter unit. The control means, using a pulse signal having a pulse width shorter than the cycle of the resonant frequency of the resonant load as the inverter drive signal, starts driving of the inverter unit at a frequency away from the resonant frequency as a starting point. Then, the control means shifts the frequency of the inverter drive signal to the resonant frequency or a vicinity of the resonant frequency and performs control so that the frequency of the inverter drive signal substantially matches the resonant frequency.

Description

逆變器裝置及逆變器裝置之控制方法    Inverter device and control method of inverter device   

本發明係關於一種逆變器裝置及逆變器裝置之控制方法。更詳細而言，本發明係關於一種連接於共振負載而使用之逆變器裝置及逆變器裝置之控制方法。 The invention relates to an inverter device and a control method of the inverter device. More specifically, the present invention relates to an inverter device and a control method of the inverter device used in connection with a resonance load.

一般而言，作為連接於如感應加熱電路等之共振負載之電源裝置，已知有逆變器裝置。 In general, as a power supply device connected to a resonant load such as an induction heating circuit, an inverter device is known.

先前，於此種逆變器裝置中，作為對具有逆變器電路之逆變器部進行控制之逆變器控制部，使用一種由鎖相迴路(PLL：Phase Locked Loop)電路所構成之逆變器控制部，藉由該逆變器控制部而控制逆變器部。 Previously, in this type of inverter device, as an inverter control section that controls an inverter section having an inverter circuit, an inverter composed of a phase locked loop (PLL: Phase Locked Loop) circuit was used. The inverter control unit controls the inverter unit through the inverter control unit.

參照圖1(a)、(b)對由使用PLL電路之逆變器控制部所控制之先前公知之逆變器裝置進行說明。 A conventionally known inverter device controlled by an inverter control section using a PLL circuit will be described with reference to FIGS. 1 (a) and 1 (b).

再者，圖1(a)中示出構成說明圖，該構成說明圖表示由使用PLL電路之逆變器控制部所控制並且連接於共振負載之逆變器裝置之整體構成。 In addition, FIG. 1 (a) shows a configuration explanatory diagram showing the overall configuration of an inverter device controlled by an inverter control unit using a PLL circuit and connected to a resonant load.

又，圖1(b)中表示圖1(a)所示之逆變器裝置中之逆變器控制部之詳細之構成說明圖。 In addition, FIG. 1 (b) is a diagram illustrating a detailed configuration of an inverter control unit in the inverter device shown in FIG. 1 (a).

如圖1(a)所示般，逆變器裝置100係將自交流(AC)電源102所供給之交流電壓轉換成所需之電壓之高頻交流電壓，並 朝如感應加熱電路等之共振負載200供給者。 As shown in FIG. 1 (a), the inverter device 100 converts an AC voltage supplied from an AC (AC) power source 102 into a high-frequency AC voltage of a required voltage, and resonates toward an induction heating circuit or the like Load 200 providers.

再者，作為交流電源102，例如可使用商用交流電源，於該情形時，逆變器裝置100將商用交流電壓轉換成高頻交流電壓並朝共振負載200供給。 In addition, as the AC power source 102, for example, a commercial AC power source can be used. In this case, the inverter device 100 converts a commercial AC voltage into a high-frequency AC voltage and supplies the AC power to the resonance load 200.

更詳細而言，逆變器裝置100係具有如下部分而構成：轉換器部104，其具有將自交流電源102所供給之交流電壓輸入後轉換成直流(DC)電壓並輸出之轉換器電路；逆變器部106，其具有將自轉換器部104輸出之直流電壓輸入後逆轉換成高頻交流電壓並輸出之逆變器電路；輸出感測器108，其對來自逆變器部106之輸出(此處，所謂來自逆變器部106之「輸出」，係指自逆變器部106輸出之電壓即「輸出電壓Vh」、或自逆變器部106輸出之電流即「輸出電流Ih」、或自逆變器部106輸出之電力即「輸出電力」)進行檢測並將其檢測結果作為輸出感測器信號而輸出；轉換器控制部110，其基於自外部設定逆變器部106之輸出之信號即輸出設定信號及自輸出感測器108輸出之輸出感測器信號，對轉換器部104轉換之直流電壓進行反饋控制；及逆變器控制部112，其具有基於自輸出感測器108輸出之輸出感測器信號而對逆變器部106之動作進行反饋控制之PLL電路112a(參照圖1(b))。 In more detail, the inverter device 100 includes a converter unit 104 having a converter circuit that converts an AC voltage supplied from an AC power source 102 into a direct current (DC) voltage and outputs the converter circuit. The inverter section 106 has an inverter circuit that inversely converts the DC voltage output from the converter section 104 into a high-frequency AC voltage and outputs it, and an output sensor 108 for detecting the voltage from the inverter section 106. Output (here, the “output” from the inverter section 106 refers to the “output voltage Vh” that is the voltage output from the inverter section 106 or the “output current Ih” that is the current output from the inverter section 106 Or "output power" output from the inverter section 106) to detect and output the detection result as an output sensor signal; the converter control section 110 sets the inverter section 106 based on external settings The output signals are the output setting signal and the output sensor signal output from the output sensor 108, and perform feedback control on the DC voltage converted by the converter section 104; and the inverter control section 112, which has a Detector 108 output The PLL circuit 112a (refer to FIG. 1 (b)) which outputs a sensor signal and performs feedback control on the operation of the inverter section 106.

再者，轉換器部104之轉換器電路例如由閘流體(Thyristor)整流電路或斬波(chopper)電路等所構成。 The converter circuit of the converter unit 104 is constituted by, for example, a thyristor rectifier circuit or a chopper circuit.

此處，圖1(b)中示出了逆變器控制部112之詳細構成。於逆變器控制部112中，根據輸入至PLL電路112a中之輸出感測器信號，輸出作為供PLL電路112a驅動逆變器部106之逆變器驅動信號之矩形波逆變器驅動信號Q、NQ。 Here, a detailed configuration of the inverter control section 112 is shown in FIG. 1 (b). In the inverter control section 112, a rectangular wave inverter drive signal Q is output as an inverter drive signal for the PLL circuit 112a to drive the inverter section 106 according to the output sensor signal input to the PLL circuit 112a. , NQ.

再者，於本說明書及本申請專利範圍中，關於「矩形波逆變器驅動信號Q、NQ」，適宜地簡稱為「逆變器驅動信號」。 In addition, in this specification and the scope of the present patent application, the “rectangular wave inverter drive signals Q, NQ” are appropriately referred to simply as “inverter drive signals”.

於以上構成，在逆變器裝置100中，將交流電壓自商用交流電源等交流電源102輸入至轉換器部104。自交流電源102輸入了交流電壓之轉換器部104根據來自轉換器控制部110之控制信號對直流電壓進行可變控制，並朝逆變器部106輸出。 With the above configuration, in the inverter device 100, an AC voltage is input to the converter unit 104 from an AC power source 102 such as a commercial AC power source. The converter unit 104 that receives the AC voltage from the AC power source 102 performs variable control of the DC voltage according to a control signal from the converter control unit 110 and outputs the variable voltage to the inverter unit 106.

逆變器部106將自轉換器部104輸出而輸入之直流電壓根據構成逆變器電路之電晶體之ON(接通)/OFF(斷開)之開關動作而轉換成高頻電壓並輸出。 The inverter section 106 converts the DC voltage input from the converter section 104 and inputs it into a high-frequency voltage according to the ON / OFF switching operation of a transistor constituting the inverter circuit, and outputs the high-frequency voltage.

於逆變器裝置100中之逆變器部106之輸出級，如上所述般設置有輸出感測器108，輸出感測器108對來自逆變器部106之輸出(為輸出電壓Vh或輸出電流Ih或輸出電力)進行檢測，並將其檢測結果作為輸出感測器信號而朝轉換器控制部110及逆變器控制部112輸出。 The output stage of the inverter section 106 in the inverter device 100 is provided with the output sensor 108 as described above, and the output sensor 108 outputs the output from the inverter section 106 (which is the output voltage Vh or the output). The current Ih or the output power) is detected, and the detection result is output to the converter control unit 110 and the inverter control unit 112 as an output sensor signal.

轉換器控制部110以使逆變器部106之輸出成為由輸出設定信號所指示之設定位準之方式，進行可改變轉換器部104之輸出即直流電壓值之控制。 The converter control section 110 controls the output of the inverter section 106 to be a setting level indicated by the output setting signal, and controls the output voltage of the converter section 104, that is, the DC voltage value.

此處，逆變器控制部112藉由PLL電路112a，以逆變器部106之輸出頻率成為共振負載200之共振頻率之方式進行自動控制。 Here, the inverter control section 112 performs automatic control so that the output frequency of the inverter section 106 becomes the resonance frequency of the resonance load 200 by the PLL circuit 112a.

且說，於連接於共振負載之逆變器裝置中，關於使用高頻電壓與高頻電流之相位控制之輸出控制電路，除上文所述之習知之逆變器裝置100中所示之構成以外，使用有幾種方法。 In addition, in the inverter device connected to the resonance load, the output control circuit using the phase control of the high-frequency voltage and the high-frequency current is in addition to the configuration shown in the conventional inverter device 100 described above. There are several ways to use.

然而，先前所使用之任一方法均存在如下問題，即， 成為當進行輸出控制時逆變器部之輸出頻率偏離共振頻率的特性，從而於實用上成為問題。 However, any of the methods previously used has a problem in that the output frequency of the inverter section deviates from the resonance frequency when the output control is performed, which is a practical problem.

另一方面，於低電力機器所使用之逆變器裝置中，亦使用有脈寬調變(PWM：Pulse Width Modulation)控制方式之輸出控制。 On the other hand, in inverter devices used in low-power equipment, output control with a pulse width modulation (PWM: Pulse Width Modulation) control method is also used.

此處，圖2中示出構成說明圖，該構成說明圖表示藉由PWM控制方式進行輸出控制並且連接於共振負載之逆變器裝置之整體構成。 Here, FIG. 2 shows a configuration explanatory diagram showing the overall configuration of an inverter device that performs output control by a PWM control method and is connected to a resonant load.

再者，於以下說明中，關於與參照圖1(a)、(b)並進行了說明之構成以及作用相同或相當之構成以及作用，藉由分別標註與圖1(a)、(b)中所使用之符號相同之符號進行表示，而省略其詳細之構成以及作用之說明。 It should be noted that in the following description, the components and operations that are the same as or equivalent to the components and operations described with reference to FIGS. 1 (a) and (b) are denoted by the same components as those in FIGS. 1 (a) and (b), respectively. The same symbols are used in the description, and detailed descriptions of the structures and functions are omitted.

如圖2所示般，逆變器裝置300係將自交流電源102供給之交流電壓轉換成所需之電壓之高頻交流電壓，並朝如感應加熱電路等之共振負載200供給者。 As shown in FIG. 2, the inverter device 300 is a high-frequency AC voltage that converts an AC voltage supplied from the AC power source 102 into a required voltage, and supplies the high-frequency AC voltage to a resonant load 200 such as an induction heating circuit.

再者，作為交流電源102，與上文所述之逆變器裝置100同樣地，例如可使用商用交流電源，於該情形時，逆變器裝置300將商用交流電壓轉換成高頻交流電壓並朝共振負載200供給。 Moreover, as the AC power source 102, similar to the inverter device 100 described above, for example, a commercial AC power source may be used. In this case, the inverter device 300 converts the commercial AC voltage into a high-frequency AC voltage and It is supplied to the resonance load 200.

更詳細而言，逆變器裝置300係具有如下部分而構成：轉換器部302，其將自交流電源102供給之交流電壓輸入後藉由二極體之整流而轉換成直流電壓並輸出；逆變器部106，其具有將自轉換器部302輸出之直流電壓輸入後逆轉換成高頻交流電壓並輸出之逆變器電路；輸出感測器108，其對來自逆變器部106之輸出(此處，所謂來自逆變器部106之「輸出」，係指自逆變器部106 輸出之電壓即「輸出電壓Vh」、或自逆變器部106輸出之電流即「輸出電流Ih」、或自逆變器部106輸出之電力即「輸出電力」)進行檢測，並將其檢測結果作為輸出感測器信號而輸出；及PWM控制部304，其基於自外部設定逆變器部106之輸出之信號即輸出設定信號及自輸出感測器108輸出之輸出感測器信號，對逆變器部106進行反饋控制。 In more detail, the inverter device 300 is configured with a converter unit 302 that converts an AC voltage supplied from an AC power source 102 into a DC voltage through rectification of a diode and outputs the inverter voltage. A transformer unit 106 having an inverter circuit that inversely converts a DC voltage output from the converter unit 302 into a high-frequency AC voltage and outputs it, and an output sensor 108 that outputs an output from the inverter unit 106 (Here, the “output” from the inverter section 106 refers to the “output voltage Vh” that is the voltage output from the inverter section 106 or the “output current Ih” that is the current output from the inverter section 106 Or "output power" output from the inverter section 106), and outputs the detection result as an output sensor signal; and the PWM control section 304, which sets the inverter section 106 from the outside based on The output signal is an output setting signal and an output sensor signal output from the output sensor 108, and performs feedback control on the inverter section 106.

於以上構成中，參照圖3(a)、(b)、(c)中示意性地表示之波形圖，對逆變器裝置300之動作進行說明。 In the above configuration, the operation of the inverter device 300 will be described with reference to the waveform diagrams schematically shown in FIGS. 3 (a), (b), and (c).

此處，於圖3(a)、(b)、(c)中，波形A：逆變器部106之輸出(輸出電壓Vh或輸出電流Ih)；波形B：逆變器部106之輸出(輸出電壓Vh或輸出電流Ih)；波形C：逆變器部106之輸出(輸出電壓Vh或輸出電流Ih)；T：逆變器部106之輸出(輸出電壓Vh或輸出電流Ih)之基本波成分之1個週期；T/4：逆變器部106之輸出(輸出電壓Vh或輸出電流Ih)之基本波成分之1/4週期；tw：逆變器驅動信號之脈衝寬度。 Here, in FIGS. 3 (a), (b), and (c), waveform A: the output of the inverter section 106 (output voltage Vh or output current Ih); waveform B: the output of the inverter section 106 ( Output voltage Vh or output current Ih); waveform C: output of inverter section 106 (output voltage Vh or output current Ih); T: fundamental wave of output of inverter section 106 (output voltage Vh or output current Ih) 1 cycle of the component; T / 4: 1/4 cycle of the fundamental wave component of the output (output voltage Vh or output current Ih) of the inverter section 106; tw: pulse width of the inverter drive signal.

於逆變器裝置300中，於藉由PWM控制部304之PWM控制而驅動開始時(起動時)，藉由脈衝寬度tw較窄之逆變器驅動信號(矩形波逆變器驅動信號Q、NQ)在共振頻率附近進行驅動(圖3(a))，要對逆變器部106之輸出進行可變控制，就要藉由PWM 控制部304之PWM控制而使脈衝寬度tw可變，從而對逆變器部106之輸出進行可變控制。 In the inverter device 300, when driving is started (when starting) by the PWM control of the PWM control unit 304, an inverter driving signal (rectangular wave inverter driving signal Q, NQ) is driven in the vicinity of the resonance frequency (Figure 3 (a)). To control the output of the inverter unit 106 variablely, the PWM width of the PWM control unit 304 is required to make the pulse width tw variable. The output of the inverter section 106 is variably controlled.

例如，要使逆變器部106之輸出上升，就要如圖3(b)以及圖3(c)所示般，藉由PWM控制部304之PWM控制來擴大脈衝寬度tw。 For example, to increase the output of the inverter unit 106, as shown in FIG. 3 (b) and FIG. 3 (c), the pulse width tw is increased by the PWM control of the PWM control unit 304.

即，於習知之逆變器裝置300中，藉由PWM控制部304之PWM控制，自起動時使用PLL電路等而在共振頻率附近控制驅動，且於其頻帶內進行PWM控制。 That is, in the conventional inverter device 300, the PWM control by the PWM control unit 304 is used to control driving near the resonance frequency using a PLL circuit or the like at the time of self-starting, and PWM control is performed in its frequency band.

因此，習知之逆變器裝置300存在對共振頻率變動之負載之追蹤特性較差之問題。 Therefore, the conventional inverter device 300 has a problem that the tracking characteristics of a load with a changed resonance frequency are poor.

再者，本案申請人在專利申請時所知之先前技術並非文獻公知發明之發明，因此無應記載於本案說明書中之先前技術文獻資訊。 Furthermore, the prior art known to the applicant at the time of patent application is not an invention of a well-known invention in the literature, and therefore there is no prior art literature information that should be recorded in the description of this case.

本發明係鑒於如上所述之習知技術中之各種問題而成者，其目的在於欲提供一種逆變器裝置及逆變器裝置之控制方法，其即便進行輸出控制，逆變器部之輸出頻率亦不會偏離共振頻率，又，改善了對共振頻率變動之負載之追蹤特性。 The present invention has been made in view of various problems in the conventional technology as described above, and an object thereof is to provide an inverter device and a control method of the inverter device. Even if output control is performed, the output of the inverter unit The frequency does not deviate from the resonance frequency, and the tracking characteristic of the load with the fluctuation of the resonance frequency is improved.

為達成上述目的，本發明係一種作為連接於共振負載且受到PWM控制之電壓型逆變器之逆變器裝置，其中，以如下方式進行控制：使用較共振頻率週期短之脈衝寬度(例如下文所述之「最低脈衝寬度」)之脈衝信號(於本說明書及本申請專利範圍中，將 「較共振頻率週期短之脈衝寬度之脈衝信號」適宜地稱為「窄幅脈衝信號」)作為逆變器驅動信號，將與共振頻率分開之頻率作為起點而開始逆變器部之驅動，藉由頻率控制使逆變器驅動信號頻移至共振頻率或共振頻率附近，使得逆變器驅動信號之頻率與共振頻率大致一致。 To achieve the above object, the present invention is an inverter device as a voltage-type inverter connected to a resonant load and subject to PWM control, wherein the control is performed in such a manner that a pulse width shorter than the resonant frequency period is used (for example, below The "minimum pulse width") pulse signal (in this specification and the scope of this application patent, "a pulse signal with a pulse width shorter than the resonant frequency period" is appropriately referred to as a "narrow pulse signal") The inverter drive signal starts the drive of the inverter with the frequency separated from the resonance frequency as the starting point. The frequency of the inverter drive signal is shifted to the resonance frequency or the resonance frequency by frequency control, so that the inverter drive signal The frequency is approximately the same as the resonance frequency.

並且，本發明係以如下方式進行控制：於根據上述內容以逆變器驅動信號之頻率與共振頻率大致一致之方式進行控制後，藉由PWM控制使逆變器驅動信號之脈衝寬度變寬，藉此逆變器部之輸出(為輸出電壓或輸出電流或輸出電力)成為預先設定之值。 In addition, the present invention performs control in such a manner that after the control is performed in such a manner that the frequency of the inverter drive signal and the resonance frequency are substantially consistent, the pulse width of the inverter drive signal is widened by PWM control. As a result, the output of the inverter unit (which is the output voltage, output current, or output power) becomes a preset value.

因而，根據本發明，即便進行輸出控制，逆變器部之輸出頻率亦不會偏離共振頻率，又，可改善對共振頻率變動之負載之追蹤特性。 Therefore, according to the present invention, even if output control is performed, the output frequency of the inverter section does not deviate from the resonance frequency, and the tracking characteristic of a load that fluctuates at the resonance frequency can be improved.

即，於本發明中，藉由將逆變器驅動信號之驅動開始時之頻率與共振頻率分開，並且刻意地頻移使得該驅動開始之後逆變器驅動信號之頻率成為共振頻率，而不論共振負載側之共振頻率如何偏離，均可藉由該頻移而自動地找出共振頻率。 That is, in the present invention, by separating the frequency at the start of driving of the inverter drive signal from the resonance frequency, and deliberately shifting the frequency, the frequency of the inverter drive signal after the start of the drive becomes the resonance frequency, regardless of the resonance If the resonance frequency on the load side deviates, the resonance frequency can be automatically found by the frequency shift.

此處，較佳為將逆變器驅動信號之頻率頻移之區域(於本說明書及本申請專利範圍中，將「將逆變器驅動信號之頻率頻移之區域」適宜地稱為「頻移區域」)決定為考慮了對逆變器電路最佳之二極體逆向恢復特性的感應性區域。 Here, it is preferable to frequency-shift the frequency of the inverter drive signal (in the scope of this specification and the patent of this application, "the frequency-shifted area of the inverter drive signal" is appropriately referred to as "frequency Shift region ") is determined as an inductive region that takes into account the best diode reverse recovery characteristics for the inverter circuit.

換言之，與共振頻率分開之頻率之起點較佳為決定為如下，即，頻移區域成為基於逆變器電路之二極體逆向恢復特性之感應性區域。 In other words, the starting point of the frequency separated from the resonance frequency is preferably determined as follows, that is, the frequency shift region becomes an inductive region based on the reverse recovery characteristic of the diode of the inverter circuit.

即，本發明之逆變器裝置係作為連接於共振負載且受到PWM控制之電壓型逆變器者，其中，具有連接於共振負載且由逆變器驅動信號所驅動之逆變器部、及控制上述逆變器部之動作之控制手段，且上述控制手段係以如下方式進行控制：將較上述共振負載之共振頻率之週期短之脈衝寬度之脈衝信號作為上述逆變器驅動信號，將與上述共振頻率分開之頻率作為起點而開始上述逆變器部之驅動後，使上述逆變器驅動信號之頻率頻移至上述共振頻率或上述共振頻率附近，使得上述逆變器驅動信號之頻率與上述共振頻率大致一致。 That is, the inverter device of the present invention is a voltage-type inverter connected to a resonance load and subject to PWM control, and includes an inverter unit connected to the resonance load and driven by an inverter drive signal, and A control means for controlling the operation of the inverter section, and the control means is controlled in such a manner that a pulse signal having a pulse width shorter than the period of the resonance frequency of the resonance load is used as the inverter drive signal, and After starting the driving of the inverter section with the frequency separated by the resonance frequency as a starting point, the frequency of the inverter drive signal is shifted to the resonance frequency or the vicinity of the resonance frequency, so that the frequency of the inverter drive signal and The resonance frequencies are approximately the same.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述較短之脈衝寬度係使上述逆變器部之輸出成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值的脈衝寬度。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the shorter pulse width is such that the output of the inverter section becomes a setting indicated by an external output setting signal The lowest value sets the pulse width of the output value.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述起點係以如下方式設定，即，上述頻移之區域成為基於構成上述逆變器部之逆變器電路之二極體逆向恢復特性的感應性區域。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the starting point is set in such a manner that the frequency shifted region becomes an inverter based on the inverter unit. The inductive region of the diode's reverse recovery characteristic of the transistor circuit.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述共振負載為並聯共振負載，上述起點為低於上述共振頻率之頻率。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the resonance load is a parallel resonance load, and the starting point is a frequency lower than the resonance frequency.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，於上述逆變器部之輸出級連接有電感器。 The inverter device of the present invention is the inverter device of the present invention as described above, and an inductor is connected to the output stage of the inverter section.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述控制部具有對由上述電感器引起之電壓相位之 延遲進行修正之延遲修正手段。 The inverter device according to the present invention is the inverter device according to the present invention as described above, wherein the control unit includes delay correction means for correcting a delay of a voltage phase caused by the inductor.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述共振負載為串聯共振負載，上述起點為高於上述共振頻率之頻率。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the resonance load is a series resonance load, and the starting point is a frequency higher than the resonance frequency.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述控制部具有對上述逆變器部之電路延遲進行修正之延遲修正手段。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the control unit includes a delay correction means for correcting a circuit delay of the inverter unit.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述共振負載為串聯共振負載，上述逆變器部使用SiC(碘化矽)二極體作為逆變器開關元件中之飛輪二極體(freewheel diode)，上述起點為低於上述共振頻率之頻率。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the resonance load is a series resonance load, and the inverter unit uses a SiC (silicon iodide) diode as an inverter. The starting point of the freewheel diode in the switch element of the device is a frequency lower than the resonance frequency.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述起點為相對於上述共振頻率之頻率分開5%以上之頻率。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the starting point is a frequency separated by 5% or more from the frequency of the resonance frequency.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述控制部於以上述逆變器驅動信號之頻率與上述共振頻率大致一致之方式進行控制後，藉由PWM控制使上述逆變器驅動信號之脈衝寬度變寬。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the control section controls the frequency of the inverter drive signal and the resonance frequency to substantially match, and then borrows The pulse width of the inverter drive signal is widened by PWM control.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述控制部具有最低位準感測手段，該最低位準感測手段對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之情況進行感測。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the control unit has a lowest level sensing means, and the lowest level sensing means outputs to the inverter unit Sensing is performed when the output level of phase sensing becomes possible.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述控制部具有頻率感測手段，該頻率感測手段對 上述逆變器部之輸出成為能夠進行相位感測之輸出位準之頻率之情況進行感測。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the control unit has a frequency sensing means, and the frequency sensing means is capable of phasing the output of the inverter unit. The sensed frequency of the output level is sensed.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，利用空冷同軸纜線將上述逆變器裝置之輸出端子與並聯共振電容器箱連接，並將變流器連接至上述並聯共振電容器箱，而向加熱線圈傳送高頻電流。 In addition, the inverter device of the present invention is the inverter device of the present invention as described above, wherein the output terminal of the inverter device is connected to a parallel resonant capacitor box using an air-cooled coaxial cable, and the converter is It is connected to the parallel resonance capacitor box described above, and transmits a high-frequency current to the heating coil.

又，本發明之逆變器裝置係如上所述之本發明之逆變器裝置，其中，上述共振負載由包含感應加熱用之加熱線圈及共振電容器之共振電路所構成。 The inverter device of the present invention is the inverter device of the present invention as described above, wherein the resonance load is constituted by a resonance circuit including a heating coil for induction heating and a resonance capacitor.

又，本發明之逆變器裝置之控制方法係作為連接於共振負載且受到PWM控制之電壓型逆變器之逆變器裝置之控制方法，其中，以如下方式進行控制：將較共振負載之共振頻率之週期短之脈衝寬度之脈衝信號作為逆變器驅動信號，將與上述共振頻率分開之頻率作為起點而開始逆變器部之驅動後，使上述逆變器驅動信號之頻率頻移至上述共振頻率或上述共振頻率附近，使得上述逆變器驅動信號之頻率與上述共振頻率大致一致。 In addition, the control method of the inverter device of the present invention is a control method of an inverter device of a voltage-type inverter connected to a resonance load and subject to PWM control, wherein the control is performed as follows: A pulse signal with a short pulse width of the resonance frequency is used as an inverter drive signal. After starting the drive of the inverter section with a frequency separated from the resonance frequency as a starting point, the frequency of the inverter drive signal is shifted to The resonance frequency or the vicinity of the resonance frequency is such that the frequency of the inverter drive signal substantially coincides with the resonance frequency.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述較短之脈衝寬度係上述逆變器部之輸出成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值的脈衝寬度。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the shorter pulse width is such that the output of the inverter section becomes an output setting from the outside Pulse width of the lowest set output value of the set value represented by the signal.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述起點係以如下方式設定，即，上述頻移之區域成為基於構成上述逆變器部之逆變器電路之二極體逆向恢復特性的感應性區域。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the starting point is set in such a manner that the region of the frequency shift is based on the composition of the inverter. The inductive region of the reverse recovery characteristic of the diode of the inverter circuit of the inverter section.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述共振負載為並聯共振負載，上述起點為低於上述共振頻率之頻率。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the resonance load is a parallel resonance load, and the starting point is a frequency lower than the resonance frequency.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，於上述逆變器部之輸出級連接有電感器。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein an inductor is connected to the output stage of the inverter section.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，對由上述電感器引起之電壓相位之延遲進行修正。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the delay of the voltage phase caused by the inductor is corrected.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述共振負載為串聯共振負載，上述起點為高於上述共振頻率之頻率。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the resonance load is a series resonance load, and the starting point is a frequency higher than the resonance frequency.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，對上述逆變器部之電路延遲進行修正。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the circuit delay of the inverter unit is corrected.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述共振負載為串聯共振負載，上述逆變器部使用SiC二極體作為逆變器開關元件中之飛輪二極體，上述起點為低於上述共振頻率之頻率。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the resonance load is a series resonance load, and the inverter section uses a SiC diode as a reverse In the flywheel diode in the switching element of the transformer, the starting point is a frequency lower than the resonance frequency.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述起點為相對於上述共振頻率之頻率分開5%以上之頻率。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the starting point is a frequency separated by 5% or more from the frequency of the resonance frequency.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，以上述逆變器驅動信號之頻 率與上述共振頻率大致一致之方式進行控制後，藉由PWM控制使上述逆變器驅動信號之脈衝寬度變寬。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the control is performed in such a manner that the frequency of the inverter drive signal is substantially consistent with the resonance frequency. The pulse width of the inverter drive signal is widened by PWM control.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之情況進行感測。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, in which the output of the inverter section becomes an output level capable of phase sensing Perform sensing.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之頻率之情況進行感測。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, in which the output of the inverter section becomes a frequency at which the phase of the output level can be sensed. The situation is sensed.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其係利用空冷同軸纜線將上述逆變器裝置之輸出端子與並聯共振電容器箱連接，並將變流器連接至上述並聯共振電容器箱，而向加熱線圈傳送高頻電流。 In addition, the control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, which uses an air-cooled coaxial cable to connect the output terminal of the inverter device to a parallel resonant capacitor box , And connect the converter to the parallel resonance capacitor box mentioned above to send high-frequency current to the heating coil.

又，本發明之逆變器裝置之控制方法係如上所述之本發明之逆變器裝置之控制方法，其中，上述共振負載由包含感應加熱用之加熱線圈及共振電容器之共振電路所構成。 The control method of the inverter device of the present invention is the control method of the inverter device of the present invention as described above, wherein the resonance load is composed of a resonance circuit including a heating coil for induction heating and a resonance capacitor.

本發明係藉由以上所說明之方式而構成，因此實現如下優異之效果：即便進行輸出控制，逆變器部之輸出頻率亦不會偏離共振頻率，又，可改善對共振頻率變動之負載之追蹤特性。 The present invention is constituted by the method described above, and therefore achieves the excellent effect that even if output control is performed, the output frequency of the inverter section does not deviate from the resonance frequency, and the load on the fluctuation of the resonance frequency can be improved. Tracking characteristics.

10‧‧‧逆變器裝置 10‧‧‧ Inverter device

12‧‧‧控制部(控制手段) 12‧‧‧control department (control means)

12a‧‧‧PWM控制部(控制手段) 12a‧‧‧PWM control unit (control means)

12b‧‧‧頻移控制部(控制手段) 12b‧‧‧Frequency shift control section (control means)

20‧‧‧逆變器裝置 20‧‧‧Inverter device

22‧‧‧並聯共振電路(並聯共振負載) 22‧‧‧Parallel resonance circuit (parallel resonance load)

24‧‧‧電感器 24‧‧‧Inductor

26‧‧‧電壓感測器 26‧‧‧Voltage sensor

28‧‧‧控制部(控制手段) 28‧‧‧Control Department (Control Means)

30‧‧‧頻移電路 30‧‧‧frequency shift circuit

32‧‧‧電壓控制振盪器(VCO：Voltage-controlled oscillator)電路 32‧‧‧Voltage-controlled oscillator (VCO) circuit

34‧‧‧窄幅脈衝信號產生電路 34‧‧‧ Narrow pulse signal generating circuit

36‧‧‧輸出電路 36‧‧‧Output circuit

38‧‧‧相位比較電路 38‧‧‧phase comparison circuit

40‧‧‧延遲設定電路 40‧‧‧ Delay setting circuit

42‧‧‧鎖定結束電路 42‧‧‧Lock end circuit

44‧‧‧檢波電路 44‧‧‧detection circuit

46‧‧‧誤差放大濾波器 46‧‧‧ Error Amplification Filter

48‧‧‧三角波產生電路 48‧‧‧ triangle wave generating circuit

50‧‧‧PWM電路 50‧‧‧PWM circuit

60‧‧‧逆變器裝置 60‧‧‧Inverter device

62‧‧‧串聯共振負載(串聯共振電路) 62‧‧‧series resonance load (series resonance circuit)

64‧‧‧電流感測器 64‧‧‧Current sensor

66‧‧‧共振電容器 66‧‧‧Resonant capacitor

70‧‧‧控制部(控制手段) 70‧‧‧control department (control means)

72‧‧‧最低位準感測電路(最低位準感測手段) 72‧‧‧ Lowest level sensing circuit (lowest level sensing means)

80‧‧‧控制部(控制手段) 80‧‧‧control department (control means)

82‧‧‧最低位準頻率感測電路(頻率感測手段) 82‧‧‧Lowest level frequency sensing circuit (frequency sensing means)

100‧‧‧逆變器裝置 100‧‧‧ Inverter device

102‧‧‧交流(AC)電源 102‧‧‧AC Power

104‧‧‧轉換器部 104‧‧‧ Converter Department

106‧‧‧逆變器部 106‧‧‧Inverter Department

108‧‧‧輸出感測器 108‧‧‧Output sensor

110‧‧‧轉換器控制部 110‧‧‧ converter control unit

112‧‧‧控制部 112‧‧‧Control Department

112a‧‧‧PLL電路 112a‧‧‧PLL circuit

200‧‧‧共振負載 200‧‧‧Resonant load

300‧‧‧逆變器裝置 300‧‧‧ Inverter device

302‧‧‧轉換器部 302‧‧‧ Converter Department

304‧‧‧PWM控制部 304‧‧‧PWM Control Department

400‧‧‧逆變器裝置 400‧‧‧ Inverter device

406‧‧‧逆變器部 406‧‧‧Inverter Department

406a‧‧‧逆變器開關元件 406a‧‧‧Inverter switching element

406b‧‧‧環流二極體(飛輪二極體) 406b‧‧‧Circulation Diode (Flywheel Diode)

406c‧‧‧半導體開關元件 406c‧‧‧semiconductor switching element

500‧‧‧輸出端子 500‧‧‧output terminal

502‧‧‧並聯共振電容器箱 502‧‧‧parallel resonant capacitor box

504‧‧‧空冷同軸纜線 504‧‧‧Air-cooled coaxial cable

506‧‧‧變流器 506‧‧‧ converter

508‧‧‧加熱線圈 508‧‧‧Heating coil

600‧‧‧逆變器裝置 600‧‧‧ Inverter device

600a‧‧‧輸出端子 600a‧‧‧output terminal

602‧‧‧水冷纜線 602‧‧‧Water-cooled cable

604‧‧‧中繼盒 604‧‧‧Relay Box

606‧‧‧變流器 606‧‧‧ converter

608‧‧‧加熱線圈 608‧‧‧Heating coil

700‧‧‧逆變器裝置 700‧‧‧ inverter device

700a‧‧‧輸出端子 700a‧‧‧output terminal

702‧‧‧空冷同軸纜線 702‧‧‧Air-cooled coaxial cable

704‧‧‧中繼盒 704‧‧‧ relay box

706‧‧‧變流器 706‧‧‧ converter

708‧‧‧加熱線圈 708‧‧‧Heating coil

Vh‧‧‧輸出電壓 Vh‧‧‧Output voltage

Ih‧‧‧輸出電流 Ih‧‧‧Output current

Q‧‧‧矩形波逆變器驅動信號 Q‧‧‧Rectangular wave inverter drive signal

NQ‧‧‧矩形波逆變器驅動信號 NQ‧‧‧Rectangular wave inverter drive signal

T‧‧‧逆變器部之輸出(輸出電壓或輸出電流)之基本波成分之1個週期 One cycle of the fundamental wave component of the output (output voltage or output current) of the T‧‧‧ inverter section

T/4‧‧‧逆變器部之輸出(輸出電壓或輸出電流)之基本波成分之1/4週期 1/4 period of the fundamental wave component of the output (output voltage or output current) of the T / 4‧‧‧ inverter section

Tw‧‧‧矩形波逆變器驅動信號Q、NQ之脈衝寬度 Pulse width of Tw‧‧‧ rectangular wave inverter drive signal Q, NQ

圖1(a)、(b)係使用PLL電路來控制之先前公知之逆變器裝置之構成說明圖。更詳細而言，圖1(a)係對由使用PLL電路之逆變器控制部所控制並且連接於共振負載之逆變器裝置之整體構成進行 表示之構成說明圖。又，圖1(b)係圖1(a)所示之逆變器裝置中之逆變器控制部之詳細之構成說明圖。 1 (a) and 1 (b) are explanatory diagrams of the structure of a conventionally known inverter device controlled using a PLL circuit. In more detail, FIG. 1 (a) is an explanatory diagram showing the overall configuration of an inverter device controlled by an inverter control section using a PLL circuit and connected to a resonant load. Fig. 1 (b) is a detailed configuration explanatory diagram of an inverter control section in the inverter device shown in Fig. 1 (a).

圖2係對藉由PWM控制方式進行輸出控制並且連接於共振負載之先前公知之逆變器裝置之整體構成進行表示之構成說明圖。 FIG. 2 is a configuration explanatory diagram showing the overall configuration of a conventionally known inverter device that performs output control by a PWM control method and is connected to a resonant load.

圖3(a)、(b)、(c)係表示圖2所示之逆變器裝置之動作之示意性波形圖。 3 (a), (b), and (c) are schematic waveform diagrams showing the operation of the inverter device shown in FIG.

圖4係本發明之實施形態之一例之逆變器裝置的構成說明圖。更詳細而言，圖4係對由控制部所控制並且連接於共振負載之逆變器裝置之整體構成進行表示之構成說明圖。 FIG. 4 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. In more detail, FIG. 4 is a configuration explanatory diagram showing the overall configuration of an inverter device controlled by a control unit and connected to a resonance load.

圖5係圖4所示之逆變器裝置中之控制部之詳細之構成說明圖。 Fig. 5 is a detailed configuration explanatory diagram of a control unit in the inverter device shown in Fig. 4.

圖6係本發明之實施形態之一例之逆變器裝置的構成說明圖。更詳細而言，圖6係對由控制部所控制並且連接於並聯共振負載之逆變器裝置之整體構成進行表示之構成說明圖。 FIG. 6 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. In more detail, FIG. 6 is a configuration explanatory diagram showing the overall configuration of an inverter device controlled by a control unit and connected to a parallel resonance load.

圖7(a)、(b)、(c)、(d)、(e)係表示圖6所示之逆變器裝置之動作之示意性波形圖。 7 (a), (b), (c), (d), and (e) are schematic waveform diagrams showing the operation of the inverter device shown in FIG.

圖8係本發明之實施形態之一例之逆變器裝置之構成說明圖。更詳細而言，圖8係對由控制部所控制並且連接於串聯共振負載之逆變器裝置之整體構成進行表示之構成說明圖。 FIG. 8 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. In more detail, FIG. 8 is a configuration explanatory diagram showing the overall configuration of an inverter device controlled by a control unit and connected to a series resonance load.

圖9(a)、(b)、(c)、(d)、(e)係表示圖8所示之逆變器裝置之動作之示意性波形圖。 9 (a), (b), (c), (d), and (e) are schematic waveform diagrams showing the operation of the inverter device shown in FIG. 8.

圖10係本發明之實施形態之一例之逆變器裝置中之控制部之構成說明圖。 FIG. 10 is a diagram illustrating a configuration of a control unit in an inverter device as an example of an embodiment of the present invention.

圖11係本發明之實施形態之一例之逆變器裝置中之控制部之 構成說明圖。 Fig. 11 is a diagram illustrating a configuration of a control unit in an inverter device as an example of an embodiment of the present invention.

圖12係本發明之實施形態之一例之逆變器裝置之構成說明圖。更詳細而言，圖12係對由控制部所控制並且連接於串聯共振負載之逆變器裝置之整體構成進行表示之構成說明圖。 Fig. 12 is a diagram illustrating the configuration of an inverter device as an example of an embodiment of the present invention. In more detail, FIG. 12 is a configuration explanatory diagram showing the overall configuration of an inverter device controlled by a control unit and connected to a series resonance load.

圖13係圖12所示之逆變器裝置中之逆變器部之放大說明圖。 FIG. 13 is an enlarged explanatory diagram of an inverter section in the inverter device shown in FIG. 12.

圖14(a)係示意性地表示使用連接於共振負載之本發明之逆變器裝置之電源構成的構成說明圖。又，圖14(b)係示意性地表示使用連接於串聯共振負載之習知技術之逆變器裝置之電源構成的構成說明圖。又，圖14(c)係示意性地表示使用連接於並聯共振負載之習知技術之逆變器裝置之電源構成的構成說明圖。 FIG. 14 (a) is a configuration explanatory view schematically showing a power supply configuration using the inverter device of the present invention connected to a resonance load. 14 (b) is a configuration explanatory diagram schematically showing a power supply configuration of an inverter device using a conventional technique connected to a series resonance load. 14 (c) is a configuration explanatory diagram schematically showing a power supply configuration of an inverter device using a conventional technique connected to a parallel resonance load.

圖15(a)、(b)係表示感應加熱用共振負載作為共振負載之一例之構成說明圖。更詳細而言，圖15(a)係表示串聯共振負載之情形時之感應加熱用串聯共振負載之構成說明圖。圖15(b)係表示並聯共振負載之情形時之感應加熱用並聯共振負載之構成說明圖。 15 (a) and 15 (b) are explanatory diagrams showing the configuration of an example of a resonance load for induction heating. In more detail, FIG. 15 (a) is an explanatory diagram showing the configuration of a series resonance load for induction heating in the case of a series resonance load. Fig. 15 (b) is an explanatory diagram showing the configuration of a parallel resonance load for induction heating in the case of a parallel resonance load.

以下，參照隨附圖式對本發明之逆變器裝置及逆變器裝置之控制方法之實施形態之一例詳細地進行說明。 Hereinafter, an example of an embodiment of the inverter device and the control method of the inverter device according to the present invention will be described in detail with reference to the accompanying drawings.

再者，於以下「實施方式」之項目之說明中，關於與已參照圖1(a)、(b)、圖2以及圖3(a)、(b)、(c)之各圖而說明之構成以及作用、或參照圖4以下之各圖而說明之構成以及作用相同或相當之構成以及作用，藉由分別標註與圖1(a)、(b)、圖2以及圖3(a)、(b)、(c)或圖4以下中所使用之符號相同之符號，而省略其詳細之構成以及作用之說明。 In addition, in the following description of the items of the "embodiment", explanations have been made with reference to each of Figs. 1 (a), (b), Fig. 2 and Figs. 3 (a), (b), and (c). Structures and functions, or structures and functions that are the same as or equivalent to those described with reference to each of the following figures in FIG. 4, are labeled with those in FIGS. 1 (a), (b), 2 and 3 (a), respectively. , (B), (c), or the same symbols used in FIG. 4 and below, and the detailed description of the structure and function is omitted.

(I)第1實施形態 (I) First Embodiment

(I-1)構成 (I-1) Composition

於圖4中表示本發明之實施形態之一例之逆變器裝置之構成說明圖。再者，於圖4中表示由控制部所控制並且連接於共振負載之逆變器裝置之整體構成。 FIG. 4 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. The overall configuration of the inverter device controlled by the control unit and connected to the resonant load is shown in FIG. 4.

又，於圖5中表示圖4所示之逆變器裝置中之控制部之詳細之構成說明圖。 In addition, FIG. 5 is a detailed configuration explanatory diagram of a control unit in the inverter device shown in FIG. 4.

參照該等圖4及圖5對本發明之實施形態之一例之逆變器裝置10進行說明。 An inverter device 10 as an example of an embodiment of the present invention will be described with reference to these FIGS. 4 and 5.

本發明之實施形態之一例之逆變器裝置10係連接於共振負載200之PWM控制之電壓型逆變器。 The inverter device 10 as an example of the embodiment of the present invention is a PWM-controlled voltage-type inverter connected to a resonance load 200.

即，逆變器裝置10係將自交流電源102所供給之交流電壓轉換成所需之電壓之高頻交流電壓，並朝如感應加熱電路等之共振負載200供給者。 That is, the inverter device 10 is a high-frequency AC voltage that converts an AC voltage supplied from the AC power source 102 into a required voltage, and supplies it to a resonance load 200 such as an induction heating circuit.

再者，作為交流電源102，與習知之逆變器裝置100同樣地，例如可使用商用交流電源，於該情形時，逆變器裝置10將商用交流電壓轉換成高頻交流電壓並朝共振負載200供給。 In addition, as the AC power source 102, similar to the conventional inverter device 100, for example, a commercial AC power source can be used. In this case, the inverter device 10 converts a commercial AC voltage into a high-frequency AC voltage and loads it toward a resonant load. 200 supply.

更詳細而言，逆變器裝置10具備轉換器部302，其將自交流電源102供給之交流電壓輸入後，藉由二極體之整流而轉換成直流電壓並進行輸出。 More specifically, the inverter device 10 includes a converter unit 302 that inputs an AC voltage supplied from the AC power source 102 and converts the AC voltage to a DC voltage by rectification of a diode and outputs the DC voltage.

即，逆變器裝置10之轉換器部302由不使用轉換器控制部之二極體整流電路所構成，且自交流電源102輸入交流電壓，將所輸入之交流電壓轉換成直流電壓並朝逆變器部106輸出。 That is, the converter section 302 of the inverter device 10 is constituted by a diode rectifier circuit that does not use the converter control section, and an AC voltage is input from the AC power source 102, and the input AC voltage is converted into a DC voltage and reversed. The transformer unit 106 outputs.

逆變器部106將自轉換器部302輸出之直流電壓輸入後，逆轉換成高頻交流電壓並進行輸出。 The inverter unit 106 inputs the DC voltage output from the converter unit 302, and inversely converts it into a high-frequency AC voltage and outputs it.

於逆變器部106之輸出級設置有輸出感測器108，其對來自逆變器部106之輸出(此處，所謂來自逆變器部106之「輸出」，係指自逆變器部106輸出之電壓即「輸出電壓Vh」、或自逆變器部106輸出之電流即「輸出電流Ih」、或自逆變器部106輸出之電力即「輸出電力」)進行檢測並將其檢測結果作為輸出感測器信號進行輸出。 An output sensor 108 is provided at the output stage of the inverter section 106, and its output to the inverter section 106 (herein, the so-called "output" from the inverter section 106 refers to the output from the inverter section 106) The voltage output from 106 is "output voltage Vh", or the current output from inverter section 106 is "output current Ih", or the power output from inverter section 106 is "output power") and detected. The result is output as an output sensor signal.

逆變器裝置10具備控制部12作為控制逆變器部106之動作之控制手段。 The inverter device 10 includes a control unit 12 as a control means for controlling the operation of the inverter unit 106.

如圖5所示般，控制部12係具有PWM控制部12a、及頻移控制部12b而構成。 As shown in FIG. 5, the control unit 12 includes a PWM control unit 12 a and a frequency shift control unit 12 b.

控制部12基於自外部設定逆變器部106之輸出之信號即輸出設定信號及自輸出感測器108輸出之輸出感測器信號，對逆變器部106進行反饋控制。 The control unit 12 performs feedback control on the inverter unit 106 based on an output setting signal that is an externally set signal output from the inverter unit 106 and an output sensor signal output from the output sensor 108.

即，控制部12以來自逆變器部106之輸出成為輸出設定信號所表示之輸出設定值之方式，藉由PWM控制部12a之PWM控制而使對構成逆變器部106之電壓型逆變器之電晶體進行驅動之作為逆變器驅動信號之矩形波逆變器驅動信號Q、NQ的脈衝寬度可變，從而使由逆變器部106所轉換之高頻交流電壓之輸出可變。 That is, the control section 12 inverts the voltage type constituting the inverter section 106 by the PWM control of the PWM control section 12a so that the output from the inverter section 106 becomes the output setting value indicated by the output setting signal. The pulse widths of the rectangular-wave inverter drive signals Q and NQ, which are driven by the transistor of the inverter as inverter drive signals, are variable, so that the output of the high-frequency AC voltage converted by the inverter section 106 is variable.

再者，來自逆變器部106之輸出經由輸出感測器108輸入至外部之共振負載200。 Furthermore, the output from the inverter section 106 is input to the external resonance load 200 via the output sensor 108.

(I-2)動作 (I-2) Action

於以上構成中，逆變器裝置10之控制部12進行以下說明之動作作為本發明之實施之相關動作。 In the above configuration, the control unit 12 of the inverter device 10 performs operations described below as operations related to the implementation of the present invention.

即，於開始來自逆變器裝置10之輸出之驅動開始時(起動時)，藉由矩形波逆變器驅動信號Q、NQ進行驅動開始(起動)，該矩形波逆變器驅動信號Q、NQ為較共振頻率週期足夠短之脈衝寬度、例如成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)的脈衝寬度(於本說明書及本專利申請中，將「成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值的脈衝寬度」適宜地稱為「最低脈衝寬度」)，且其將與共振負載200之共振頻率分開之頻率作為起點。 That is, when the drive from the inverter device 10 is started (at the time of starting), the drive is started (started) by the rectangular wave inverter drive signals Q, NQ, and the rectangular wave inverter drive signals Q, NQ is a pulse width that is sufficiently short than the resonant frequency period, such as the minimum set output value (for output voltage or output current or output power) that becomes the set value indicated by an external output setting signal (in this manual and this In the patent application, "the pulse width which becomes the lowest set output value of the set value indicated by the output setting signal from the outside" is appropriately referred to as the "minimum pulse width"), and it is separated from the resonance frequency of the resonance load 200. Frequency is the starting point.

藉此，即便共振負載200之共振頻率變動，藉由自驅動開始時(起動時)將藉由控制部12之頻移控制部12b所獲得之矩形波逆變器驅動信號Q、NQ之頻率向共振頻率進行偏移之頻移，仍可進行對變動之共振頻率之自動追蹤。 Thus, even if the resonance frequency of the resonance load 200 fluctuates, the frequency of the rectangular wave inverter drive signals Q and NQ obtained by the frequency shift control section 12b of the control section 12 at the start of self-driving (at the time of starting) will be If the resonance frequency is shifted, the automatic tracking of the changed resonance frequency can still be performed.

並且，於逆變器裝置10中，控制部12之PWM控制部12a於矩形波逆變器驅動信號Q、NQ之頻率成為共振頻率(共振點)或共振頻率附近後，以成為來自外部之輸出設定信號所表示之設定值之輸出之方式，藉由PWM控制來擴大矩形波逆變器驅動信號Q、NQ之脈衝寬度。 Further, in the inverter device 10, the PWM control section 12a of the control section 12 becomes an output from the outside after the frequencies of the rectangular wave inverter drive signals Q and NQ become the resonance frequency (resonance point) or near the resonance frequency. The way of outputting the set value indicated by the setting signal is to increase the pulse width of the rectangular wave inverter drive signals Q and NQ by PWM control.

即，逆變器裝置10使用輸出來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)並且較共振頻率週期足夠短之脈衝寬度(例如為上述最低脈衝寬度)之脈衝信號(窄幅脈衝信號)作為逆變器驅動信號即矩形波逆變器驅動信號Q、NQ，將該窄幅脈衝信號以與共振頻率分開之頻率為起點進行起動後使頻率偏移至共振頻率或共振頻率附近，其後藉由頻率控制而控制於共振頻率。 That is, the inverter device 10 uses a pulse width that is the lowest set output value (that is, the output voltage or output current or output power) that outputs the set value indicated by the output setting signal from the outside and is sufficiently shorter than the resonance frequency period (for example, the above-mentioned The minimum pulse width) pulse signal (narrow pulse signal) is used as the inverter drive signal, that is, the rectangular wave inverter drive signals Q and NQ. The narrow pulse signal is started at a frequency separate from the resonance frequency. The frequency is shifted to or near the resonance frequency, and thereafter controlled at the resonance frequency by frequency control.

其後，逆變器裝置10藉由PWM控制使窄幅脈衝信號之脈衝寬度變寬，而使之成為來自外部之輸出設定信號所表示之設定值之輸出(為輸出電壓或輸出電流或輸出電力)。 Thereafter, the inverter device 10 widens the pulse width of the narrow-width pulse signal by PWM control, so that it becomes the output of the set value indicated by an external output setting signal (for output voltage or output current or output power). ).

(I-3)作用效果 (I-3) Effect

因而，根據上述所說明之逆變器裝置10，即便進行輸出控制，逆變器部之輸出頻率亦不會偏離共振頻率，又，可改善對共振頻率變動之負載之追蹤特性。 Therefore, according to the inverter device 10 described above, even if output control is performed, the output frequency of the inverter section does not deviate from the resonance frequency, and the tracking characteristics of a load that fluctuates at the resonance frequency can be improved.

又，於上述所說明之逆變器裝置10中，由於逆變器部106中可進行輸出控制，故而無需如習知技術般使用閘流體整流電路或斬波電路作為轉換器部之轉換器電路。 Further, in the inverter device 10 described above, since the output control can be performed in the inverter section 106, there is no need to use a thyristor rectifier circuit or a chopper circuit as a converter circuit of the converter section as is known in the art. .

因此，與使用閘流體整流電路或斬波電路之習知技術相比，逆變器裝置10可謀求電源功率因數之改善、輸出響應速度之大幅度改善(根據本案發明者之實驗，響應速度自習知技術中之100ms大幅度地改善為10ms)、藉由零件數量之大幅度削減所獲得之成本降低以及可靠性提高。 Therefore, compared with the conventional technique using a thyristor rectifier circuit or a chopper circuit, the inverter device 10 can improve the power factor of the power supply and greatly improve the output response speed (according to the experiments of the inventor of this case, the response speed is self-study (100ms in the known technology is greatly improved to 10ms), the cost obtained by the substantial reduction in the number of parts is reduced, and the reliability is improved.

又，逆變器裝置10由於係將逆變器驅動信號之驅動開始時(起動時)之頻率即起動頻率設為與共振頻率分開之頻率，然後以使逆變器驅動信號之頻率接近共振頻率之方式頻移，故而大幅度地改善對共振頻率變動之共振負載200之追蹤特性，又，即便於將共振頻率不同之複數個共振負載200進行切換而連接之情形時，亦可無問題地應對。 In addition, the inverter device 10 sets the starting frequency, that is, the frequency at the start of the driving of the inverter driving signal (at the time of starting) to a frequency separate from the resonance frequency, and then makes the frequency of the inverter driving signal close to the resonance frequency. This method significantly shifts the tracking characteristics of the resonance load 200 whose resonance frequency fluctuates, and it can cope with the problem even when a plurality of resonance loads 200 having different resonance frequencies are switched and connected. .

進而，不論共振負載200為並聯共振負載亦或是串聯共振負載，均可用作相同電壓型逆變器，因此可謀求逆變器裝置之共用化。 Furthermore, regardless of whether the resonance load 200 is a parallel resonance load or a series resonance load, it can be used as an inverter of the same voltage type. Therefore, it is possible to share the inverter device.

此處，藉由頻移控制部12b頻移之區域(頻移區域)較佳為決定為考慮了對於逆變器電路最佳之二極體逆向恢復特性之感應性區域。 Here, the region (frequency shift region) shifted by the frequency shift control unit 12b is preferably determined as an inductive region that takes into account the diode's reverse recovery characteristics that are optimal for the inverter circuit.

換言之，起動頻率較佳為以頻移區域成為基於逆變器電路之二極體逆向恢復特性之感應性區域之方式進行決定。 In other words, the starting frequency is preferably determined in such a manner that the frequency shift region becomes an inductive region based on the reverse recovery characteristic of the diode of the inverter circuit.

根據本案發明者之實驗，作為逆變器驅動信號之驅動開始時(起動時)之頻率即起動頻率，若設為相對於共振頻率之頻率分開5%以上之頻率(例如，若共振頻率設為20kHz，則相對於共振頻率之頻率分開5%以上之頻率成為19kHz以下之頻率或21kHz以上之頻率)，則可獲得良好之結果。 According to the experiments by the inventor of the present case, the frequency at the start of the drive of the inverter drive signal (at the time of starting) is the starting frequency, if it is set to a frequency separated by more than 5% from the frequency of the resonance frequency (for example, if the resonance frequency is 20kHz, the frequency separated by more than 5% from the frequency of the resonance frequency becomes the frequency below 19kHz or the frequency above 21kHz), and good results can be obtained.

再者，於將起動頻率設為相對於共振頻率之頻率分開5%以上之頻率時，即將起動頻率自共振頻率之頻率分開5%以上時，可向共振頻率之低頻側(低於共振頻率之頻率方向)分開(例如，若共振頻率設為20kHz，則向共振頻率之低頻側分開5%以上之頻率成為19kHz以下之頻率)，或，亦可向共振頻率之高頻側(高於共振頻率之頻率方向)分開(例如，若共振頻率設為20kHz，則向共振頻率之高頻側分開5%以上之頻率成為21kHz以上之頻率)。 In addition, when the starting frequency is set to a frequency separated by more than 5% from the frequency of the resonance frequency, that is, when the starting frequency is separated by more than 5% from the frequency of the resonance frequency, the low frequency side of the resonance frequency (below the resonance frequency) Frequency direction) (for example, if the resonance frequency is set to 20kHz, the frequency above 5% will be separated to a frequency below 19kHz to the low frequency side of the resonance frequency), or it can be separated to the high frequency side (higher than the resonance frequency) of the resonance frequency In the frequency direction) (for example, if the resonance frequency is set to 20 kHz, a frequency separated by 5% or more to the high frequency side of the resonance frequency becomes a frequency of 21 kHz or more).

再者，根據本案發明者之見解，並不存在如下所述之習知技術：如上文所述之本發明之逆變器裝置10般，將起動頻率與共振頻率之頻率分開(例如，相對於共振頻率之頻率分開5%以上)，並自該起動頻率藉由窄幅脈衝信號開始逆變器部之驅動後，使該窄幅脈衝信號向共振頻率頻移，其後以共振頻率開始將窄幅脈衝信號之脈衝寬度擴大之PWM控制。 Furthermore, according to the inventor's opinion of the present case, there is no conventional technique as follows: as with the inverter device 10 of the present invention described above, the frequency of the starting frequency and the frequency of the resonance frequency are separated (for example, relative to The frequency of the resonance frequency is separated by more than 5%), and after the starting frequency starts to drive the inverter section by a narrow pulse signal, the narrow pulse signal is shifted to the resonance frequency, and then the narrow pulse signal starts to be narrowed at the resonance frequency. PWM control for increasing the pulse width of the amplitude pulse signal.

(II)第2實施形態 (II) Second embodiment

(II-1)構成 (II-1) Composition

於圖6中表示本發明之實施形態之一例之逆變器裝置之構成說明圖。再者，於圖6中表示由控制部所控制並且連接於並聯共振負載之逆變器裝置之整體構成。 FIG. 6 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. FIG. 6 shows the overall configuration of an inverter device controlled by a control unit and connected to a parallel resonance load.

於參照圖6對本發明之實施形態之一例之逆變器裝置20進行說明時，逆變器裝置20連接於並聯共振負載22。 When the inverter device 20 which is an example of the embodiment of the present invention is described with reference to FIG. 6, the inverter device 20 is connected to the parallel resonance load 22.

話說，可知並聯共振負載於頻率低於共振頻率之範圍內具有成為感應性之特性，另一方面，電壓型逆變器由於並聯地連接於逆變器元件之二極體之電流之逆向恢復特性，故而感應性下之開關動作較電容性而言比較穩定。 In other words, it can be seen that the parallel resonance load has an inductive characteristic at a frequency lower than the resonance frequency. On the other hand, the voltage-type inverter has a reverse recovery characteristic of the current connected to the diode of the inverter element in parallel Therefore, the switching action under inductive is more stable than capacitive.

因而，本發明之逆變器裝置20係將較並聯共振電路22之共振頻率低之頻率(例如為較共振頻率低5%以上之頻率)作為逆變器驅動信號之起動頻率，自該起動頻率頻移而使逆變器驅動信號之頻率上升至共振頻率，並以共振頻率鎖定逆變器驅動信號之頻率。 Therefore, the inverter device 20 of the present invention uses a frequency lower than the resonance frequency of the parallel resonance circuit 22 (for example, a frequency that is more than 5% lower than the resonance frequency) as the starting frequency of the inverter drive signal. The frequency shift causes the frequency of the inverter drive signal to rise to the resonance frequency, and locks the frequency of the inverter drive signal with the resonance frequency.

以下，於對逆變器裝置20進行說明時，符號24為電感器，符號26為電壓感測器，符號28為控制部。 In the following description of the inverter device 20, reference numeral 24 is an inductor, reference numeral 26 is a voltage sensor, and reference numeral 28 is a control unit.

再者，電壓感測器26係相當於上述輸出感測器108之構成要素，對電壓進行感測，並輸出表示所感測到之電壓之信號作為輸出感測器信號。 In addition, the voltage sensor 26 is a constituent element equivalent to the output sensor 108 described above, senses a voltage, and outputs a signal indicating the sensed voltage as an output sensor signal.

控制部28係具有如下部分而構成：頻移電路30、電壓控制振盪器(VCO：Voltage-controlled oscillator)電路32、窄幅脈衝信號產生電路34、輸出電路36、相位比較電路38、延遲設定電路40、鎖定結束電路42、檢波電路44、誤差放大濾波器46、三角 波產生電路48、及PWM電路50。 The control unit 28 is composed of a frequency shift circuit 30, a voltage-controlled oscillator (VCO: Voltage-controlled oscillator) circuit 32, a narrow pulse signal generation circuit 34, an output circuit 36, a phase comparison circuit 38, and a delay setting circuit. 40. A lock completion circuit 42, a detection circuit 44, an error amplification filter 46, a triangle wave generation circuit 48, and a PWM circuit 50.

此處，逆變器裝置20除與本發明之實施相關聯地讓控制部28具備頻移電路30而將逆變器驅動信號之頻率頻移之方面及信號切換之方面以外，可應用先前公知之逆變器裝置之技術，因此關於除將逆變器驅動信號之頻率頻移之方面及信號切換之方面以外之其他構成，省略詳細說明。 Here, the inverter device 20 can apply a conventionally known aspect except that the control unit 28 is provided with the frequency shift circuit 30 in association with the implementation of the present invention, and the aspect of the frequency shift of the inverter drive signal and the aspect of signal switching. As for the technology of the inverter device, detailed explanations are omitted for other configurations except for the aspect of shifting the frequency of the inverter drive signal and the aspect of signal switching.

(II-2)動作 (II-2) Action

於以上構成中，關於逆變器裝置20之動作，以與本發明之實施相關之控制部28之動作為中心進行說明。 In the above configuration, the operation of the inverter device 20 will be described focusing on the operation of the control unit 28 related to the implementation of the present invention.

於控制部28中，將來自外部之輸出接通(ON)信號輸入至頻移電路30，以自較並聯共振負載22之共振頻率低之頻率(例如為較共振頻率低5%以上之頻率)開始逆變器部106之驅動之方式向VCO電路32輸入信號，來自VCO電路32之輸出之頻率信號被輸入至窄幅脈衝信號產生電路34，從而藉由窄幅脈衝信號產生電路34產生VCO電路32之輸出之頻率之窄幅脈衝信號並輸出至輸出電路36。於輸出電路36中，根據鎖定結束電路42之信號，自窄幅脈衝信號產生電路34之信號切換成PWM電路50之信號。 In the control unit 28, an external output ON signal is input to the frequency shift circuit 30 to a frequency lower than the resonance frequency of the parallel resonance load 22 (for example, a frequency that is more than 5% lower than the resonance frequency). The inverter unit 106 is driven to input a signal to the VCO circuit 32, and the frequency signal output from the VCO circuit 32 is input to the narrow pulse signal generating circuit 34, thereby generating the VCO circuit by the narrow pulse signal generating circuit 34. A narrow pulse signal having a frequency of 32 is output to the output circuit 36. In the output circuit 36, the signal from the narrow pulse signal generating circuit 34 is switched to the signal of the PWM circuit 50 according to the signal of the lock end circuit 42.

此處，由窄幅脈衝信號產生電路34所產生之窄幅脈衝信號之脈衝寬度較佳為設定為如下，即，自逆變器部106輸出之輸出值成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)。 Here, the pulse width of the narrow-width pulse signal generated by the narrow-width pulse signal generating circuit 34 is preferably set as follows. That is, the output value output from the inverter section 106 is represented by an output setting signal from the outside. The lowest set output value (for output voltage or output current or output power).

於圖7(a)、(b)、(c)、(d)、(e)中表示將逆變器裝置20之動作示意性地表示之波形圖。 7 (a), (b), (c), (d), and (e) are waveform diagrams showing the operation of the inverter device 20 schematically.

再者，於圖7(a)、(b)、(c)、(d)、(e)中，波形D、波 形E、波形F、波形G以及波形H係由電壓感測器26感測到之電壓(電容器電壓Vc)波形。 7 (a), (b), (c), (d), and (e), the waveform D, waveform E, waveform F, waveform G, and waveform H are sensed by the voltage sensor 26. To the voltage (capacitor voltage Vc) waveform.

圖7(a)表示作為驅動開始時(起動時)之起動頻率中之逆變器部106之輸出而由電壓感測器26感測到之電壓(電容器電壓Vc)波形(波形D)與作為逆變器驅動信號之窄幅脈衝信號之相位差。 Fig. 7 (a) shows the waveform (waveform D) of the voltage (capacitor voltage Vc) sensed by the voltage sensor 26 as the output of the inverter section 106 at the start frequency at the start of the drive (at the time of start) and as Phase difference of narrow pulse signal of inverter drive signal.

於逆變器裝置20連接有並聯共振負載22之情形時，可知於共振頻率以下之頻率區域中逆變器驅動信號之相位較電容器電壓Vc之相位而言延遲。 When the parallel resonance load 22 is connected to the inverter device 20, it can be seen that the phase of the inverter drive signal is delayed from the phase of the capacitor voltage Vc in a frequency region below the resonance frequency.

此處，於相位比較電路38中，將逆變器驅動信號之脈衝之週期之1/4延遲之位置即A點作為相位檢波脈衝之脈衝位置，將進行比較之電容器電壓Vc相位波形(波形E)之零交叉點作為B點(參照圖7(b))，對A點與B點之相位差進行比較，並以相位差成為零(0)或預先設定之相位差之頻率進行鎖定(參照圖7(c))。 Here, in the phase comparison circuit 38, the point A of the 1/4 delay period of the pulse period of the inverter drive signal, that is, point A is the pulse position of the phase detection pulse, and the phase voltage of the capacitor voltage Vc to be compared (waveform E The zero-crossing point of) is taken as point B (refer to Figure 7 (b)), and the phase difference between point A and point B is compared, and locked at a frequency at which the phase difference becomes zero (0) or a preset phase difference (see Figure 7 (c)).

另一方面，將來自電壓感測器26之波形信號及來自VCO電路32之頻率信號輸入至相位比較電路38後對各自之相位進行比較，以成為共振頻率之方式控制VCO電路32之頻率。 On the other hand, the waveform signal from the voltage sensor 26 and the frequency signal from the VCO circuit 32 are input to the phase comparison circuit 38 and the respective phases are compared to control the frequency of the VCO circuit 32 so as to become a resonance frequency.

具體而言，藉由將與共振頻率分開之頻率、例如較共振頻率低5%以上之頻率作為起動頻率之窄幅脈衝信號之逆變器驅動信號而開始逆變器部106之驅動(參照圖7(a))，使該逆變器信號之頻率頻移並上升(參照圖7(b))。 Specifically, the drive of the inverter unit 106 is started by an inverter drive signal that uses a frequency separated from the resonance frequency, for example, a frequency that is more than 5% lower than the resonance frequency, as a narrow pulse signal of the starting frequency (see FIG. 7 (a)), frequency shift and increase the frequency of the inverter signal (refer to FIG. 7 (b)).

然後，藉由相位比較電路38以共振頻率鎖定逆變器驅動信號之頻率(參照圖7(c))，鎖定結束電路42感測到鎖定結束並向輸出電路36輸出信號。根據該信號，而自輸出電路36輸出藉由PWM控制而脈衝寬度tw自窄幅脈衝信號變大之逆變器驅動信號， 從而逆變器部106之輸出上升至由輸出設定信號所設定之設定值之輸出(參照圖7(d)、(e))。 Then, the phase comparison circuit 38 locks the frequency of the inverter drive signal at the resonance frequency (see FIG. 7 (c)), and the lock completion circuit 42 senses the completion of the lock and outputs a signal to the output circuit 36. According to this signal, the inverter driving signal whose pulse width tw is increased from the narrow pulse signal by PWM control is output from the output circuit 36, so that the output of the inverter section 106 rises to the setting set by the output setting signal Value output (see Figures 7 (d) and (e)).

即，逆變器裝置20係連接並聯共振負載22作為共振負載，使用輸出來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)之較共振頻率週期足夠短之脈衝寬度之脈衝信號(窄幅脈衝信號)作為逆變器驅動信號即矩形波逆變器驅動信號Q、NQ，以與共振頻率分開之頻率(例如為較共振頻率低5%以上之頻率)為起點使該窄幅脈衝信號起動後進行將頻率上升至共振頻率或共振頻率附近的頻移之頻率控制，而將逆變器驅動信號之頻率控制於共振頻率。 That is, the inverter device 20 is connected to the parallel resonance load 22 as a resonance load, and uses the lowest resonance output frequency (which is the output voltage, output current, or output power) of the lowest set output value (output voltage or output current or output power) output from the external output setting signal. A pulse signal (narrow pulse signal) with a sufficiently short pulse width is used as the inverter drive signal, that is, the rectangular wave inverter drive signal Q, NQ, at a frequency separate from the resonance frequency (for example, more than 5% lower than the resonance frequency) Frequency) as a starting point, after the narrow pulse signal is started, the frequency control is performed to increase the frequency to a resonance frequency or a frequency shift near the resonance frequency, and the frequency of the inverter drive signal is controlled to the resonance frequency.

其後，逆變器裝置20藉由PWM控制而使窄幅脈衝信號之脈衝寬度變寬，而使之成為來自外部之輸出設定信號所表示之設定值之輸出(為輸出電壓或輸出電流或輸出電力)。 Thereafter, the inverter device 20 widens the pulse width of the narrow-width pulse signal by PWM control, so that it becomes the output of the set value indicated by an external output setting signal (for output voltage or output current or output). electric power).

(II-3)作用效果 (II-3) Effect

因而，即便於逆變器裝置20中仍可獲得與關於逆變器裝置10而在上述(I-3)中所說明之作用效果相同之作用效果。 Therefore, even in the inverter device 20, the same effects as those described in (I-3) regarding the inverter device 10 can be obtained.

(II-4)第2實施形態中之其他特徵性構成 (II-4) Other characteristic structures in the second embodiment

(a)於逆變器裝置20中，在逆變器部106之輸出級、即逆變器部106與電壓感測器26之間連接有防止高諧波電流之電感器24。 (a) In the inverter device 20, an inductor 24 for preventing a high harmonic current is connected between the output stage of the inverter section 106, that is, between the inverter section 106 and the voltage sensor 26.

即，於逆變器裝置20中，在將作為電壓型逆變器之逆變器部106連接於並聯共振負載22之情形時，由於因矩形波電壓之高諧波成分之電壓導致高諧波電流流過，故而將用以防止該高諧波電流之電感器24串聯連接於逆變器部106之輸出級。 That is, in the inverter device 20, when the inverter unit 106, which is a voltage-type inverter, is connected to the parallel resonance load 22, high harmonics are caused by the voltage of the high-harmonic component of the rectangular wave voltage. The current flows, so an inductor 24 for preventing the high harmonic current is connected in series to the output stage of the inverter section 106.

逆變器部106之輸出電壓成為矩形波，但是一般已知矩形波包含正弦波與奇次高諧波之合成波形，若直接在矩形波狀態下連接於並聯共振負載22，則奇次高諧波成分由於頻率較高故而電容器之電抗變小，而高諧波電流增大，引起電流波形失真，或引起作為逆變器部106之開關元件之電晶體之損耗惡化等。 The output voltage of the inverter section 106 is a rectangular wave, but it is generally known that the rectangular wave includes a composite waveform of a sine wave and an odd-order high harmonic. If the rectangular wave is directly connected to the parallel resonant load 22, the odd-order high-harmonic Due to the high frequency of the wave component, the reactance of the capacitor becomes small, and the high harmonic current increases, which causes distortion of the current waveform or deterioration of the loss of the transistor which is the switching element of the inverter section 106.

因此，為了抑制此種高諧波電流，而於逆變器裝置20中在逆變器部106之輸出級連接了電感器24。 Therefore, in order to suppress such a high harmonic current, an inductor 24 is connected to the output stage of the inverter section 106 in the inverter device 20.

(b)於逆變器裝置20之控制部28中，在將來自VCO電路32之輸出信號輸入至相位比較電路38進行相位比較時，設置了用以設定信號延遲時間之延遲設定電路40。 (b) In the control unit 28 of the inverter device 20, when the output signal from the VCO circuit 32 is input to the phase comparison circuit 38 for phase comparison, a delay setting circuit 40 for setting a signal delay time is provided.

即，於逆變器裝置20中，在將作為電壓型逆變器之逆變器部106連接於並聯共振負載22之情形時，由於因矩形波電壓之高諧波成分之電壓導致高諧波電流流過，故而為了防止該高諧波電流而將電感器24串聯連接，但是因藉由該電感器24之串聯連接所獲得之電感器成分，導致共振時之電壓相位產生延遲。 That is, in the inverter device 20, when the inverter unit 106, which is a voltage-type inverter, is connected to the parallel resonance load 22, high harmonics are caused by the voltage of the high-harmonic component of the rectangular wave voltage. The current flows, so in order to prevent the high harmonic current, the inductor 24 is connected in series, but the phase of the voltage at resonance is delayed due to the inductor component obtained by the series connection of the inductor 24.

於逆變器裝置20之控制部28中，為了對該電壓相位之延遲進行修正，而設置使向相位比較電路38輸入之驅動側之脈衝相位延遲之延遲設定電路40來進行延遲修正。 In order to correct the delay of the voltage phase, the control unit 28 of the inverter device 20 includes a delay setting circuit 40 for delaying the pulse phase of the driving side input to the phase comparison circuit 38 to perform delay correction.

(III)第3實施形態 (III) Third Embodiment

(III-1)構成 (III-1) Composition

於圖8中表示本發明之實施形態之一例之逆變器裝置之構成說明圖。再者，於圖8中表示由控制部所控制並且連接於串聯共振負載之逆變器裝置之整體構成。 FIG. 8 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. FIG. 8 shows the overall configuration of an inverter device controlled by a control unit and connected to a series resonance load.

於參照圖8對本發明之實施形態之一例之逆變器裝 置60進行說明時，逆變器裝置60連接於串聯共振負載62。 When the inverter device 60 as an example of the embodiment of the present invention is described with reference to FIG. 8, the inverter device 60 is connected to a series resonance load 62.

話說，可知串聯共振負載於頻率高於共振頻率之範圍內具有成為感應性之特性，另一方面，電壓型逆變器由於並聯地連接於逆變器元件之二極體之電流之逆向恢復特性，故而在感應性下之開關動作較電容性而言比較穩定。 In other words, it can be seen that the series resonance load has an inductive characteristic in a frequency range higher than the resonant frequency. On the other hand, the voltage type inverter has a reverse recovery characteristic of the current of the diodes connected in parallel to the inverter elements. Therefore, the switching action under inductive is more stable than capacitive.

因而，本發明之逆變器裝置60係將較串聯共振電路22之共振頻率高之頻率(例如為較共振頻率高5%以上之頻率)作為逆變器驅動信號之起動頻率，自該起動頻率頻移並使逆變器驅動信號之頻率下降至共振頻率，並且以共振頻率鎖定逆變器驅動信號之頻率。 Therefore, the inverter device 60 of the present invention uses a frequency higher than the resonance frequency of the series resonance circuit 22 (for example, a frequency that is more than 5% higher than the resonance frequency) as the starting frequency of the inverter drive signal. Frequency shifts and reduces the frequency of the inverter drive signal to the resonance frequency, and locks the frequency of the inverter drive signal with the resonance frequency.

以下，於對逆變器裝置60進行說明時，符號64為電流感測器，符號66為串聯共振負載62之共振電容器。 Hereinafter, when the inverter device 60 is described, reference numeral 64 is a current sensor, and reference numeral 66 is a resonance capacitor of the series resonance load 62.

再者，電流感測器64係相當於上文所述之輸出感測器108之構成要素，對電流進行感測，並輸出表示所感測到之電流之信號作為輸出感測器信號。 In addition, the current sensor 64 is a constituent element equivalent to the output sensor 108 described above, and senses the current, and outputs a signal indicating the sensed current as an output sensor signal.

控制部28之構成由於與上述中所說明之逆變器裝置20中之構成相同，故而省略其詳細說明。 The configuration of the control unit 28 is the same as the configuration in the inverter device 20 described above, and thus detailed description thereof is omitted.

(III-2)動作 (III-2) Action

於以上構成中，關於逆變器裝置60之動作，以與本發明之實施相關之控制部28之動作為中心進行說明。 In the above configuration, the operation of the inverter device 60 will be described focusing on the operation of the control unit 28 related to the implementation of the present invention.

於控制部28中，將來自外部之輸出接通(ON)信號輸入至頻移電路30，以自較串聯共振負載62之共振頻率高之頻率(例如為較共振頻率高5%以上之頻率)開始逆變器部106之驅動之方式向VCO電路32輸入信號，來自VCO電路32之輸出之頻率信號被 輸入至窄幅脈衝信號產生電路34，從而藉由窄幅脈衝信號產生電路34產生VCO電路32之輸出之頻率之窄幅脈衝信號並輸出至輸出電路36。於輸出電路36中，根據鎖定結束電路42之信號，自窄幅脈衝信號產生電路34之信號切換成PWM電路50之信號。 In the control unit 28, an external output ON signal is input to the frequency shift circuit 30 to a frequency higher than the resonance frequency of the series resonance load 62 (for example, a frequency that is more than 5% higher than the resonance frequency). The inverter unit 106 is driven to input a signal to the VCO circuit 32, and the frequency signal output from the VCO circuit 32 is input to the narrow pulse signal generating circuit 34, thereby generating the VCO circuit by the narrow pulse signal generating circuit 34. A narrow pulse signal having a frequency of 32 is output to the output circuit 36. In the output circuit 36, the signal from the narrow pulse signal generating circuit 34 is switched to the signal of the PWM circuit 50 according to the signal of the lock end circuit 42.

此處，由窄幅脈衝信號產生電路34所產生之窄幅脈衝信號之脈衝寬度較佳為設定為如下，即，以自逆變器部106輸出之輸出值成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)。 Here, the pulse width of the narrow-width pulse signal generated by the narrow-width pulse signal generating circuit 34 is preferably set as follows, which is represented by an output value output from the inverter section 106 as an output setting signal from the outside The lowest set output value of the set value (for output voltage or output current or output power).

於圖9(a)、(b)、(c)、(d)、(e)中表示將逆變器裝置60之動作示意性地表示之波形圖。 9 (a), (b), (c), (d), and (e) are waveform diagrams showing the operation of the inverter device 60 schematically.

再者，於圖9(a)、(b)、(c)、(d)、(e)中，波形I、波形J、波形K、波形L以及波形M係由電流感測器64所感測到之電流(輸出電流)波形。 Furthermore, in FIGS. 9 (a), (b), (c), (d), and (e), the waveform I, waveform J, waveform K, waveform L, and waveform M are sensed by the current sensor 64. To the current (output current) waveform.

圖9(a)表示作為驅動開始時(起動時)之起動頻率中之逆變器部106之輸出而由電流感測器64感測到之電流(輸出電流)波形(波形I)與作為逆變器驅動信號之窄幅脈衝信號之相位差。 Fig. 9 (a) shows the waveform (waveform I) of the current (output current) sensed by the current sensor 64 as the output of the inverter section 106 at the start frequency at the start of the drive (at the time of start) and the inverse Phase difference of the narrow pulse signal of the drive signal of the transformer.

於逆變器裝置60連接有串聯共振負載62之情形時，可知於共振頻率以上之頻率區域中輸出電流之相位較逆變器驅動信號之相位而言延遲。 When the series resonance load 62 is connected to the inverter device 60, it can be seen that the phase of the output current in the frequency region above the resonance frequency is delayed from the phase of the inverter drive signal.

此處，於相位比較電路38中，將逆變器驅動信號之脈衝之週期之1/4延遲之位置即C點作為相位檢波脈衝之脈衝位置，將進行比較之輸出電流相位波形(波形J)之零交叉點作為D點(參照圖9(b))，對C點與D點之相位差進行比較，並以相位差成為零(0)或預先設定之相位差之頻率進行鎖定(參照圖9(c))。 Here, in the phase comparison circuit 38, the position of the quarter of the period of the pulse of the inverter drive signal, that is, the point C is the pulse position of the phase detection pulse, and the phase waveform of the output current to be compared (waveform J) The zero crossing point is used as the D point (refer to Fig. 9 (b)), and the phase difference between the C point and the D point is compared, and locked at a frequency at which the phase difference becomes zero (0) or a preset phase difference (refer to the figure) 9 (c)).

另一方面，將來自電流感測器64之波形信號及來自VCO電路32之頻率信號輸入至相位比較電路38後對各自之相位進行比較，以成為共振頻率之方式控制VCO電路32之頻率。 On the other hand, the waveform signal from the current sensor 64 and the frequency signal from the VCO circuit 32 are input to the phase comparison circuit 38 and the respective phases are compared to control the frequency of the VCO circuit 32 so as to become a resonance frequency.

具體而言，藉由將與共振頻率分開之頻率、例如較共振頻率高5%以上之頻率作為起動頻率之窄幅脈衝信號之逆變器驅動信號而開始逆變器部106之驅動(參照圖9(a))，使該逆變器信號之頻率頻移並下降(參照圖9(b))。 Specifically, the drive of the inverter unit 106 is started by an inverter drive signal that uses a frequency separated from the resonance frequency, for example, a frequency that is 5% or more higher than the resonance frequency, as a narrow pulse signal of the starting frequency (see FIG. 9 (a)), frequency shift and decrease the frequency of the inverter signal (refer to Figure 9 (b)).

然後，藉由相位比較電路38以共振頻率鎖定逆變器驅動信號之頻率(參照圖9(c))，鎖定結束電路42感測到鎖定結束並向輸出電路36輸出信號。根據該信號，而自輸出電路36輸出藉由PWM控制而脈衝寬度tw自窄幅脈衝信號變大之逆變器驅動信號，從而逆變器部106之輸出上升至由輸出設定信號所設定之設定值之輸出(參照圖9(d)、(e))。 Then, the phase comparison circuit 38 locks the frequency of the inverter drive signal at the resonance frequency (see FIG. 9 (c)). The lock completion circuit 42 senses the end of the lock and outputs a signal to the output circuit 36. According to this signal, the inverter driving signal whose pulse width tw is increased from the narrow pulse signal by PWM control is output from the output circuit 36, so that the output of the inverter section 106 rises to the setting set by the output setting signal Value output (see Figures 9 (d) and (e)).

再者，延遲設定電路40於連接有串聯共振負載62之逆變器裝置60中，用以對逆變器部106之電路延遲進行修正。 Furthermore, the delay setting circuit 40 is used in the inverter device 60 connected to the series resonance load 62 to correct the circuit delay of the inverter section 106.

即，逆變器裝置60連接串聯共振負載62作為共振負載，使用輸出來自外部之輸出設定信號所表示之設定值之最低設定輸出值(為輸出電壓或輸出電流或輸出電力)之較共振頻率週期足夠短之脈衝寬度之脈衝信號(窄幅脈衝信號)作為逆變器驅動信號即矩形波逆變器驅動信號Q、NQ，以與共振頻率分開之頻率(例如為較共振頻率高5%以上之頻率)為起點使該窄幅脈衝信號起動後進行將頻率下降至共振頻率或共振頻率附近的頻移之頻率控制，而將逆變器驅動信號之頻率控制於共振頻率。 That is, the inverter device 60 is connected to the series resonance load 62 as a resonance load, and uses the lower resonance frequency period of the lowest set output value (for output voltage or output current or output power) that outputs the set value represented by the output setting signal from the outside. A pulse signal (narrow pulse signal) with a sufficiently short pulse width is used as the inverter drive signal, that is, the rectangular wave inverter drive signal Q, NQ, at a frequency separate from the resonance frequency (for example, it is more than 5% higher than the resonance frequency). Frequency) is the starting point, after the narrow pulse signal is started, the frequency control is performed to reduce the frequency to a resonance frequency or a frequency shift near the resonance frequency, and the frequency of the inverter drive signal is controlled to the resonance frequency.

其後，逆變器裝置60藉由PWM控制而使窄幅脈衝 信號之脈衝寬度變寬，而使之成為來自外部之輸出設定信號所表示之設定值之輸出(為輸出電壓或輸出電流或輸出電力)。 Thereafter, the inverter device 60 widens the pulse width of the narrow-width pulse signal by PWM control, so that it becomes an output of a set value represented by an external output setting signal (for output voltage or output current or output). electric power).

(III-3)作用效果 (III-3) Effect

因而，即便於逆變器裝置60中仍可獲得與關於逆變器裝置10而在上述(I-3)中所說明之作用效果相同之作用效果。 Therefore, even in the inverter device 60, the same effects as those described in the above (I-3) regarding the inverter device 10 can be obtained.

(IV)第4實施形態 (IV) Fourth Embodiment

於圖10中表示本發明之實施形態之一例之逆變器裝置中之控制部的構成說明圖。 FIG. 10 is a diagram illustrating a configuration of a control unit in an inverter device as an example of an embodiment of the present invention.

再者，於該第4實施形態中，關於除了控制部以外之其他構成，由於無與上文所述之第2、3各實施形態之逆變器裝置20、60及下文所述之第7實施形態之逆變器裝置400之構成不同之處，故而省略除控制部以外之其他構成之圖示以及說明。 In addition, in this fourth embodiment, the configurations other than the control unit are different from the inverter devices 20 and 60 of the second and third embodiments described above and the seventh and seventh embodiments described below. Since the configuration of the inverter device 400 according to the embodiment is different, illustrations and descriptions of other configurations other than the control unit are omitted.

相較於上文所述之各實施形態(第2、3、7實施形態)中之控制部28，該第4實施形態之逆變器裝置之控制部70除了控制部28之構成還具備最低位準感測電路72，於此方面而言兩者不同。 Compared with the control section 28 in each of the above-mentioned embodiments (the second, third, and seventh embodiments), the control section 70 of the inverter device of the fourth embodiment has the minimum configuration in addition to the configuration of the control section 28. The level sensing circuit 72 is different in this respect.

於第2、3、7實施形態之逆變器裝置20、60、400中，若頻率與共振頻率分開則輸出位準(共振電壓或共振電流)降低，而無法自逆變器部106之輸出進行準確之相位感測。 In the inverter devices 20, 60, and 400 of the second, third, and seventh embodiments, if the frequency is separated from the resonance frequency, the output level (resonance voltage or resonance current) decreases, and the output from the inverter unit 106 cannot be achieved. Perform accurate phase sensing.

因此，於第4實施形態之逆變器裝置中，在控制部70設置最低位準感測電路72，對逆變器部106之輸出成為可藉由最低位準感測電路72進行相位感測之輸出位準之情況進行感測，而開始相位比較。 Therefore, in the inverter device according to the fourth embodiment, the control unit 70 is provided with the lowest level sensing circuit 72, and the output to the inverter unit 106 can be phase-sensed by the lowest level sensing circuit 72. The output level is sensed and the phase comparison is started.

即，第4實施形態之逆變器裝置係藉由控制部70之 最低位準感測電路72感測藉由作為逆變器驅動信號之脈衝驅動信號所獲得之共振負載之輸出(為輸出電壓或輸出電流或輸出電力)位準，於成為預先設定之位準以上之情形時使控制於共振頻率附近之相位比較電路38開始動作。 That is, the inverter device of the fourth embodiment senses the output of the resonance load (which is the output voltage) obtained by the pulse drive signal as the inverter drive signal by the lowest level sensing circuit 72 of the control unit 70. (Or output current or output power) level, the phase comparison circuit 38, which is controlled near the resonance frequency, starts to operate when it becomes equal to or higher than a preset level.

(V)第5實施形態 (V) Fifth Embodiment

於圖11中表示本發明之實施形態之一例之逆變器裝置中之控制部的構成說明圖。 FIG. 11 is an explanatory diagram showing a configuration of a control unit in an inverter device as an example of an embodiment of the present invention.

再者，於該第5實施形態中，關於除了控制部以外之其他構成，由於無與上文所述之第2、3各實施形態之逆變器裝置20、60及下文所述之第7實施形態之逆變器裝置400之構成不同之處，故而省略除了控制部以外之其他構成之圖示以及說明。 In addition, in this fifth embodiment, the configuration other than the control unit is different from the inverter devices 20 and 60 of the second and third embodiments described above and the seventh one described below. Since the configuration of the inverter device 400 according to the embodiment is different, illustrations and descriptions of other configurations other than the control unit are omitted.

相較於上文所述之各實施形態(第2、3、7實施形態)中之控制部28，該第5實施形態之逆變器裝置之控制部80除了控制部28之構成還具備最低位準頻率感測電路82，於該方面而言兩者不同。 Compared with the control section 28 in each of the above-mentioned embodiments (the second, third, and seventh embodiments), the control section 80 of the inverter device of the fifth embodiment has the minimum configuration in addition to the configuration of the control section 28. The level frequency sensing circuit 82 is different in this respect.

於第2、3、7實施形態之逆變器裝置20、60、400中，若頻率與共振頻率分開則輸出位準(共振電壓或共振電流)降低，而無法自逆變器部106之輸出進行準確之相位感測。 In the inverter devices 20, 60, and 400 of the second, third, and seventh embodiments, if the frequency is separated from the resonance frequency, the output level (resonance voltage or resonance current) decreases, and the output from the inverter unit 106 cannot be achieved. Perform accurate phase sensing.

因此，於第5實施形態之逆變器裝置中，在控制部80設置最低位準頻率感測電路82，對逆變器部106之輸出成為可藉由最低位準頻率感測電路82進行相位感測之輸出位準之頻率(最低位準頻率)之情況進行感測，而開始相位比較。 Therefore, in the inverter device of the fifth embodiment, the control section 80 is provided with the lowest level frequency sensing circuit 82, and the output to the inverter section 106 can be phased by the lowest level frequency sensing circuit 82. The frequency of the sensed output level (lowest level frequency) is sensed, and a phase comparison is started.

即，第5實施形態之逆變器裝置係藉由控制部80之最低位準頻率感測電路82對使作為逆變器驅動信號之脈衝驅動信 號之頻率頻移時成為預先設定之頻率(最低位準頻率)之情況進行感測，並於該感測之時間點使相位比較電路38開始動作。 That is, in the inverter device of the fifth embodiment, the lowest level frequency sensing circuit 82 of the control unit 80 sets the frequency of the pulse drive signal as the inverter drive signal to a preset frequency (minimum frequency). Level frequency), and the phase comparison circuit 38 starts to operate at the time point of the sensing.

(VI)第6實施形態 (VI) Sixth embodiment

本發明之第6實施形態之一例之逆變器裝置具有上文所述之第4實施形態中之最低位準感測電路72及上文所述之第5實施形態中之最低位準頻率感測電路82兩者。 An inverter device according to an example of the sixth embodiment of the present invention includes the lowest level sensing circuit 72 in the fourth embodiment described above and the lowest level frequency sense in the fifth embodiment described above.测 电路 82 both.

再者，於該第6實施形態中，除了在控制部設置有最低位準感測電路及最低位準頻率感測電路兩者以外，關於其他構成，並無與上文所述之各實施形態(第2、3、4、5各實施形態)及下文所述之第7實施形態中之構成不同之處，因此藉由引用上文所述之各實施形態(第2、3、4、5各實施形態)及下文所述之第7實施形態中之說明，而省略其圖示以及說明。 Furthermore, in this sixth embodiment, except for the lowest level sensing circuit and the lowest level frequency sensing circuit provided in the control unit, the other configurations are not the same as those of the above embodiments. (The second, third, fourth, and fifth embodiments) and the seventh embodiment described below are different in structure, so by referring to each of the above-mentioned embodiments (second, third, fourth, and fifth) Each embodiment) and the description of the seventh embodiment described below, and the illustration and description thereof are omitted.

(VII)第7實施形態 (VII) Seventh embodiment

於圖12中表示本發明之實施形態之一例之逆變器裝置之構成說明圖。再者，於圖12中表示由控制部所控制並且連接於串聯共振負載之逆變器裝置之整體構成。 FIG. 12 is a diagram illustrating a configuration of an inverter device as an example of an embodiment of the present invention. The overall configuration of the inverter device controlled by the control unit and connected to the series resonance load is shown in FIG. 12.

又，於圖13中表示圖12所示之逆變器裝置中之逆變器部之放大說明圖。 13 is an enlarged explanatory diagram of an inverter section in the inverter device shown in FIG. 12.

該圖12所示之逆變器裝置(本發明之第7實施形態之一例之逆變器裝置)400與圖8所示之上文所述之第3實施形態之逆變器裝置60之構成相比，於具備逆變器部406以代替逆變器部106之方面上，兩者不同。 The configuration of the inverter device 400 (an inverter device as an example of the seventh embodiment of the present invention) 400 shown in FIG. 12 and the inverter device 60 of the third embodiment described above shown in FIG. 8 The two are different from each other in that the inverter unit 406 is provided instead of the inverter unit 106.

如圖13所示般，逆變器裝置400之逆變器部406係使用SiC二極體作為逆變器開關元件406a中之環流二極體(飛輪二 極體)406b者。 As shown in FIG. 13, the inverter section 406 of the inverter device 400 uses a SiC diode as a circulating diode (flywheel diode) 406b in the inverter switching element 406a.

更詳細而言，如圖13所示般，於逆變器部406之逆變器開關元件406a中，使用SiC二極體作為與半導體開關元件406c相反且並聯地連接之飛輪二極體406b。 More specifically, as shown in FIG. 13, in the inverter switching element 406 a of the inverter section 406, a SiC diode is used as the flywheel diode 406 b connected in parallel with the semiconductor switching element 406 c in an opposite manner.

於該第7實施形態之逆變器裝置400中，共振負載形成串聯共振電路62，以較共振頻率低之頻率(例如為較共振頻率低5%以上之頻率)為起點使可確保最低設定輸出值(為輸出電壓或輸出電流或輸出電力)之足夠短之逆變器驅動信號即脈衝驅動信號之頻率起動，進行將頻率上升至共振頻率附近之頻移之頻率控制，而將作為逆變器驅動信號之脈衝驅動信號之頻率控制於共振頻率。 In the inverter device 400 of the seventh embodiment, the resonance load forms a series resonance circuit 62, and the lowest setting output can be ensured with a frequency lower than the resonance frequency (for example, a frequency lower than the resonance frequency by 5% or more) as a starting point. Value (for output voltage or output current or output power) is short enough to start the inverter drive signal, that is, the frequency of the pulse drive signal, to perform frequency control to increase the frequency to a frequency near the resonance frequency, and it will be used as an inverter The frequency of the pulse driving signal of the driving signal is controlled at the resonance frequency.

即，於逆變器裝置400中，使用SiC二極體作為逆變器開關元件406a之飛輪二極體406b。 That is, in the inverter device 400, a SiC diode is used as the flywheel diode 406b of the inverter switching element 406a.

因此，由於該特性故而幾乎無電流再生時之恢復時間，因此可利用串聯共振電路進行電容性(C性)下之逆變器動作，可以較低頻率(C性區域)為起點，偏移至頻率較高之共振頻率。 Therefore, due to this characteristic, there is almost no recovery time during current regeneration. Therefore, the series resonant circuit can be used for capacitive (C) inverter operation, and the lower frequency (C region) can be used as a starting point to shift to Higher frequency resonance frequency.

(VIII)第8實施形態 (VIII) Eighth embodiment

其次，參照圖14(a)、(b)、(c)對本發明之第8實施形態之一例之逆變器裝置進行說明。 Next, an inverter device according to an example of the eighth embodiment of the present invention will be described with reference to Figs. 14 (a), (b), and (c).

此處，於圖14(a)中表示將使用連接於共振負載之本發明之逆變器裝置之電源構成示意性地表示之構成說明圖。 Here, FIG. 14 (a) shows a configuration explanatory diagram schematically showing a power supply configuration using an inverter device of the present invention connected to a resonance load.

又，於圖14(b)中表示將使用連接於串聯共振負載之習知技術之逆變器裝置之電源構成示意性地表示之構成說明圖。 In addition, FIG. 14 (b) is a configuration explanatory diagram schematically showing a power supply configuration of an inverter device using a conventional technique connected to a series resonance load.

進而，於圖14(c)中表示將使用連接於並聯共振負載之習知技術之逆變器裝置之電源構成示意性地表示之構成說明圖。 Furthermore, FIG. 14 (c) is a configuration explanatory diagram schematically showing a power supply configuration of an inverter device using a conventional technique connected to a parallel resonance load.

圖14(a)所示之使用上文所述之本發明之連接於共振負載之逆變器裝置10、20、60、400之電源構成係可用於感應加熱用途者，係利用空冷同軸纜線504將連接於共振負載之本發明之逆變器裝置10、20、60、400之輸出端子500與並聯共振電容器箱502連接，並將小型變流器(手持型變流器)506連接於並聯共振電容器箱502，而向加熱線圈508傳送高頻電流。 The power supply structure of the inverter device 10, 20, 60, and 400 connected to the resonant load using the present invention described above is shown in FIG. 14 (a). Those that can be used for induction heating are air-cooled coaxial cables. 504 connects the output terminal 500 of the inverter device 10, 20, 60, 400 of the present invention connected to the resonance load with the parallel resonance capacitor box 502, and connects a small converter (hand-held converter) 506 to the parallel The resonance capacitor box 502 transmits a high-frequency current to the heating coil 508.

於感應加熱用途中，存在逆變器裝置至加熱線圈之距離變長，而藉由手動進行加熱作業之情況，習知，如圖14(b)所示般，對連接於串聯共振負載之習知技術之逆變器裝置600之輸出端子600a連接水冷纜線602而延長，通過中繼盒604而利用小型變流器(手持型變流器)606進行阻抗轉換，而向加熱線圈608傳送高頻電流。 In the application of induction heating, there is a case where the distance between the inverter device and the heating coil becomes long, and the heating operation is performed manually. As shown in FIG. 14 (b), it is known that the connection to a series resonance load is used. The output terminal 600a of the inverter device 600 of the prior art is connected to the water-cooled cable 602 and extended. The relay box 604 is used to perform impedance conversion by using a small converter (hand-held converter) 606, and transmits high voltage to the heating coil 608. Frequency current.

或，習知，如圖14(c)所示般，使用連接於並聯共振負載之習知技術之逆變器裝置700，對逆變器裝置700之輸出端子700a連接空冷同軸纜線702而延長，通過中繼盒704而利用小型變流器(手持型變流器)706進行阻抗轉換，而向加熱線圈708傳送高頻電流。 Or, as shown in FIG. 14 (c), the inverter device 700 using a conventional technique connected to a parallel resonance load is connected to an air-cooled coaxial cable 702 to the output terminal 700a of the inverter device 700 and extended. Through the relay box 704, impedance conversion is performed by a small converter (hand-held converter) 706, and a high-frequency current is transmitted to the heating coil 708.

然而，於圖14(b)所示之使用連接於串聯共振負載之習知技術之逆變器裝置600之情形時，由於在水冷纜線602之往復之雜散電容中高諧波電流流過，故而延長距離存在極限，一般而言，延長距離之極限為50m左右。 However, in the case of the inverter device 600 using the conventional technology connected to a series resonant load as shown in FIG. 14 (b), since a high harmonic current flows in the stray capacitance of the water-cooled cable 602, Therefore, there is a limit to the extension distance. Generally, the limit of the extension distance is about 50m.

又，於圖14(c)所示之使用連接於並聯共振負載之習知技術之逆變器裝置700，並延長空冷同軸纜線702之距離之情形時，由於逆變器裝置700內部之串聯電抗器變大變重，故而電源本 身亦變大變重，從而無法作為小型電源而於作業現場容易地使用者。 In addition, in the case where the inverter device 700 using the conventional technology connected to a parallel resonant load is shown in FIG. 14 (c), and the distance of the air-cooled coaxial cable 702 is extended, due to the series connection inside the inverter device 700 The reactor becomes larger and heavier, so the power source itself becomes larger and heavier, so that it cannot be easily used as a small power source at the job site.

另一方面，於圖14(a)所示之使用連接於共振負載之本發明之逆變器裝置10、20、60、400的構成中，由於使用了無需較大之直流電抗器之電壓型逆變器，故而可成為小型電源構成，藉由對其連接空冷同軸纜線504，可構成即便為200m以上亦可容易地延長空冷同軸纜線504之小型電源。 On the other hand, in the configuration using the inverter devices 10, 20, 60, and 400 of the present invention connected to a resonant load shown in FIG. 14 (a), a voltage type that does not require a large DC reactor is used The inverter can be a compact power supply. By connecting the air-cooled coaxial cable 504 to the inverter, it is possible to configure a small power supply that can easily extend the air-cooled coaxial cable 504 even at 200 m or more.

再者，並聯共振電容器箱502係包含並聯共振用電容器者。 The parallel resonance capacitor box 502 includes a capacitor for parallel resonance.

又，作為小型變流器(手持型變流器)506，可使用習知之構成、即與小型變流器(手持型變流器)606、706相同者。 As the small-sized converter (hand-held converter) 506, a conventional configuration, that is, the same as the small-sized converter (hand-held converter) 606, 706 can be used.

同樣地，加熱線圈508亦可使用習知之構成、即與加熱線圈608、708相同者。 Similarly, the heating coil 508 may use a conventional structure, that is, the same as the heating coils 608 and 708.

(IX)第9實施形態 (IX) Ninth Embodiment

本發明之第9實施形態之一例之逆變器裝置係藉由如下方式而成者，即，構成上文所述之各實施形態中之共振負載200、並聯共振負載22或串聯共振負載62之共振電路由包含感應加熱用之加熱線圈及共振電容器之共振電路所構成。 An inverter device according to an example of the ninth embodiment of the present invention is formed by constituting the resonance load 200, the parallel resonance load 22, or the series resonance load 62 in each of the embodiments described above. The resonance circuit is composed of a resonance circuit including a heating coil for induction heating and a resonance capacitor.

即，作為連接於包含逆變器裝置10、20、60、400在內之本發明之逆變器裝置的共振負載200、並聯共振負載22或串聯共振負載62，可使用各種構成者，例如可將如圖15(a)、(b)所示之感應加熱用共振負載連接於本發明之逆變器裝置。 That is, as the resonance load 200, the parallel resonance load 22, or the series resonance load 62 connected to the inverter device of the present invention including the inverter devices 10, 20, 60, and 400, various components can be used, for example A resonance load for induction heating as shown in Figs. 15 (a) and (b) is connected to the inverter device of the present invention.

此處，於圖15(a)中表示對串聯共振負載之情形時之感應加熱用串聯共振負載進行表示之構成說明圖。 Here, FIG. 15 (a) shows a structure explanatory diagram showing a series resonance load for induction heating in the case of a series resonance load.

又，於圖15(b)中表示對並聯共振負載之情形時之感應加熱用並聯共振負載進行表示之構成說明圖。於該圖15(b)所示之構成中，在感應加熱用並聯共振負載中串聯連接有高諧波去除用之濾波器。 In addition, FIG. 15 (b) is a structural explanatory diagram showing a parallel resonance load for induction heating in the case of a parallel resonance load. In the configuration shown in FIG. 15 (b), a filter for high harmonic wave removal is connected in series to a parallel resonance load for induction heating.

再者，於圖6所示之逆變器裝置20中，濾波器作為電感器24而接線於逆變器裝置20內。 Furthermore, in the inverter device 20 shown in FIG. 6, the filter is wired as an inductor 24 in the inverter device 20.

(X)其他實施形態及變形例之說明 (X) Explanation of other embodiments and modifications

再者，上文所述之實施形態僅為例示，本發明可以其他各種形態進行實施。即，本發明並不限於上文所述之實施形態，可於不脫離本發明之主旨之範圍內進行各種省略、置換、變更。 The embodiments described above are merely examples, and the present invention can be implemented in various other forms. That is, the present invention is not limited to the embodiments described above, and various omissions, substitutions, and changes can be made without departing from the spirit of the present invention.

例如，上文所述之實施形態可如以下(X-1)至(X-4)所示般進行變形。 For example, the embodiment described above may be modified as shown in the following (X-1) to (X-4).

(X-1)於上文所述之實施形態中，於將起動頻率與共振頻率分開時，具體而言例示了與共振頻率分開5%以上之情況。 (X-1) In the embodiment described above, when the starting frequency is separated from the resonance frequency, specifically, a case where it is separated from the resonance frequency by 5% or more is exemplified.

然而，本發明並不限於與共振頻率分開5%以上，亦可與共振頻率分開未滿5%。 However, the present invention is not limited to being separated from the resonance frequency by more than 5%, and may be separated from the resonance frequency by less than 5%.

即，「5%」數值係本案發明者藉由實驗而實證地求出之較佳之數值，但是本發明並不限於「5%」之數值，只要起動頻率與共振頻率分開即可。 That is, the "5%" value is a better value empirically obtained by the inventor of the present case through experiments, but the present invention is not limited to the "5%" value, as long as the starting frequency and the resonance frequency are separated.

藉由將起動頻率與共振頻率分開，而不論共振負載側之共振頻率如何偏離，均可藉由頻移而自動地找出共振頻率。 By separating the starting frequency from the resonance frequency, the resonance frequency can be automatically found by the frequency shift regardless of the deviation of the resonance frequency on the resonance load side.

此處，頻移之區域(頻移區域)較佳為決定為考慮了對逆變器電路最佳之二極體逆向恢復特性之感應性區域，根據本案發明者之實驗，為自共振頻率起5%以上之區域。 Here, the frequency shifted region (frequency shifted region) is preferably determined as an inductive region that takes into account the best diode reverse recovery characteristics for the inverter circuit. According to the experiment by the inventor of the present application, Areas above 5%.

(X-2)於上文所述之實施形態中，各構成中之具體之電路構成等省略了說明，但是理所當然可使用與各構成對應之先前公知之電路構成。 (X-2) In the embodiments described above, descriptions of specific circuit configurations and the like in each configuration are omitted, but it is a matter of course that a conventionally known circuit configuration corresponding to each configuration can be used.

(X-3)於上文所述之實施形態中，省略了各構成中之具體之電路常數等說明，但是理所當然可使用與各構成對應之先前公知之電路常數。 (X-3) In the embodiment described above, descriptions of specific circuit constants and the like in each configuration are omitted, but it is a matter of course that previously known circuit constants corresponding to each configuration may be used.

(X-4)理所當然，上文所述之各實施形態以及上文所述之(X-1)至(X-3)所示之各實施形態亦可適宜地組合。 (X-4) As a matter of course, each of the embodiments described above and each of the embodiments shown in (X-1) to (X-3) described above may be appropriately combined.

(產業上之可利用性)     (Industrial availability)    

本發明可用於連接於如感應加熱電路等之共振負載之電源裝置即逆變器裝置。 The present invention can be used for an inverter device that is a power supply device connected to a resonant load such as an induction heating circuit.

Claims (30)

一種逆變器裝置，其係作為連接於共振負載且受到PWM控制之電壓型逆變器者；其特徵在於，其包括：逆變器部，其連接於共振負載且由逆變器驅動信號所驅動；及控制手段，其控制上述逆變器部之動作；上述控制手段係以如下方式進行控制，即，將較上述共振負載之共振頻率之週期短之脈衝寬度之脈衝信號作為上述逆變器驅動信號，將與上述共振頻率分開之頻率作為起點而開始上述逆變器部之驅動後，使上述逆變器驅動信號之頻率頻移至上述共振頻率或上述共振頻率附近，使得上述逆變器驅動信號之頻率與上述共振頻率大致一致。     An inverter device is a voltage-type inverter connected to a resonance load and subject to PWM control. The inverter device includes an inverter unit connected to the resonance load and controlled by an inverter driving signal. Drive; and control means for controlling the operation of the inverter section; the control means is controlled in such a manner that a pulse signal having a pulse width shorter than the period of the resonance frequency of the resonance load is used as the inverter The driving signal starts the driving of the inverter unit with a frequency separated from the resonance frequency as a starting point, and then shifts the frequency of the inverter driving signal to the resonance frequency or the vicinity of the resonance frequency, so that the inverter The frequency of the driving signal is approximately the same as the resonance frequency.     如請求項1之逆變器裝置，其中，上述較短之脈衝寬度係上述逆變器部之輸出成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值的脈衝寬度。     For example, the inverter device of claim 1, wherein the shorter pulse width is a pulse width at which the output of the inverter section becomes the lowest set output value of the set value indicated by an external output setting signal.     如請求項1或2之逆變器裝置，其中，上述起點係以如下方式設定，即，上述頻移之區域成為基於構成上述逆變器部之逆變器電路之二極體逆向恢復特性的感應性區域。     For the inverter device of claim 1 or 2, wherein the starting point is set in such a manner that the frequency shifted region is based on a reverse recovery characteristic of a diode of an inverter circuit constituting the inverter section. Inductive area.     如請求項1至3中任一項之逆變器裝置，其中，上述共振負載為並聯共振負載，上述起點為低於上述共振頻率之頻率。     The inverter device according to any one of claims 1 to 3, wherein the resonance load is a parallel resonance load, and the starting point is a frequency lower than the resonance frequency.     如請求項4之逆變器裝置，其中，於上述逆變器部之輸出級連接有電感器。     The inverter device according to claim 4, wherein an inductor is connected to the output stage of the inverter section.     如請求項5之逆變器裝置，其中，上述控制部具有對由上述電感器引起之電壓相位之延遲進行修 正之延遲修正手段。     The inverter device according to claim 5, wherein the control unit has a delay correction means for correcting a delay of a voltage phase caused by the inductor.     如請求項1至3中任一項之逆變器裝置，其中，上述共振負載為串聯共振負載，上述起點為高於上述共振頻率之頻率。     The inverter device according to any one of claims 1 to 3, wherein the resonance load is a series resonance load, and the starting point is a frequency higher than the resonance frequency.     如請求項7之逆變器裝置，其中，上述控制部具有對上述逆變器部之電路延遲進行修正之延遲修正手段。     The inverter device according to claim 7, wherein the control unit has a delay correction means for correcting a circuit delay of the inverter unit.     如請求項1或2之逆變器裝置，其中，上述共振負載為串聯共振負載，上述逆變器部使用SiC二極體作為逆變器開關元件中之飛輪二極體，上述起點為低於上述共振頻率之頻率。     For example, the inverter device of claim 1 or 2, wherein the resonance load is a series resonance load, and the inverter section uses a SiC diode as a flywheel diode in the switching element of the inverter, and the starting point is lower than The frequency of the above resonance frequency.     如請求項1至9中任一項之逆變器裝置，其中，上述起點為相對於上述共振頻率之頻率分開5%以上之頻率。     The inverter device according to any one of claims 1 to 9, wherein the starting point is a frequency separated by more than 5% from the frequency of the resonance frequency.     如請求項1至10中任一項之逆變器裝置，其中，上述控制部於以上述逆變器驅動信號之頻率與上述共振頻率大致一致之方式進行控制後，藉由PWM控制使上述逆變器驅動信號之脈衝寬度變寬。     The inverter device according to any one of claims 1 to 10, wherein the control unit controls the inverter drive signal so that the frequency of the inverter drive signal substantially coincides with the resonance frequency, and then causes the inverter to be inverted by PWM control. The pulse width of the drive signal of the inverter becomes wider.     如請求項1至11中任一項之逆變器裝置，其中，上述控制部具有最低位準感測手段，該最低位準感測手段對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之情況進行感測。     The inverter device according to any one of claims 1 to 11, wherein the control unit has a lowest level sensing means, and the lowest level sensing means enables phase sensing of the output of the inverter unit The output level is sensed.     如請求項1至12中任一項之逆變器裝置，其中，上述控制部具有頻率感測手段，該頻率感測手段對上述逆變器部 之輸出成為能夠進行相位感測之輸出位準之頻率之情況進行感測。     The inverter device according to any one of claims 1 to 12, wherein the control unit has a frequency sensing means, and the frequency sensing means has an output level capable of performing phase sensing on the output of the inverter unit. Frequency.     如請求項1至13中任一項之逆變器裝置，其中，利用空冷同軸纜線將上述逆變器裝置之輸出端子與並聯共振電容器箱連接，並將變流器連接至上述並聯共振電容器箱，向加熱線圈傳送高頻電流。     The inverter device according to any one of claims 1 to 13, wherein an output terminal of the inverter device is connected to a parallel resonance capacitor box using an air-cooled coaxial cable, and a converter is connected to the parallel resonance capacitor. Box, transmitting high-frequency current to the heating coil.     如請求項1至14中任一項之逆變器裝置，其中，上述共振負載由包含感應加熱用之加熱線圈及共振電容器之共振電路所構成。     The inverter device according to any one of claims 1 to 14, wherein the resonance load includes a resonance circuit including a heating coil for induction heating and a resonance capacitor.     一種逆變器裝置之控制方法，其係作為連接於共振負載且受到PWM控制之電壓型逆變器的逆變器裝置之控制方法；其特徵在於，以如下方式進行控制：將較共振負載之共振頻率之週期短之脈衝寬度之脈衝信號作為逆變器驅動信號，將與上述共振頻率分開之頻率作為起點而開始逆變器部之驅動後，使上述逆變器驅動信號之頻率頻移至上述共振頻率或上述共振頻率附近，使得上述逆變器驅動信號之頻率與上述共振頻率大致一致。     An inverter device control method is a control method of an inverter device as a voltage-type inverter connected to a resonance load and subject to PWM control; it is characterized in that it is controlled in the following manner: A pulse signal with a short pulse width of the resonance frequency is used as an inverter drive signal. After starting the drive of the inverter section with a frequency separated from the resonance frequency as a starting point, the frequency of the inverter drive signal is shifted to The resonance frequency or the vicinity of the resonance frequency is such that the frequency of the inverter drive signal substantially coincides with the resonance frequency.     如請求項16之逆變器裝置之控制方法，其中，上述較短之脈衝寬度係上述逆變器部之輸出成為來自外部之輸出設定信號所表示之設定值之最低設定輸出值的脈衝寬度。     For example, the control method of the inverter device according to claim 16, wherein the shorter pulse width is a pulse width at which the output of the inverter unit becomes the lowest set output value of the set value indicated by the output setting signal from the outside.     如請求項16或17之逆變器裝置之控制方法，其中，上述起點係以如下方式設定，即，上述頻移之區域成為基於構成上述逆變器部之逆變器電路之二極體逆向恢復特性的感應性區域。     For example, the method for controlling an inverter device according to claim 16 or 17, wherein the starting point is set in such a manner that the frequency shift region becomes a diode inversion based on the inverter circuit constituting the inverter section Inductive area of recovery characteristics.     如請求項16至18中任一項之逆變器裝置之控制方法，其中，上述共振負載為並聯共振負載， 上述起點為低於上述共振頻率之頻率。     The control method of the inverter device according to any one of claims 16 to 18, wherein the resonance load is a parallel resonance load, and the starting point is a frequency lower than the resonance frequency.     如請求項19之逆變器裝置之控制方法，其中，於上述逆變器部之輸出級連接電感器。     The control method of the inverter device according to claim 19, wherein an inductor is connected to the output stage of the inverter section.     如請求項20之逆變器裝置之控制方法，其中，對由上述電感器所引起之電壓相位之延遲進行修正。     The control method of the inverter device according to claim 20, wherein the delay of the voltage phase caused by the inductor is corrected.     如請求項16至18中任一項之逆變器裝置之控制方法，其中，上述共振負載為串聯共振負載，上述起點為高於上述共振頻率之頻率。     The control method of the inverter device according to any one of claims 16 to 18, wherein the resonance load is a series resonance load, and the starting point is a frequency higher than the resonance frequency.     如請求項22之逆變器裝置之控制方法，其中，對上述逆變器部之電路延遲進行修正。     The control method of the inverter device according to claim 22, wherein the circuit delay of the inverter unit is corrected.     如請求項16或17之逆變器裝置之控制方法，其中，上述共振負載為串聯共振負載，上述逆變器部使用SiC二極體作為逆變器開關元件中之飛輪二極體，上述起點為低於上述共振頻率之頻率。     For example, the method for controlling an inverter device according to claim 16 or 17, wherein the resonance load is a series resonance load, and the inverter section uses a SiC diode as a flywheel diode in the switching element of the inverter. A frequency lower than the above-mentioned resonance frequency.     如請求項16至24中任一項之逆變器裝置之控制方法，其中，上述起點為相對於上述共振頻率之頻率分開5%以上之頻率。     The control method of the inverter device according to any one of claims 16 to 24, wherein the starting point is a frequency separated by more than 5% from the frequency of the resonance frequency.     如請求項16至25中任一項之逆變器裝置之控制方法，其中，於以上述逆變器驅動信號之頻率與上述共振頻率大致一致之方式進行控制後，藉由PWM控制使上述逆變器驅動信號之脈衝寬度變寬。     The control method of the inverter device according to any one of claims 16 to 25, wherein after the control is performed in such a manner that the frequency of the inverter drive signal is substantially consistent with the resonance frequency, the inversion is performed by PWM control. The pulse width of the drive signal of the inverter becomes wider.     如請求項16至26中任一項之逆變器裝置之控制方法，其中，對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之情況進行感測。     The method for controlling an inverter device according to any one of claims 16 to 26, wherein the case where the output of the inverter section becomes an output level capable of phase sensing is sensed.     如請求項16至27中任一項之逆變器裝置之控制方法，其中，對上述逆變器部之輸出成為能夠進行相位感測之輸出位準之頻率之情況進行感測。     The control method of the inverter device according to any one of claims 16 to 27, wherein the case where the output of the inverter section becomes a frequency at which the phase of the output level can be sensed is sensed.     如請求項16至28中任一項之逆變器裝置之控制方法，其中，利用空冷同軸纜線將上述逆變器裝置之輸出端子與並聯共振電容器箱連接，並將變流器連接至上述並聯共振電容器箱，向加熱線圈傳送高頻電流。     The control method of the inverter device according to any one of claims 16 to 28, wherein the output terminal of the inverter device is connected to a parallel resonance capacitor box by using an air-cooled coaxial cable, and the converter is connected to the above Resonant capacitor box is connected in parallel to transmit high-frequency current to the heating coil.     如請求項16至29中任一項之逆變器裝置之控制方法，其中，上述共振負載由包含感應加熱用之加熱線圈與共振電容器之共振電路所構成。     The control method of the inverter device according to any one of claims 16 to 29, wherein the resonance load is constituted by a resonance circuit including a heating coil for induction heating and a resonance capacitor.    
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