TW201212373A

TW201212373A - Transmission line structure

Info

Publication number: TW201212373A
Application number: TW99129519A
Authority: TW
Inventors: Ju-Hung Chen; Shih-Yuan Chen; Po-Wen Hsu
Original assignee: Univ Nat Taiwan
Priority date: 2010-09-01
Filing date: 2010-09-01
Publication date: 2012-03-16
Also published as: TWI459631B

Abstract

The invention provides a transmission line structure for suppressing the energy leakage. The transmission line structure is formed by cascading a plurality of unit cells. The unit cell comprises a signal line unit, and comprises open units, short units, or side conductor units respectively in the proximity of the signal line unit, wherein a Bloch impedance of the unit cell is about 0.6 times through 1.4 times of a system impedance of the transmission line structure.

Description

201212373 07A-100506 34792twf.doc/n 六、發明說明：【發明所屬之技術領域】本發明是有關於一種傳輸線結構，且特別是有關於一種抑制能量洩漏的傳輸線結構。【先前技術】傳統微波電路的信號線在傳輸信號時，會因為能量洩 • 漏的原因，而可能限制其操作頻率與導致信號品質的衰減。傳統傳輸線結構可能為一傳統傳輸線結構可能為一背覆導體共平面波導（Conductor-Backed Coplanar Waveguide ’簡稱為CBCPW)，其結構為習知共平面波導 (Coplanar Waveguide，簡稱為CPW)的改良結構。背覆導體共平面波導的特徵在於，其共平面波導下方外加一層完整的導體面於介質版的另一側，其主要用以加強機械強度以及散熱能力。由於有平行板模態的存在，背覆導體共平 =波導會有能量損耗與能量耦合洩漏的問題存在，因此目刚有數種傳輸線結構被提出，以抑制傳輸信號的能量洩漏。产無洩漏共平面波導(Non-Leaky Coplanar Waveguide，，稱為NLC)與背面鑿溝(Backside Gro〇ving)傳輸線結構被 j出來克服前述的問題。無洩漏共平面波導藉由增加額外一層介質板使共平面波導模態速度低於主要平行板模態的，度來達到抑制能量洩漏的功效；背面鑿溝傳輸線結&則 =在介質板背面製造空氣溝槽，來_抑概量茂漏的功效。然而，上述無洩漏共平面波導與背面鑿溝傳輸線結構 201212373 υ/Λ-ινν-?ι/6 34792twf.doc/n 需要額外的介質板，且必須對介質板的介電係數與厚度做特別的限制’而使得結構複雜化與成本額外增加。上述結構的詳細内容可分別參照Liu etal.在1995年5月於IEEE Transactions on Microwave Theory and Technique 發表的論文 “Non-leaky coplanar (NLC) waveguides with conductor backing”，以及 Hotta et al.在 2001 年於 Asia-Pacific Microwave Conference 發表的論文 “Effects of backside grooving on leakage loss of conductor-backed coplanar waveguide” ° 電磁能隙帶(Electro-Magnetic Band Gap，簡稱為 EBG) 與單一平面緊密光子隙帶(Uni-Planar Compact Photonic Band Gap，簡稱為UC-PBG)傳輸線結構也被提出來解決能量洩漏的問題。電磁能隙帶與單一平面緊密光子隙帶傳輸線結構使用數量甚多的週期結構鋪滿導體面，其分佈式的電感與電容值所形成的止帶(Stop Band)之效果有助於抑制平行板模態的傳遞。然而，上述電磁能隙帶與單一平面緊进光子隙帶傳輸線結構的結構形狀複雜，且其龐大的週期結構除了佔用巨大的導體面積之外，其電磁模擬上也相當地耗費時間’而不利於設計與製造。此外，上述結構在止帶以外的頻帶並無抑制損耗的能力。況且，此種結構要達到寬頻的止帶是極為困難的事情，因此上述結構僅是具備窄頻的抑制損耗能力。上述結構的詳細内容可參照Yanget al.在 1999 年 8 月於 IEEE Transactions on Microwave Theory and Technique 發表的論文 “A uniplanar compact 201212373 W $ χ v,J506 34792twf.doc/n photonic-bandgap (UC-PBG) structure and its applications for microwave circuits” o201212373 07A-100506 34792twf.doc/n VI. Description of the Invention: [Technical Field] The present invention relates to a transmission line structure, and more particularly to a transmission line structure for suppressing energy leakage. [Prior Art] When a signal line of a conventional microwave circuit transmits a signal, it may limit its operating frequency and cause degradation of signal quality due to energy leakage. The conventional transmission line structure may be a conventional transmission line structure which may be a Conductor-Backed Coplanar Waveguide (CBCPW), and its structure is a modified structure of a conventional Coplanar Waveguide (CPW). The back-conducting coplanar waveguide is characterized by the addition of a complete conductor surface underneath the coplanar waveguide to the other side of the dielectric plate, which is mainly used to enhance mechanical strength and heat dissipation. Due to the existence of parallel plate modes, the backplane conductors are flat = the waveguide has energy loss and energy coupling leakage problems, so several transmission line structures have been proposed to suppress the energy leakage of the transmitted signal. Non-Leaky Coplanar Waveguide (NLC) and Backside Gro〇ving transmission line structures have been developed to overcome the aforementioned problems. The leak-free coplanar waveguide achieves the effect of suppressing energy leakage by adding an additional dielectric plate to make the modal velocity of the coplanar waveguide lower than that of the main parallel plate mode; the back trenching transmission line junction & = on the back of the dielectric plate The air groove is made to reduce the amount of leakage. However, the above-mentioned leak-free coplanar waveguide and back-groove transmission line structure 201212373 υ/Λ-ινν-?ι/6 34792twf.doc/n requires an additional dielectric plate and must be special for the dielectric constant and thickness of the dielectric plate. Limiting ' complicates the structure and adds extra cost. The details of the above structure can be referred to the paper "Non-leaky coplanar (NLC) waveguides with conductor backing" by Liu et al., IEEE Transactions on Microwave Theory and Technique, May 1995, and Hotta et al. Papers published by Asia-Pacific Microwave Conference "Effects of backside grooving on leakage loss of conductor-backed coplanar waveguide" ° Electro-Magnetic Band Gap (EBG) and single-plane compact photonic gap band (Uni-Planar The Compact Photonic Band Gap (referred to as UC-PBG) transmission line structure has also been proposed to solve the problem of energy leakage. The electromagnetic energy gap band and the single plane compact photonic band transmission line structure use a large number of periodic structures to cover the conductor surface, and the effect of the distributed inductance and capacitance value of the Stop Band helps to suppress the parallel plate. Modal delivery. However, the structure of the above-mentioned electromagnetic energy gap band and the single plane tight-in photonic-gap transmission line structure is complicated, and its large periodic structure is quite time-consuming in electromagnetic simulation in addition to occupying a large conductor area. Design and manufacturing. Further, the above configuration has no ability to suppress loss in a frequency band other than the stop band. Moreover, it is extremely difficult to achieve a broadband stop band in such a structure, and therefore the above structure is only capable of suppressing loss with a narrow frequency. For details of the above structure, refer to the paper published by Yang et al., IEEE Transactions on Microwave Theory and Technique, August 1999 "A uniplanar compact 201212373 W $ χ v, J506 34792twf.doc/n photonic-bandgap (UC-PBG) Structure and its applications for microwave circuits" o

另外，還有承載金屬聯通柱背金屬共平面波導(Via LoadedCBCPW)被提出。承載金屬聯通柱背金屬共平面波導使用金屬聯通柱佈滿信號線兩側的導體面來製造類似金屬合成波導(Substrate Integrated Waveguide，簡稱為 SIW) 的效果，以有效地減少傳輸線到導體面的能量耦合。承載金屬聯通柱背金屬共平面波導目前雖被廣泛地使用於微波電路應用上，然而’製造金屬聯通柱需要額外的光罩與製程’因此，其製造成本也將被提高。上述結構的詳細内容可參照 Haydl 在 2002 年 6 月於 IEEE Transactions on Microwave Theory and Technique 發表的論文“〇n the use of vias in conductor-backed coplanar circuits”。總之，上述各種傳統傳輸線結構都有成本增加與製程增加的問題存在。據此，有需要減少傳統傳輸線結構的製造成本與製程，以達到節能省碳的環保趨勢。In addition, a metal-conducting column back-metal coplanar waveguide (Via Loaded CBCPW) has been proposed. The metal-conducting column back-metal coplanar waveguide uses metal-conducting posts to fill the conductor faces on both sides of the signal line to fabricate a Substrate Integrated Waveguide (SIW) effect to effectively reduce the energy from the transmission line to the conductor surface. coupling. Although the metal-conducting column back-metal coplanar waveguide is widely used in microwave circuit applications, the manufacture of metal communication posts requires additional masks and processes. Therefore, the manufacturing cost thereof will also be improved. For details of the above structure, reference is made to the paper "〇n the use of vias in conductor-backed coplanar circuits" by Haydl in IEEE 2002 on Microwave Theory and Technique. In summary, the above various conventional transmission line structures have problems in that the cost increases and the process increases. Accordingly, there is a need to reduce the manufacturing process and process of the conventional transmission line structure in order to achieve an environmentally friendly trend of energy saving and carbon saving.

【發明内容】本發明提出-種傳輸線結構，用以抑制能量沒漏。傳輸，結構是由多個·單元實質串接(Cascade)而組成。週 ==线:線單元’以及包括分別位於信號線單元旁側的開路早70、短路單元或旁侧導體單元，其中週期單元 =布=且抗_eh impeda㈣約為傳輸線結構之系統阻机的0.6至1.4倍。 34792twf.doc/n 201212373 本發明提出-種傳輸線結構，用以抑制能量茂漏。傳輸，結構，由多個週期單元實質串接而組成。週期單元包括信號線單元，以及包括餘錢線單元關其中之一的開路單元或短路料，其巾週鮮元的布洛_抗不受限於需為傳輸線結構之系統阻抗之G 6至14倍的限制條件。出-種至少包括上述其中—㈣輸線結構的電子裝置，所述電子裝置可能為電子晶片、微波電路、 =訊裝置、電路板、筆記型電腦、手機、顯示裝置或天線總之’本發明是透過週期性地改變導體面的形狀，供傳輸線結構的料與短路條件，或者透過同時改或導，面的形狀，來提升傳輸線結構的慢波係數，二藉此抑制能量浪漏之功效。基於上述，本發明的傳輸線結構僅需要實質單層之介 ^板就可以達到抑魏_漏之功效，而林發明輸線結構可以減少使用金相通_使用。除此之外發明的傳輸線結構所佔用的導體面_、，際用 ^、1=^傳統的傳輸線結構，本發明的傳輸線結構具有衣le成本較低且製程較為簡化的優勢。舉實=本ίΓί上述特徵和優點能更明㈣懂，下文特舉實靶例’並配合所附圖式作詳細說明如下。【實施方式】本發明用以提供—種具有抑概量&漏之能力的傳 201212373 ν,Λ-χ^0506 34792twf.doc/n f線結構°相較於傳統的傳輸線結構，本發_傳輸線結冓具有製造成本較低且製程較為簡化的優勢。本發明所提供的傳輸線結構僅需要實質單層之介質板便可以實施。然而’本發明不限制於實施於單層介質板上，，要原因在於具有多層介質版的材料，實質上仍可等效為單層介質版。況且，本發明無須對介質板的介電係數與厚度做特別的限制。因此在某一些情況下，本發明所提瞻#的傳輸線結構可以使用多層介質板的設計，例如實施於，溫共燒多層喊(LTCQ製程、石増)晶圓、坤化鎵(GaAs) 晶圓、氮化鎵(GaN)晶圓、磷化銦(1111>)晶圓、矽鍺（siGe) 材料、氧化銘製程、軟板及其他類似半導體或印刷電路板 (PCB)製程的基板上。本發明所提供的傳輸線結構不需要在其信號線單元旁侧使用金屬聯通柱，便能夠有效地抑舰量$漏。然而，本發明並非排斥在傳輸線結構之旁側以外的其他區域使用金屬聯通柱。在實際的應用上，金屬聯通柱可能用來電氣 _ 地連接傳輸線結構乏基板上下層。請參照圖1八與圖把，圖1八與圖13是全通(八11卩挪）傳輸線結構示意圖。在圖1A中，全通傳輸線結構1〇包括信號線102與開路線101。開路線1〇1的電氣長度為0，且開路線101兩端浮接，呈現開路狀態。信號線1〇2的一端連接輸入信號端點，其另一端則連接輸出信號端點。透過開路線101所製造的開路條件，信號線102的轉換函數為全通轉換函數。在圖1Β中，全通傳輸線結構u包括信號 201212373 ϋ7Α-10〇5ϋ6 34792twf.doc/n 線Π2與短路線11卜短路線111的電氣長度為θ，且短路線111兩端接地，呈現短路狀態。透過短路線111所製造的短路條件，信號線112的轉換函數為全通轉換函數。以上概念已在Pozar於1998年的著作Microwave Engineering揭示’並且廣泛的使用在遽波器的設計中。然而，在幾乎所有的設計中’信號線的寬度都大致與開路或短路線的寬度相同，並且上述三條線的電氣長度都在約略等於或小於半個波長。更重要的是，濾波器的設計概念是希望得到高通(HighPass)、低通 (Low Pass)、帶通(Band Pass)、帶拒(Band Reject)或其組合的響應，而非在設計全通響應，因此在濾波器的設計並不會見到所謂的全通濾波器設計。本發明是採用上述具有全通響應的元件.作為週期單元，並將該週期單元作實質地串接(Cascade)後得到一個真有全通響應的傳輸線’用以降低能量從信號線洩漏到旁側導體面的問題。此種概念雖未在任何參考文獻中被揭露，但是類似的結構可以從]Via et al.於2005年在IEEE MTT-S International Microwave Symposium Digest 所發表的論文 ^Experimentally investigating slow-wave transmission lines and filters based on conductor-backed CPW periodic cells”發現。然而，根據Maetal.的描述，無論在旁側導體面製造週期性圓形槽洞(類似製造開路條件，如圖1A所示）或週期性地改變信號線與旁側導體面的形狀呈大致圓形，其改良結構的插入損耗(Insertion Loss)僅在介於5億到14.3億赫茲的頻率範圍區間内比原本習知的背覆導體共面波導來 201212373 u / λ- i uu506 34792twf.doc/n 好。但遺撼的是’ 5億到14.3億赫兹的這個頻率區間對大部分的微波產品來說都是遠遠不足的。舉例來說，手持行動通訊裝置必須包括9億與18億赫茲的頻段，藍芽是24 5 億赫茲，常用的IEEE 802.11尚包含50億到60億赫兹的頻#又。另外，Ma et al.的設計特意選擇較短的旁側導體面的寬度(大約為信號線寬度的兩到三倍)以降低能量測漏的鲁損耗’然而這個選擇並不適用於絕大多數的電子或微波產品設計。另一種設計’可參照Haydl在2002年6月於ieee Transactions on Microwave Theory and Technique 發表的論文 On the use of vias in conductor-backed coplanar circuits”。此種設計，利用到圖1B的概念，其僅製造短路條件於信號線旁側。雖然，Haydl的設計可以改善效能，然而，如先前所述，Haydl之設計的製造成本以及製程複雜度問題依舊無法解決。因此’非常需要有一種設計能夠鲁同時兼顧降低背覆導體共面波導的能量洩漏損耗問題與降低製造成本。 ' 本發明所提供的傳輸線結構是採用圖1A與圖1B的全通傳輸線結構10或11，透過週期性地改變傳輸線結構的仏號線與/或導體面的形狀，以得到信號線旁側的週期性短路條件或開路條件。本發明所提供的另一種傳輸線結構，是利用週期性地改變傳輸線結構的信號線與/或導體面的形狀去達到提升慢波係數。要說明的是，光靠上述條件是 201212373 34792twf.doc/n 無法必然降低背覆導體共面波導的能量洩漏損耗問題，其尚且必須仰賴以下的條件:上述週期單元的布洛赫阻抗大約為傳輸線結構之⑽阻抗0·6 i 14倍，且其較佳值可能為系統，抗。在一般的應用下，系統阻抗可能是50歐姆，而，期單7G的布洛赫阻抗可能為30至7〇歐姆。若系統阻抗疋100歐姆’而週期單元的布洛赫阻抗可能為60至140 I姆以下數個實施例都將依此類推適用此條件。另一要說^月的疋’在實際應用上，信號線與旁侧導體面的個數是隨設計需要而賴整的，目此有數種組合的可能性存在，使用者可以依圖1A與圖1B去做不同湖的組合與調整。在以下各個實施财’除非制說明，使用版材為SUMMARY OF THE INVENTION The present invention proposes a transmission line structure for suppressing energy leakage. Transmission, the structure is composed of multiple units of Cascade. Week == line: line unit 'and includes an open circuit 70, a short-circuit unit or a side conductor unit respectively located on the side of the signal line unit, wherein the period unit = cloth = and anti-eh impeda (four) is about the system resistance of the transmission line structure 0.6 to 1.4 times. 34792 twf.doc/n 201212373 The present invention proposes a transmission line structure for suppressing energy leakage. Transmission, structure, consisting of multiple periodic units in substantial concatenation. The cycle unit includes a signal line unit, and an open circuit unit or a short-circuit material including one of the remaining money line units, and the Bloor resistance of the fresh-keeping element is not limited to the G 6 to 14 of the system impedance required for the transmission line structure. Multiple restrictions. An electronic device including at least the above-mentioned (4) transmission line structure, which may be an electronic chip, a microwave circuit, a signal device, a circuit board, a notebook computer, a mobile phone, a display device, or an antenna. By periodically changing the shape of the conductor surface, for the material and short-circuit conditions of the transmission line structure, or by simultaneously changing or guiding the shape of the surface, the slow wave coefficient of the transmission line structure is improved, thereby suppressing the effect of energy leakage. Based on the above, the transmission line structure of the present invention only needs a substantially single layer of the board to achieve the effect of suppressing the Wei_leak, and the invention of the transmission line structure can reduce the use of the metal. In addition to the conventional transmission line structure occupied by the transmission line structure of the invention, the transmission line structure of the present invention has the advantages of lower cost and simplified process. The above features and advantages can be more clearly understood. (IV) Understand the following, and the following is a detailed description of the target example and the following description. [Embodiment] The present invention provides a transmission structure having a capability of suppressing the amount & leakage of 201212373 ν, Λ-χ^0506 34792 twf.doc/nf line structure compared with the conventional transmission line structure, the transmission line The knot has the advantages of lower manufacturing cost and simplified process. The transmission line structure provided by the present invention can be implemented only by a substantially single layer of dielectric board. However, the present invention is not limited to being implemented on a single-layer dielectric plate because the material having the multi-layered dielectric plate is substantially equivalent to a single-layer dielectric plate. Moreover, the present invention does not require any particular limitation on the dielectric constant and thickness of the dielectric plate. Therefore, in some cases, the transmission line structure of the present invention can be designed using a multilayer dielectric plate, for example, in a co-fired multi-layer shatter (LTCQ process, sarcophagus) wafer, a gallium arsenide (GaAs) crystal. Circular, gallium nitride (GaN) wafers, indium phosphide (1111) wafers, germanium (siGe) materials, oxidized processes, flexible boards, and other substrates such as semiconductor or printed circuit board (PCB) processes. The transmission line structure provided by the present invention does not need to use a metal communication post on the side of the signal line unit, so that the ship amount can be effectively suppressed. However, the present invention does not exclude the use of metal communication posts in other areas than the side of the transmission line structure. In practical applications, the metal communication post may be used to electrically connect the upper and lower layers of the transmission line structure. Please refer to FIG. 1 and FIG. 1 and FIG. 13 is a schematic diagram of the structure of the all-pass (eight 11 卩) transmission line. In Fig. 1A, the all-pass transmission line structure 1A includes a signal line 102 and an open path 101. The electrical length of the open route 1〇1 is 0, and the open route 101 is floated at both ends, showing an open state. One end of the signal line 1〇2 is connected to the end of the input signal, and the other end is connected to the end of the output signal. The switching function of the signal line 102 is an all-pass conversion function by the open condition manufactured by the opening route 101. In FIG. 1A, the all-pass transmission line structure u includes the signal 201212373 ϋ7Α-10〇5ϋ6 34792twf.doc/n line Π2 and the short-circuit line 11 and the short-circuit line 111 has an electrical length of θ, and the short-circuit line 111 is grounded at both ends, and is short-circuited. . The switching function of the signal line 112 is an all-pass conversion function by the short-circuit condition created by the short-circuit line 111. The above concept has been revealed in Pozar's 1998 book Microwave Engineering and is widely used in the design of choppers. However, in almost all designs, the width of the signal line is approximately the same as the width of the open or shorted line, and the electrical lengths of the above three lines are approximately equal to or less than half a wavelength. More importantly, the design concept of the filter is to get the response of HighPass, Low Pass, Band Pass, Band Reject or a combination thereof instead of designing all-pass. Responsive, so the so-called all-pass filter design is not seen in the design of the filter. The invention adopts the above-mentioned component with all-pass response as a periodic unit, and substantially cascading the periodic unit to obtain a true all-pass response transmission line 'to reduce energy leakage from the signal line to the side The problem of the conductor surface. Although this concept has not been disclosed in any of the references, a similar structure can be derived from the paper published by IEEE et al. in IEEE MTT-S International Microwave Symposium Digest in 2005^Experimentally investigating slow-wave transmission lines and filters Based on conductor-backed CPW periodic cells, however, according to Maetal., periodic circular grooves are created on the side conductor faces (similar to manufacturing open circuit conditions, as shown in Figure 1A) or periodically changing the signal. The shape of the line and the side conductor surface is substantially circular, and the insertion loss of the improved structure is only in the range of the frequency range of 500 million to 1.43 billion Hz, which is more common than the conventionally known backplane conductor. 201212373 u / λ- i uu506 34792twf.doc/n Good. But the testament is that the frequency range of '500 million to 1.43 billion Hz is far from enough for most microwave products. For example, handheld The mobile communication device must include the frequency band of 900 million and 1.8 billion Hz, the Bluetooth is 245 billion Hz, and the commonly used IEEE 802.11 still contains the frequency of 5 billion to 6 billion Hz. In addition, Ma et al.'s design deliberately chooses the width of the shorter side conductor surface (about two to three times the width of the signal line) to reduce the energy loss of the leak detection. However, this option is not suitable for the vast majority. Electronic or microwave product design. Another design can be found in "The paper on the use of vias in conductor-backed coplanar circuits" by Haydl in June 2002 on ieee Transactions on Microwave Theory and Technique. This design utilizes the concept of Figure 1B, which only creates a short circuit condition on the side of the signal line. Although Haydl's design can improve performance, as previously stated, the manufacturing cost and process complexity of Haydl's design remain unresolved. Therefore, it is highly desirable to have a design that simultaneously reduces the energy leakage loss of the backplane conductor coplanar waveguide and reduces manufacturing costs. The transmission line structure provided by the present invention adopts the all-pass transmission line structure 10 or 11 of FIGS. 1A and 1B, and periodically changes the shape of the symmetry line and/or the conductor surface of the transmission line structure to obtain the side of the signal line. Periodic short circuit condition or open circuit condition. Another transmission line structure provided by the present invention is to increase the slow wave coefficient by periodically changing the shape of the signal line and/or the conductor surface of the transmission line structure. It should be noted that the above condition is 201212373 34792twf.doc/n, which cannot necessarily reduce the energy leakage loss problem of the coplanar waveguide of the back conductor. It must rely on the following conditions: the Bloch impedance of the above periodic unit is approximately the transmission line. The (10) impedance of the structure is 0·6 i 14 times, and its preferred value may be system, anti-. In general applications, the system impedance may be 50 ohms, while the Bloch impedance of a single 7G may be 30 to 7 ohms. If the system impedance is 疋100 ohm' and the Bloch impedance of the periodic unit may be 60 to 140 I, the following embodiments will apply this condition. Another thing to say is that in the practical application, the number of signal lines and side conductor faces is dependent on the design requirements. There are several possibilities for combination. The user can follow Figure 1A. Figure 1B is a combination and adjustment of different lakes. In the following implementations, unless the instructions are stated, the use of the plate is

Duriod 5880 或 FR4。波導爾體共面構示意圖。在圖2A中，習知的背覆導體共縣而!〇傳輸線結構12至少包括—個介質基版12卜第一導體：122、第二導體面123與兩個線槽124、⑵其 :體面122與第二導體面123位於介質基版i2i的上下成r號：條線槽124與125位於第一導體面122，用以形 =:2二與兩個旁側導體面127、128，而第二導體面這可 201212373 u/a-u/u506 34792twf.doc/n 下方，引起額外的問題》因此，大致保持完整的第二導體面123為較佳的實施例，而其它的實施例除非特別說明亦依照此原則去做設計。另外，雖說此實施例僅呈現更動旁側導體面形狀以達到開路條件的功效，但在不影響實際抑制損耗效能的情況下，信號線單元也允許做些微的更動，而其它的實施例除非特別說明亦依照此原則去做設計。在圖2B中，傳輸線結構20位於背覆導體共面波導傳輸線結構的第一導體面2031，且傳輸線結構2〇由多個週期單元(Unit Cell)204實質串接所組成。在這個實施例中，旁側導體面202位於信號線201的兩旁側，且具有實質週期性排列呈大致凹字形的開路單元2〇21，用以提供開路條件。週期單元204的布洛赫阻抗大約為傳輸線結構2〇之系統阻抗的0.6〜1.4倍，且週期單元204為實質一維週期結才冓。 " 傳輸線結構20的部份203放大示意圖亦繪示於圖2B 中。傳輸線結構20可以由週期單元204實質週期性排列而 _ 組成，週期單元2〇4包括了信號線單元與位於旁側導體面的開路單元。傳輸線結構20位於背覆導體共面波導傳輸線結構的第一導體面2031，且第一導體面2031與第二導體面2033位於介質基板2〇32的上下兩側，其中第二導體面 2033大致保持完整，以形成第二導體面，而第一導體面具有多個週期性的大致上呈凸字形的槽洞2034,以形成k號線201與旁側導體面202。請參照圖2C與圖2D，圖2C是本發明另一實施例所 34792twf.doc/n 201212373. 提供的傳輸線結構示意圖，圖2〇是本發明另提供的傳輸線結構示意圖。在圖2C 路 I20中列於信號線201的兩旁側導體、、在圖2D的實施例中，開路單元2021 1TT4 僅排列於信號線2〇1的一個旁侧導體面2〇2,2^ = (Microstrip Line，簡稱為紙)旁側且 ^微帶線上兩種實施例，皆說明本發明的傳ς :::況。以 ^ 2021 . ^mtcDuriod 5880 or FR4. Schematic diagram of the common body of the waveguide. In FIG. 2A, a conventional back-conducting conductor has a total of at least one dielectric substrate 12, a first conductor: 122, a second conductor surface 123 and two wire grooves 124, and (2) a decent surface. 122 and the second conductor surface 123 are located on the upper and lower sides of the dielectric substrate i2i with r numbers: the strip grooves 124 and 125 are located on the first conductor surface 122 for the shape = 2 2 and the two side conductor faces 127, 128, and The second conductor face may be under the 201212373 u/au/u506 34792 twf.doc/n, causing additional problems. Therefore, the substantially intact second conductor face 123 is a preferred embodiment, while other embodiments are unless otherwise specified. Designed according to this principle. In addition, although this embodiment only exhibits the effect of changing the shape of the side conductor surface to achieve the open circuit condition, the signal line unit also allows slight changes without affecting the actual suppression loss performance, while other embodiments are not particularly The instructions are also designed according to this principle. In Fig. 2B, the transmission line structure 20 is located on the first conductor face 2031 of the back conductor coplanar waveguide transmission line structure, and the transmission line structure 2 is composed of a plurality of unit cells 204 substantially in series. In this embodiment, the side conductor faces 202 are located on both sides of the signal line 201, and have open circuit units 2〇21 which are substantially circumferentially arranged in a substantially concave shape for providing open circuit conditions. The Bloch impedance of the period unit 204 is approximately 0.6 to 1.4 times the impedance of the transmission line structure 2, and the period unit 204 is a substantially one-dimensional period. " An enlarged schematic view of portion 203 of transmission line structure 20 is also shown in Figure 2B. The transmission line structure 20 may be composed of a periodic unit 204 substantially periodically arranged, and the period unit 2〇4 includes a signal line unit and an open unit located on the side conductor surface. The transmission line structure 20 is located on the first conductor surface 2031 of the backplane conductor coplanar waveguide transmission line structure, and the first conductor surface 2031 and the second conductor surface 2033 are located on the upper and lower sides of the dielectric substrate 2〇32, wherein the second conductor surface 2033 is substantially maintained. Completely to form a second conductor face, the first conductor face having a plurality of periodic substantially convex-shaped slots 2034 to form a k-line 201 and a side conductor face 202. Referring to FIG. 2C and FIG. 2D, FIG. 2C is a schematic structural diagram of a transmission line provided by another embodiment of the present invention, 34792 twf.doc/n 201212373. FIG. 2 is a schematic structural diagram of a transmission line according to another embodiment of the present invention. In the embodiment of Fig. 2D, the open circuit unit 2021 1TT4 is arranged only on one side conductor surface 2〇2 of the signal line 2〇1, 2^ = in the embodiment of Fig. 2C. (Microstrip Line, abbreviated as paper) and two embodiments on the microstrip line, the description of the invention is described. To ^ 2021 . ^mtc

的這兩種結構的週期單元2G4由於本身就具備了開路條件’因此倾受料布洛_抗的_ 加=續回ΓΓΒ’圖沈的實施例雖然以一個信號線卻不限定於此，在兩旁側導體面202 =中間’亦有可能包括兩個以上的信號線。除此之外，請 tf2E至圖2Η’圖2Ε至圖2Η分別是本發明另一實施 =所提供的傳輸線結構示意圖。圖2Ε至圖2Η的每一個傳The two units of the periodic unit 2G4 have an open circuit condition by themselves. Therefore, the embodiment of the immersion material is not limited to this, although the signal line is not limited thereto. Both side conductor faces 202 = intermediate 'may also include more than two signal lines. In addition, tf2E to FIG. 2A' FIG. 2A to FIG. 2B are respectively schematic diagrams showing the structure of the transmission line provided by another embodiment of the present invention. Figure 2Ε to Figure 2Η

Ϊ線ί構依ΐ是由多個週期單元串接而成，且週期單元包 Ή:號線單元與位於信號線單元旁侧的開路單元，其中週期單元的布洛赫阻抗大約為傳輸線結構之系統阻抗的 :〜1.4倍。圖2Β與圖2Ε至圖2H，可以得知實質上凸字形，槽洞除了包括上述圖2Β的凸字形的槽洞2〇34外，還 ^包括如同圖2Ε與圖2F的蛋糕形狀之槽洞2〇91、〇92、圖2G的三角形狀之槽洞2〇93與圖2H的半圓形狀之槽酒2〇94。上述的這些槽洞2091〜2094，以巨觀的角來看，基本上皆為貫質上凸字形的槽洞。另外，由圖2B與 12 201212373 υ/Α-ιυυ506 34792twf.doc/n 圖2E至圖2H，可以得知，開路單元經實質串接後所形成的旁側導體面的每-點至信號線單元經實質串接後所形成的信號線的實質最短轉可能會有部分地不同。 m 菌是本發明另一實施例所提供的傳輸線結構示意圖。傳輸線結構30是由多個週期單元3〇4串接形成，因此傳輸線結構30會包括由多個信號線單元則經實質串接後形成的信號線301與由多個開路單元3〇21經實質串接後個旁側導體面3〇2。傳輸線結構3〇與圖2的傳輸 ^差異在於開路單^21與開路單元2021的形 2線結構30的部份3G3放大示意圖請示於圖组成，调^線結構3G可以由週期單元304週期性排列而旁側的開括線單錢11與信號線單元 ⑽m ^早疋3021。傳輸線結構30位於第一導體面週期單元3〇4、經實質串接後所組成，且第一導體伽，並第二導體面3〇33位於介質基板3032的上下兩而’/二—第二導體面3033大致保持完整，以形成第二導體套伽個實施例中，旁側導體面302位於信號線301的二開路單元3〇21除了具有實質週期性排列呈大致宝㈣=的導體3〇22之外，在第一導體面的實質上為凸門祕㈣3034内另有矩形的導體區塊3023，用以提供二個凹槽。換言之，第一導體面3031具有多個凹槽，且每 e盥=興t具有導體區塊，以形成每一個具有凹字形的導 ^ 區塊的開路單元3021。週期單元304的布洛赫阻几，力為傳輪線結構30之系統阻抗的〇 6〜14倍，且週 201212373 ν/Λ·ινν^ν〇 34792twf.doc/n 期單元304為實質一維週期結構。請參照圖3B至圖3E，圖3B至圖3E分 -實施例所提供的傳輸線結構示意圖。圖3B至圖3= -個傳輸線結構韻是由多個週期單元經士母且週期單元包括了信號線單元與位於 =的開，其中週期單元的布洛赫阻抗大約為傳之系統阻抗的G.6〜1.4倍^圖3A與圖3B至圖犯以得知實質上凸字形的槽洞除了包括上述圖从的= 狀之_ 圖與圖3C的蛋糕形狀之槽洞309卜3092、圖3D的三角形狀之槽洞3〇93 3E的+圓形狀之槽洞3〇94。上述的這些槽洞料 =觀的角來看，基本上皆為實質上凸字形的槽洞:卜4, f槽洞内的導體區塊也得隨著槽洞的形狀而改變，因此圖 =鱧=081'3。82，圖3〇的三角形狀之槽有= 内具有二絲狀的導體區塊侧槽洞綱内具㈣形狀輸區塊腿的丰圓械之圖==:==:A與圖4B分別是_與傳輸線之r ㈤長度的1知魏金屬共面波導 r H 對應頻率曲線圖。由圖4A與圖4B可以寸發明可以得到較高的無損耗茂漏的操作頻率。模擬㈣Λ中，曲線C41為傳統背覆導體共平面波導的 7, *線C42是由15個週期單元204作實質串接後所組成之傳财結構20賴赌果。由曲紅41 質〜串^ 14 201212373 v///\-iv；w506 34792twf.d〇c/n 可以得知，傳統背覆導體共平面波導可以操作的頻率最多僅在100億赫茲附近’而由15個週期單元2〇4作實質串接所組成之傳輸線結構2 0可以操作的頻率達到約4 2 〇債附近。〜灶The Ϊ line ΐ ΐ is composed of a plurality of periodic units connected in series, and the periodic unit includes: a line unit and an open unit located beside the signal line unit, wherein the Bloch impedance of the periodic unit is approximately the structure of the transmission line System impedance: ~1.4 times. 2A and FIG. 2A to FIG. 2H, a substantially convex shape can be known, and the groove includes a cavity of a cake shape like FIG. 2A and FIG. 2F in addition to the above-mentioned convex-shaped groove 2〇34 of FIG. 2〇91, 〇92, the triangular shaped groove 2〇93 of Fig. 2G and the semicircular shaped grooved wine 2〇94 of Fig. 2H. The above-mentioned grooves 2091 to 2094 are viewed at a giant angle, and are basically grooves having a peri-convex shape. In addition, as shown in FIG. 2B and FIG. 2B and 12 201212373 υ/Α-ιυυ506 34792 twf.doc/n FIG. 2E to FIG. 2H, it can be seen that each side of the side conductor surface formed by the open circuit unit after substantially serially connecting to the signal line unit The substantial shortest turn of the signal lines formed after substantial concatenation may be partially different. The m bacteria is a schematic diagram of a transmission line structure provided by another embodiment of the present invention. The transmission line structure 30 is formed by serially connecting a plurality of periodic units 3〇4. Therefore, the transmission line structure 30 includes a signal line 301 formed by substantially connecting a plurality of signal line units and substantially separated by a plurality of open units 3. The next side conductor surface 3〇2 is connected in series. The transmission line structure 3〇 differs from the transmission of FIG. 2 in that the open circuit unit 21 and the portion 3G3 of the 2-wire structure 30 of the open circuit unit 2021 are enlarged. FIG. 3 is a schematic diagram, and the adjustment line structure 3G can be periodically arranged by the period unit 304. On the side of the opening line, the single money 11 and the signal line unit (10) m ^ is earlier than 3021. The transmission line structure 30 is located on the first conductor surface periodic unit 3〇4, which is substantially serially connected, and the first conductor galvanic, and the second conductor surface 3〇33 is located on the upper and lower sides of the dielectric substrate 3032 and the second/second to the second The conductor surface 3033 is substantially intact to form a second conductor sleeve. In the embodiment, the two side open unit 3〇21 of the side conductor surface 302 located at the signal line 301 has a conductor 3 which is substantially periodically arranged to be substantially treasure (four)= In addition to the 22, a rectangular conductor block 3023 is formed in the substantially convex surface of the first conductor surface (30) 3034 to provide two grooves. In other words, the first conductor face 3031 has a plurality of grooves, and each of the conductor faces 3011 has a conductor block to form an open circuit unit 3021 each having a concave shaped guide block. The Bloch block of the periodic unit 304 has a force of 6 to 14 times the system impedance of the transmission line structure 30, and the week 201212373 ν/Λ·ινν^ν〇34792twf.doc/n period unit 304 is a substantial one-dimensional Periodic structure. Referring to FIG. 3B to FIG. 3E, FIG. 3B to FIG. 3E are schematic diagrams showing the structure of a transmission line provided by the embodiment. Figure 3B to Figure 3 = - The transmission line structure rhyme is composed of a plurality of periodic units through the mother and the periodic unit includes the signal line unit and the opening at =, wherein the Bloch impedance of the periodic unit is approximately the G of the transmitted system impedance Fig. 3A and Fig. 3B to Fig. 3B to Fig. 3B showing that the substantially convex shape of the groove includes the shape of the shape of the above figure and the groove of the cake shape of the Fig. 3C 309, 3092, Fig. 3D The triangular shape of the slot 3〇93 3E + the circular shape of the slot 3〇94. The above-mentioned slots are generally substantially convex-shaped slots in view of the angle of view: the conductor blocks in the trenches of the 4th and the f-holes also change with the shape of the slots, so鳢=081'3.82, the triangular-shaped groove of Fig. 3〇 has a figure of a round-shaped machine with a wire-shaped conductor block on the side of the channel. (4) Shaped block block ==:== :A and FIG. 4B are respectively corresponding frequency curves of the 知Wei metal coplanar waveguide r H of the length of r (five) of the transmission line. From Fig. 4A and Fig. 4B, it is possible to obtain a higher operating frequency of lossless leakage. In the simulation (4), the curve C41 is the conventional back-conductor coplanar waveguide, and the line C42 is composed of 15 periodic units 204. It can be known from the song red 41 quality ~ string ^ 14 201212373 v / / / \ - iv; w506 34792twf.d 〇 c / n, the traditional back-conductor coplanar waveguide can operate at frequencies up to only 10 billion Hz ' and The transmission line structure 20 composed of 15 periodic units 2〇4 as a substantial concatenation can operate at a frequency of approximately 4 2 〇 debt. ~ stove

在圖4B中，曲線C43為傳統背覆導體共平面波導的模擬結果，曲線C44是由15個週期單元3〇4作實質串接所組成之傳輸線結構30的模擬結果。由曲線C43〜C44可以得知，傳統背覆導體共平面波導可以操作的頻率最多僅在100億赫茲附近，而15個週期之週期單元3〇4作實質串接所組成之傳輸線結構30可以操作的頻率達到約425億赫兹附近。謂·翏照圖曰力艽復導體共面波導傳輸線結構之能直茂露示意圖。圖5是在信號 265億赫兹的情況下之模擬結果的示意圖。在本文中，能量浪漏的能量密度以顏色的亮度表示，換言之，越暗的區，表示$漏的能量越少，越亮的區域表示$漏的能量越二。由圖5可喔請，能量在賴導體面朗的問題相當嚴重。請參照圖6A與圖6B，圖6A是由圖沈之週期單兀204經實質串接後所形成之傳輸線結構之圖，圖6B是由圖2B之開路單元2〇21排列於曳In Fig. 4B, curve C43 is a simulation result of a conventional back-conductor coplanar waveguide, and curve C44 is a simulation result of a transmission line structure 30 composed of 15 periodic units 3〇4 as a substantial series. It can be known from the curves C43 to C44 that the conventional back-conductor coplanar waveguide can operate at a frequency of at most only about 10 billion Hz, and the transmission line structure 30 composed of a periodic unit of 3 cycles of 15 cycles can be operated. The frequency reaches around 42.5 billion Hz.翏翏图曰曰艽艽艽艽导体导体导体导体导体导体导体导体导体导体导体导体导体导体共。。 Figure 5 is a schematic diagram of the simulation results in the case of a signal of 26.5 billion Hz. In this paper, the energy density of energy leakage is expressed by the brightness of the color. In other words, the darker the area, the less energy is indicated by $leak, and the brighter area indicates the energy of $leak. As can be seen from Figure 5, the problem of energy in the surface of the conductor is quite serious. Referring to FIG. 6A and FIG. 6B, FIG. 6A is a diagram showing a structure of a transmission line formed by substantially serially connecting the period 兀 204 of the graph, and FIG. 6B is arranged by the open unit 2〇21 of FIG. 2B.

=體面所形f之傳輸綠結構之能量茂漏示意圖。圖6A= Schematic diagram of the energy leakage of the green structure of the f-shaped shape. Figure 6A

f6B是在信號之頻率為撕億赫兹的情況下之模擬结果。由圖6A與圖6B可以得知，由圖2B 排列於㈣狀科_導㈣切叙频線:冓的能. 20121237¾ 34792twf.doc/n 量洩漏會大幅下降。由圖2C之週期單元所組成的傳輸線結構’由於僅使用開路單元2021排列於信號線之左側的導體面，因此導致傳輸線結構的能量會洩漏於信號線右半面。請參照圖6C與圖6D，圖6C是由圖3A之週期單元 304經實質串接後所形成之傳輸線結構之能量洩漏示意圖，圖6D是由圖3A之開路單元3〇21排列於信號線之二旁侧導體面所形成之傳輸線結構之能量洩漏示意圖。圖6C 與圖6D是在信號之頻率為265億赫茲的情況下之模擬結果。由圖6C與圖6D可以得知，由圖3A之開路單元3〇2ι 排列於信號線之兩旁側的導體面上所得之傳輸線結構的能量浪漏會大幅下降。由圖3A之開路單元3〇21排列於信號線之左側所組成的傳輸線結構，由於僅使用開路單元^i 排列於信號線之左側的導體面，因此導致傳輸線結構的能量會洩漏於信號線右半面。參關7，圖7是習知背覆導體共面波導轉角傳輸線、，·。構之能量浪攀示意圖。圖7的傳輸線結構是一種直線的傳輸線結構，故稱為具轉角的傳 ^貫質多角形或其上述之組合。此外，由於，傳輸線結構之不連續情況最嚴重，因此將漏問題在傳統的背覆導體共面波導中。故在本選擇郷狀做从㈣顯本發Μ的功用。凊參照圖8Α〜8C，阁曰丄η 域乃的功用經實質串接所形虑#疋由圖2B之週期單元204 接所形成的轉角傳輸線結構之能量茂漏示意圖，】6 201212373 506 34792twf.d〇c/n 圖8B是由圖2B之開路單元2021排列於信號線之右侧導體面所形成之轉角傳輸線結構之能量洩漏示意圖，圖8c 是由圖2B之開路單元2021排列於信號線之左侧導體面所形成之轉角傳輸線結構之能量洩漏示意圖。圖8A〜8(:是在信號之頻率為250億赫茲的情況下之模擬結果。由圖8A〜8C可以得知，由圖2之週期單元204經實質串接所組成的轉角傳輸線結構的能量洩漏大幅下降，由圖2之開路單元2021排列於信號線之右侧導體面的轉角傳輸線結構的能量會洩漏於信號線左侧的導體面上，由圖2 之開路單元2021排列於信號線之左側導體面的轉角傳輸線結構的能量會洩漏於信號線右側的導體面上。請參照圖9A〜9C，圖9A是由圖3A之週期單元304 經實質串接所組成的轉角傳輸線結構之能量洩漏示意圖，圖9B是由圖3A之開路單元3021排列於信號線之左側導體面所形成之轉角傳輸線結構之能量洩漏示意圖，圖9C 是由圖3A之開路單元3021排列於信號線之右側導體面所形成之轉角傳輸線結構之能量泡漏示意圖。圖9A〜9C是在信號之頻率為250億赫茲的情況下之模擬結果。由圖9A〜9C可以得知，由圖3A之開路單元3021排列於信號線之兩旁側導體面的轉角傳輸線結構的能量洩漏大幅下降，由圖3A之開路單元3021排列於信號線之左側導體面的轉角傳輸線結構的能量會洩漏於信號線右側地面，由圖3A之開路單元3021排列於信號線之右側導體面的轉角傳輸線結構的能量會洩漏於信號線左側導體面。 17 201212373 v ; v6 34792twf.doc/n 由圖7至圖9C可以得知，雖然傳輸線結構在轉角處極度不對稱，導致在轉角位置的信號線旁側導體面上無法將開路單元做對稱地放置，但是模擬的結果依然顯示本發明能夠有效地抑制能量洩漏的問題。由以上結果可以支持’由週期單元“實質”串接的傳輸線結構依然能夠有效地抑制能量的損耗。同理可推得，在多個轉角的傳輸線結構中本發明將依然能夠適用。請參照圖10A〜10C，圖10A為利用習知背覆導體共面波導傳輸線結構饋入的共平面天線（Coplanar Patch Antenna)之能量洩漏示意圖。以上設計可參考Li et al於 2000 年 Asia-Pacific Microwave Conference 所發表的論文 Simulation and experimental study on coplanar patch and array antennas”。此實施例是設計在5 5 ghz並且使用便宜的FR4 基版’以映證本發明的設計概念能夠在不同版材上達到類似抑制能量損耗的效果。圖10B與圖i〇c分別是由圖2B 與圖3A之傳輸線結構應用於共平面天線之能量洩漏示意圖。由圖10B與圖10C可以得知，傳輸線結構20與30可以作為共平面天線的信號傳輸線，與圖1〇A傳統的背覆導體共面波導饋入的天線相比，可發現本發明的結構能大幅降低洩漏到側導體面的能量，除了可以降低天線交叉極化的問題之外’對天線輻射效率的增進也會有幫助。此實施例日在映證使用本發明傳輸線饋入天線的效能，而依此概念，本發明依然得適用各種不同形式的天線。圖11A是本發明另一實施例所提供的傳輪線結構示 18 201212373 wn-lw506 34792twf_d〇c/n 意圖。傳輸線結構5〇的部份5〇3放大示意圖亦緣示於圖 11A中。傳輸線結構50可以由週期單元5〇4經實質串接後所組成，週期單元504包括了信號線單元5〇11與位於旁側之第一導體面與第二導體面所形成的短路單元5〇21，且第導體面5031與第二導體面5〇33位於介質基板5〇32的上下兩側。傳輸線結構5〇同時使用第一導體面5〇31與第二導體面5033 ’由週期單元504實質串接所組成。在這個實 Φ 施例中，旁側導體面5〇2位於信號線5〇1的旁側，具有實質週期性排列且大致呈凹字形的槽洞5〇24,第二導體面 5033位於信號線501的下方，具有實質[形的槽洞5〇331。本發明利用上下兩導體面上的槽洞所圍成的導體區塊達到電容，再以第二導體面5033之兩個L形的槽洞50331的細導體區塊5051形成電感，以形成電感電容！^^接地之實質週期性排列的短路單元5021，並藉此提供短路條件。因此，電谷得以用各種不同的形狀組成，而電感亦可藉由改變上述細導體區塊的大小或粗細獲得。週期單元504的布 • 洛赫阻抗大約為傳輸線結構50之系統阻抗的〇._6〜1.4 倍，且週期單元504為實質一維週期結構。需要說明的是，上述的實施例雖然以一個信號線501為例，但本發明卻不限疋於此’在兩旁側導體面502的中間，亦有可能包括兩個以上的信號線。另外，雖說此實施例僅呈現更動第一與第二導體面形狀以達到短路條件的功效，但在不影響實際抑制損耗效能的情況下，信號線單元也允許做些微的更動’而其它的實施例除非特別說明亦依照此原則去做設計。 201212373 ---------5 34792twf.doc/n 請參照圖11B至圖11E，圖11B至圖i1E分別是本發明另一實施例所提供的傳輸線結構示意圖。圖11]3至圖 11E的傳輸線結構同樣是由具有信號單元與兩個短路單元的週期單元所串接而成，且其週期單元的布洛赫阻抗也約為系統阻抗的0.6至1.4倍。圖11B與圖ha不同處在於，圖11B的第二導體面5053上的槽洞並非為L形的槽洞，而是閃電形的槽洞50531 ’同樣地，第二導體面5033的兩個閃電形的槽洞50531之間的細導體區塊5〇532會形成一個電感。圖11C與圖11B不同處在於，圖iic的第一導體面5051上的槽洞並非為凹字形的槽洞，而是c字形的槽洞50512。圖11D與圖11A不同處在於，圖11D的第二導體面5063上的槽洞並非為L形的槽洞，而是蜿蜒線形的槽洞50631 ’同樣地，第二導體面5〇63的兩個蜿蜒線形的槽洞50631之間的細導體區塊5〇632會形成一個電感。圖 11E與圖11A不同處在於，圖11E的第二導體面5〇73上的槽洞並非為L形的槽洞，而是直線形的槽洞5〇731，使細導體區塊與電容合併’亦能得到類似的抑制能量茂漏的效果。由圖11A至圖he，可以得知，短路單元所形成的旁侧導體面的每-點至信號線單元所形成的信號線的實質最短距離可能會有部分地不同。立圖11F是圖11A至圖11E之傳輸線結構的等效電路示意圖。於圖11A至圖11E的任一實施例中，由第一導體面 2第二導體面之槽洞所大致圍成的重疊導體區域會提供電容C，而由第一導體面或第二導體面之槽洞所規劃出的細 20 201212373 w//\-iW506 34792twf.doc/n 導體區塊可以提供電感L。因此，可以合成為串聯的電感電容LC元件取代在旁側導體面製造金屬聯通柱(其用以提供串電感）的效果。圖11A至圖11E的任一實施例所形成傳輸線結構可以等效為圖11F的傳輸線結構1〇5，傳輸線結構105包括信號線1〇52與具有串聯電感電容lc接地的短路線1051。請參照圖11G’圖11G是本發a月另一實施例所提供的鲁傳輸線結構示意圖。圖11G的傳输線結構同樣是由具有信號單元與兩個短路單元的週期單元實質串接而成，且其週期單元的布洛赫阻抗也約為系統阻抗的〇.6至1.4倍。圖 11G與圖ΠΑ不同處在於，第二導體面5〇83大致保持完整’且採用圖11B的第二導體面5〇53作為第一導體面 5081 ’藉由上述的結構’圖11G的短路單元為並聯電感電谷LC接地的短路單元。請參照圖11H，圖11H是圖iig 之傳輸線結構的等效電路示意圖。圖11G僅使用第一導體面利用其槽洞所圍成的區域製造電感與電容的效果，形成鲁並聯LC電路，同樣可以取代在側旁導體面製造金屬聯通柱的效果。圖11G的實施例所形成傳輸線結構可以等效為圖11H的傳輸線結構106,傳輸線結構106包括信號線1062 與具有並聯電感電容LC接地的短路線1061。圖12A是本發明另一實施例所提供的傳輸線結構示意圖。傳輸線結構60形成於第一導體面6031，傳輸線結構60由週期單元604經實質串接後所組成。傳輸線結構 60的主要特徵在於週期性地改變第一導體面6031之信號 201212373 v w^vO 34792twf.doc/n 線601以及旁側導體單元6021的形狀以提升慢波係數 (Slow Wave Factor)。除此之外，此處將原來兩條平行的槽洞用實質蛇形的槽洞6024取代，以形成旁侧導體面6〇2。傳輸線結構60的部份603放大示意圖亦繪示於圖12A中。傳輸線結構60可以由週期單元604週期性排列而組成，週期單元604具有信號線單元6011與旁側導體單元6〇21。第一導體面601的實質蛇形的槽洞6024會同時改變信號線 601與兩旁側導體面602的形狀，以提升慢波係數。圖12a 的旁側皆地面602並非形成短路信號線與開路信號線，但若設計週期單元604的布洛赫阻抗約為系統阻抗的〇 6至 1.4倍’則可以達到大量提升慢波係數的效果，而同樣形成一個具有較大無能量洩漏頻寬的傳輸線結構。請接著參照圖12B至圖12E，圖12B至圖12E分別是本發明另一實施例所提供的傳輸線結構示意圖。圖12B至圖12E的傳輸線結構同樣是由具有信號線單元與旁側導體單元的週期單元所實質串接而成，且其週期單元的布洛赫阻抗也·約為系統阻抗的0.6至1.4倍。由圖12A至圖12E，可以得知實質蛇形的槽洞除了包括上述圖12A的蛇形槽洞 6024外，還可能包括如同圖12B至圖12E的槽洞6091〜 6094。上述的這些槽洞6〇91〜6094,以巨觀的角來看，基本上皆為實質蛇形的槽洞。另外，由圖12A至圖12E，可以得知’旁側導體單元所形成的旁侧導體面的每一點至信號線單元所形成的信號線的實質最短距離可能會有部分地不同。 22 J506 34792twf.doc/n 201212373 請參照圖13A與圖13B，圖m與圖i3B 11A與圖12A之傳輪線結構 =圖在圖：，曲線C71為傳統背_共=:= 結果，曲線C72是15個调如留-<Λ>1 、的模擬構50的模擬結果。由曲線C71 =所組成之傳輸線結丹个田曲線C7卜C72可以得知，傳轉呰結構50可雜作輪線 j 13B中，曲線⑺為傳統背覆導體共平面波導的模擬w果’而曲線C76是15個週期單元6〇4所組成之輸線結構60的模擬結果。由曲線C75、C76可以得知，統背覆導體共平面波導可以操作的頻率最多僅在ι⑻億赫茲附近’而由15個週期單元6〇4經實質串接後所組成之傳輸線結構60可以操作的頻率達到約36〇億赫茲附近。明參照圖14A與圖14B，圖14A是由圖ha之週期，元504排列於信號線之兩旁側所形成之傳輸線結構之能量洩漏示意圖，圖14B是由圖11A之缉路單元5〇21排列於仏號線之一旁侧所形成之傳輸線結構之能量洩漏示意圖。圖13A與圖14B是在信號之頻率為265億赫茲的情況下之模擬結果。由圖14A與圖14B可以得知，由圖11A 之短路單元5021排列於信號線之兩旁側的導體面上所得之傳輸線結構的能量洩漏會大幅下降，由圖11A之短路單 7G 5021排列於信號線之左側所組成的傳輸線結構，由於僅使用短路單元5021排列於信號線之左側的導體面，因此導 23 201212373 ν^Λ-ινν^νο 34792twf.doc/n 致傳輸線結構的能量會洩漏於信號線右半面。凊參照圖15 ,圖15是由圖12Α之週期單元6〇4實質 ”串接所形成之傳輸線結構之能量韻示意圖。圖15是在信號之頻率為2仍億赫兹的情況下之模擬結果。由圖15可以得知，由圖12Α之週期單元6〇4排列於信號線之兩旁側的傳輸線結構的能量洩漏大幅下降。請參照圖偷〜H圖1从是由圖11Α之週期單元 504經實質串接所形成的轉角傳輸線結構之能量浪漏示意圖，圖16Β是由圖11Α之短路單元篇排列於信號線之左側導，面所形成之轉角傳輸線結構之能量茂漏示意圖，圖16C是由圖UA之短路單元篇排列於信號線之右側導體面所形成之轉角傳輸線結構之能量浪漏示意圖。圖 16Α 16C疋在彳5號之頻率為250億赫兹的情況下之模擬結果。、由圖16Α〜16C可以得知，由圖πΑ之週期單元5〇4 經實質串接所組成的轉角傳輸線結構的能量洩漏大幅下降’由圖11Α之短路單元5021排列於信號線之左側導體面的轉角傳輸線結構的能量會洩漏於信號線右側的導體面上，由圖11Α之短路單元5021排列於信號線之右側導體面的轉角傳輸線結構的能量會洩漏於信號線左側的導體面上0 請參照圖17,圖17是由圖12Α之週期單元604經實質串接所形成的轉角傳輸線結構之能量洩漏示意圖。圖17 是在信號之頻率為260億赫茲的情況下之模擬結果。由圖 24f6B is the simulation result in the case where the frequency of the signal is tear billion Hz. It can be seen from Fig. 6A and Fig. 6B that the leakage of the quantity is significantly reduced by the energy of the 四频四四四四四四四四 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 2012 Since the transmission line structure constituting the periodic unit of Fig. 2C is arranged only on the conductor surface on the left side of the signal line using the open circuit unit 2021, the energy of the transmission line structure leaks to the right half of the signal line. Please refer to FIG. 6C and FIG. 6D. FIG. 6C is a schematic diagram of energy leakage of a transmission line structure formed by substantially serially connecting the periodic unit 304 of FIG. 3A, and FIG. 6D is arranged by the open circuit unit 3〇21 of FIG. 3A on the signal line. Schematic diagram of the energy leakage of the transmission line structure formed by the two side conductor faces. Figures 6C and 6D show the simulation results with a signal frequency of 26.5 billion Hz. As can be seen from Fig. 6C and Fig. 6D, the energy leakage of the transmission line structure obtained by arranging the open cells 3 〇 2 i of Fig. 3A on the conductor sides on both sides of the signal line is drastically lowered. The transmission line structure consisting of the open cells 3〇21 of FIG. 3A arranged on the left side of the signal line, because only the open circuit unit ^i is arranged on the conductor surface on the left side of the signal line, causes the energy of the transmission line structure to leak to the right of the signal line. Half face. Reference 7, Figure 7 is a conventional back-conductor coplanar waveguide corner transmission line, . The structure of the energy wave climbing diagram. The transmission line structure of Fig. 7 is a linear transmission line structure, so it is called a transmissive polygon with a corner or a combination thereof. In addition, since the discontinuity of the transmission line structure is the most serious, the leakage problem is in the conventional back-conductor coplanar waveguide. Therefore, in this choice, the function of the (4) display is used. Referring to Figures 8A to 8C, the function of the 曰丄 η domain is substantially concatenated. The energy leakage diagram of the corner transmission line structure formed by the periodic unit 204 of Fig. 2B is ???6 201212373 506 34792twf. D〇c/n FIG. 8B is a schematic diagram showing the energy leakage of the structure of the corner transmission line formed by the open circuit unit 2021 of FIG. 2B arranged on the right conductor surface of the signal line, and FIG. 8c is arranged by the open circuit unit 2021 of FIG. 2B on the signal line. Schematic diagram of the energy leakage of the corner transmission line structure formed by the left conductor surface. 8A to 8(: is a simulation result in the case where the frequency of the signal is 25 billion Hz. It can be seen from Figs. 8A to 8C that the energy of the corner transmission line structure composed of the periodic unit 204 of Fig. 2 is substantially serially connected. The leakage is greatly reduced. The energy of the corner transmission line structure arranged by the open circuit unit 2021 of FIG. 2 on the right conductor surface of the signal line leaks on the conductor surface on the left side of the signal line, and is arranged in the signal line by the open circuit unit 2021 of FIG. The energy of the corner transmission line structure of the left conductor surface leaks on the conductor surface on the right side of the signal line. Referring to Figures 9A to 9C, Figure 9A is an energy leakage of the corner transmission line structure composed of the substantially serial connection of the period unit 304 of Figure 3A. FIG. 9B is a schematic diagram showing the energy leakage of the corner transmission line structure formed by the open circuit unit 3021 of FIG. 3A arranged on the left conductor surface of the signal line, and FIG. 9C is arranged by the open circuit unit 3021 of FIG. 3A on the right conductor surface of the signal line. Schematic diagram of energy bubble leakage of the formed corner transmission line structure. Figures 9A to 9C are simulation results in the case where the frequency of the signal is 25 billion Hz. It can be known from Figs. 9A to 9C that The energy leakage of the corner transmission line structure arranged on the side conductor surfaces of the signal lines by the open circuit unit 3021 of FIG. 3A is greatly reduced, and the energy of the corner transmission line structure arranged by the open circuit unit 3021 of FIG. 3A on the left conductor surface of the signal line is leaked. On the right side of the signal line, the energy of the corner transmission line structure arranged by the open circuit unit 3021 of FIG. 3A on the right conductor surface of the signal line leaks to the left conductor surface of the signal line. 17 201212373 v ; v6 34792twf.doc/n Figure 7 to Figure 7 9C can be seen that although the transmission line structure is extremely asymmetrical at the corners, the open circuit unit cannot be placed symmetrically on the side conductor surface of the signal line at the corner position, but the simulation results still show that the present invention can effectively suppress energy leakage. The problem can be supported by the above results. The transmission line structure which is connected by the periodic unit "substantially" can still effectively suppress the loss of energy. Similarly, the present invention can still be applied to the transmission line structure of a plurality of corners. 10A to 10C, FIG. 10A is a feed structure using a conventional back-conductor coplanar waveguide transmission line structure. Schematic diagram of the energy leakage of the Coplanar Patch Antenna. The above design can be found in the paper "Impression and experimental study on coplanar patch and array antennas" published by Li et al at the Asia-Pacific Microwave Conference 2000. This embodiment is a design At 5 5 ghz and using the cheap FR4 base plate 'to demonstrate that the design concept of the invention can achieve similar effects on suppressing energy loss on different plates. 10B and i〇c are schematic diagrams of energy leakage applied to the coplanar antenna by the transmission line structure of Figs. 2B and 3A, respectively. As can be seen from FIG. 10B and FIG. 10C, the transmission line structures 20 and 30 can be used as signal transmission lines of the coplanar antenna, and the structure of the present invention can be found as compared with the antenna of the conventional back-conductor coplanar waveguide of FIG. The ability to significantly reduce the energy leaking to the side conductor surface, in addition to reducing the problem of cross polarization of the antenna, can also help to improve the radiation efficiency of the antenna. This embodiment exemplifies the performance of feeding the antenna using the transmission line of the present invention, and according to this concept, the present invention still has to be applied to various forms of antennas. FIG. 11A is a schematic diagram of a transmission line structure according to another embodiment of the present invention. 18 201212373 wn-lw506 34792twf_d〇c/n. An enlarged view of the portion 5〇3 of the transmission line structure 5〇 is also shown in Fig. 11A. The transmission line structure 50 may be composed of a periodic unit 5〇4 substantially after being serially connected. The period unit 504 includes a signal line unit 5〇11 and a short-circuit unit 5 formed on the side of the first conductor surface and the second conductor surface. 21, and the first conductor surface 5031 and the second conductor surface 5〇33 are located on the upper and lower sides of the dielectric substrate 5〇32. The transmission line structure 5 is composed of a first conductor surface 5?31 and a second conductor surface 5033' which are substantially serially connected by the period unit 504. In this embodiment, the side conductor surface 5〇2 is located on the side of the signal line 5〇1, and has substantially periodically arranged and substantially concave-shaped slots 5〇24, and the second conductor surface 5033 is located at the signal line. Below the 501, there is a substantial [shaped groove 5 〇 331. The invention utilizes a conductor block surrounded by a cavity on the upper and lower conductor faces to reach a capacitance, and then forms an inductance by a thin conductor block 5051 of two L-shaped slots 50331 of the second conductor face 5033 to form an inductor and a capacitor. ! ^^ The grounded short-circuit unit 5021 is periodically arranged and thereby provides a short-circuit condition. Therefore, the electric valley can be formed in various shapes, and the inductance can also be obtained by changing the size or thickness of the above-mentioned fine conductor block. The Bucher's impedance of the periodic unit 504 is approximately 〇6_1.4 times the system impedance of the transmission line structure 50, and the periodic unit 504 is a substantially one-dimensional periodic structure. It should be noted that although the above embodiment has one signal line 501 as an example, the present invention is not limited thereto. In the middle of the side-side conductor faces 502, it is also possible to include two or more signal lines. In addition, although this embodiment only exhibits the effect of changing the shape of the first and second conductor faces to achieve the short-circuit condition, the signal line unit allows slight adjustments without affecting the actual suppression loss performance, and other implementations For example, design should be done according to this principle unless otherwise stated. 201212373 ---------5 34792 twf.doc/n Referring to FIG. 11B to FIG. 11E, FIG. 11B to FIG. 1E are respectively schematic diagrams showing the structure of a transmission line provided by another embodiment of the present invention. The transmission line structure of Fig. 11] 3 to Fig. 11E is also formed by serially connecting a periodic unit having a signal unit and two short-circuit units, and the Bloch impedance of the periodic unit is also about 0.6 to 1.4 times the system impedance. 11B is different from the diagram ha in that the slot on the second conductor surface 5053 of FIG. 11B is not an L-shaped slot, but a lightning-shaped slot 50531'. Similarly, two lightnings of the second conductor surface 5033 The thin conductor blocks 5 〇 532 between the shaped holes 50531 form an inductance. 11C is different from FIG. 11B in that the groove on the first conductor surface 5051 of the diagram iic is not a concave groove but a c-shaped groove 50512. 11D is different from FIG. 11A in that the slot on the second conductor surface 5063 of FIG. 11D is not an L-shaped slot but a meandering slot 50631'. Similarly, the second conductor surface 5〇63 The thin conductor block 5 〇 632 between the two turns of the linear groove 50631 forms an inductance. 11E is different from FIG. 11A in that the groove on the second conductor surface 5〇73 of FIG. 11E is not an L-shaped groove, but a linear groove 5〇731, which merges the thin conductor block with the capacitor. 'A similar effect of suppressing energy leakage can also be obtained. From Fig. 11A to Fig., it can be seen that the substantial shortest distance of the signal line formed by the short-side unit from the side of the side conductor surface to the signal line unit may be partially different. The vertical view 11F is an equivalent circuit schematic of the transmission line structure of Figs. 11A to 11E. In any of the embodiments of FIGS. 11A-11E, the overlapping conductor regions substantially surrounded by the slots of the second conductor face of the first conductor face 2 provide a capacitance C from the first conductor face or the second conductor face. The thin 20 201212373 w//\-iW506 34792twf.doc/n conductor block can provide the inductance L. Therefore, it is possible to synthesize a series-connected inductor-capacitor LC element instead of fabricating a metal interconnect post on the side conductor surface for providing a series inductance. The transmission line structure formed by any of the embodiments of Figs. 11A to 11E can be equivalent to the transmission line structure 1〇5 of Fig. 11F, and the transmission line structure 105 includes the signal line 1〇52 and the short-circuit line 1051 having the series inductance capacitor lc grounded. Referring to FIG. 11G', FIG. 11G is a schematic structural diagram of a Lu transmission line provided by another embodiment of the present invention. The transmission line structure of Fig. 11G is also formed by substantially serially connecting the period unit having the signal unit and the two short-circuit units, and the Bloch impedance of the period unit is also about 66 to 1.4 times the system impedance. 11G differs from FIG. 11 in that the second conductor surface 5〇83 is substantially intact and the second conductor surface 5〇53 of FIG. 11B is used as the first conductor surface 5081′ by the above-described structure “short-circuit unit of FIG. 11G”. A short-circuit unit that is grounded to the shunt inductor valley G. Please refer to FIG. 11H. FIG. 11H is an equivalent circuit diagram of the transmission line structure of FIG. Fig. 11G uses only the region where the first conductor face is surrounded by the cavity to create the inductance and capacitance effect, and forms a Lu-parallel LC circuit, which can also replace the effect of manufacturing the metal-connected column on the side-side conductor surface. The transmission line structure formed by the embodiment of Fig. 11G can be equivalent to the transmission line structure 106 of Fig. 11H. The transmission line structure 106 includes a signal line 1062 and a shorting line 1061 having a shunt inductor LC connected to ground. Figure 12A is a block diagram showing the structure of a transmission line according to another embodiment of the present invention. The transmission line structure 60 is formed on the first conductor face 6031, and the transmission line structure 60 is formed by the periodic unit 604 substantially in series. The main feature of the transmission line structure 60 is to periodically change the shape of the signal of the first conductor face 6031 201212373 v w^vO 34792twf.doc/n line 601 and the side conductor unit 6021 to increase the slow wave factor. In addition to this, the original two parallel slots are replaced here with substantially serpentine slots 6024 to form the side conductor faces 6〇2. An enlarged schematic view of portion 603 of transmission line structure 60 is also shown in FIG. 12A. The transmission line structure 60 may be composed of periodic units 604 which are periodically arranged, and the period unit 604 has a signal line unit 6011 and a side conductor unit 6〇21. The substantially serpentine cavity 6024 of the first conductor face 601 simultaneously changes the shape of the signal line 601 and the two side conductor faces 602 to increase the slow wave coefficient. The ground side 602 of FIG. 12a does not form a short-circuit signal line and an open-circuit signal line, but if the Bloch impedance of the design period unit 604 is about 至6 to 1.4 times of the system impedance, a large amount of effect of increasing the slow-wave coefficient can be achieved. And also form a transmission line structure with a large energy-free leakage bandwidth. Referring to FIG. 12B to FIG. 12E, FIG. 12B to FIG. 12E are respectively schematic diagrams showing the structure of a transmission line according to another embodiment of the present invention. The transmission line structure of FIGS. 12B to 12E is also substantially formed by a periodic unit having a signal line unit and a side conductor unit, and the Bloch impedance of the periodic unit is also about 0.6 to 1.4 times the system impedance. . From Fig. 12A to Fig. 12E, it can be seen that the substantially serpentine groove may include the slots 6091 to 6094 as in Figs. 12B to 12E in addition to the above-described serpentine groove 6024 of Fig. 12A. The above-mentioned slots 6〇91~6094 are substantially serpentine slots in terms of giant angles. Further, from Figs. 12A to 12E, it can be understood that the substantial shortest distance of the signal line formed by each point of the side conductor surface formed by the side conductor unit to the signal line unit may be partially different. 22 J506 34792twf.doc/n 201212373 Please refer to FIG. 13A and FIG. 13B, FIG. m and FIG. i3B 11A and FIG. 12A are the structure of the transmission line=Fig.: the curve C71 is the traditional back_common =:= result, curve C72 It is the simulation result of the simulation structure 50 of 15 adjustments such as stay-<Λ>1. It can be known from the transmission line formed by the curve C71 = the knot curve C7 and C72 that the transfer structure 50 can be mixed into the wheel line j 13B, and the curve (7) is the simulation of the conventional back-conductor coplanar waveguide. Curve C76 is a simulation result of the transmission line structure 60 composed of 15 period units 6〇4. It can be seen from curves C75 and C76 that the transmission line structure 60 can be operated by the transmission line structure of the back-conductor coplanar waveguide which can be operated at a frequency of at most only ι (8) megahertz and by 15 periodic units 6 〇 4 after substantial concatenation. The frequency reaches around 3.36 billion Hz. 14A and FIG. 14B, FIG. 14A is a diagram showing the energy leakage of the transmission line structure formed by the side of the signal line 504 arranged on both sides of the signal line, and FIG. 14B is arranged by the routing unit 5〇21 of FIG. 11A. Schematic diagram of the energy leakage of the transmission line structure formed on the side of one of the lines. 13A and 14B are simulation results in the case where the frequency of the signal is 26.5 billion Hz. As can be seen from FIG. 14A and FIG. 14B, the energy leakage of the transmission line structure obtained by arranging the short-circuiting unit 5021 of FIG. 11A on the conductor faces on both sides of the signal line is greatly reduced, and the short-circuited single 7G 5021 of FIG. 11A is arranged in the signal. The transmission line structure composed of the left side of the line is arranged on the conductor surface on the left side of the signal line by using only the short-circuit unit 5021. Therefore, the energy of the transmission line structure leaks from the signal of the conductor 23 201212373 ν^Λ-ινν^νο 34792twf.doc/n The right half of the line. Referring to Fig. 15, Fig. 15 is a schematic diagram showing the energy distribution of the transmission line structure formed by the substantial "series" of the periodic unit 6〇4 of Fig. 12. Fig. 15 is a simulation result in the case where the frequency of the signal is 2 megahertz. As can be seen from Fig. 15, the energy leakage of the transmission line structure which is arranged on both sides of the signal line by the period unit 6〇4 of Fig. 12 is greatly reduced. Referring to the figure, the figure 1 is from the period unit 504 of Fig. 11 FIG. 16 is a schematic diagram of the energy leakage of the corner transmission line structure formed by the short-circuit unit of FIG. 11 arranged on the left side of the signal line, and FIG. 16C is a schematic diagram of the energy leakage of the corner transmission line structure formed by the short-circuit unit of FIG. The energy leakage diagram of the structure of the corner transmission line formed by the short-circuit unit of Figure UA arranged on the right conductor surface of the signal line is shown in Fig. 16Α16C疋 in the case of the frequency of 彳5 of 25 billion Hz. 16Α~16C can be seen that the energy leakage of the corner transmission line structure consisting of the substantially continuous connection of the periodic unit 5〇4 of the figure πΑ is greatly reduced by the short-circuit unit 5021 of FIG. The energy of the corner transmission line structure of the left conductor surface of the line leaks on the conductor surface on the right side of the signal line, and the energy of the corner transmission line structure which is arranged on the right conductor surface of the signal line by the short-circuit unit 5021 of FIG. 11 leaks to the left side of the signal line. On the conductor surface 0, please refer to Fig. 17, which is a schematic diagram of the energy leakage of the corner transmission line structure formed by the substantially serial connection of the period unit 604 of Fig. 12. Fig. 17 is a simulation in the case where the signal frequency is 26 billion Hz. Results. Figure 24

201212373 \r I Λ ^ ± W 506 34792twf.doc/n 17可以得知，由圖17之週期單元6〇4經實質串接所組成的轉角傳輸線結構的能量、漏大幅下降。201212373 \r I Λ ^ ± W 506 34792twf.doc/n 17 It can be seen that the energy and leakage of the corner transmission line structure composed of the periodic units 6〇4 of Fig. 17 substantially reduced in series are greatly reduced.

請參照圖18A與圖18B，圖18A與圖18B分別是由圖11A與圖12A之傳輸線結構應用於共平面天線之能量洩漏示意圖。由圖18A與圖18B可以得知，傳輸線結構5〇與60可以作為共平面天線的信號傳輸線，而且其能量大幅下降，與圖1GA傳統的背覆導體共錢導饋人的天線相比，可發現本發明的結構能大幅降低洩漏到側導體面的能量，以便降低天線交叉極化的問題。此實施例旨在映證使用本發明傳輸線饋人天制贱，缝此概念，本發明依然得適用各種不同形式的天線。請參照圖19A〜19D’ ® 19A〜19D是本發明一實施例於第-導體面所.提供的其他用⑽成傳齡結構之週期早元的示意圖。本發明所提供的傳輸線結 ' 非限定為圖…、卿的週期單元詞：:〜：Referring to Figures 18A and 18B, Figures 18A and 18B are schematic diagrams of energy leakage applied to the coplanar antenna by the transmission line structure of Figures 11A and 12A, respectively. It can be seen from FIG. 18A and FIG. 18B that the transmission line structures 5〇 and 60 can be used as signal transmission lines of the coplanar antenna, and the energy thereof is greatly reduced, compared with the antenna of the conventional back conductor of FIG. 1GA. It has been found that the structure of the present invention can greatly reduce the energy leaking to the side conductor faces in order to reduce the problem of cross polarization of the antenna. This embodiment is intended to demonstrate the use of the transmission line of the present invention to feed the shackles, and the present invention is still applicable to a variety of different forms of antennas. 19A to 19D' ® 19A to 19D are schematic diagrams of other periods (10) of the first conductor of the present invention which are provided by the first conductor surface. The transmission line junction provided by the present invention is not limited to the figure..., the periodic unit word of the Qing::~:

成傳輸線結構，只是所形成的傳期早元的布洛赫阻抗_略介於系統阻抗: Μ用於任何的電子裝置，所述電子裝再白Τ 微波電路、通訊裝置、電路板、筆記晶片、裝置或天線等。 1心'手機、顯示基於上述，本發明的傳輸線結構僅質基板就可以達到抑制能量喊之功效，而且本 25 34792twf.d〇c/n 201212373 tit可以減少金屬聯通柱的使用。除此之外，本發明的傳輸線結構所佔用的導體面積甚小，符合實際 ===:的傳輸線結構具有製造成 ^本發明已財施例揭露如上，然其並非用以限定本ί日12所屬技術領域中具有通常知識者，在不脫離和範圍内’當可作些許之更動與潤饰，故本之保護範圍當視後附之申請專利範圍所界定者為準。【圖式簡單說明】圖1A與圖1B是全通傳輸線結構示意圖。圖圖2A是習知的背覆導體共面波導傳輸線結構之示意圖圖2B是本發明一實施例所提供的傳輸線結構示意圖2C至圖3E分別是本發明另一實施例所提供的傳輸線結構示意圖。圖4A與圖4B分別是圖2B與圖3八之傳輸線結構與 j同長度的習知背覆金屬共面波導傳輸線之損失因子對應頻率曲線圖。圖5是由圖2A之習知背覆導體共面波導傳輸線結構之能量洩露示意圖。圖6A是由圖2B之週期單元2〇4經實質串接後所形成之傳輸線結構之能量$漏示意圖。 26 201212373 υ/Α-χυυ506 34792twf.doc/n 旁側開路單元排列於信號線之- 構之能量賴示意圖。之傳輸線結構之能量二圖元-經實質串接後所形成旁側Μ之開路單元3G21排列於信號線之一輪線結漏示意圖。示意圖。共面波導轉角傳輸線結構之能量圖8A是由圖2B之週期單元轉角傳議軸i輪_。㈣祕成的圖2B之開路單元期排列於信號線之右側導體面所形成之轉角傳輸線結構之能量茂漏示意圖。如莲圖2B之開路單元2〇21排列於信號線之左侧導體面所T成之轉角傳輪線結構之能量$漏示意圖。二：由圖3A之週期單元304經實質串接所組成的轉角傳輸線結構之能量洩漏示意圖。，9B是由圖3A之開路單元遍排列於信號線之左側導體面所形狀㈣傳輸_構之能量脑示意圖。圖9C是由圖3A之開路單元3〇21排列於信號線之右侧導體面所形成之㈣傳輪線結構之能量韻示意圖。圖10A為利用習知背覆導體共面波導傳輸線結構饋入的共平面天線之能量洩漏示意圖。圖10B與圖i〇c分別是由w 2B與圖3八之傳輸線結構應用於共平面天線之能量洩漏示意圖。 201212373 07A-100506 34792twf.doc/n 圖11A至圖11E分別是本發明另一實施例所提供輸線結構示意圖。立圖11F是圖11A至圖UE之傳輸線結構的等效電路示意圖。圖11G是本發明另一實施例所提供的傳輸線結意圖。圖疋圖1 ig之傳輸線結構的等效電路示意圖。馨圖12A至圖12E分別是本發明另一實施例所提供輸線結構示意圖。接认f 13A與圖邮分別是圖11A與圖12A之傳輸線結構的知失因子對應頻率曲線圖。雨会由圖UA之週期單元504排細f號線之兩旁側卿成之傳輸線結構m麻意圖。 -旁3二Γ由圖11A之短路單元5°21排列於信號線之圓P之傳輸線結構之能量汽漏示意圖。圖15疋由圖夕、田口〇旁側輪線於信號線之兩成的經贈接所形圖16B是由圖1 ιΑ 。右側導體面所形成之路早元遍排列於信號線之圖收是由圖】fA角傳輸線結構之能量茂漏示意圖。左側導體面_叙^^路單元遍於信號線之圖π是由l轉角傳輸線結構之能量茂漏示意圖。 A之週期單元604經實質串接所形成 28 201212373 07A-100506 34792twf.doc/n 的轉角傳輸線結構之能量洩漏示意圖。圖18A與圖18B分別是由圖11A與圖12A之傳輸線結構應用於共平面天線之能量洩漏示意圖。圖19A〜19D是本發明一實施例所提供的其他用以形成傳輸線結構之週期單元的示意圖。【主要元件符號說明】 10、105、106、11 :全通傳輸線結構 101 :開路線 111、1051、1061 :短路線 102、1052、1062、112、126、2(U、301、501、601 : 信號線 12:習知的背覆導體共面波導傳輸線結構 121、 2032、3032、5032、6032 :介質基版 122、 203卜 3031、5031、5081、6031 :第一導體面 123、 2033、3033、5033、5053、5063、5073、5083、 6033:第二導體面 124、 125 :線槽 127、128、202、302、502、602 :旁側導體面 20、30、50、60 :傳輸線結構 2011、3011、5011、6011 :信號線單元 2021、3021 :開路單元 5021 :短路單元 6021 :旁側導體面單元 29 201212373 υ /a-iuudu6 34792twf.doc/n 203、 303、503、603 :傳輪線 204、 304、504、604 :週期單^構的*份放大 2034、3034:凸字形的槽洞疋 209卜 2092、3091、3092 :开， 2093、3G93 :三角職之知‘、、、形狀之槽洞 2094、3094 : 半圓形狀之槽洞 3022 :凹字形的導體 3023 :矩形的導體區塊 3081、3082 :蛋糕形狀之導體區塊 3083 :三角形狀之導體區塊 3084 :半圓形狀之導體區塊 3022 :凹字形的導體 5024 :凹字形的槽洞 50331 : L形的槽洞 50512 . C子形的槽洞 50531 :閃電形的槽洞 50631 :婉蜒線形的槽洞 50731 :直線形的槽洞 5051、50532、50632 :細導體區塊 6024、6091〜6094 :實質蛇形的槽洞 C41 〜C44、C71、C72、C75、C76 :曲線 30The transmission line structure is only the Bloch impedance of the formed early-earth element _ slightly between the system impedance: Μ used in any electronic device, the electronic device is re-whitened, microwave circuit, communication device, circuit board, note chip , device or antenna, etc. 1 heart' mobile phone, display Based on the above, the transmission line structure of the present invention can achieve the effect of suppressing energy shouting only on the substrate, and the use of the metal communication post can be reduced by using the 25 34792 twf.d〇c/n 201212373 tit. In addition, the transmission line structure of the present invention occupies a very small conductor area, and the transmission line structure conforming to the actual ===: has been manufactured as a method of the invention disclosed above, but it is not intended to limit the present day. Those skilled in the art will be able to make a few changes and modifications without departing from the scope of the invention, and the scope of the invention is defined by the scope of the appended claims. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1A and FIG. 1B are schematic diagrams showing the structure of an all-pass transmission line. 2A is a schematic diagram of a transmission line structure of a conventional backplane conductor. FIG. 2B is a schematic diagram of a transmission line structure according to an embodiment of the present invention. FIG. 2C to FIG. 3E are respectively schematic diagrams of a transmission line structure according to another embodiment of the present invention. 4A and FIG. 4B are graphs showing the loss factor corresponding frequency curves of the transmission line structure of FIGS. 2B and 38, respectively, and the conventional back-clad metal coplanar waveguide transmission line of the same length. Figure 5 is a schematic illustration of the energy leakage from the structure of the back-conductor coplanar waveguide transmission line of Figure 2A. Figure 6A is a schematic diagram of the energy $ drain of the transmission line structure formed by the substantially serial connection of the periodic cells 2〇4 of Figure 2B. 26 201212373 υ/Α-χυυ 506 34792twf.doc/n The side open circuit unit is arranged in the energy line of the signal line. The energy of the transmission line structure is two elements - the open circuit unit 3G21 formed by the substantially parallel connection is arranged on one of the signal lines. schematic diagram. The energy of the coplanar waveguide corner transmission line structure is shown in Fig. 2A by the periodic unit angle of the periodic unit of Fig. 2B. (4) The schematic diagram of the energy leakage of the structure of the corner transmission line formed by the open conductor unit of Fig. 2B arranged on the right side conductor surface of the signal line. For example, the open circuit unit 2〇21 of the lotus diagram 2B is arranged on the left side of the signal line, and the energy leakage diagram of the corner structure of the corner line is formed. Two: Schematic diagram of the energy leakage of the corner transmission line structure composed of the periodic unit 304 of Fig. 3A. 9B is a schematic diagram of the energy brain of the shape (4) of the left side conductor surface of the signal line arranged by the open circuit unit of FIG. 3A. Fig. 9C is a schematic diagram showing the energy rhyme of the (four) transmission line structure formed by the open circuit unit 3〇21 of Fig. 3A arranged on the right side conductor surface of the signal line. Figure 10A is a schematic diagram of energy leakage of a coplanar antenna fed with a conventional back-conductor coplanar waveguide transmission line structure. 10B and FIG. 2〇c are schematic diagrams of energy leakage applied to the coplanar antenna by the transmission line structure of w 2B and FIG. 8 , respectively. 201212373 07A-100506 34792twf.doc/n FIG. 11A to FIG. 11E are respectively schematic diagrams showing the structure of a transmission line according to another embodiment of the present invention. Figure 11F is an equivalent circuit diagram of the transmission line structure of Figure 11A to UE. Figure 11G is a schematic diagram of a transmission line connection provided by another embodiment of the present invention. Figure 等效 Figure 1 shows the equivalent circuit diagram of the transmission line structure. 12A to 12E are schematic views showing the structure of a transmission line according to another embodiment of the present invention. The f 13A and the pictorial mail are respectively the frequency curves corresponding to the loss factor of the transmission line structure of Fig. 11A and Fig. 12A. The rain will be arranged by the cycle unit 504 of the figure UA, and the transmission line structure of the two sides of the f-line is inferred. - A schematic diagram of the energy vapor leakage of the transmission line structure of the short-circuiting unit 5° 21 of Fig. 11A arranged in the circle P of the signal line. Fig. 15 shows the shape of the gift box formed by the two side of the signal line from the side of the road and the Taguchi line. Fig. 16B is shown in Fig. 1 by ιΑ. The road formed by the right conductor surface is arranged in the signal line in the early time. The figure is the energy leakage diagram of the structure of the fA angle transmission line. The left-side conductor surface _ _ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ A schematic diagram of the energy leakage of the corner transmission line structure formed by the periodic unit 604 of A by substantial concatenation 28 201212373 07A-100506 34792twf.doc/n. 18A and 18B are schematic diagrams of energy leakage applied to the coplanar antenna by the transmission line structure of Figs. 11A and 12A, respectively. 19A to 19D are diagrams showing other periodic units for forming a transmission line structure according to an embodiment of the present invention. [Description of main component symbols] 10, 105, 106, 11: All-pass transmission line structure 101: Open routes 111, 1051, 1061: Short-circuit lines 102, 1052, 1062, 112, 126, 2 (U, 301, 501, 601: Signal line 12: a conventional back-conductor coplanar waveguide transmission line structure 121, 2032, 3032, 5032, 6032: dielectric substrate 122, 203, 3031, 5031, 5081, 6031: first conductor faces 123, 2033, 3033, 5033, 5053, 5063, 5073, 5083, 6033: second conductor faces 124, 125: wire grooves 127, 128, 202, 302, 502, 602: side conductor faces 20, 30, 50, 60: transmission line structure 2011, 3011, 5011, 6011: signal line unit 2021, 3021: open circuit unit 5021: short circuit unit 6021: side conductor surface unit 29 201212373 υ /a-iuudu6 34792twf.doc/n 203, 303, 503, 603: transfer line 204 , 304, 504, 604: the cycle of the unit structure * copy 2034, 3034: the groove of the convex shape 疋 209 209 2902, 3091, 3092: open, 2093, 3G93: the knowledge of the triangle job ',,, the shape of the groove Holes 2094, 3094: Semi-circular shaped slots 3022: concave shaped conductors 3023: rectangular conductor blocks 3081, 3082: cake shape Conductor block 3083: triangular shaped conductor block 3084: semi-circular shaped conductor block 3022: concave shaped conductor 5024: concave shaped groove 50331: L-shaped slot 50512. C-shaped slot 50531 : lightning-shaped groove 50631 : 婉蜒 line-shaped groove 50731 : linear groove 5051, 50532, 50632 : thin conductor block 6024, 6091 ～ 6094: substantially serpentine groove C41 ~ C44, C71, C72 , C75, C76: Curve 30

Claims

201212373 υ/Α-ιυυ506 34792twf.doc/n VII. Patent application: 1. A transmission line structure for suppressing energy leakage, comprising at least: a first conductor surface and a second conductor surface, which are composed of a plurality of periodic units ( Unit cell) consisting of substantially cascades, each of which is composed of a signal line unit and an open circuit unit or a short circuit unit or a side conductor unit located on both sides of the signal line unit, wherein the periodic unit Bloch Impedance is about 0.6 to 1.4 times the system impedance of the transmission line structure; and a dielectric substrate is disposed between the first conductor surface and the second conductor surface to separate The first conductor surface and the second conductor surface. 2. The transmission line junction of claim 1, wherein the open circuit single 7G is located on the first conductor surface and has a slot on a side of the signal line, and the second conductor surface remains substantially intact. And the substantially shortest distance of each of the side conductor faces formed by the plurality of open circuit units after substantially serially connecting to the signal lines formed after the substantially serial connection of the plurality of ring line cells is not all the same. 3. The transmission line structure of claim 1, wherein the open circuit single 7G is located on the first conductor surface and has a slot on a side of the signal line, and the conductor has a conductor block therein. The second conductor surface is substantially intact, and each of the side conductor surfaces formed by the plurality of open circuit units after substantially serially connecting to the signal lines formed by the substantially parallel connection of the plurality of signal line units The essence of the shortest distance is not the same as β. 4. The transmission line structure of claim 1, wherein the short-circuiting unit is located on the first conductor surface and the second conductor surface and is adjacent to the signal line by 31 201212373 v6 34792twf.doc/n a slot formed by the slot of the first and second conductor faces to provide a capacitance, and a thin conductor block surrounded by the slot of the first or second conductor face Providing an inductor to form a short circuit unit of the inductor and the capacitor ground, wherein the plurality of short circuit units are substantially serially connected after each point of the side conductor surface formed by substantially serially connecting to the plurality of signal line units The shortest distances of the signal lines are not all the same.

5. The transmission line structure of claim 1, wherein the short-circuiting unit is located on the first conductor surface and is formed by a slot on a side of the signal line and surrounded by the slot. Forming a conductor region to form a short-circuiting unit in which an inductor and a capacitor are grounded, and the second conductor surface is substantially intact, and the plurality of short-circuiting units are substantially serially connected to each point of the side conductor surface formed to the plurality of The shortest distances of the signal lines formed by the signal line units through the real (four) button are not all the same.

6. The transmission line structure of claim 2, wherein the substantially serpentine slot is formed on the first conductor surface by changing a miscellaneous of the bypass unit to form a substantially serpentine slot to enhance the a slow wave coefficient (the slow shoulder ve factor) and the second conductor surface remains substantially intact, wherein the plurality of side dissolving units pass through the (four) 贱_ into the (four) conductor surface of the mother-point to the plurality of signal line units The substantial shortest distances of the signal lines formed after the actual f series connection are not all the same. (4) An electronic device having at least a transmission line that suppresses energy, . The transmission line structure comprises at least: a guiding and a second conductor surface are composed of a plurality of periodic units _ which are cascaded, each of the periodic units being signal line 32 201212373 ^J506 34792twf The .doc/n unit and the open circuit unit located on both sides of the signal line unit are formed by a side conductor unit or a side conductor unit, wherein the period unit has a Bloch Impedance of about the transmission line structure. The system impedance is 1.4 times; and: the dielectric substrate is recorded between the first conductor surface and the second conductor surface to separate the first conductor surface from the second conductor surface. The electronic device of claim 7, wherein the electronic device is an electronic chip, a microwave circuit, a communication device, a circuit, a notebook computer, a mobile phone, a display, or an antenna. _9\7 kinds of electronic devices having at least a transmission line for suppressing energy, wherein the transmission line structure comprises at least . - a first conductor surface and a second conductor surface are composed of a plurality of Each cycle unit: the letter = the open circuit unit of the single-handle side of the signal line ΐ 2: 70: into the 'Bloch impedance of the periodic unit is not limited: = system impedance of the transmission line structure G6 i Μ times the limit of a dielectric substrate, the first surface is spaced apart from the first conductor surface and the second conductor surface. * ▼ π门 for sub-two: the electronic device of the ninth item, wherein the electricity: "an electronic day, a microwave circuit, a communication device, a circuit board, a notebook computer, a mobile phone, - display device or an antenna. 33