TW201117544A - Power supply - Google Patents

Abstract

A power supply includes two or more input waveforms being shaped or selected so that after being separately level-shifted and rectified, their additive combination results in a DC output waveform with substantially no ripple. The power supply may comprise a waveform generator, a level conversion stage for step up or down conversion, a rectification stage, and a combiner. The waveform generator may generate complementary waveforms, preferably identical but phase offset from each other, such that after the complementary waveforms are level-converted, rectified and additively combined their sum will be constant, thus requiring no or minimal smoothing for generation of a DC output waveform. The level conversion may be carried out using transformers or switched capacitor circuits. Feedback from the DC output waveform may be used to adjust the characteristics of the input waveforms.

Description

201117544 VI. Description of the Invention: Field of the Invention The field of the invention relates generally to power supplies, and more particularly to a universal DC output power supply. [Prior Art] There are two main power supply or converter classifications: (i) ac to dc and (2) DC to DC. The -AC to DC power supply typically converts the AC line voltage as its input to a DC output voltage and, for example, in applications such as home audio amplifiers. It can usually be implemented as a linear or switched power supply. A DC to DC power supply is implemented from an existing port (: voltage to another voltage, such as from one battery to another higher or lower voltage level. It is typically implemented with a switched power supply. Typically used, the DC to DC power supply converts the voltage and also provides isolation between the input and output. The common components of the S power supply include a transformer, rectifier and smoothing/storage capacitors. Commonly used in a switched power supply. The additional components include a control 1C chip, power transistors, filtering and shielding to prevent electromagnetic interference (EMI). The need for smaller and smaller equipment has led to one of the advantages of switched power supplies. For example, A conventional linear power supply in a home audio amplifier uses a large, bulky, expensive transformer to convert a low frequency, high voltage AC line supply to a lower voltage suitable for the amplifier or other application. First, the high The voltage AC line is stepped down to a lower AC voltage and then the lower AC voltage waveform is rectified to DC. However, the rectified power is 149927. Doc -4 - 201117544 The pressure system is discontinuous and therefore requires a large storage capacitor to provide a smooth money for the amplifier. Even so, the Dc supply has a sensible irregularity superimposed on the sink (corrugated electric dust) ), which can appear as an audible click and beep at the output of the amplifier unless considerable attention is paid to the design and layout of the amplifier. Although the design of this power supply is relatively simple and the transmission is relatively low However, the transformer is large, bulky and extremely expensive. These storage capacitors are also large and mussel. Therefore, the total volume of this power supply solution is excluded from being used for lightweight, low profile designs. The power loss in the supplier is relatively low, and a total efficiency is usually in the range of 85 to 9〇%. One of the alternatives to using a linear power supply is to use a switching mode power conversion technique. In this technique, first, Rectifying and smoothing the line voltage at full line voltage. This allows the storage capacitor to be smaller and less expensive than a linear power supply. The resulting high voltage DC signal is chopped at a very high frequency (usually tens of kHz) to produce a lower output voltage converted to a lower voltage by a small transformer to convert it to a lower Voltage. Since the operating frequency is much higher than the operating frequency of one of the linear power supplies', the transformer can be much smaller than in a conventional linear power supply. However, the AC signal on the output side of the transformer has to be rectified. To obtain DC, and also must be smoothed by means of a storage capacitor 'but a storage capacitor + than in a linear power supply. One example of this power supply is usually used to power a laptop. 149927.doc 201117544 One of the costs to pay for this solution is: To maintain efficiency, the chopping (: chopping wave produces a high frequency AC with a discontinuous, square waveform. This—the waveform produces a very high frequency of very high frequencies that cause radio frequency interference (EMI). Careful design, layout, and shielding are required to reduce these emissions to an acceptable level. The switching frequency components also need to be removed or isolated from the input and output lines, requiring additional magnetic components, which increases the cost and size of the supply. Although theoretically the efficiency can be extremely high, it is usually in the range of 80 to 90%. In summary, the size and weight of the switched mode power supply can be significantly reduced compared to a conventional linear power supply, and the basic component cost can be lower. However, the inherent complexity of a switched power supply design significantly increases design and certification costs and results in months of market time. In summary, linear power supplies tend to be large, relatively expensive, and cumbersome in size and profile. However, they are advantageous in terms of efficiency and low EMI. Switched power supplies tend to be smaller and lighter. However, due to higher frequency operation, the transformer and capacitor of a switched power supply tend to be smaller than a linear power supply. However, switched-mode power supplies can be less effective than linear power supplies' and produce significantly more EMI, which requires careful filtering and shielding. Switched power supplies are also more complex, requiring control circuitry and power switching devices. It takes a long time to design and is usually more expensive than a linear power supply. The trend is toward smaller and smaller power supplies', which requires higher frequency operations and therefore more about E]v1I2 potential problems. Larger power supplies can utilize three-phase power generation, which is one of the power supply technologies described in 149927.doc 201117544. In a three-phase system, three power lines carrying three alternating currents of the same frequency but different phases, etc., reach their instantaneous peaks at different times. The current waveforms are offset from each other by 120 degrees (i.e., each current is offset by one cycle from the other two waveforms). This interlacing of the waveform allows energy to be continuously supplied to the negative enthalpy in the case of reduced but no substantial ripple. Therefore, each cycle of current is transferred - a constant amount of power. The transformer can be used to boost or step down voltage levels at various points in a three-phase power network. A three-phase rectifier bridge typically contains six diodes, two of which are used for each of the three-phase systems. Although three-phase power supply systems have some benefits, they also suffer from certain drawbacks or limitations. For example, 'usually requires a minimum of three conductors or power lines' and three sets of circuits for level shifting (by means of a transformer) and rectification of each knives. Moreover, the official ripple is reduced by a single phase power supply, but the ripple is still substantial and generally requires storage capacitors to reduce it to an acceptable level. It needs to be made small, light and suitably cheap and has a minimum emi - power supply or converter. There is a further need to avoid the complexity and complication of a switched power supply - the power supply. Further steps are needed to reduce the need for large components and thus can be made into a power supply that is small and lightweight in terms of size and profile. SUMMARY OF THE INVENTION In the context of the present invention, a power supply is provided in which one or more inputs (four) (four) are shaped or otherwise selected such that the output waveform requires 149927.doc 201117544 for minimum smoothing of a DC output waveform generation . In accordance with one or more embodiments, a power supply is provided with one or more input waveforms that are shaped or otherwise selected prior to being provided to an isolation transformer. The nature of the input waveforms is shaped or selected such that the transformed waveform does not need to be smoothed for a DC output waveform or requires minimal smoothing. The power supply can include a waveform generator, a level conversion stage for boosting (or stepping down) voltage levels, a rectification stage, and a signal combiner. The waveform generator can generate a complementary waveform 'so that after rectifying and combining each of the complementary waveforms, the sum of them will be constant, so there is no need to smooth for the generation of a DC output waveform or to minimize smooth. In one embodiment, a DC output power supply includes a waveform generator, at least one transformer, a rectification stage, and a signal combiner. The waveform generator can generate complementary waveforms such that after rectifying and combining each of the complementary waveforms, their sum will be constant. The complementary waveforms are preferably identical but different from each other by a phase of 9 degrees, but in other embodiments, the waveforms may have a - different relationship. These complementary waveforms are applied to a transformer or to a single transformer with one of the individual windings. The output of the transformers 7 is provided to a sigma rectification stage that outputs a pair of rectified signals. The rectified signals have the property that their sums are constant when added together. A rectified signal is provided to the signal combiner, which sums the signals and produces a constant DC output signal. In some embodiments, the output voltage is monitored and fed back to the input side of the 149927.doc 201117544 ', A, to adjust the amplitude or other characteristics of the complementary waveform signals before being applied to the transformer. . In other embodiments, a switched capacitor technique is used in place of the transformer to adjust (e.g., boost) the voltage levels of the complementary waveforms. In other respects the power supply operates in a similar manner. The embodiments set forth herein may yield one or more advantages, including being smaller, lighter, thinner, and/or less expensive than a conventional power supply, with fewer components while maintaining high efficiency. The power supply can be designed to produce minimal or no significant EMI. Because the power supply is designed and built to be simple, it can be brought to market faster, resulting in a faster product design cycle. Further embodiments, alternatives, and variations are also set forth herein or illustrated in the drawings. [Embodiment] According to one or more embodiments, a power supply is provided with one or more input waveforms that are shaped or otherwise selected prior to being provided to an isolation transformer. The nature of the input waveforms is shaped, selected, or otherwise generated such that the transformed waveform needs to be minimally rectified and/or smoothed for the generation of a DC output waveform. Figure 8 is a conceptual block diagram of one of the power supply units 8 disclosed herein. In Fig. 8, a signal source (waveform) generator 8A5 produces a pair of complementary waveform numbers 823, 824. The complementary waveform signals 823, 824 are selected to provide a constant DC output bit after being coupled to an output (rectification) stage 84 by a one-bit conversion stage 830 (on which the level-converted signal is rectified and combined) Standard, 149927.doc 201117544 At the same time minimize the need for storage/smoothing capacitors in output stage 840. The complementary waveform signals 823, 824 are preferably of a type described hereinafter. The complementary waveform signals 823, 824 are boosted or stepped down via blocks 835, 836, respectively. The blocks may be implemented as one or more transformer or switched capacitor networks, for example as explained in further detail herein. Level conversion stage 830 provides signals 837, 838 to output stage 840. Signal 837 from first level shift block 835 is provided to one of rectifier stage blocks 860 of output stage 840. Signal 839 from second level shift block 836 is provided to a second rectifier block 861 of one of output stages 840. Each of the rectifier blocks 86A, 861 can be implemented as, for example, a full wave rectifier bridge. The rectified output signals 866, 867 of the rectifier blocks 860, 861 are complementary in nature such that when summed together, the result is a constant DC level waveform. To this end, the rectified output signals 866, 867 are provided to a signal combiner 870 that combines or otherwise combines the rectified output signals 866, 867 and typically does not need to A DC output signal 885 that is substantially constant in nature is provided in the case of a storage/smoothing capacitor. 1 is a conceptual block diagram of a DC output power supply i 基于 based on the general principles of FIG. 8 and using one or more transformers for signal level conversion. As shown in FIG. 1, a signal source (waveform) generator ι5 produces a pair of complementary waveform signals Vini, vIN2 on signal lines 123, 124. The complementary waveform signals Vini, ViN2 are selected to provide a constant DC output level while being coupled to an output stage 14 (by rectifying and combining the complementary waveform signals) by a transformer stage 130 while minimizing Wheel 149927.doc •10· 201117544 Required for storage/smoothing capacitors in the output mo. The complementary waveform signals v: N, 〜2 are preferably of a type described later herein. The complementary waveform signals vIN1, vIN2 are coupled to the output stage 14A by the variable M stage 13G and more specifically by the W variators 135, 136 of the variable = U0. The transformers 135, 136 can be lifted or depressurized in nature, and preferably have the same characteristics (assuming that the complementary waveforms are missing V Λ, the collar is 1. The amplitudes of the sir VIN 丨 and V 丨Ν 2 are the same). The transformer "5, 136 entity can be implemented as a single transformer with input windings 123, 124 and separate windings for output signals 137, 138 but u can be deliberately 杳 + & only J The sentence of the sentence is a transformer separated by two entities. Transmitter stage 130 provides signals 137, 138 to output stage 14A. A signal 137 from the secondary output of transformer U5 is provided to one of the output stages (10). The signal W from the output of the sub-stage of the waste-crushing-to-water state 136 is supplied to the _th:rectifier block 161 of the output stage 14〇. Each of the rectifier blocks 160, 161 can be implemented as, for example, a full wave rectifier bridge. Rectified output signals 166, 167 of the rectifier blocks 160, 161

The coefficients may be complementary in nature such that when the sum is summed, the result is a periodic waveform of the DC level. To this end, the rectified output signals i66, i67 are provided to a -signal combiner 170 which sums the rectified output signals 166, 167 and provides properties in the event that normally no storage/smoothing capacitors are required. One of the DC output signals 185 is substantially constant. In practice, a small amount of ripple may occur, which may be smoothed out by means of a relatively small smoothing capacitor (not shown). Capacitors may be provided in any convenient location, such as at the output of rectifier blocks 160, 161 and/or in a signal combiner. After 17 baht. 149927. Doc 11 201117544 The characteristics of the generated waveforms V1N1, Viw are selected as periodic waveforms such that after transforming, rectifying, and combining (e.g., adding) the signals, the resulting output signal 185 is a constant DC level. Preferably, the waveforms ViNi, ViN2 are identical in shape but offset from each other by 9 degrees. Moreover, the waveforms are preferably substantially smooth and do not have undesired sharp waves or other features from the - angle. Examples of suitable waveforms for signals vIN1, vINS are shown in Figure 1, and are also illustrated in more detail in Figure 2. In Fig. 2, graphs 2-8 and 2B respectively show waveforms VlN1 & VlN2 (which are represented in Fig. 2 as waveforms 2〇3, 204), each of which constitutes an alternating unreversed/warm Reverse the raised cosine waveform, but the phases are offset from each other by 90 degrees. After full-wave rectification, the resulting waveforms 213, 214 are illustrated in Figure 2 (: and 2 £), which are associated with waveforms Vm, VIN2, respectively. The waveforms 213, 214 are sinusoidal waveforms that are offset from each other by 9 degrees, i.e., have a relationship between sine and cosine 'this phase shifts the original waveforms VIN!, V1NZ. When summed together, the rectified waveforms 213, 214 produce an output waveform 22 having a constant DC output level, as shown in Figure 2E. In other words, the rectification and summation of the waveforms VlNi, ViN2 produces a constant DC output level, and generally does not require as large a storage/smoothing capacitor as would normally be required in conventional switched power supplies. Other waveforms may be used other than the waveforms 2〇3, 2〇4 illustrated in Figures 2A and 2B of Figure 2 and these waveforms provide a similar final result. Figure 3 illustrates a second example of a complementary periodic waveform selected to provide a constant DC output level after rectification and summing. In Fig. 3, the patterns 3A and 3B respectively show waveforms V1N1 & V1N2 (which are shown as waveforms 303, 304 in Fig. 3). Each of the waveforms constitutes a triangular waveform, 149927. Doc 12 201117544 The waveform has alternating unreversed/reversed triangular waves, but the phases are offset by 90 degrees from each other. After full-wave rectification, the resulting waveforms 313, 314 are shown in Figures 3C and 3D, which are associated with waveforms VIN1, VIN2, respectively. The rectified waveforms 313 and 314 are all equilateral triangle waveforms, which have a symmetrical shape and are offset from each other by 90 degrees. The phase of the original waveforms V1N丨 and VINZ is shifted. When summed together, the rectified waveforms 3 13, 3 14 produce an output waveform 320 having a predetermined DC output level, as shown in Figure 3E. Since the rectified waveforms 3 13 , 3 14 have the same linear slope for the rising and falling portions of the triangular wave, the voltage drop of the first rectified waveform 313 matches the voltage of the second rectified waveform 314 and vice versa . Thus, the rectification and summation of the waveforms Vini, ViN2 produces a 'determined DC output level, and typically does not require large storage/smoothing capacitors as would normally be required in conventional switched power supplies. In addition to the waveforms for V1N1 and Vin2 shown in Figures 2 and 3, other waveforms can be used. Preferably, the 'waveforms V丨N1, V丨Nz are selected or generated such that after the transformer and full-wave rectification' the rectified waveforms are complementary to each other so that they can be added together to produce a constant DC level. . These waveforms may include a periodic waveform of a rectified waveform that is symmetric in nature to increase its slope and curvature to the same slope and curvature as its falling slope. Similarly, the rectified waveform is preferably symmetrical about its midpoint such that its alternating "positive" and "negative" waves are identical in shape but inverted from each other. The waveform examples shown in Figures 2 and 3 are sufficient for the above criteria. In the case where the rectified waveforms are the same but offset by 9 degrees from each other, the symmetrical nature of the rectified waveforms means that the rise of one rectified waveform will exactly match the fall of the other rectified waveform, thus causing a strange 149927. Doc 13 201117544 The standard combination output level. In addition to the above waveforms, it is also possible to make VlN2 °, for example, waveforms, and/or change over time. Using more complex waveforms for V1N1, VIN2 can be constructed from multiple different harmonics. The power conversion techniques described above can be applied to voltage-based or current-based power supplies. More detailed examples are further elaborated herein. 4 is a block diagram showing one of the components of one of the disclosed voltage controlled DC output power supplies 4 according to the conceptual block diagram of FIG. The power supply 400 can be supplied by a local power source (e.g., a battery) or by an external power source (e.g., a line source). In FIG. 4, a signal generator 4A5 produces a pair of complementary waveform signals 412, 413 which are preferably periodic in nature and generally have the characteristics previously described for ViN1 and VW2 - that is, They are shaped or selected to provide a constant DC output after being coupled, rectified, and combined by a transformer stage. The complementary waveform signals 412, 413 are provided to a voltage controlled amplifier (V(:A) 415 that adjusts the amplitude of the waveform signals 412, 413 based on feedback received from the DC output signal 485 via the feedback sense amplifier 490. In some embodiments, the voltage control amplifier 41 5 can be omitted as the feedback path 491 and the sense amplifier 490. The voltage control amplifier 4 1 5 outputs the pair of amplitude-adjusted complementary waveform signals VinI and ν1 Ν: ί to the linear amplifier 430, respectively. , 43 1, as reflected by the waveforms 423, 424 in the overlay pattern shown in circle 4, which illustrate one example of a waveform similar to that used in the similar examples of Figures 1 and 2. 430, 43 The power input of 1 is connected to the power supply rails +V and _v, and the linear amplifier outputs amplified signals 432 and 433, which are substantially on rail 149927. Doc • 14· 201117544 Inter-channel crossing (self-amplifiers 430, 431 experience less loss). The voltage characteristics of the signals 432, 43 3 for one waveform instance in the case where the initial generated waveform is presented as in the graphs 423, 424 for Vin] and ViN2 respectively correspond to the overlay pattern 4 illustrated in Fig. 4 And 4 4 丨 (showing waveforms vpi and Vp2). The corresponding current characteristics of VP1 and Vp2 are respectively reflected in the overlay patterns 442 and 443 (illustrated waveforms Ipl and Ip2). As can be seen from Figures 44〇, 441 442 and 443, the voltage waveforms Vp丨 and VP2 for this particular example are characterized by alternating inverted and unreversed raised cosine waves (where Vpi and Vp2 are identical but offset from each other). Shifting 9 degrees), corresponding to the current waveform ip 1 and in the form of a square wave having a constant positive current corresponding to one of the time periods of the unreversed raised cosine wave, and corresponding to the inverted raised cosine The strange cycle of the k-cycle between the waves. Similar to the voltage waveform, the current waveforms Ip 1 and Ip2 are the same but offset by 90 degrees from each other. The output of the first linear amplifier 430 is coupled to the primary winding of a first transformer 435. The output of the second linear amplifier 431 is coupled to the primary winding of a second transformer 436. The secondary windings of transformers 435, 436 are coupled to an output stage 440 that receives transformer output signals 437, 438 from transformers 435, 436. Transformers 435, 436 may be boosted or stepped down in nature, and are preferably identical in characteristics (assuming that the complementary waveform signals vp and vp2 have the same amplitude). The transformers 435, 436 can be physically implemented with a single transformer for the input signals 432, 433 and for the output windings 437, 438 but sharing one of the same cores 'otherwise it can be implemented as two separate transformers . Transformers 435, 436 are preferably designed to have a low leakage inductance. 149927. Doc 15 201117544 The wheeling stage 450 preferably includes a pair of rectifier blocks 46A, 461 which may be implemented as, for example, a full wave rectifier bridge. Signal 437 from the secondary output of transformer 435 is provided to one of first stage rectifiers 46 of output stage 45. A signal 439 from the secondary stage output of transformer 436 is provided to one of the output stage 45's second rectifier block 461. Each of the rectifier blocks 46A, 46 can be implemented as, for example, a full wave rectifier bridge. In this case, the rectified output signals of the rectifier blocks 460, 461 are periodic waveforms that are complementary in nature such that when summed together, the result is a constant DC level. To this end, the outputs of the rectifier blocks 460, 461 are combined in series such that the additive combination is derived from its rectified output signal, thereby providing one of the substantially constant properties in the case where a storage/smoothing capacitor is typically not required. Output signal 485. In practice, a small amount of ripple may occur, which may be smoothed out by means of a relatively small smoothing capacitor (not shown), which may be provided at any convenient location, such as at the output of rectifier blocks 46, 46, and/or Across load 470. Therefore, the load 470 is supplied with a constant DC output supply signal. If desired, feedback can be provided via sense amplifier 49, which samples the DC output signal 485 and provides a voltage feedback signal to voltage control amplifier 415, which in turn adjusts the amplitude of input waveforms 412, 413 to Suitable for linear amplifiers 43A, 431. In this manner, the DC output signal 485 can be maintained at a constant voltage level. The operation of power supply 400 is generally similar to power supply 100 of FIG. For example, the input waveforms 412, 413 exhibit alternating periods of inverted/uninverted raised cosine 149927, such as illustrated in Figures 2A and 2B of Figure 2. Doc •16· 201117544 The shape of the wave, the resulting rectified and combined waveforms will be similar to those shown in Figures 2C, 2D and 2E of Figure 2, as previously explained. In the case where the input waveforms 412, 4 1 3 exhibit a shape of a triangular waveform having alternating inverted/non-inverted triangular waves as illustrated in the patterns 3a and 3B of FIG. 3, the resulting rectified and combined The waveforms will be similar to those shown in Figures 3C, 3D and 3E of Figure 3, as also explained previously. As with Figure 1, any suitable periodic waveform can be used, including waveforms with multiple harmonics or alternating over time. With the appropriate waveforms described herein, the power supply 400 can theoretically generate a constant DC output signal 485 without the need for a storage/smoothing capacitor. Figure 5 is a block diagram showing one of the components of another embodiment of the power supply unit 5 according to one of the general methods of Figure i. Unlike the power supply of Figure 4, which is a voltage controlled DC output power supply, Figure 5 illustrates a current controlled DC output power supply 5 . In Fig. 5, the component power month b labeled 5 通常 is generally similar to the similarly labeled component 4 图 in Fig. 4. The power supply unit 5 can be supplied as previously provided by a local power source (e.g., a battery) or by an external power source (e.g., a line source). A signal generator 5 〇 5 produces a pair of complementary waveforms L 5 5 5 13 13 ' which are preferably periodic in nature and generally have the characteristics previously described for V, NjViN 2 · that is, they are plasticized Shape or selection to provide a constant DC output after being lighted, rectified, and combined by the transformer-level. The mutual (quad) shaped signals 512, 513 are provided to a battery control, and the voltage control amplifier adjusts the amplitude of the waveform signals π, 513 based on the feedback received from the DC output signal 585 via the feedback sense amplifier 590. In some embodiments, the voltage controlled amplifier 515 can be returned as 149927. Doc -17- 201117544 Feed path 591 and sense amplifier 590 are omitted. The voltage control amplifier 51 is outputting the pair of amplitude-adjusted complementary waveform signals Vini&V1N:j to the linear transconductance amplifiers 53A, 531, respectively, as reflected by the waveforms 523, 524 in the overlay pattern as shown in FIG. The overlay image depicts an example of a wave row similar to that used in the similar examples of Figures 1 and 2. Transconductance amplifiers 530, 531 output a current proportional to their input voltage and can therefore be considered a voltage controlled current source. The effect of the transconductance amplifiers 53A, 53 1 is that the waveforms 512, 513 generated by the signal generator 505 will substantially be converted to similarly shaped current waveforms. As discussed below, this can have advantages for downstream processing and can produce even better EMI characteristics. Transconductance amplifiers 530, 531 are coupled to power supply rails + and _, and output amplified signals 532, 533 to transformers 535, 536. In the case where the initial generated waveform is presented as in the graphs 523, 524 for Vi»丨 and V丨Μ, the current characteristics of the signals 5 3 2, 5 3 3 are respectively reflected in the overlay pattern 540 illustrated in FIG. 5, respectively. And 541 (showing waveforms Ip 1 and ip2). The corresponding voltage characteristics of signals 432, 433 are reflected in overlay patterns 542 and 543 (showing waveforms Vp 1 and Vp2, respectively). As can be seen from the figures 540, 541, 542 and 543, the current waveforms Ip 1 and Ip2 for this particular example are characterized by alternating inverted and unreversed raised cosine waves (where Ip 1 and Ip2 are identical but each other Offset 9〇), and the corresponding voltage waveforms Vp 1 and Vp2 are in the form of square waves having a constant positive voltage corresponding to one of the time periods of the unreversed raised cosine wave, and corresponding to the inverted rise The value of the time period of the cosine wave is constant. The negative voltage β is the same as the current waveforms Ip 1 and Ιρ2. The voltage waveforms Vp 1 and Vp2 are the same but offset from each other by 90 degrees. 149927. Doc •18· 201117544 The output of the first transconductance amplifier 530 is coupled to the primary winding of a first transformer 53 5 . The output of the second transconductance amplifier 531 is coupled to the primary winding of a second transformer 536. The secondary windings of transformers 535, 536 are coupled to an output stage 540 that receives transformer output signals 53 7, 538 from transformers 535, 536. The transformers 535, 536 may be boosted or stepped down in nature and are preferably identical in characteristics (assuming the amplitudes of the incoming signals 532, 533 are the same). The transformers 535, 536 can be physically implemented as a single transformer having input windings 532, 533 and separate windings for outputting signals 537, 538 but sharing the same magnetic core, otherwise the entities can be implemented as two separate transformers . Output stage 550 preferably includes a pair of rectifier blocks 56A, 561, which may be implemented, for example, as a full wave rectifier bridge. Signal 537 from the secondary output of transformer 535 is provided to one of the first rectifier blocks 56 of output stage 550. Signal 539 from the secondary output of transformer 536 is provided to one of second rectifier blocks 561 of output stage 550. Each of the rectifier blocks 560, 561 can be implemented as, for example, a full wave rectifier bridge. In this case, the rectified output signals of the rectifier blocks 560, 561 are periodic waveforms that are complementary in nature such that when summed together, the result is a constant DC level. To this end, the outputs of the rectifier blocks 56A, 561 are coupled in parallel such that the additive combination is derived from its rectified output signal 'by providing one of a substantially constant property in the event that a storage/smoothing capacitor is typically not required. DC output L number 585. In practice, a small amount of ripple may occur, which may be smoothed out by means of a relatively small flat container (not shown), which may be provided in any convenient location, such as at the output of rectifier blocks 560, 561 and/or I49927. Doc •19- 201117544 铋 负载 load 570. Therefore, a constant d signal is supplied to the load 57 。. /Required to provide a feedback via sense amplifier 590, which samples the DC output nickname 585 and provides a voltage feedback signal to the voltage control amplifier 515 'This control amplifier then adjusts the amplitude of the input waveforms M2, 513 For the transconductance amplifiers 53 (), 531 - suitable for the level. In this way, the DC output h number 585 can be maintained at a strange voltage level. The feedback loop is preferably designed such that the transconductance amplifier 53 is operated close to the track for maximum efficiency, but is far enough so that the A|| is still in the linear operating region and is not limited. The voltage feedback loop helps ensure that the voltage level remains relatively constant even when the characteristics of the load (eg, its resistance) fluctuate over time. Voltage feedback can also be used to ensure that if the input voltage drops (for example, using a battery as a Input source), the output voltage will remain relatively constant. When the output signals 123, 124 of the waveform generator 105 are considered to be current dependent, the operation of the power supply 5 is substantially similar to the power supply 500 of the figure. In the case where the input waveforms 512, 513 are alternately inverted or unreversed raised cosine waves in a period such as illustrated in graphs 2A and 2B of FIG. 2, the resulting rectified and combined waveforms will be similar to the graph. The waveforms shown in Figures 2C, 2D and 2E of Figure 2 are as previously explained. The resulting rectified and combined waveforms are obtained in the case where the input waveforms 5 12, 513 are in the shape of a triangular waveform having alternating inverted/non-inverted triangular waves as illustrated in Figures 3A and 3B of FIG. The waveforms similar to those shown in Figures 3C, 3D and 3E of Figure 3 are also as previously explained. With Figure 1 a 149927. Doc •20· 201117544, any suitable periodic waveform can be used, including waveforms with multiple erroneous waves or over time. With the appropriate waveforms described herein, the power supply 500 can theoretically eliminate the need for storage/smoothing capacitors. In the event of a value, a fixed DC output signal 585 is generated. Another embodiment of a power supply using one of the alternative amplifier configurations is shown in Figures 11A and. In these examples, for the sake of simplicity, only the half of the primary side power supply is shown; the circuit in each case will be duplicated to complete the primary side portion of the power supply. Thus, the transformer 1148 shown in Figure uA will conceptually correspond to transformer ΐ 35 (τι) in Figure i, and will be completed using a second set of circuits and a second transformer corresponding to transformer 136 (Τ2). The main side of the unit. Similarly, since only the power supply circuit 11() 2 on the primary side is shown in FIGS. 11 and 113, the circuit on the secondary side will typically be shown as, for example, the rectifier 160 (R1) in FIG. Alternatively, a half of the bridge circuit shown in FIG. 5 (that is, the diodes 〇1 to 〇4 of the output stage 55〇) is formed. The general method of Figures 11A and 11B employs a push-pull amplifier design; therefore, transformer U48 has a single secondary winding 1146 but two primary windings 1147. Referring first to the example of Fig. 11A, voltage sources 1105, 11〇6 respectively produce output waveforms 1112 and 1113, which are shown in the accompanying overlay pattern adjacent to voltage sources 11〇5, 11〇6. Waveforms 1112 and U13 are typically equivalent to the positive half cycle and the negative half cycle of the periodic waveform shown in Figure 2, respectively. The first voltage source n〇5 produces a waveform 1112 corresponding to the unreversed raised cosine wave of Fig. 2A, and the second voltage source 1106 produces a wave corresponding to the inverted raised cosine wave of Fig. 2A 149927. Doc 21 201117544; however, these waves are shown as positive rather than negative, as they are applied to the inverting side of the dual main transformer 1148. For a second transformer (not shown) that produces a complementary waveform, two similar voltage sources will be provided to generate a waveform corresponding to the positive half cycle and the negative half cycle of the periodic waveform shown in Figure 2B, respectively, and the self voltage generator The waveforms of 1105 and 1106 are similarly phase shifted, as shown in Figures 2a and 2B. Each of the waveforms 111 2, 111 3 constitutes a series of unreversed raised cosine waves' which are phase shifted from each other by 18 degrees in this example. Voltage sources 11 05, 11 06 are supplied as inputs to linear amplifiers 〇 2 〇, 1 j 21 , which in turn feed field effect transistors (FETs) 113 〇, 1131. One of the transistors 1130, 1131 is connected to one of the main windings ι147 of the transformer 1148, and the source of each is also connected to the non-inverting input of the respective signal amplifiers 11 2 0, 1121 and to each Do not use current sensing resistors 丨丨丨6 and 1117. Similarly, the center tap 1149 of transformer 1149 and the power supply inputs of amplifiers 1120, 1121 are coupled to a single power supply 11 07 ' which may include, for example, a series of batteries or other DC power sources. Amplifier 1120 and transistor (1) 丨 together with amplifier 1121 and transistor 113 1 (Q2) form a push-pull amplifier that provides a defined current output defined by voltage waveforms 1112, 1113, such The voltage waveform is applied by sources 11 05 and 106. The current waveforms are fed to a transformer 1149' and then appear on the secondary windings 46 for rectification by the output stage (not shown in Figure a). In some configurations, the device of Figure 11A provides an advantage due to the availability of a unipolar power transistor device and the drive voltage can be monopolar and referenced to 149927. Doc •22· 201117544 Ground. To achieve optimum performance, the transistors 1130, 1131 can be configured according to conventional methods to conduct a permanent quiescent current to improve the linearity and speed of response at lower output current levels. However, this quiescent current reduces the overall efficiency of the power supply. The slightly modified operational configuration shown in Figure 11B reduces the amount of quiescent current. The basic structure of Figure 11B is similar to Figure 11A, but the waveforms supplied by signal generators 1105, 1106 are modified to improve the linearity and speed of response at low output power >>IL levels while minimizing overall efficiency reduce. The additional periodic waveforms 1197, 1198 shown below the main drive waveforms 1112, 1113 are amplitude-amplified views in each case where a common mode waveform is simultaneously added to the two halves of the push-pull amplifier. This common mode waveform causes the transistors 1130, 1131 to conduct quiescent current only around the region where the respective main waveforms m2, m3 are near zero; at all other cycles outside the conduction period, the transistors 1130, 1131 are biased OFF. The common mode current causes the electric crystal. The bodies 1130, 1131 enter their conduction regions shortly before they are required to operate, thereby reducing conduction distortion. The common mode current in each half of the output stage (on the secondary side) is cancelled in transformer 11 48 and therefore does not appear in the output from the duster secondary winding 1146. The period during which the common mode waveform causes the transistors 1130, 1131 to conduct may be different from the illustrated example. In this way, the average power loss due to the quiescent current can be significantly reduced compared to continuous conduction. The power amplifier configuration illustrated in Figures 5 and ΠΑ and 11B can generally be referred to as a linear transconductance amplifier' which has a nominal flat frequency response such that it accurately reproduces the complementary waveform fed to its input. The complementary waves 149927. Doc •23- 201117544 The shape is not sinusoidal and therefore usually requires a high gain bandwidth product from the amplifier to achieve optimum performance. In the case of the particular complementary waveforms shown in Figures 2A and 2B, this constraint can be relaxed by appropriately modifying the complementary waveforms such that the amplifiers can be configured as integrators. The closed loop response of an integrator typically decreases with frequency by 6 dB/octave, which allows for an amplifier with a lower open loop bandwidth. An example of this method that can be configured using one of the amplifiers is shown in Figure 2. In this embodiment, as in the designs of Figs. 11A and 11B, only the half of the main-stage side power supply corresponding to the circuit associated with one of the two transformers is illustrated. As with earlier designs, transformer 1248 in this example has a single secondary winding 1246 but two primary windings 1247. As just described, 'only the power supply circuit 丨2〇2 on the main stage side is shown, and the circuit on the sub-stage side of the half of the main stage side circuit will generally include a similar to, for example, FIG. 1 or FIG. The bridge circuit of the other half of the output stage. In this example, a pair of voltage sources 12〇5, 1206, respectively, produce output waveforms 1212 and 1213, which are shown in the accompanying drawings of proximity voltage sources 1205, 1206. The outputs of the voltage sources 1205, 1206 are supplied to the linear amplifiers 丨22〇, 丨221 via resistors 1270(R3) and 1271(R4), respectively, and the bulk 丨220, 1221 feeds the field effect transistor (FET) again. 123〇, 1231. Each of the transistors 1230, 1231 is coupled to one of the main windings 1247 of the transformer 1248, and the source of each of them is also coupled to current sense resistors 1216 and 1217, respectively, and to respective integrator capacitors 1272 ((:1) and 1274((:2), each of these integral electric grids consists of a resistor 1273 (R5) and 149927 respectively. Doc •24· 201117544 1275 (R6) riding across. The center tap 1249 of the transformer 1249 and the power supply input of the amplifiers 1220, 1221 are coupled to a separate power supply 1207' which may include, for example, a series of batteries or other DC power sources. In operation, the feedback from current sense resistors 1216 (R1) and 1217 (R2) is achieved by capacitors 1272 (C1) and 1273 (C2), including resistors i273 (R5) and 1274 (R6). ) to provide DC stability. The integrator action of capacitors 1272 and 1 73 forces the voltage across resistors 1216 (R1) and 1217 (R2) and thus the current through transistors 1230 (Q1) and 1231 (Q2) to become signal generators 1205 and 1206. The components of the output voltage (ie, voltages 1212 and 12 13). In order to match the current to the desired shape, the voltage waveforms 1212 and 1213 are selected to be differential waveforms of the waveform 203 (or the waveform 204 for the complementary section of the main-stage power supply circuit) depicted in FIG. 2A, and then Similar to FIG. 11A), waveforms 1212 and waveforms 1213 are only intercepted from waveform 203 every half cycle. Since waveform 1213 is applied to the negative winding of dual main stage transformer 1248, the waves are shown to be positive in nature. An alternative integrator configuration can be constructed by eliminating capacitors 1273 and 1274 ((:1 and C2) and replacing the current sense resistors 1216 and 1217 (R1 and R2) with inductors. In this case, through the inductor The current will be a component of its electrical voltage. • The use of an integrator for the power amplifier section is not limited to these specific examples. In a more general version of the power supply circuit of Figure 5, the amplifier 53〇 And 531 can be configured as a transconductance amplifier having an integrator characteristic that is fed with a modified voltage waveform instead of the waveforms 523 and 524 shown in Figure 5. The modified waveform for this purpose is shown as the waveform in Figure 13. 1312, i3i3, same as 149927. Doc •25· 201117544 The solid line shows the waveforms 1303, 1304 after the integration. The modified waveforms 13 12, 13 13 can be described as a sequence of sine or cosine waves, which are inverted at the end of each cycle. . 2A and 2B, the waveforms 13 12, 13 13 and the resulting integrated waveforms 〇3〇3, 丨3〇4 are identical in shape, but the phases are offset from each other. The goal of low static power can also be achieved in other ways, for example by using a feedforward technique to linearize the power amplifier. This method is illustrated in Figure 14. For simplicity, the circuit 14〇2 shown in FIG. 14 corresponds to one side of the power amplifier of the figure; a second set of similar components corresponding to the other half of the power amplifier of FIG. 11A will be provided to form a complete amplifier. And then, the entire set of circuits will be replicated again to provide complementary signals for rectification and combination on the other side of the power supply. In Fig. 4, amplifier 1420, transistor 1430 (Q1) and resistor 1416 (R1) form one of amplifiers A1 as in UA, but with a quiescent current as low as zero. The output 1432 of the transistor 1430 (Q1) is coupled to one of the main windings of a dual main stage transformer (similar to the transformer 1148 shown in Figure 11A). The Dc power supply 1407 supplies power to the amplifiers 420 and 1421, and the power supply is also connected to one of the transformer's center taps (similar to the DC source signal connected to the center tap of the transformer 1148 of Figure uA). Amplifier 1421, transistor 143 1 (Q2) and resistor 1417 (R2) form a low power error correction amplifier A2 that amplifies and regulates the input voltage (from signal generator 1405 output) and across resistor 1416 ( The difference between the output voltages of R1). One of the differential voltages is converted to a current through one of the transistors 1431 (Q2) to be added to the electricity from the transistor "(10)(1)") 149927. Doc •26· 201117544 Stream. This portion is achieved using a differentiator 1418 that receives a voltage signal from voltage source 1405 (V1) and subtracts the source between transistor ^(10)(1)丨) and sense resistor 1 4 16(R1). The voltage signal at the node. Amplifier A2 therefore adds a correction current that compensates for the error in A1 to the output. The correction current required from amplifier A2 is typically significantly less than the current output from amplifier A, and thus amplifier A2 can be a lower power amplifier than amplifier A1 and can also have a much smaller static power waste. The output 1432 of the transistor pair 1430, 1431 can be fed to one of the main windings of a transformer similar to the one of Figure 11A. Another similarly configured feedforward amplifier will be connected to the other main stage winding of the transformer as shown in Figure 11A. The signal generator (1405 and its peers) can be configured to produce signals similar to those of the other embodiments disclosed in Figure 11A or herein. The use of one of the feedforward correction alternatives as illustrated in Figure 14 applies both feedforward and feedback techniques in the configuration shown in the embodiment of Fig. 15. As in Figure 14, circuit 152 in Figure 15 corresponds to one side of the power amplifier of Figure 11A; a second set of similar components will correspond to the other half of the power amplifier of Figure A to form a complete amplifier; The entire set of circuits is then re-copied to provide complementary signals for rectification and combination on the other side of the power supply. In Fig. 15, amplifier 1520, transistor 1530 (Q1) and impedance element 1516 (Z4) form an amplifier A1 that is executed as in Fig. 11A, but has a quiescent current as low as zero. Amplifier ι52ι, transistor 1531 (Q2) and impedance element 1517 (Z3) form a low power correction amplifier. Another impedance element 1572 (Z2) is formed from the output of the amplifier 1520 to one of its inverting input feedback paths, and the impedance element 1571 (Z1) is coupled to the amplifier 149927. Doc •27· 201117544 The reverse of 1520 is input to the node between the transistor and the impedance element 1516 (Z4). If the relationship Ζ2·Ζ4=Ζ1·Ζ3 is satisfied, the distortion in the transistor i53〇(qi) can be freely eliminated by the output current formed by the sum of the currents of the transistors 153〇(Q1) and 1531((^2). The amplifier stage A1 can operate at a quiescent current as low as zero to achieve maximum efficiency. Further, if the impedance element 1 572 (Z2) is selected as a capacitor, the impedance element 1516 (Z4) is selected as an inductor, and The impedance elements 1571 (21) and 15 17 (Z3) are resistors that satisfy the balance equation while the output current is derived from the input voltage of the signal generator 1505. This allows the waveform shown in Figure 12 to be used. Other combinations of impedance elements Z1 to Z4 can also be used to achieve similar results, and the impedance element does not need to be an integral circuit component, but can be a network of components. For example, impedance component 1572 (Z2) can be a capacitor, impedance component 1571 (Z1) may be a series combination of a resistor and a capacitor, the impedance element 1516 (Z4) may be a resistor, and the impedance element 1517 (Z3) may be combined in parallel from one of the resistor and the electric grid. The waveform shown in Figure 12 is used as input. As another example, the impedance element 1 572 (Z2) can be a capacitor. The impedance element 1571 (Z1) can be a resistor, the impedance element 1516 (Z4) can also be a resistor, and the impedance element 1517 (Z3) can be A capacitor is used. In this case, the device can use the input waveform or other suitable waveform shown in Figure 11A. One other alternative is to combine the impedance component of one of Z3 with the input of the non-inverting input terminal to amplifier 1521. One of the choppers. The transfer function of the correction amplifier A2 can also be added by adding the feedback element 149927 as shown in FIG. Doc -28- 201117544 1675 (Z5) and 1676 (Z6) to change. For example, 'impedance element 1675 (Ζ5) can be a resistor, and impedance element 1676 (Ζ6) can be a capacitor. The transfer function of amplifier Α2 can be modified to make impedance element l6i7(z3) look like the same type of impedance element; for example, it can be expected to implement impedance element MiVZS) as a resistor, thus avoiding the use of a reactive element Impedance element 1617. In other respects, Figure 16 is the same as Figure 15, and component 16xx in Figure 16 generally corresponds to its peer component 1 5xx ° in Figure 15 although a feedforward error has been explained and illustrated in relation to a particular power amplifier configuration. Correction and feedforward plus feedback correction techniques, but they can also be applied to other power amplifiers and related designs. Figure 7 is a block diagram showing one embodiment of a power supply 7 使用 using a switched capacitor in accordance with the principles of the conceptual diagram of Figure 8. As with the other examples set forth herein, the power supply 7 can be supplied by a local power source (e.g., a battery) or by an external power source (e.g., a line source). In Figure 7, a waveform generator comprising (in this example) a pair of signal generators 7〇5, 715 produces a pair of complementary waveform signals 7〇6, 716, which are preferably of a nature (fourth) And typically have the characteristics previously described for 乂(8) and ^ - that is, they are shaped or selected to provide a constant sink output after level shifting, rectifying, and combining. Examples of such waveforms are shown as alternating J-inverted/non-inverted raised cosine signal waveforms and 717 (corresponding to waveform signals 706 and 716, respectively). Complementary periodic waveform signals 706, 716 may optionally be provided to a voltage controlled amplifier (VCA) (not shown) to receive a feedback signal 149927 based on the self output from DC output signal 785. Doc -29·201117544 (also not shown) adjusts the amplitude of the waveform signals 7〇6, 716. The waveform signal 706 is supplied to the transconductance amplifiers 731 and 75 I while the waveform signal 71 6 is supplied to the transconductance amplifiers 74 and 761. Transconductance amplifiers 731, 741, 751, and 761 output a current that is proportional to their input voltage and can therefore be considered a voltage controlled current source. The effects of transconductance amplifiers 73A and 741 substantially convert waveform signals 706, 716 to similarly shaped current waveforms 735, 745. The effects of the transconductance amplifiers 751 and 761 substantially convert the waveform signals 706, 7 16 to a similarly shaped but inversely inverted current waveform 755, 765 'the inverse of the nature due to the waveform signals 7〇6, 7 16 coupled to The fact that the transconductance amplifiers 751 and 761 are inverted inputs. The conversion to a current drive waveform as in the embodiment of Figure 5 can have advantages for downstream processing and can result in improved EMI characteristics. Transconductance amplifiers 731, 741, 751, and 761 can be configured similar to their previously described configurations. For the example illustrated in Figure 7, the current characteristics of signals 735 and 745 may be characterized by alternating inverted/non-inverted raised cosine waves (where the current waveforms of signals 73 5 and 745 are the same but offset from each other by 9 〇). Degrees, and the corresponding voltage waveforms associated with signals 73 5 and 745 are typically square waves having a constant positive voltage corresponding to one of the time periods of the unreversed raised cosine wave, and corresponding to the inverted rise A constant negative voltage for the time period of the cosine wave. Like the current waveforms of signals 735 and 745, the voltage waveforms are the same but offset by 90 degrees from each other. Similarly, the current and voltage characteristics of signals 755 and 765 are inverted from signals 735 and 745. Thus, the current characteristics of signals 755 and 765 for this example may be characterized by alternating unreversed/reversed raised cosine waves (where the current waveforms of signals 755 and 765 are the same but offset by 9 degrees from each other). With the letter 149927. Doc •30· 201117544 No. 755 and 765 related voltage waveforms are usually square waves, which have a constant positive voltage corresponding to one of the time periods of the unreversed raised cosine wave and correspond to the inverted raised cosine wave A constant negative voltage for the time period. Like the current waveforms of signals 755 and 765, the voltage waveforms are the same but offset by 90 degrees from each other. The outputs of transconductance amplifiers 73, 74i, 751, and 761 are each coupled to a similar component network that operates to boost (or step down) the input voltage level using, for example, a charge boost switched capacitor circuit and A level-converted output is provided as a constant DC source signal 785 to the load 77 〇. The output of the first transconductance amplifier 731 is coupled to a capacitor 732, the other of which is coupled to the input power supply rail 789. Transconductance amplifier 731 is used to periodically charge capacitor 732 in such a manner as to cause the level of the applied signal to boost (approximately double), thus producing a level-shifted signal 737. Diode 734 is used to rectify the boosted (or stepped down) signal 737. In a similar manner, transconductance amplifiers 741, 751, and 761 are coupled to capacitors 742, 75 2, and 762', respectively, each of which is consuming to the input power supply via diodes m3, 753, and 763, respectively. Track 789. Capacitors 742, 752, and 762 and associated diodes 743, 753, and 763 form switched capacitor circuits that boost (or step down) input signal levels, thereby producing level-shifted signals 747, 757, and 767 . Rectifier diodes 744, 754, and 764 are respectively used to rectify boosted (or step-down) signals 747, 757, and 767 in the same manner as for rectifier diode 734 with boosted (or stepped down) signal 737. The additive combination of the rectified signals obtained from the level-shifted signals 737 and 757 (for the example illustrated in Figure 7) is similar to the waveform 213 of Figure 2. Since 149927. Doc 31 201117544 The additive combination of the rectified signals obtained by the level-shifted signals 747 and 767 (for this same example) is similar to the waveform 214 in FIG. 2, ie, from the self-leveling signals 737 and 757 Acquire an additive combination of the rectified signals to produce a 90 degree offset version of the same waveform. As described above, the additive combination of waveforms 2 1 3 and 2 14 is a constant DC signal level. Thus, by combining all four rectified signals obtained from the level-shifted signals 737, 747, 757, and 767, the resulting result is substantially constant in strength, one of the boosted (or step-down) DC signals 785, Storage/smoothing capacitors are usually not required. In practice, a small amount of ripple may occur, which may be smoothed out by a relatively small smoothing capacitor 772, which may be provided in any convenient location, such as across a load 77 。. Thereby, a constant DC output supply signal is supplied to the load 77 。. The four-phase design also ensures that the current drawn from the supply 789 is substantially free of ripples. The example of Figure 7 illustrates a single voltage boost stage, but the same principles can be applied to a multi-stage boost converter.

In one aspect, Figure 7 shows one of the voltage boosters used to provide a single boost stage (approximately double supply voltage Vsupply). This method can be extended by adding other rectifiers and capacitors as shown, for example, in the embodiment of Figure 17, to create an additional boost stage. In Fig. 17, the voltage waveforms... and V2 can be the same as those of Fig. 7 (i.e., similar to the waveform and 717). The component labeled 17 in Figure π generally corresponds to its equivalent in Figure 7 labeled 7χχ. Additionally, a second boost (or buck) signal 1795 is provided in FIG. Using the same principle of Figure 7, an additional round-out state 1772 has been added to the circuit and to other charging capacitors (1732, i742 'PM 149927) in a similar diode/capacitor configuration as shown in Figure 7. .doc -32· 201117544 and 1762) performing periodic charging similar to one of 1744, 1752', 1753, 1732, 1733, 1743, mode, via diodes 1762' and 1 763' to charging capacitors Π32 , 1,742, 17521, and 1762, for periodic charging. No other power amplifier, stage 'required' but this other power amplification can be used as appropriate and the output and input ripple of the device is still extremely low. The voltage across the output of the transconductance amplifier is a square wave, as in Figure 7, so the total amplifier of Figure 17 can still operate with high efficiency. The technique for positive boosting as illustrated in Figures 7 and 17 can also be used to generate an inverted power supply by varying the polarity of the rectifier and replacing the charging rectifier with a reference to ground. The same method can be used to combine a two-stage boost to a set of power amplifiers with the dual booster supply method, as can the positive boost and reverse boosters. Figure 18 is a schematic illustration of one of the power supplies having one of a combination of a positive booster circuit and a reverse booster circuit. Here, the upper half of the circuit (i.e., a non-inverted power section 1802) is substantially equivalent to the circuit of Figure 17, while a reverse power supply section 1803 has been added. Thus, in Figure 18, the component labeled 18A generally corresponds to its peer portion labeled 7A in Figure 7. In the reverse power supply section 1803, the additional charging capacitor 1836 is coupled via diodes 1837, 1838, 1847, 1848, 1857, 1858, 1867, and 1868 in a manner similar to charging capacitors 1832, 1842, 1852, and 1862, 1846, 1856, and 1866 periodically charge 'but with the same input waveform but have opposite polarities', so the result is across one of the output capacitors 78 7 6 negative power supply output voltage 1896. In this manner, the power supply can provide both a positive output 1885 and a negative output voltage 1896 in the same device. 149927.doc -33- 201117544 FIG. 6 is an illustration of one of signal generators 600 for generating one of waveforms having alternating inverted/non-inverted raised cosine waves, which can be used in conjunction with the various embodiments disclosed herein. One of the examples simplifies the block diagram. As shown in Fig. 6, signal generator 600 can include a first sinusoidal waveform generator 〇2 having an output 603 in the form of a sine wave having one of the peaks at the soil Vs. The sine wave signal 603 is coupled as a round-in to a summer 61 〇. The other input of summer 610 is a DC input signal 608 at a fixed +Vs level. The resulting signal 607 is a DC offset version of the sine wave signal 603 having a ground and +Vs The peak between. The DC offset sine wave signal 607 is split into two paths 'one of which is provided to an analog inverter 604, which outputs one of the De offset sinusoidal signals 607 whose peak is between ground and _Vs. The phase inversion version ^ DC offset sine wave signal 607 and the inverted DC offset sine wave signal 6〇9 are optionally provided to a pair of amplifiers 605, 606 for gain adjustment (if needed), where two amplifiers 605, The gain of 606 is the same. Outputs from amplifiers 6〇5, 606 61 2, 61 3 are DC offset sine waves that are phase shifted relative to each other, and are analogous to input signals 607, 609. The switch 620 is between the outputs 612 and 613, that is, when the sine wave from the lower amplifier 6〇6 reaches the upper peak (this is the same time as the sine wave from the upper amplifier 605 reaches its lower peak) at the output. Switch between 612 and 613. The result is an output signal 621 that alternates between a "non-reversed" raised cosine wave and a "reversed" raised cosine wave every half cycle, where the unreversed and reversal raised cosine waves There is a smooth transition between 'as illustrated by the output V! in Figure 6. A similar technique can be used to generate one of the output signals 621 9 〇 phase shift 149927.doc -34· 201117544 version. The signal generator 600 can include a second sinusoidal waveform generator 622' having an output 623 in the form of a sine wave having one of the peaks at the soil Vs. Signal 623 is an inverted version of one of the signals 603; therefore, signal 623 can also be generated by only inverting signal 603. The sine wave signal 623 is passed as an input to a summer 630. The other input of summer 630 is a DC input signal 608' which is at a fixed -Vs level. The resulting signal 627 is a DC offset version of a sine wave 彳 5 623 having a peak between ground and _vs. The DC offset sine wave signal 627 splits into two paths, one of which provides an analogy Inverter 624' outputs a phase inverted version of one of the DC offset sine wave signals 627 having a peak between ground and +Vs. The DC offset sine wave signal 627 and the inverted DC offset sine wave signal 629 are optionally provided to a pair of amplifiers 625, 626 for gain adjustment (if needed) where the gains of the two amplifiers 625, 626 are the same. The outputs 632, 633 from amplifiers 625, 626 are DC offset sinusoids that are phase shifted relative to each other, similar to input signals 627, 629. Switch 64 is alternated between outputs 632 and 633, each time the sine wave from lower amplifier 626 reaches its upper peak (this is the same time as the sine wave from upper amplifier 625 reaches its lower peak) Switch between. The result is an output signal 641 that alternates between a "non-reversed" raised cosine wave and a "reversed" raised cosine wave every half cycle, where the unreversed and inverted raised cosine waves There is a smooth transition between them, as illustrated by the output % in Figure 6. The turns 621 and 641 can be used as the input signal Vini & Vini in the transformer based power supply embodiment disclosed herein. 149927.doc -35· 201117544 In practical applications, the output signal from signal generator 600 can pass through a small electric or past frequency filter to remove any residual D (: component, which can be tied to the signal generation Inadvertently formed. In addition, various bias current adjustments and other implementation details may be added in accordance with techniques well known in the art. Alternatively, other techniques may be used to generate periodic alternating waveforms. In other words, digital synthesis can be used to generate waveforms similar to those described above. According to one such embodiment illustrated in Figure 9, a waveform generator 900 stores the waveform data in a digital form in a lookup table 905. (eg, in a read-only memory (R〇M) or other non-volatile memory storage device) and in a proper sequence under the control of a microcontroller, microsequencer, finite state machine, or other controller Read out. The digital data can be provided to a pair of digital to analog converters (DACs) 91 〇, 911, one for one waveform, that is, 'the first DAC 910 outputs a first transit Waveform 914' and first DAC 911 outputs a second converted waveform 915 that is identical to first converted waveform 914 but offset from the first converted waveform by 9 degrees, as previously explained. Converted waveform 914 915 is provided to filters 920, 921 for smoothing. Outputs 930 and 931 can be used as input signals 乂丨... and VlN2 in the transformer-based power supply embodiment disclosed herein. In other embodiments, A rotor-type mechanical generator, which is similar in principle to a hub dynamo, can be used to generate alternating reversals having the same as illustrated in Figure 2 and illustrated in Figure 2 And one of the characteristics of the unreversed raised cosine wave. This 149927.doc -36- 201117544 a waveform generator may be particularly suitable for the larger wattage application of the power supply design of the present invention disclosed herein. A DC generator typically operates by rotation of a permanent magnet on a shaft, wherein the magnet is disposed within a wire coil. The output of a digital DC generator has been observed to have alternating transversals. And a waveform of one of the unreversed raised cosine waves. The complementary waveform can be generated, for example, by adding a second permanent magnet oriented perpendicular to the first magnet on the same axis as the first magnet. The second permanent magnet is in a second wire coil separate from the first wire coil. As with the two wire coils, the two permanent magnets preferably have the same size and physical properties, 4 of which can be along the length of the axis Lateral offset. The rotation of the shaft can be achieved by any suitable method, including motorization techniques, wind power or other methods. More generally, a rotating AC generator can be used to generate the appropriate waveform, the generator having a relative waveform Or one of a plurality of magnetic fields in a relative rotational motion, wherein the power supply is used to convert a relatively high DC voltage to a lower DC voltage, in one aspect, by one or more A small transformer, such as illustrated in the various embodiments described herein, transforms the high frequency AC waveform generated from a relatively voltage DC source to a lower voltage. The power supply is designed to avoid the need for large storage capacitors to smooth out the output voltage from the transformers after rectifying the transformed signals. It is theoretically possible to have both the input and output of the power converter without ripple at all output levels so that no additional magnetic components are required for filtering. Eliminating output storage needs and eliminating integrated filtering can reduce size and cost compared to, for example, a conventional switched-mode supply. !49927^〇〇 •37- 201117544 As mentioned previously, in practice, some small round-out capacitors may be required to reduce any residual ripple from the transformer stage or other stages. This slight ripple can be caused by the inductance inherent in the amplifier stage. It is expected that for a 50 watt power supply operating with a periodic waveform of 25 Ku〇hertz, a capacitor of approximately 3 〇〇 to 6 〇〇 nF will be sufficient. The capacitance of this size is significantly less than the capacitance required for a conventional switched power supply. Another technique that can be used to reduce any residual ripple at the output is to use a low dropout (LDO) linear regulator. An lD〇 linear regulator can typically include a power FET in series with the output signal. A differential amplifier controls the power FET in a manner to maintain a small Dc voltage difference between the input and output of the LD〇 linear regulator. The voltage difference is maintained at a value above the peak-to-peak ripple voltage at the output of the rectifier circuit. The ld〇 linear regulator Is is configured to remove the ripple voltage by means of a filter and prevent the ripple voltage from appearing at its output. Since the residual ripple voltage is generally expected to be relatively small in the embodiments illustrated and described herein, an ld〇 linear regulator is used to reduce or eliminate an option for the residual ripple - thus reducing or eliminating otherwise The need for a small smoothing capacitor at the output can be expected without significantly damaging efficiency. Some of the power supply embodiments disclosed herein may be constructed using two transformers. These variations (4) can be made into a low profile and @this does not significantly affect the total size of the power supply electronics. For example, for a 2 watt power supply for a one-tone system, a pair of toroidal transformers can be used, each of which is approximately 丨". The result is a smaller power supply than the one of the wattage-like switching power supply II. 149927.doc -38- 201117544 The power supply design described herein is not limited to a power range of hundreds of watts, but can also be used for much larger DC to DC conversion applications, in kilowatts or more. One embodiment of the power supply disclosed herein can have significantly reduced EMI compared to a conventional switched power supply. In the case where the voltage waveform appears as in Fig. 2, that is, the period reversed/uninverted raised cosine wave, the corresponding current waveform is a square wave, which is less desirable from an EMI point of view. The embodiment of Figure 5 overcomes these problems by transforming the inverted cosine waves to the current waveform before being sent to the transformer stage via the inverted/non-inverted. The relatively smooth current waveform in this embodiment mitigates EMI issues. Although the corresponding voltage waveform becomes a square wave, the electrostatic emission ratio formed by the voltage square wave is easily shielded and processed by the electromagnetic emission formed by a current square wave. The iEMI generated by the DC to DC conversion method can be extremely low due to the low ripple characteristics of the preferred input and output voltage and current waveforms, but can be further reduced by the frequency associated with the time-modulated complementary waveform. Shoot. This type of modulation will cause the spectral components of the residual interference to be spread over a wider spectral band, thus reducing the average amplitude of the interference at any given frequency. Modulated waveforms can be cyclical or arbitrary in nature (including virtual arbitrary). An example of one of the set of frequency modulated complementary waveforms 丨〇3〇, 〇3丨 is shown in Figure 10. This particular example is based on 啁啾 modulation, where the wavelength of the waveforms 1030, 1031 is exaggerated over time for illustration purposes only for purposes of illustration. A variety of different transformer designs and techniques can be used in conjunction with transformer stages 149927.doc-39-201117544 (130, 430 or 530) of the various power supply embodiments described herein. This particular transformer design can be selected based on the desired application. For example, the variable voltage can be a two-wire winding in which the primary and secondary conductors are wound together around the core, which can have the effect of reducing leakage inductance. Alternatively, a coaxial winding can be used in which the primary and secondary conductors are combined in a coaxial manner. This also significantly reduces leakage inductance. In terms of transformer shape and configuration, the transformer can be toroidal, otherwise it can be flat (for spiral windings) to achieve a particularly low profile and potentially simple manufacturing. Another option is to use a series of hollow cube-shaped magnetic windings, for example, as generally described in U.S. Patent 4,665,357, the entire disclosure of which is incorporated herein by reference. Yet another possibility is to embed one of the primary/secondary windings of the transformer (like a twisted pair or a coaxial pair) in a hollowed out slot in the side wall of one of the toroidal cores having an edge that is divided into squares , for example, as generally described in US Pat. in

iHj "fell Φ 5 O , another variator main/secondary winding is repeatedly wound around the core, similar to a conventional toroidal transformer, but in which the main/secondary winding 1 is a pair of slave pairs. This provides orthogonal but non-interactive magnetic enthalpy and provides increased energy density. This design allows two separate transformers to share the same core. Tian d can also use other transformer designs. The power supply design and technology described in the description can be used for different types of *' 匕3 local battery power supply 'other lines for deer, 149927.doc 201117544 which first switches to an input before switching to a DC output level Dc level. In the case of using an AC line power supply, the line AC voltage is first rectified to produce a high voltage dc. Although the DC to DC conversion process can then be performed at a relatively high frequency, which is different from the switching mode power converter', the AC waveform used for this process has a very low level of radio frequency component and thus electromagnetic interference does not become a problem. The AC waveform (although smooth and with very low EMI) is used in such a way that the supply remains extremely efficient' typically as good as or better than a conventional switching mode supply. According to some embodiments as described herein, the high frequency ACi generated from the high voltage DC is again transformed to a lower voltage by one or more small transformers. However, the specific design potentially avoids the use of The need for a storage capacitor that smoothes the output voltage after rectification. In theory, both the input and output of the converter can be free of ripple at all output levels, and therefore no additional magnetic components are needed to wave. Eliminating output storage needs and eliminating integrated ripples typically reduces size and cost compared to a switched supply. Eliminating the output storage capacitor brings a further benefit. According to embodiments disclosed herein, the power supply can respond quickly to the control signal and can therefore be used as a fast tracking power supply for efficient, high quality, low noise and low EMI audio power amplifiers. In the case where the existing -Dc supply (from the battery or from the external power supply) is present, the input rectification and storage can be dispensed with and then the power supply can be made to have a very low profile due to the elimination of the output storage capacitor. The mounting method results in an effective supply or there is a loss associated with the minimum fish EMI reduction and there is no desire/, the electrosurgical device dynamically switches 149927.doc •41 · 201117544 loss, and thus the efficiency in the transaction can exceed 90〇/0 . Driving the transformer mode, eliminating switching artifacts, and simplifying the control architecture significantly simplifies the short time to market for the design process compared to a switched mode supply. The power supply and quotation described and illustrated herein is designed for use in a variety of applications, including audio devices, portable electronic devices (eg, laptops, cellular phones, wireless devices, etc.) , avionics, medical equipment, solar energy conversion, power distribution and other applications. In various implementations, one of the power supplies constructed in accordance with the embodiments described above can be used, for example, as a vehicle power supply for an audio amplifier, for example, in Automaker #. Embodiments as described herein can produce a smaller, lighter, and/or thinner power supply that can be less expensive, more efficient, and have fewer major components, while being relatively good from a standpoint. Since the power supply is designed and manufactured to be simple, it can be launched more quickly, resulting in a faster product design cycle. In addition, low emissions reduce the time and cost for certification. The simple design process 'low component cost and low proof cost creates a significant cost savings compared to existing power supply methods. Moreover, low profile, low cost and weight and very low emissions allow the use of the power supply of the present invention in a location within a vehicle that is currently extremely difficult to implement using a switched mode power supply design. For portable battery-operated products, the low-wheel temple capability provides a form factor that is currently difficult to achieve. For more general heavy-duty power distribution applications, the ability to produce a ripple-free output without the use of a large energy storage: storage component has unique advantages over the conventional method of 149927.doc • 42· 201117544. In various embodiments, a low cost, lightweight, efficient, isolated, fast response DC output power converter having a very low input and output ripple and very low EMI emissions is provided. Power converters typically require very small output storage capacity' and can therefore be implemented with very low profile configurations. The design process is also simpler than the conventional switching mode converter, which produces a rapid design process. It is beneficially available for audio amplifiers, but the general principles embodied in this concept allow it to be used in a variety of power conversion applications. Certain embodiments described herein produce a DC output signal by combining two rectified signals having certain characteristics. However, the same principle can be extended to configurations with three or more signals that are rectified and additively combined (assuming sufficient waveforms are selected). Although the preferred embodiment of the invention has been described herein, numerous variations are possible within the spirit and scope of the invention. These variations will be apparent to those skilled in the art after reviewing the specification and drawings. Therefore, the invention is not limited except in the spirit and scope of any accompanying claims. BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 is a conceptual block diagram of one of the DC output power supplies using one or more transformers for signal level conversion as disclosed herein. Figure 2 is a set of waveform diagrams illustrating the operation of the power supply of Figure 1 in accordance with an example. Figure 3 is a set of waveform diagrams illustrating the operation of the power supply of Figure 1 in accordance with another example. 149927.doc -43- 201117544 FIG. 4 is a block diagram showing one of the components of one embodiment of a voltage controlled DC output power supply according to the conceptual block diagram of the disclosure. 5 is a block diagram showing one of the components of one embodiment of a current controlled DC output power supply in accordance with the conceptual block diagram of the disclosure. 6 is a block diagram illustrating one example of a signal generator that can be used in conjunction with the various embodiments disclosed herein. Figure 7 is a schematic diagram showing one embodiment of a power supply implemented using a switching capacitor circuit using one of the techniques similar to Figure i. Figure 8 is a conceptual block diagram of a D C output power supply disclosed herein. 9 is a block diagram illustrating a second example of one of the signal generators that can be used in conjunction with the various embodiments disclosed herein. Figure 10 is a waveform diagram illustrating one example of a frequency modulated signal that can be rotated by a signal generator. Figures 11A and 11B are schematic illustrations of one portion of a DC power supply using one of the different input waveforms in each case operating in accordance with the principles of Figure 1. Figure 12 is a schematic illustration of one of a portion of a power supply having an amplifier configured as an integrator. Figure 13 is a diagram of a waveform that can be used in conjunction with a DC power supply having one of the transconductance amplifiers having an integrator characteristic. Figure 14 is a schematic diagram of one of the power supplies of one of the power amplifiers using feedforward techniques. Figure 15 is a schematic diagram of a portion of a DC power supply using either feedforward or feedback techniques. 149927.doc •44- 201117544 Figure 16 is a schematic diagram of another embodiment of a DC power supply using one of the front cranes b _ _ J feed and feedback technology. Figure 17 is a schematic diagram of one embodiment of a multi-stage power converter formed using a switched capacitor circuit. Figure 18 is a schematic diagram showing one of a combination of switched capacitor power supplies having a positive booster circuit and a reverse booster circuit. [Main component symbol description] 100 DC output power supply source 105 (waveform) generator 123 signal line 124 signal line 130 transformer stage 135 transformer 136 transformer 137 signal 138 signal 140 output stage 160 first rectifier block 161 second rectifier Block 166 Rectified Output Signal 167 Rectified Output Signal 170 Signal Combiner 185 DC Output Signal 400 Voltage Control DC Output Power Supply 149927.doc 201117544 405 Signal Generator 412 Complementary Waveform Signal 413 Complementary Waveform Signal 415 Voltage Control Amplifier 430 Linear Amplifier 431 linear amplifier 432 amplified signal 433 amplified signal 435 transformer 436 transformer 437 transformer output signal 438 transformer output signal 450 output stage 460 rectifier block 461 rectifier block 470 load 485 DC output signal 490 feedback sense amplifier 491 feedback path 500 Power Supply 505 Signal Generator 512 Complementary Waveform Signal 513 Complementary Waveform Signal 515 Voltage Control Amplifier 149927.doc • 46- 201117544 530 Linear Transconductance Amplification 531 Linear Transconductance Amplification 532 amplified signal 533 amplified signal 550 output stage 560 rectifier block 561 rectifier block 570 load 585 DC output signal 590 sense amplification 591 feedback path 602 first sinusoidal waveform generator 603 output 604 analog inverter 605 amplifier 606 Amplifier 607 DC Offset Sine Wave Signal 608 DC Input Signal 609 Inverted DC Offset Sine Wave Signal 610 Summer 612 Output 613 Output 620 Switch 621 Output Signal 149927.doc • 47- 201117544 622 Second Sinusoidal Waveform Generation 623 Output 624 Analog Inverter 625 Amplifier 626 Amplifier 627 DC Offset Sine Wave Signal 629 Inverted DC Offset Sine Wave Signal 630 Summer 632 Output 633 Output 640 Switch 641 Output 705 Signal Generator 706 Complementary Waveform Signal 715 Signal Generator 716 Complementary Waveform Signal 731 Transconductance Amplification 732 Capacitor 734 Rectifier Diode 735 Current Waveform 737 Post-Level Conversion Signal 741 Transconductance Amplification 742 Capacitor 743 Diode 149927.doc 48- 201117544 744 Rectifier Diode 745 Current waveform 747 Conversion signal 751 transconductance amplifier 752 capacitor 753 diode 754 rectifying diode 755 current waveform 757 via level conversion signal 761 transconductance amplification 762 capacitor 763 diode 764 rectifying diode 765 current waveform 767 level conversion signal 772 Smoothing Capacitor 785 DC Output Signal 789 Power Supply Rail 805 Signal Source (Waveform) Generator 823 Complementary Waveform Signal 824 Complementary Waveform Signal 830 Level Conversion Stage 835 Level Alignment Block 836 Level Quasi Conversion Block 149927.doc - 49 - 201117544 837 Signal 838 Signal 840 Output Stage 860 First Rectifier Block 861 Second Rectifier Block 866 Rectified Output Signal 867 Rectified Output Signal 870 Signal Combiner 885 DC Output Signal 905 Lookup Table 910 Digital to Analog Converter 911 Digital Analog to analog converter 914 first converted waveform 915 second converted waveform 920 filtered benefit 921 waver 930 output 931 output 1102 power supply circuit 1105 on the main stage side voltage source 1106 voltage source 1107 separate power supply 1116 current sense Measuring resistor 1117 Current Sensing Resistors 149927.doc -50- 201117544 1120 Linear Amplifier 1121 Linear Amplifier 1130 Transistor 1131 Transistor 1146 Secondary winding 1147 Main winding 1148 Transformer 1149 Central tap 1202 Power supply circuit 1205 on the main stage side Source 1206 Voltage Source 1207 Separate Power Supply 1216 Current Sense Resistor 1217 Current Sense Resistor 1220 Amplifier 1221 Amplifier 1230 Field Effect Transistor 1231 Field Effect Transistor 1246 Secondary Winding 1247 Main Stage Winding 1248 Transformer 1249 Center Tap 1270 Resistor 1271 Resistor 149927.doc -51 - 201117544 1272 Integral Capacitor 1273 Resistor 1274 Integral Capacitor 1275 Resistor 1402 Circuit 1405 Signal Generation 1407 DC Power Supply 1416 Resistor 1417 Transistor 1418 Divider 1420 Amplifier 1421 Amplifier 1430 Transistor 1431 Crystal 1432 Mountain 1502 Circuit 1505 Signal Generation 1516 Impedance Element 1517 Impedance Element 1520 Amplifier 1521 Amplifier 1530 Transistor 1531 Transistor 1571 Impedance Component Device -52- 149927.doc 201117544 1572 1617 1675 1676 1732 1732' 1733' 1742 1742' 1743' 1744 1752 1752, 1753' 1762 1762' 1763' 1772' 1795 1802 1803 1832 1836 1837 Impedance element impedance element feedback element feedback element charging capacitor charging capacitor diode charging Capacitor Charging Capacitor Diode Diode Charging Capacitor Charging Capacitor Diode Charging Capacitor Charging Capacitor Diode Extra Output Capacitor Second Boost (or Buck) DC Signal Unreversed Power Section Inverting Power Supply Area Segment charging capacitor charging capacitor diode 149927.doc -53- 201117544 1838 1842 1846 1847 1848 1852 1856 1857 1858 1862 1866 1867 1868 1876 1885 1896 Diode charging capacitor charging capacitor diode diode charging capacitor charging capacitor diode Body diode charging capacitor charging capacitor diode diode output capacitor positive output voltage negative output voltage 149927.doc -54-

Claims (1)

201117544 VII. Patent application scope: 1 _ A power supply device comprising: a waveform generator outputting a first waveform and a second waveform; a first rectifier bridge coupled to the first waveform, the first a rectifier bridge outputs a first rectified signal; a second rectifier bridge 'coupled to the second waveform 'the second rectifier bridge output - a second rectified signal; and a DC output signal, which is continuously added The first rectified signal is combined with the second rectified signal. 2. The power supply of claim 1, further comprising a one-bit conversion circuit interposed between the waveform generator and the first rectifier bridge and the second rectifier bridge, the level conversion signal outputting the first A level shifted version of a waveform and a level shifted version of the second waveform of s. 3. The power supply of claim 2, wherein the level conversion circuit comprises: a first transformer 'the output corresponding to the first output of the level shifted version of the first waveform; and a second A transformer having an output corresponding to the second output of the level shifted version of the second waveform. 4. The power supply of claim 3, wherein the first rectifier bridge comprises a first full wave rectifier, wherein the second rectifier bridge comprises a second full wave rectifier. 5. The power supply of claim 2, wherein the level conversion circuit comprises: - the first-to-switch capacitor circuit 'their output corresponding to the first shifted version of the J-waveform Output; / ^ ^ The second pair of switched-type electric grid circuit 'their output corresponds to the second output of the second turbid shape of the level 149927.doc 201117544 shifted version. 6. The power supply of claim 5, wherein the first rectifier bridge comprises a 'pair of rectifiers', the first pair of rectifiers are connected between the first pair of switched capacitor circuits and the DC output signal, and wherein The second rectifier bridge includes a second pair of rectifiers respectively connected between the first pair of switched capacitor circuits and the DC output signal, wherein the first pair and the second pair of diodes are Each of the cathodes is connected to the dc output signal. 7. As requested! The power supply unit, wherein the first waveform and the second waveform each comprise an alternating periodic sequence of one of the unreversed wave and the inverted wave, the second and second waveforms being the same but offset from each other by 90 degrees. 8. The power supply of claim 6, wherein the first waveform and the second waveform each comprise an alternating periodic sequence of one of the unreared raised cosine wave and the inverted raised cosine wave. 9. If the request item is a power supply, wherein the first waveform and the second waveform are selected such that after rectification and additive combination, the additive combination of the first waveform and the second waveform form a constant voltage of the D c output signal Level without significant ripples. 10. The power supply of claim 9, wherein the predetermined power/1 level of the DC output signal is generated without a load capacitor. η. The power supply of claim 1, wherein the first rectified signal and the first rectified signal comprise a cosine waveform and a sinusoidal waveform, respectively. 12) The power supply of claim 1, wherein the waveform generator comprises a rotating AC generator having one of the wire coils in a relative rotation with respect to one or more magnetic fields. 13. A power supply, comprising: a waveform generator that outputs a first waveform and a second waveform; a first transformer that receives the first waveform as an input; a second transformer Receiving the second waveform as an input; • a first rectifier bridge coupled to one of the outputs of the first transformer, the first rectifier bridge outputting a first rectified signal; a second rectifier bridge coupled to the One of the second transformer outputs, the second rectifier bridge outputs a second rectified signal; and a DC output signal 'which is formed by continuously additively combining the first rectified signal with the second rectified signal. 14. The power supply of claim 13, wherein the first waveform and the second waveform each comprise an alternating periodic sequence of unreversed raised cosine waves and inverted raised cosine waves, the first and second waveforms The waveforms are the same but offset by 90 degrees from each other. 15. The power supply of claim 14, wherein the first rectified signal and the first rectified signal comprise a cosine waveform and a sinusoidal waveform, respectively. The power supply of claim 13, further comprising obtaining a feedback signal from the DC output signal, the feedback signal being provided to the waveform generator. 1 7. The power supply of claim 3, wherein the waveform generator comprises a signal generator having an output signal coupled from 0 to a voltage controlled amplifier. 18. The power supply of claim 13, further comprising a first amplifier positioned to amplify the first periodic waveform prior to the first voltage press and 149927.doc 201117544 positioned prior to the second transformer Amplifying the second amplifier of one of the second periodic waveforms. 19. The power supply of claim 1, wherein the first amplifier and the second amplifier are transconductance amplifiers. 20. The power supply of claim 13, wherein the first transformer and the second transformer share a common core. 21. The power supply of claim 13, wherein the first rectifier bridge comprises a first set of four diodes full-wave rectifier, and wherein the second rectifier bridge comprises a second set of four One of the polar body full-wave rectifiers. 22. A method for power conversion, comprising: generating a first alternating waveform and a second alternating waveform; rectifying the first alternating waveform and the second alternating waveform by level conversion to respectively generate a first rectified a signal and a second rectified signal; and forming a DC output signal by continuously combining the first rectified signal and the second rectified signal. The method of claim 2, further comprising converting the first alternating waveform and the second alternating waveform to a boosted or stepped bit before rectifying the first alternating waveform and the second alternating waveform The exact steps. 24. The method of claim 23, wherein the step of converting the first alternating waveform and the second alternating waveform to the boosted or stepped-down level comprises receiving the first alternating at a first transformer And outputting an alternating waveform of a first level-converted waveform from the first transformer; and receiving the second alternating waveform at a second transformer and rotating from the second transformer--a second level-converted waveform . 149927.doc -4- 201117544 25. The method of claim 24, wherein the first alternating waveform of the level-converted and the second alternating waveform of the level-converted are rectified to generate the first rectified signal and The step of rectifying the second rectified signal includes: applying the first alternately converted alternating waveform to a first full-wave rectifier to generate the first rectified signal; and alternating the second level-converted alternating waveform Applying to a first full-wave rectification gain to generate the second rectified signal. 26. The method of claim 23, wherein the step of converting the first alternating waveform and the first parent waveform to the boosted or stepped down step comprises applying the first alternating waveform to a a first pair of switched capacitor circuits, the first pair of switched capacitor circuits outputting a first alternating waveform of the level conversion, and applying the second alternating waveform to a second pair of switched capacitor circuits, the second An alternate waveform of the second level-converted output is output to the switched capacitor circuit. 27. The method of claim 26, further comprising: coupling a first pair of rectifiers between the first pair of switched capacitor circuits and the DC output signal to perform the first level of turn The rectification of the alternating waveforms; and coupling a second pair of rectifiers between the second pair of switched capacitor circuits and the DC output signal to perform the rectification of the alternating waveforms for the second leveled conversion. 28. The method of claim 22, wherein the first alternating waveform and the second alternating waveform each comprise an alternating periodic sequence of one of an unreversed wave and an inverted wave and the second alternating waveform Same but shifted 90 degrees to each other. 29. The method of claim 28 wherein the first alternating waveform and the second alternating 149927.doc 201117544 waveform each comprise an alternating periodic sequence of unreversed raised cosine waves and inverted raised cosine waves. The method of claim 29, wherein the first rectified signal and the second rectified signal comprise a cosine waveform and a sinusoidal waveform, respectively. The method of claim 22, wherein the first alternating waveform and the second parent waveform are selected such that after the rectifying and additive combination, the additive combination of the first alternating waveform and the second alternating waveform A constant voltage level of one of the DC turn-off signals is formed without significant ripple. 32. The method of claim 3, wherein the constant voltage level of the DC output signal is generated without a storage capacitor. 3. The method of claim 22, wherein the first alternating waveform and the second alternating waveform are generated using a rotating ac generator having a wire coil in relative rotational motion relative to one or more magnetic fields . 149927.doc