200910744 九、發明說明： 【發明所屬之技術領域】 本發明是有關於一種升壓電路，特別是指一種直流電 壓轉直流電壓的升壓電路。 【先前技術】 現今的電子設備，例如PDA、MP3 player等可攜式影 音設備或其它的可攜式通訊設備，都需要用到升壓電路來 將低電壓的電池電源轉換成較高電壓，以提供數位及類比 電路運作。 這些電子設備對於輸出電源的漣波與雜訊要求相當高 ，但是傳統所使用的升壓型boost電路（如圖1所示），由於 其輸出電流呈現脈衝型式，因此輸出電壓的漣波也較大， 一般有二種解決方式：第一種方式是在輸出端使用低 ESR(equivalent series resistance，等效串聯電阻）的電容；第 二種方式是提高切換頻率。第一種方式的缺點是會造成成 本增加；而第二種方式雖然藉著提高切換頻率使得輸出電 流漣波以及輸出電壓漣波變小，不過缺點是會造成開關切 換損失增加，且對周邊電路的電磁干擾增加。 針對這些問題，雖然有人提出低漣波的升壓電路架構 ，但是缺點是需要兩組儲能電感，外加元件多，電路複雜 且體積大，另外控制電路較為複雜造成控制器不易設計， 穩定性不佳是其缺點。 【發明内容】 因此，本發明之目的，即在提供一種使用較少元件、 200910744 c、疋I1生佳且負載暫態響應較好的升壓電路。 於是，本發明升壓電路是電連接於一電源及—負載之 間’使施加於該負載的電壓高於該電源供給的電屢 電路包含-順向導通元件、一電感、第一開關元件、第二 開關元件及一電容。 …順向導通元件具有—與電源電連接的第—端，及—第 电墩具有一與順向導通元件 ，及一與負載電連接的第二端 第-開關元件具有一與順向導通元件的第一端電連接 的第—端，及一第二端。 ::開：元件具有一與第—開關元件的第二端電連接 弟& ’及一接地的第二端。 電容是電連接於順向導通元 件的第二端之間。 -件的弟-…-開關元 當第—開關元件導通且第_ 導通元件不莫、…1關兀件不導通時’順向 & 由電源依序流經第-開關元件、電 谷、電感及負載，而斟帝代亡啦 € 上升… 對’感充電，使流經電感的電流逐漸 ，田弟一開關元件導通且第— 向導通元件被導通，使電 ^ 通時’順 成兩路由電源流經順向導通元件後分 依序流經容及第二開關元件，另-路 【實施方式】 經電感的電流逐漸下降。 有關本發明之月,』述及其他技術内容、特點與功效，在 200910744 以下配合參考圖式之一個較 清楚的呈i 較佳實知例的詳細說明中，將可 一電ή/及^明升M電路1的較佳實施例是電連接於 虿源91及一負載92之間，1 ^ # Μ μ ， 八力用疋將電源91供給的直 :電=換成另—電壓值較高的直流電壓而施加於負載” 上升壓電路1包含一順向莫_ 、 開關元件4、—第二開關 π 2、一電感3、-第- 。上述的元#比 开兀 、—電容6及一濾波電容7 上述的讀皆具有一第一端21、3 二端 22、32、40 ^ 及一弟 順^ 52、72(但電容6之兩端未編號）。 貝向V通元件2的第一端2 二端22與電感…广1與電源91電連接，其第 ，順向導通元件、4 31電連接。在本較佳實施例中 牛2為二極體，如飛輪_极躺 21為P極，第二端22A / 體，且其第一端 為電晶體等U ‘然，順向導通元件2也可 :體44成順向導it賴的元件。 電感3的第二端32 的第-端71電連接，而二7:，也與渡波電容7 其第二端72接地。思皮…疋與負載92並聯’且 第—開關元件4及第一 為N型金氧第1關疋件5在本較佳實施例中 為沒極，第二電晶體(N-M0S)，它們的第一端41、51 與第二端42、52 2、52為源極’且兩者的第-端41、51 未導通時放電之之間&反向連接—個二極體93，以利兩者 為問極的第三端4/另外’兩開關元件4、5還分別具有一 8控制以決定 、53 ’此第三端43、53係受-控制單元 μ第1關元件4及第二開關元件5的導通與 200910744 否。 第-開關元件4的第一端4 端21帝揸姑社吐 ，、壙向導通兀件2的第一 5】電連^ ， 端42則與第二卩·元件5的第-端 5】電連接’而第二開關元件5的第二❹為接地。“ 另外，電容6是電連接於順向導 與第-開關元件4的第二端42之間。除此之：,:-： = 電源91並聯的輸入# 還有一與 電㈣雜訊。 電谷94’用以減低電源91的輸入 參閲圖3(圖中的箭頭方向為電流的流動方 開關元件4導通且第二開關元件5不導通時，順)向 元件4、電容6、=及 負載92，而對電感3充電，使法 的電流逐漸上升。由於第一開關元件4導通； 視八兩柒41、42並無壓差所以電感3 壓㈣電源91的電壓加上跨電容6的電壓 =端32的電職為輸出電壓V32，兩者相減可以得到電 感3兩端31、32的跨壓^91+¥ 办 。。（丄）〇 〔閱圖4(圖中的箭頭方向為電流的流動方向卜 _ :關7"件5導通且第-開關元件4不導通時，順向：通元 :皮:Γ使電流由電源91流經順向導通元件2後分成 ”中一路依序流經電容6及第二開關元件5，另一路 依：流經電感3及負載92’而流經電感3的電 。，由於順向導通元件2導通，可視其兩端2卜22並無壓差 所以電感3的第一端31的電m值為電源91的電壓~ , 200910744 /、第一端32的電壓值為輪出電壓 到電感3兩心H的_V3=V v32兩者相減可以得 Μ 32 V91 …。 =電的週期為D’放電的週期相對的 :據:秒平衡(即充電量等於放電量)與 而 上式化簡成W(1+D^ :用广〜可將 得知輸出電壓V32、輸入電 纟公式（3)可以 ^ ^ ^ 电堙V91及週期D的關係，由卜 J看㈣出電屡與週期的關係是與—般的 ^ 同，它的貞㈣mm 路有所不 為穩定。 且控制早几8的設計上也較 92暫:閱皮:2円圖5與圖^圊5所示為空載至滿載的負载 92暫d波，圖6多1 :¾鲁二u α 〇為滿载至空载的負載92暫 都是第二端32所量測的波开》）-Γ、“ ^ ' / ’可以觀察到，輸出電壓暫離 回復㈣相當的短。財也可以發現到雖岐處於了 但是流經電感3的電流仍然是連續模式（CQnti咖 Mode，CCM)，並非县吉 τ l rent r t μ Η η/ 非連續模式（1)说〇_〇似 ⑽爐麟’職），這是因為本升壓電路1具有類似同 步整流的性質，亦即電感3 ♦ 电级3電流可以雙向流動（通 負載92的值較小的情況）， ^ 亚非早純的僅能由輸入端傳送能 量至輸出端而已。這樣的特性 了以棱同負載92的暫態響應 速度。 參閱圖2目7與圖8，圖7所示為本升壓電路1啟動 時的波形模擬，由圖中我彳pq -P、，％々 我們可以觀察到，輪出濾波電容7 上的漣波電流的確是連續恭^ 1 而非脈衝電流，因此輸出電 200910744 壓連波也較小。一開始的時候 動瞬間必須對輸出濾波電容7 可更清楚地說明本升壓電路1 圖8中（b)的波形則是流經電感 會有較大電流，這是因為啟 充電所致。圖8中（a)的波形 的輸出電壓漣波是較小的。 3的電流波形。 此外，® 8中（c)的波形是控制單元8用以控制兩開關 元件4、5的其中之一的控制訊號波形。配合參閱圖2,控 制單元8包括—比較器81、—場可程式閘陣列（Filed Prog腦maMe Gate Array，FPGA)處理器μ及一間極驅動 器83。比較器81與電感3的第二端32電連接，並由電感 3的第二端32取得輸出電壓值以當成—回授訊號來與另一 參考電壓值作比較，比較之後比較器81會輸出一個方波訊 號丄送到場可程式閘陣列處理器82的—主控龍組821做 運算，主控制模組821根據内部的數位參考值計算出輸出 電壓的誤差值，將 组兰^ 左值肘此误差值达至一比例積分微分 (Pr〇P〇rti_l-integral_Derivative，piD)控制模組 822 計算出 一控制力訊號，並將此控制力訊號回傳給主控制模組821，· 主控制模組821根據此控制力訊號計算出一控制訊號，並 藉此控制訊號驅動閘極驅動器83，而控制兩開關元件4、5 的導通時間。 在本較佳實施例中，第一開關元件4及第二開關元件5 為N型金氧半場效電晶體（N_M〇s)，然熟知此技藝之人士 ，當可用P型金氧半場效電晶體（p_M〇s)來加以取代，此變 化仍屬本創作所涵蓋的範圍。 綜上所述’本發明升壓電路1使用較少的元件，相當 10 200910744 簡單且容易實現，且由於流經電《3的電流是連續模式， 所以輪出電壓的漣波較小，再加上電感3電流在本發明中 為可以雙向流動，因此暫態回復較快，具有較佳的暫態響 應’故確實能達成本發明之目的。 ^惟以上所述者，僅為本發明之較佳實施例而已，當不 =以此限定本發明實施之範圍，即大凡依本發明中請專利 範圍及發明說明内容所作之簡單的等效變化與修飾，皆仍 屬本發明專利涵蓋之範圍内。 【圖式簡單說明】 圖疋示意圖，說明習知升壓型boost電路的結構； 圖2是一示意圖，說明本發明升壓電路的較佳實施例 3疋一不意圖’說明該較佳實施例於-第—開關元 件導通且一第二p弓a月-μ —汗1關兀件不導通時，電流的流向； 圖4疋7F思圖，說明該較佳實施例於該第 件導通且該第一閉Μ ^ 關几 予、二第開關兀件不導通時，電流的流向； 負載=波是形―示意圖’說明該較佳實施例由空載至滿載的 說明該較佳實施例由滿載至空載的 圖6是一示意圖 負載暫態波形； 圖 7 是一1 备_ “ 圖，說明該較佳實 壓與流經電感的電流之波形;及 ㈣輸出- 1 圖泰& 圖’說明該較佳實施例的輸出電壓漣波 、&經電感的電流與一 皮 役制早7L的控制訊號的波形。 200910744 【主要元件符號說明】 1 升壓電路 6 電容 2 順向導通元件 7 濾波電容 21 第一端 71 第一端 22 第二端 72 第二端 3 電感 8 控制單元 31 第一端 81 比較器 32 第二端 82 場可程式閘陣列處理器 4 第一開關元件 821 主控制模組 41 第一端 822 比例積分微分控制模組 42 第二端 83 閘極驅動器 43 第三端 91 電源 5 第二開關元件 92 負載 51 第一端 93 二極體 52 第二端 94 濾波電容 53 第三端 12200910744 IX. Description of the Invention: [Technical Field] The present invention relates to a booster circuit, and more particularly to a booster circuit for a DC voltage to DC voltage. [Prior Art] Today's electronic devices, such as PDAs, MP3 players and other portable audio-visual equipment or other portable communication devices, need to use a boost circuit to convert low-voltage battery power to a higher voltage, Provide digital and analog circuit operation. These electronic devices have quite high requirements for chopping and noise of the output power supply, but the conventional boost-type boost circuit (shown in Figure 1) has a pulsed output current, so the output voltage is also chopped. Large, there are generally two solutions: the first way is to use a low ESR (equivalent series resistance) capacitor at the output; the second way is to increase the switching frequency. The disadvantage of the first method is that it will increase the cost; while the second method makes the output current chopping and the output voltage chopping smaller by increasing the switching frequency, but the disadvantage is that the switching switching loss is increased, and the peripheral circuit is increased. The electromagnetic interference increases. In response to these problems, although some people propose a low-chopper boost circuit architecture, the disadvantage is that two sets of energy storage inductors are needed, more components are added, the circuit is complicated and bulky, and the control circuit is more complicated, so that the controller is not easy to design, and the stability is not Jia is its shortcoming. SUMMARY OF THE INVENTION Accordingly, it is an object of the present invention to provide a booster circuit that uses fewer components, is better in 200910744, and has better load transient response. Therefore, the booster circuit of the present invention is electrically connected between a power source and a load, so that the voltage applied to the load is higher than the power supply circuit of the power supply includes a forward conduction component, an inductor, and a first switching component. a second switching element and a capacitor. The forward conduction element has a first end electrically connected to the power source, and the first electric pole has a forward conduction element, and a second end first connection element electrically connected to the load has a forward conduction element The first end is electrically connected to the first end, and the second end is electrically connected. ::On: The component has a second end electrically coupled to the second end of the first switching element and a grounded second end. The capacitor is electrically connected between the second ends of the forward conducting elements. - The younger brother of the ...--switching element when the first switching element is turned on and the first _ conducting element is not, ... when the closing element is not conducting, the forward direction & the power supply sequentially flows through the first switching element, the electric valley, Inductance and load, and the Emperor of the Emperor died. The rise is... The charge is charged, the current flowing through the inductor is gradually turned on, the Tiandi one switching element is turned on and the - the conduction element is turned on, so that the electric current is turned into two After the routing power flows through the forward conduction component, it flows through the second switching component in sequence, and the other way [the implementation method] gradually decreases the current through the inductor. With regard to the month of the present invention, the description of other technical contents, features and effects will be made in accordance with a more detailed description of the preferred embodiment of the reference pattern below 200910744. The preferred embodiment of the L-M circuit 1 is electrically connected between the source 91 and a load 92, 1 ^ # Μ μ , and the force supplied by the power source 91 is: straight = electric = replaced by another - higher voltage value The DC voltage is applied to the load". The boost circuit 1 includes a forward _, a switching element 4, a second switch π 2, an inductor 3, a - - the above-mentioned element # 兀 兀, - capacitance 6 And a filter capacitor 7 has a first end 21, 3 two ends 22, 32, 40 ^ and a dim 52, 72 (but the ends of the capacitor 6 are not numbered). The first end 2 and the second end 22 are electrically connected to the power source 91, and the first, the forward conducting element, and the fourth 31 are electrically connected. In the preferred embodiment, the cow 2 is a diode, such as a flywheel _ pole. The lying 21 is a P pole, the second end 22A / body, and the first end thereof is a transistor or the like U 'Ran, and the forward conducting element 2 can also be: the body 44 is a component that is guided by the guide. The first end 71 of the second end 32 is electrically connected, and the second 7: is also grounded to the second end 72 of the wave capacitor 7. The skin is connected in parallel with the load 92 and the first switching element 4 and the first type are N-type. The gold oxide first contact member 5 is in the preferred embodiment, the second transistor (N-MOS), the first ends 41, 51 and the second ends 42, 52, 52 are the source 'And the first end 41, 51 of the two are not conducting when the discharge & reverse connection - a diode 93, so that the two are the third end of the question 4 / the other 'two switching elements 4, 5 further has an 8 control to determine, 53' the third end 43, 53 is the control unit μ, the first off element 4 and the second switching element 5 are turned on and 200910744 No. The first of the first switching element 4 The end 4 end 21 emperor 揸 社 spit, the first 5] electrical connection ^, the end 42 is electrically connected to the second end of the second 元件 element 5] and the second switching element The second turn of 5 is grounded. "In addition, the capacitor 6 is electrically connected between the forward end and the second end 42 of the first switching element 4. In addition to this:,:-: = Power 91 parallel input # There is also a (4) noise. The electric valley 94' is used to reduce the input of the power source 91. Referring to FIG. 3 (the direction of the arrow in the figure is the current, the flow side switching element 4 is turned on and the second switching element 5 is not turned on, the direction is forward) to the element 4, the capacitor 6, = And the load 92, and the inductor 3 is charged, so that the current of the method gradually rises. Since the first switching element 4 is turned on; depending on the eight-two 41, 42 there is no voltage difference, the inductance 3 voltage (four) the voltage of the power source 91 plus the voltage across the capacitor 6 = the power of the terminal 32 is the output voltage V32, the two are subtracted The cross-voltage ^91+¥ of the ends 31 and 32 of the inductor 3 can be obtained. . (丄)〇 [Read Figure 4 (the direction of the arrow in the figure is the flow direction of the current _: off 7" when the member 5 is turned on and the first-switching element 4 is not turned on, the forward direction: the pass: the skin makes the current The power source 91 flows through the forward-conducting component 2 and is divided into "the middle one sequentially flows through the capacitor 6 and the second switching element 5, and the other path flows through the inductor 3 and the load 92' and flows through the inductor 3. The conduction through element 2 is turned on, and there is no voltage difference between the two ends of the two ends. Therefore, the electric m value of the first end 31 of the inductor 3 is the voltage of the power source 91, and the voltage value of the first end 32 is the turn-off voltage. Between the two cores H of the inductor 3, _V3=V v32 can be subtracted to obtain V 32 V91 .... = The period of the electricity is D' The period of the discharge is relative: According to: the second balance (that is, the charge amount is equal to the discharge amount) and The above formula is simplified into W (1+D^: use wide ~ can know the output voltage V32, the input electric 纟 formula (3) can ^ ^ ^ the relationship between the electric 堙 V91 and the period D, from the Bu J (four) power The relationship between the cycle and the cycle is the same as the general, and its 贞 (four) mm road is not stable. And the design of the early control 8 is also more than 92 temporary: read the skin: 2 円 Figure 5 and Figure ^ 圊 5 Show empty To the full load of the load 92 temporary d wave, Figure 6 more than 1 : 3⁄4 Lu 2 u α 〇 for the full load to the no-load load 92 is temporarily measured by the second end 32)) - Γ, " ^ ' / 'It can be observed that the output voltage is temporarily off the recovery (four) is quite short. It can also be found that although the current is flowing, the current flowing through the inductor 3 is still in continuous mode (CQnti Mode, CCM), not the county ji l rent Rt μ Η η / discontinuous mode (1) says 〇 _ 〇 ( 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 (When the value of the load 92 is small), ^Asian non-early pure can only transfer energy from the input to the output. This characteristic has a transient response speed of the same load 92. Referring to Figure 2, Figure 7 and Figure 8, Figure 7 shows the waveform simulation of the booster circuit 1 at startup. From the figure I 彳pq -P,, %々 we can observe that the 滤波 on the filter capacitor 7 The wave current is indeed continuous and not pulse current, so the output voltage of 200910744 is also small. At the beginning, the output filter capacitor 7 must be more clearly explained. The waveform of the booster circuit 1 in Fig. 8 is that the waveform flowing through the inductor has a large current, which is caused by the charge. The output voltage chopping of the waveform of (a) in Fig. 8 is small. 3 current waveform. Further, the waveform of (c) in the ® 8 is a control signal waveform used by the control unit 8 to control one of the two switching elements 4, 5. Referring to FIG. 2, the control unit 8 includes a comparator 81, a Filed Prog Brain Mamega Gate Array (FPGA) processor μ, and a pole driver 83. The comparator 81 is electrically connected to the second end 32 of the inductor 3, and the output voltage value is taken by the second end 32 of the inductor 3 to be compared with another reference voltage value as a feedback signal. After comparison, the comparator 81 outputs A square wave signal is sent to the main control group 821 of the field programmable gate array processor 82 for calculation. The main control module 821 calculates the error value of the output voltage according to the internal digital reference value, and sets the group blue value to the left value. The elbow error value reaches a proportional integral derivative (Pr〇P〇rti_l-integral_Derivative, piD) control module 822 calculates a control force signal, and transmits the control force signal back to the main control module 821, · main control The module 821 calculates a control signal according to the control force signal, and thereby controls the signal to drive the gate driver 83 to control the on-time of the two switching elements 4, 5. In the preferred embodiment, the first switching element 4 and the second switching element 5 are N-type MOS field-effect transistors (N_M〇s), but those skilled in the art can use P-type MOS half-field power. The crystal (p_M〇s) is substituted, and this change is still covered by this creation. In summary, the booster circuit 1 of the present invention uses fewer components, and the equivalent of 10 200910744 is simple and easy to implement, and since the current flowing through the battery is continuous mode, the ripple of the wheel-out voltage is small, plus The upper inductor 3 current can be bidirectionally flowed in the present invention, so that the transient recovery is faster and has a better transient response, so that the object of the present invention can be achieved. The above is only the preferred embodiment of the present invention, and is not intended to limit the scope of the practice of the present invention, that is, the simple equivalent change of the scope of the patent and the description of the invention in the present invention. And modifications are still within the scope of the invention patent. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 2 is a schematic diagram showing a preferred embodiment of a booster circuit of the present invention, which is not intended to illustrate the preferred embodiment. When the first switching element is turned on and a second p-a-month-μ- sweat 1 is not turned on, the current flows; FIG. 4A is a diagram illustrating the preferred embodiment in which the first member is turned on and the first A closed circuit ^ the flow direction of the current when the switch and the second switch are not conducting; the load = wave is the shape - the schematic diagram illustrates the description of the preferred embodiment from no load to full load. The preferred embodiment is from full load to Figure 6 is a schematic diagram of the load transient waveform; Figure 7 is a diagram of the current and the current flowing through the inductor; and (4) Output - 1 Figure & The output voltage of the preferred embodiment is chopped, & the current through the inductor and the waveform of the control signal of 7 liters earlier than the skin. 200910744 [Description of main component symbols] 1 booster circuit 6 capacitor 2 directional conduction component 7 filtering Capacitor 21 first end 71 first end 22 second end 72 second end 3 inductor 8 control unit 31 first end 81 comparator 32 second end 82 field programmable gate array processor 4 first switching element 821 main control module 41 first end 822 proportional integral differential control module 42 Second end 83 gate driver 43 third end 91 power supply 5 second switching element 92 load 51 first end 93 diode 52 second end 94 filter capacitor 53 third end 12