TW200410126A - Digital audio sampling scheme - Google Patents
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- TW200410126A TW200410126A TW91135532A TW91135532A TW200410126A TW 200410126 A TW200410126 A TW 200410126A TW 91135532 A TW91135532 A TW 91135532A TW 91135532 A TW91135532 A TW 91135532A TW 200410126 A TW200410126 A TW 200410126A
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200410126 五、發明說明(1) I明所屬_之技術 本發明係有關於一種數位式音訊取樣的方法,其使用 加權最小均方根演算法以展開要配置一SRC的脈衝響應時 先前技術 在音訊應用例之中,如第1圖所示,一數位式混音器 1 5現在可將來自例如一音效卡丨丨、一音源機丨2、一光碟播 ,器13及=卡匣播放器14的許多音訊,以不同取樣速率的 混合’並藉此透過一後端電路16及左右各一揚聲器 以孚殳更夕彩多姿的數位式音訊。轉換這些數位音訊資 料至所需的取樣速率是混音器的主要功能。第2圖是一 3 2 赫茲取樣速率的波形圖。第3圖是一藉由不連續傅利葉轉 換(DFT)所產生的第i圖波形的頻率響應圖。第4圖是取樣 頻率為512赫茲時所產生的第1圖的頻率響應圖。第5圖是 一用以改變取樣速率(例如,從第2圖的32赫茲至第3圖的 512赫茲)的取樣速率轉換器(SRC)的方塊圖。在第5圖中, 實務上,為了簡化計算起見,取樣速率轉^是在時間領域 上執行。如第5圖所示,在時間τ時,輸入資料χκ經過一用5 以在每一對樣本間插入零的内插裝置41、一用以執行迴旋 計算(DFT)的低通濾波器及一用以產生上述迴旋計算所 的時間刻度的定標器43,因而產生一輸出值γκ。為了在1 輸位式混音系統中安裝這樣的SRC功能,典型的方式是使 用一有限脈衝響應低通濾波器(此後,稱之為F IR渡波器) 。使·用上述内插計算以取得在取樣點間的信號振&資^200410126 V. Description of the invention (1) The technology of the invention belongs to a digital audio sampling method, which uses a weighted minimum root mean square algorithm to expand the impulse response of an SRC. In the application example, as shown in FIG. 1, a digital mixer 15 can now be played from, for example, a sound card 丨 丨 a source machine 丨 2, an optical disc player, and a cassette player 14 Many of the audios are mixed at different sampling rates, and through this a back-end circuit 16 and a speaker on the left and right are used to enhance the colorful digital audio. Converting these digital audio data to the required sample rate is the main function of the mixer. Figure 2 is a waveform diagram of a 32 Hz sampling rate. Fig. 3 is a frequency response diagram of the i-th waveform generated by a discontinuous Fourier transform (DFT). Fig. 4 is a frequency response diagram of Fig. 1 generated when the sampling frequency is 512 Hz. Figure 5 is a block diagram of a sample rate converter (SRC) for changing the sampling rate (for example, from 32 Hz in Figure 2 to 512 Hz in Figure 3). In Figure 5, in practice, in order to simplify the calculation, the sampling rate conversion is performed in the time domain. As shown in FIG. 5, at time τ, the input data χκ passes through an interpolation device 4 using 5 to insert zeros between each pair of samples, a low-pass filter for performing convolution calculation (DFT), and a The scaler 43 for generating the time scale of the above-mentioned convolution calculation, thereby generating an output value γκ. In order to install such an SRC function in a 1-input mixing system, a typical method is to use a finite impulse response low-pass filter (hereinafter, referred to as an F IR crossover). Use the above interpolation calculations to obtain the signal &
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200410126 五、發明說明(2) ==為FIR濾波器設計領域中的主 產生用於超取樣法中的脈衝響應。 ,、趣尤,、疋 換演算法來達成❶然而,在以最少士係利用―㈡互 F IR渡波器的設計+,這個演算人方來產生最佳化 軟體計算中。 无複雜又不容易安裝於 發明内灾 有鑑於此,本發明之一目的係 樣的方法,其使用加權最小均===音訊取 s R C的脈衝響應時所需的係數。…^展開要配置一 内本含安裝-軟 杳整體發明可效地極小化軟體配置時所需的計響算應藉此 貝施方式 王文中,類似元件功能以相同元件編號代表之。 第6圖顯示-本發明數位式混音器方塊圖。在第6圖中 ,所有輸入的數位式音訊資料D1_Dn係在經過各自對應的 取樣速率轉換器(SRC)有限脈衝響應(FIR)低通濾波器η (今後簡稱為FIR濾波器)後,由加法器62混音,藉以產生 一輸出波形。如第6圖所示,上述FIR濾波器61及加法器“ 形成一混音器6 5。混音器6 5的配置係相同於習知的架構, 但是在關鍵性F I R濾波器的配置方法上是使用加權最小均 方根演算法。使用加權最小均方根演算法所產生的本發明 F IR濾波器的頻率響應可以公式表示於下: 久200410126 V. Description of the invention (2) == Generates the impulse response used in the oversampling method for the master in the field of FIR filter design. ,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,, Some-not used No complexity and no easy installation in the invention. In view of this, one of the purposes of the present invention is a method that uses the weighted minimum mean === the coefficient required when taking the impulse response of s R C. … ^ Expand to configure one. Includes installation-software. The overall invention can effectively minimize the software response required for software configuration. This method should be used. Wang Wenzhong, similar component functions are represented by the same component number. Figure 6 shows a block diagram of the digital mixer of the present invention. In Figure 6, all input digital audio data D1_Dn are added by the corresponding sampling rate converter (SRC) finite impulse response (FIR) low-pass filter η (hereafter referred to as FIR filter), and then added by The mixer 62 mixes to generate an output waveform. As shown in Fig. 6, the above-mentioned FIR filter 61 and the adder "form a mixer 65. The configuration of the mixer 65 is the same as that of the conventional structure, but in the configuration method of the key FIR filter It is a weighted minimum root mean square algorithm. The frequency response of the F IR filter of the present invention produced by using a weighted minimum root mean square algorithm can be expressed by the following formula:
200410126 五、發明說明(3) Σ p^'n 以 (1) 其中,P(z)是傅利葉轉換函式(此後稱之為z函式),係數 Pn是FIR濾波器的脈衝響應,其中N是FIR濾波器的長度(階 度)。令// (z)為想要的F I r濾波器頻率響應而頻率響應誤 差函式E為: £1ζ)- Σ P«z*n - ^Cz) ^ (2) 方程式(2)可評量於一線性分佈從ω = 〇到江的頻率密度格 點上。對於一具有長度Ν的F IR遽波器而言,4 Ν頻率格點就 足以表示濾波器的功效。若頻帶邊緣未落在所設的頻率格 點上時,就須要增加額外的格點以對應上述遺漏的頻帶邊 緣。此時,可以下列向量方程式來表示: £ = Ua - (3) 其中 E - 1 [£(z丨),£(z2),…Γ (4) U - · · · · • · * · * (5) a = [p〇.·*· .p« JT (6) A [A(Z丨),夯(Z2),…Γ (7) 其中 zi + 1 > Zj .200410126 V. Description of the invention (3) Σ p ^ 'n where (1) where P (z) is a Fourier transform function (hereinafter referred to as the z-function), and the coefficient Pn is the impulse response of the FIR filter, where N Is the length (order) of the FIR filter. Let // (z) be the desired frequency response of the FI r filter and the frequency response error function E is: £ 1ζ)-Σ P «z * n-^ Cz) ^ (2) Equation (2) can be evaluated On a linear density grid from ω = 0 to Jiang. For an F IR filter with a length N, a 4 N frequency grid point is sufficient to represent the efficiency of the filter. If the frequency band edge does not fall on the set frequency grid point, it is necessary to add extra grid points to correspond to the missing frequency band edge. At this time, it can be expressed by the following vector equation: £ = Ua-(3) where E-1 [£ (z 丨), £ (z2), ... Γ (4) U-· · · · • · * · * ( 5) a = [p〇. · * · .P «JT (6) A [A (Z 丨), ram (Z2), ... Γ (7) where zi + 1 > Zj.
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在本發明加權最小均方根方法的設計中, 〒ir广)} ’皮極小化’其中,^是最小均方根加權值 (/aSweighting value)。最佳化的解決方案可 使用下列方程式來表示: /、 (8) 只在對角線具有函In the design of the weighted minimum root mean square method of the present invention, 〒ir wide)} 'skin minimization', where ^ is the minimum root mean square weighting value (/ aSweighting value). The optimized solution can be expressed using the following equation: /, (8) Only functions with diagonals
a = (iTRUriTR^ 其中R可表示成如下的一對角線矩陣 數值q、r2、···:a = (iTRUriTR ^ where R can be expressed as a diagonal matrix as follows: Values q, r2, ...:
(9)(9)
一線性相位低通濾波器的範例,其使用一指數函數代 入上述方程式(1 ) 一( 9 )的線性相位項中,並與習知做比較 ,其比較結果示於第7圖。上述比較基準為取樣頻率之頻 帶邊緣在0.15、濾波器長度為51且所有對角線值為i的條 件下。從第7圖中可看到,使用本發明最小均方根方式所 配置的濾、波器具有遠小於習知方式的漣波振盈音量 (ripple magnei tude)。又,使用本發明最小均方根方弋 所配置的濾波器在靠近頻帶邊緣處的效率,在靠近頻帶"邊 緣處使用一較大的rn值時,相較其它地方可減少更多的效 率損耗進而顯著地增加此處執行的效率。這是本發明採用 最小均方根技術的重點所在。 如上述’本發明數位式音訊取樣的方法包含安聲一^ 體程式於一電腦内,用以藉由内置的加權最小均方根演^An example of a linear phase low-pass filter uses an exponential function to substitute the linear phase term of the above equations (1) to (9), and compares it with the conventional one. The comparison result is shown in FIG. The above reference is based on the condition that the band edge of the sampling frequency is 0.15, the filter length is 51, and all diagonal values are i. It can be seen from FIG. 7 that the filter and the wave filter configured by using the minimum root mean square method of the present invention have a ripple magnei tude which is much smaller than that of the conventional method. In addition, the efficiency of the filter configured using the minimum root-mean-square method of the present invention near the edge of the frequency band, when using a larger rn value near the edge of the frequency band, can reduce more efficiency than other places The losses in turn significantly increase the efficiency of the execution here. This is the focus of the present invention using the minimum root mean square technique. As described above, the method of digital audio sampling of the present invention includes a sound program in a computer for performing weighted minimum root mean square calculation by built-in ^
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法來什算一取樣速率轉換(SRC)濾波器的脈 權最小均方根演算法也可配置在一數位作響應。該加 定積體電路内,藉以執行,並不限定於器或一特 = 本發明可效地極小化軟體配置: = : = 雖然本發明已以較佳實施 限定本發明,任何熟知此技術 精神及範圍内,當可做更動與 圍當視後附之申請專利範圍所 例揭露如上,然其並非用以 之人士,在不脫離本發明之 潤飾,因此本發明之保護範 界定者為準。The method of calculating the minimum root mean square of the pulse weight of a sampling rate conversion (SRC) filter can also be configured to respond in one digit. The implementation of the add-on integrated circuit is not limited to a device or a special = the present invention can effectively minimize the software configuration: =: = Although the present invention has been limited to the present invention with a better implementation, anyone who is familiar with the spirit of this technology Within the scope, when the scope of the patent application attached as the modification and encirclement is disclosed as above, but it is not used by those who do not depart from the embellishment of the present invention, the scope of protection of the present invention shall prevail.
200410126 圖式簡單說明 為讓本發明之上述及其它目的、特徵、與優點能更顯 而易見’下文特舉一較佳實施例,並配合所附圖式,作詳 細說明如下: 第1圖顯示一典型數位式音訊系統的方塊圖; 第2圖是一 32赫茲取樣速率的波形圖; 第3圖是一藉由不連續傅利葉轉換(DFT)所產生的第i 圖波形的頻率響應圖; 第4圖是取樣頻率為512赫茲時所產生的第1圖的頻率 響應圖; 第5圖是一用以改變取樣速率的取樣速率轉換器⑺^㈡ 的方塊圖; 第6圖顯示一本發明數位式混音器方塊圖;及 第7圖顯示一使用習知方式與本發明加權最小均方根 方式進行最佳化所產生的濾波器頻率響應的比較圖。 [符號說明] 11 音 效 卡 12 音 源 機 13 光 碟 播 放 器 14 卡 匣 播 放 器 15 數 位 式 混 音器 16 後 端 電 路 17 左 揚 聲 器 18 右 揚 聲 器 41 内 插 裝 置200410126 Brief description of the drawings In order to make the above and other objects, features, and advantages of the present invention more obvious, a preferred embodiment is given below, and in conjunction with the accompanying drawings, the detailed description is as follows: Figure 1 shows a typical Block diagram of a digital audio system; Figure 2 is a waveform diagram with a sampling rate of 32 Hz; Figure 3 is a frequency response diagram of the waveform of the i-th waveform generated by discontinuous Fourier transform (DFT); Figure 4 Fig. 1 is a frequency response diagram of Fig. 1 generated when the sampling frequency is 512 Hz; Fig. 5 is a block diagram of a sampling rate converter ⑺ ^ ㈡ for changing the sampling rate; Fig. 6 shows a digital hybrid of the present invention Fig. 7 is a block diagram of a microphone; and Fig. 7 shows a comparison diagram of a filter frequency response generated by using the conventional method and the weighted minimum root mean square method of the present invention for optimization. [Symbol description] 11 sound card 12 sound source machine 13 disc player 14 cassette player 15 digital mixer 16 rear circuit 17 left speaker 18 right speaker 41 plug-in device
0702-7568TW(nl) ;90P144 ;Sue .ptd 第10頁 200410126 圖式簡單說明 42 低通渡波器 43 定標器 61 有限脈衝響應低通濾波器(F I R濾波器) 62 加法器 6 5 混音器0702-7568TW (nl); 90P144; Sue.ptd Page 10 200410126 Brief description of the diagram 42 Low-pass crossing wave 43 Scaler 61 Finite impulse response low-pass filter (F I R filter) 62 Adder 6 5 Mixer
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