TW200409933A - A digital controlled linear swept frequency mode for FMCW radar altimeter - Google Patents
A digital controlled linear swept frequency mode for FMCW radar altimeter Download PDFInfo
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200409933 五、發明說明(1) 詳細說明 本發明係有關一種調頻連續波雷達高度計(FMCW hcUr A11 i me ter ),尤指具有數位控制式線性掃頻模式之調頻連 續波雷達高度計。 傳統連續波雷達南度计之基本技術是發射一頻率隨日夺間變 化的直線掃頻訊號,直線掃頻訊號傳至地面或物體將產生 回波,回波訊號隨距離高低產生相對的時間延遲,與發射 訊號混波後產生差頻(Beat Frequency)輸出,此時間延遲 函數經轉換計算後,可求得高度距離。 傳統連續波雷達高度計亦多採用電壓控制振盪 器VC0(Voltage Controlled Oscillator)技術產生直線掃 頻訊號。在實際的環境中,常會有許多外在的因素來影響 高度計的運作及演算;例如飛行時高度計與地面的角度造 成的誤差、高度計附近之多重反射造成的影響、不同高度 計之問的互相干擾、都普勒訊號的混合問題。傳統直線掃 頻訊號若維持於固定掃描頻寬,則電路設計之複雜度高, 且不易保持量測之精準度。另外,先前技藝利用VC0技術 產生的直線掃頻訊號,其線性度及精破度不夠準確,所以 在應用方面,常常需要多餘的電路去做計算上的校正。 本發明FMCW連續波雷達高度計之數位控制式200409933 V. Description of the invention (1) Detailed description The present invention relates to a frequency-modulated continuous wave radar altimeter (FMCW hcUr A11 i me ter), especially a frequency-modulated continuous wave radar altimeter with a digitally controlled linear frequency sweep mode. The basic technology of the traditional continuous wave radar southmeter is to transmit a linear sweep signal whose frequency changes with day to day. When the straight sweep signal is transmitted to the ground or an object, it will generate an echo, and the echo signal will have a relative time delay with the distance. After mixing with the transmitted signal, a beat frequency output is generated. After this time delay function is converted and calculated, the height distance can be obtained. Conventional continuous wave radar altimeters also use VC0 (Voltage Controlled Oscillator) technology to generate linear frequency sweep signals. In the actual environment, there are often many external factors that affect the operation and calculation of the altimeter; for example, the error caused by the angle of the altimeter and the ground during flight, the effect of multiple reflections near the altimeter, the mutual interference between different altimeters, The problem of mixed Doppler signals. If the traditional linear sweep signal is maintained at a fixed sweep bandwidth, the complexity of the circuit design is high and it is difficult to maintain the accuracy of the measurement. In addition, the linear sweep signal generated by the previous technology using VC0 technology is not accurate enough in linearity and precision. Therefore, in application, redundant circuits are often required to perform calculation correction. Digital control type of FMCW continuous wave radar altimeter of the present invention
200409933 五、發明說明(2) ---- 線性掃頻模式為解決上述先前技藝雷達高度計之 缺點,利用直接數位合成DDS(Direc1: —Dtgitai200409933 V. Description of the invention (2) ---- Linear frequency sweep mode In order to solve the above shortcomings of the prior art radar altimeter, a direct digital synthesis DDS (Direc1: —Dtgitai
Synthesis)可程式化之特性,產生高精確度及線性度 佳的 Chlrp SWeep(Linear Frequency Sweep)波形。本發 明特點之一係採取上掃頻及下掃頻方式,且於週期 間^上一段隨機產生的不定時延遲的掃描形式,以解決不 同高度計之間的互相干擾及都普勒訊號的混合問題。為使 計算距離之DSP模組電路能單純化,本發明另一特點在藉 由控制DDS之輸出頻寬使差頻值能維持於2〇1(112之中'頻範園 内0 本發明FMCW連續波雷達高度計數位控制式線 性掃頻模式之特點列述如下: 1 · 發射掃頻波形 U采目取/掃頻及下掃頻方式以解決距離與都普勒訊號混 β的現象。 b券服週加上一段隨機產生的不定時延遲的掃描形式以 見服不同兩度計間的干擾。 將系統改採以上述兩項方法後,所產生的波形將合如第丄 圖所示:其中rl及r2為DSP隨機產生的時間延遲,曰 可 以區隔不同高度計間的訊號干擾,其方法參考曰表 (一)說明如下·· 丄Synthesis) can be programmed to generate Chlrp SWeep (Linear Frequency Sweep) waveforms with high accuracy and linearity. One of the features of the present invention is to adopt the frequency sweeping method and frequency sweeping method, and the scan pattern randomly generated in the previous period is randomly delayed to solve the problem of mutual interference between different altimeters and the mixing of Doppler signals. . In order to simplify the distance of the DSP module circuit for calculating distance, another feature of the present invention is to maintain the difference frequency value at 2101 (112 out of '112 in the frequency range garden) by controlling the output bandwidth of the DDS. The characteristics of the wave radar height-count bit-controlled linear frequency sweep mode are described as follows: 1 · Transmitting sweep waveform U sampling / frequency sweeping and down sweeping methods to solve the phenomenon that the distance and Doppler signal are mixed with β. Week plus a randomly generated scan pattern with irregular delay to meet the interference between different two-meter meter. After the system is changed to the above two methods, the resulting waveform will be as shown in the figure below: where rl And r2 is the time delay randomly generated by the DSP, which can separate the signal interference between different altimeters. The method is described below with reference to the table (1).
200409933 五、發明說明(3) a· 啟始化(Initialization): • Mode =0 (FS -100MHz) •執行上掃頻(ΐ〇1),並計算高度值。 b· ,τ1 ,1:11時段,主要工作内容如下: • 10 2 :執行下掃頻 • r 1 :隨機時間延遲 • 111 :執行上掃頻 於此時間内,亦依據(式二)解決都普勒混合現象、高度計 間之干擾消除及物體比對等等執行DSP之資料處理以求出 確實的高度值。 c·在處理過程中,若fb不在3k〜10kHz區間,則會執行下 述處理方法: •若f b > 1 0 Κ Η z ’則降低掃頻速率,例如由m 〇 d e 0切換到 Mode 1 ;若fb仍大於ΙΟΚΗζ,則續降;最低至 mode 4 (sweep rate= 6.25MHz/0. 0 1 sec) •若fb<3KHz,則增加掃頻速率,最高至m〇(ie 〇 (sweep rate=100MHz/0. Olsec) d. ΐ12 ’r2 ’ΐ21時段之作法如同上述b,c兩項,依此類 推。 2 · 掃頻模式之切換 為使計算距離之DSP模組電路能單純化,且維持量測之精 準度;故藉由控制D D S之輸出頻寬使差頻值能維持於2 & η z 之中頻範圍内。由式(一)顯示,當高度計離地跟離愈高200409933 V. Description of the invention (3) a. Initialization: • Mode = 0 (FS -100MHz) • Perform up-sweep (ΐ〇1) and calculate the height value. b ·, τ1, 1:11, the main tasks are as follows: • 10 2: Execute the down sweep • r 1: Random time delay • 111: Execute the up sweep within this time, also solve the problem according to (Formula 2) Pooler phenomenon, interference elimination between altimeters, object comparison, etc. are performed by DSP data processing to obtain the exact height value. c. In the process, if fb is not in the range of 3k ~ 10kHz, the following processing methods will be performed: • If fb > 1 0 Κ Η z ', then reduce the frequency sweep rate, for example, switch from m 0de 0 to Mode 1 ; If fb is still greater than ΙΟΚΗζ, continue to drop; the lowest is mode 4 (sweep rate = 6.25MHz / 0. 0 1 sec) • If fb < 3KHz, increase the sweep rate, up to m〇 (ie 〇 (sweep rate = 100MHz / 0. Olsec) d. The method of ΐ12 'r2' 作 21 is the same as the above two items b and c, and so on. 2 · The frequency sweep mode is switched so that the DSP module circuit that calculates the distance can be simplified, and Maintain the accuracy of the measurement; therefore, by controlling the output bandwidth of the DDS, the difference frequency value can be maintained within the 2 & η z intermediate frequency range. As shown by formula (1), when the altimeter is higher than the ground, the higher the distance
第7頁 200409933 五、發明說明(4) 時,因回波時間長,故產生之 寬F s與差頻f b成反比關係,妨’ ’、‘大;然因掃頻頻 值於一定頻寬内。 故可控制掃頻頻寬以維持^之 本發明將掃頻模式分成五種% I _ 種檄彳+私 ^ w的祀雕來 、工之掃描斜率如圖(三)所 距離愈高時,其掃頻頻寬愈窄广一)所#不^ ’當高度計離地 愈低時,其掃頻頻寬愈寬。$ &反之’當兩度計離地距離 所使用的掃描頻率。五種檄^、、、會依照目前的距離來改變 不 表(一)掃頻模式 模式 掃頻範圍(MHz) 頻寬Page 7 200409933 V. Description of the invention (4), because the echo time is long, the width F s generated is inversely proportional to the difference frequency fb, so '', 'are large; however, because the frequency value of the frequency sweep is within a certain bandwidth . Therefore, the swept frequency bandwidth can be controlled to maintain ^ The present invention divides the sweep mode into five kinds of% I _ 檄 彳 + private ^ w sacrifice, the scan slope of the work as shown in Figure (3), the higher the distance, the The narrower the sweep frequency, the wider the bandwidth. When the altimeter is lower from the ground, the sweep frequency is wider. $ & Conversely ’The scanning frequency used when the distance from the ground is measured twice. The five types of 檄 ^ ,,, will change according to the current distance. Table (1) Sweep mode Mode Sweep range (MHz) Bandwidth
Mode 4Mode 4
Mode 3 Mode 2 4250-4275 5MHzMode 3 Mode 2 4250-4275 5MHz
其實際之運作如下: 若fb在3k— 10kHz區間,貝,丨掃/如 1 0 kHz區間,則會切換掃頻极,模式不變;若f b不在3 k — •若fb>10KHz,則降低掃頻y ,依下述原則處理。 Model ;若f b比仍大於! 0KHz,則續降例m〇de0切換到 4250 - 4256. 25 4250 - 4262.5 25¾ 5〇MH2 mode 4 (sweep rate=6.25MHz/0 〇13ec; •若fb<3KHZ’則增加掃頻速率,最高至_ 0 (sweepThe actual operation is as follows: If fb is in the range of 3k-10kHz, the scan frequency will be switched, and the mode is unchanged; if fb is not in 3k— • If fb> 10KHz, decrease Sweep frequency y is processed according to the following principles. Model; if f b ratio is still greater than! 0KHz, then continue to drop the m0de0 to 4250-4256. 25 4250-4262.5 25¾ 5〇MH2 mode 4 (sweep rate = 6.25MHz / 0 〇13ec; • If fb < 3KHZ 'then increase the frequency sweep rate, up to _ 0 (sweep
第8頁 200409933 五、發明說明(5) rate = lOOMHz/O. 01 sec) 以下說明本發明之工作原理。 1_待測物距離與掃頻頻寬關係 差頻 (fb: a beat frequency)可由以下計算式獲得: fb= (2R/cT)Fs 式(一) 其中 T:掃頻時間(sweep time), c:光速(the speed of light),Fs:掃頻頻寬(sweep bandwidth), R:待測 物體的距離 由式(一)得知當R愈大’ f b亦愈大;而f b即經中頻據波送至 DSP模組電路,以計算距離。故為保持不變之頻寬以簡化 設計之複雜度並保持量測之精準度,fb之值宜維持於一定 頻寬内,故改變Fs值為一最佳之方式;因此,只與。即成 反比關係。 2.解決都普勒訊號混合的現象 若高度計之載具處於移動狀態,則式(一)之fb即包含距離 與都普勒訊號混合的資料,故若欲解析出確實距離則需採 取上掃頻及下掃頻式,如式(二)所示。 式( fb= (2R/cT)Fs= kR 一 fbl = kR— fd , fb2 = kR+f d —R= ( f bl + f b2 )/2k , f d= ( f b2-f bl )/2Page 8 200409933 V. Description of the invention (5) rate = 100 MHz / O. 01 sec) The following describes the working principle of the present invention. 1_ The relationship between the distance between the object to be measured and the sweep frequency bandwidth (fb: a beat frequency) can be obtained by the following formula: fb = (2R / cT) Fs Formula (1) where T: sweep time, c : The speed of light, Fs: sweep bandwidth, R: The distance of the object to be measured is determined by formula (1). When R is greater, fb is greater; and fb passes the intermediate frequency data. The wave is sent to the DSP module circuit to calculate the distance. Therefore, in order to maintain the same bandwidth to simplify the complexity of the design and maintain the accuracy of the measurement, the value of fb should be maintained within a certain bandwidth, so changing the Fs value is an optimal way; therefore, only with. That is an inverse relationship. 2. Solve the phenomenon of Doppler signal mixing If the vehicle of the altimeter is in a moving state, fb of formula (1) contains the data of distance and Doppler signal mixing, so if you want to analyze the exact distance, you need to scan up Frequency and down-sweep mode, as shown in formula (2). (Fb = (2R / cT) Fs = kR-fbl = kR— fd, fb2 = kR + f d —R = (f bl + f b2) / 2k, f d = (f b2-f bl) / 2
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第10頁 200409933 圖式簡單說明 圖示說明 明為進—步瞭解本發明内容,以下將配合相關圖示詳細說 上,MCW連續波雷達高度計數位 控制式線性掃頻模式之掃頻波形。 控月_連續波雷達高度計數位 工第s ®在*,貝模式之掃描模式切換原則。 發明⑽⑽連續波雷達高度計數位 工筮=、,、,掃頻模式之五種掃描模式斜率。 :4a圖係FMCW雷達發射波與反射波之調頻曲 綠圖。 f 4b圖係FMCW雷達發射波與反射波之差頻。 f 5圖係本發明FMCW連續波雷達高度計數位 控制式線性掃頻模式之系統架構圖。 第1圖係說明本發明FMCW連續波雷達高度計 數位控制式線性掃頻模式之掃頻波形,其中t〇l,t丨j, t21 ,···等表示上掃頻波形,t02,tl2,ΐ22…等表示下掃頻 皮幵y τ Γ 2表示隨機時間延遲,其掃頻模式視差頻大 小’有五種掃頻模式可供選擇。 第2圖係說明本發明一較佳實施例中,當頻差fb大於 ΙΟΚΗζ時,可降低掃頻速率,例如,自M〇de 〇切換至M〇de 1 (如表一所示),若頻差fb仍大於ΙΟΚΗζ,則繼續降低其Page 10 200409933 Schematic description of the diagram Illustrated to further understand the content of the present invention, the following will be described in detail in conjunction with the related diagram, MCW continuous wave radar height count bit controlled linear sweep mode sweep frequency waveform. Control of the month_continuous wave radar height count bit The scanning mode switching principle of the s ® in *, bay mode. Invented: CW radar height count bit, 筮 = ,,,, five scan mode slopes of frequency sweep mode. : 4a is a green diagram of the FM curve of the FMCW radar transmitted and reflected waves. f 4b is the frequency difference between the FMCW radar transmitted wave and reflected wave. Figure 5 is a system architecture diagram of the FMCW continuous wave radar height-counting-controlled linear frequency sweep mode of the present invention. Figure 1 illustrates the frequency sweep waveforms of the FMCW continuous wave radar height-count bit-controlled linear frequency sweep mode of the present invention, where t0l, t 丨 j, t21, ..., etc. represent upsweep waveforms, t02, t12, ΐ22 … Etc. indicates that the lower sweep frequency 幵 y τ Γ 2 represents a random time delay, and its sweep mode has a parallax frequency of '5 sweep modes to choose from. FIG. 2 illustrates that in a preferred embodiment of the present invention, when the frequency difference fb is greater than 10KΗζ, the frequency sweep rate can be reduced, for example, switching from Mode 0 to Mode 1 (as shown in Table 1). The frequency difference fb is still greater than 10KΗζ, then continue to reduce it
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使頻差fb維持於3 KHz _ 當頻差fM、於3KHz日夺,則增加掃 KHz=間白反之’ 切換至Mode 3 (如表一所示)m,例如,自.心4 繼續增加其掃頻頻率d頻差二頻/fb仍小於,,則 間。 維持於3 KHz -丨0心之 第3圖係說明本發明肫“連續波雷 :工制式線性掃頻模式之五種掃:-率十# :者為斜率最大之Mode。,最下方者=:上 二差V頻差fb之大小選擇掃描模式斜率,可 於一定頻寬内’以簡化設計之複雜 度’並保持量測之精準度。 圖係說明FMCW雷達發射波U反射波2調 頸曲線之相互關係。 第4b圖係說明對應第4&圖1^(^雷逹發射波 ”之間的差頻時間關係,其中實線為發射 波’虛線為目標反射波。 第5圖係本發明“(^連續波雷達高度叶數位 ::式,性掃頻模式之系統架構圖,議工作原理以本 發明一較佳實施例說明如下·· 數位L旒處理器DSP 1透過直接數位合成器 出控制埠(digital i/0 port),使直接數位合 态 2輪出,例如,21 · 428〜24. 3MHz間之掃 頻訊號。 直接數位合成器DDS 2輸出掃頻訊號,經混波升Keep the frequency difference fb at 3 KHz _ When the frequency difference fM is captured at 3KHz, increase the sweep KHz = white and vice versa 'Switch to Mode 3 (as shown in Table 1) m, for example, since the heart 4 continues to increase its Sweep frequency d frequency difference two frequency / fb is still less than, then time. The third figure maintained at 3 KHz-0 heart is a description of the present invention. "Continuous wave ray: five sweeps of the linear sweep mode of the industrial system:-率 十 #: the mode with the largest slope., The bottom = : The slope of the upper two difference V frequency difference fb selects the scanning mode slope, which can be 'in order to simplify the complexity of the design' within a certain bandwidth and maintain the accuracy of the measurement. The relationship between the curves. Figure 4b illustrates the time-frequency relationship between the corresponding fourth & Figure 1 ^ (^ 雷 逹 出 波 ", where the solid line is the transmitted wave and the dashed line is the target reflected wave. Figure 5 is the original The invention "(^ continuous wave radar height leaf digital :: type, the frequency sweep mode system architecture diagram, the working principle is described in a preferred embodiment of the present invention as follows ..." Digital L 旒 Processor DSP 1 through a direct digital synthesizer Out the control port (digital i / 0 port), to make the direct digital combination 2 round out, for example, a frequency sweep signal between 21 · 428 ~ 24. 3MHz. The direct digital synthesizer DDS 2 outputs a frequency sweep signal, which is mixed up
200409933 圖式簡單說明 頻3及倍頻4,再經發射/接收模組5功率放大, 使得雷達高度計輸出,例如,4· 25〜4. 35 GHz間之 掃頻波(FMCW)。 3·接收之RF訊號與發射RF訊號經混波器(Mixer )解 調為差頻(fb ’beat frequency),此差頻頻率正比 於高度值 。 4· DSP 1透過增益控制STC 6控制璋(digital I/O port) 控制增益控制ST C 6將輸入之差頻訊號處理後,使其輸出 頻率落於中頻IF頻寬内,例如2 〇 kHz,再經由A/D擷取IF訊 號並數位化 。 5 · IF訊號數位化之後,經快速傅立葉轉換(F F τ )計算,找 出最大功率(power)值之頻率(DSP之工作)。 6 ·此頻率就是地表反射訊號經上述處理後所產生之頻 率,正比於高度,經適當之比率(s c a 1 e )轉換就得到高度 值。若此頻率不在3〜ΙΟΚΗζ間,則依本發明說明所述方法 選取適合之掃描模式,控制DDS 2輸出,例如, 21· 428〜24, 3MHz間之掃頻訊號(DSp之工作)。 由上述說明可以瞭解’本發明採取上掃頻及下掃 頻方式’且於週期間加上一段隨機產生的不定時 延遲的掃描形式’並依不同高度切換不同掃頻頻 寬’可以解決不同高度計之間的互相干擾及都普 勒訊號的混合問題。本發明!^“連續波雷達高 度計數位控制式線性掃頻模式係由以下申請專200409933 The diagram briefly explains the frequency 3 and the frequency doubling 4, and then the power is amplified by the transmitting / receiving module 5 so that the radar altimeter outputs, for example, a swept frequency wave (FMCW) between 4.25 to 4.35 GHz. 3. The received RF signal and the transmitted RF signal are demodulated by a mixer (Mixer) to a difference frequency (fb 'beat frequency), and the difference frequency is proportional to the height value. 4. DSP 1 through gain control STC 6 control 璋 (digital I / O port) Control gain control ST C 6 Processes the input differential frequency signal so that its output frequency falls within the intermediate frequency IF bandwidth, for example, 2 kHz Then, the IF signal is captured by A / D and digitized. 5 · After the IF signal is digitized, it is calculated by the fast Fourier transform (F F τ) to find the frequency of the maximum power value (work of the DSP). 6 · This frequency is the frequency generated by the surface reflection signal after the above processing. It is proportional to the height, and the height value can be obtained by converting the appropriate ratio (s c a 1 e). If the frequency is not between 3 and 10KΗζ, then according to the method described in the present invention, select a suitable scanning mode and control the DDS 2 output, for example, a swept signal between 21 · 428 ~ 24, 3MHz (the operation of DSp). From the above description, it can be understood that 'the present invention adopts an up-sweep and a down-sweep mode' and adds a period of randomly generated non-time-delayed scan form during the period 'and switches different sweep frequency bandwidths according to different heights. Mutual interference between them and the problem of mixed Doppler signals. The present invention! ^ "Continuous wave radar high counting bit control linear frequency sweep mode is
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US9660605B2 (en) | 2014-06-12 | 2017-05-23 | Honeywell International Inc. | Variable delay line using variable capacitors in a maximally flat time delay filter |
US10018716B2 (en) | 2014-06-26 | 2018-07-10 | Honeywell International Inc. | Systems and methods for calibration and optimization of frequency modulated continuous wave radar altimeters using adjustable self-interference cancellation |
CN113671504A (en) * | 2021-08-26 | 2021-11-19 | 中国空间技术研究院 | Anti-echo interference difference frequency design method for distributed double-star imaging altimeter |
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