SU362254A1 - ALL-UNION-, ^. ^, .-.:.,. F, if ^ •; 'g • m' •: •> &} lr ^ • ~ ir, \ #f ^ A? T; iifiU - ^ - l ^ 'b • ^ •.?> & yi | - Google Patents

Description

one

The invention relates to a measurement technique and can be used in various radio metering devices, in particular, in radar, in radio navigation, in devices for automatic control of technological processes.

Known digital phase meters based on using counting pulses to measure time intervals, proportional phase differences, or use phase discriminators with subsequent digital conversion of output levels to the value of the measured phase are not useful for measuring the phase of high-frequency filling of pulsed radio signals due to insufficient speed and complexity devices that stabilize the amplitude of the pulses with the preservation of the phase.

To increase the speed of the digital phase meter and simplify the device in the proposed phase meter, the inputs n of the threshold phase discriminators are connected to the corresponding n outputs of the phase shifter, the other n inputs are connected to the input device of the measuring channel, the outputs n of the threshold phase discriminators are connected to the n inputs of the path converter, to the corresponding outputs of which are turned on descrambler.

FIG. 1 shows the block diagram of the described phase meter; in fig. 2 is a block diagram of an associative positional code to positional converter; in fig. 3 - output voltage diagrams.

The digital phase meter has two inputs, the first of which (pulsed radio signal f / nsjb) is supplied with the high-frequency filling phase of which is to be measured, and the reference nanometer is fed to the other input.

Uon, whose phase is taken as zero. The measured signal is in phase distributed to the signal inputs of threshold phase discriminators (PFD) 2, the combination of which (PFD1-g-PFD) forms a p-channel phase discriminator 3. The reference voltage Uon is split into p voltages with a known phase using multiphase phase splitter 4, then each of the voltages is fed to a corresponding discriminator,

as shown in FIG. 1. The reference voltage at the inductance S is split by the phase shifter and at the adjacent outputs of the phase expansion, „,„, 360 °

l has a mutual phase shift DF -

2

which corresponds to one discrete phase measurement interval. In this case, the reference voltage is applied to the discriminator PFDH

O / QO

With the initial phase, -discrimination4 / Z torus PFDg - voltage with a phase of 90 ° +, 360 °. + 1- - and so on. 4l 2p, “The phase displacement of the reference voltage by an amount equal to half of the discrete dimension,” ,, i, i.e., is necessary for linking from 4 / g of counting to the center of the discrete interval. The output voltages of the discriminators are supplied to the converter 6 of the associative-positional code, the block diagram of which is shown in FIG. 2, where the logical processing of the output voltage of discriminators is made in order to turn it into a 15 position code, for which the converter (7n-1) coincidence circuits 7 and inverters 8 are included in the converter The signals from the output of the converter 6 are "decipher 9, where the transformation of the measurement result in the form of a position code into a digital form of a certain number system according to well-known methods is performed. The measurement results in digital form 25 are received and the output of the phase meter 10. When signals are applied to a digital phase meter in the discriminator consisting of a phase discriminator and a threshold device, the following processes occur: a) depending on the phase shift of the input signals, the output voltage of the phase discriminator takes a positive, negative, or zero value; b) using the threshold device, the output voltage of the phase discriminator is normalized, while the symbol "unit" is assigned to all values of the output voltage of one sign, i.e., the presence of an output pulse of the threshold circuit (potential "unit), and The zero symbol is attributed to the zero symbol and the opposite sign, i.e., the absence of an output pulse of the threshold circuit (-potential 45 "zero). Since the dependence of the output voltage of the phase discriminator f / sHs on the magnitude of the phase shift of the input signals is governed by the expression / Vyozf, where K is the proportionality factor, then at the output of the threshold device there will be a "one at -90" and "zero at -90 ° f 90 °. Due to the fact that the reference voltage 55 is applied to the PFD from the phase dissipator. The " 360 ° has an initial phase of 90 ° -f -, at the output of this PFD, the unit will appear at o - -180 ° (the measured phase is 30 (35 (35)). For the subsequent PFDs, the unit areas are shifted every time by one measurement increment, which is illustrated by the diagram of the PFD output voltages in FIG. 3 From consideration of FIG. 3, it can also be seen that the number of the discrete interval in which the measured phase is located can be determined by a logical comparison of the output PFD potentials and extraction from the set of PFDs having a unit at the output, the one with which has a zero at the output. For example: for the 1st discrete interval it is PFDb for n-1th -, for d / g + 1-st - PFDg, for 2n-1 - PFDtg The position of the measured phase in the zero discrete interval corresponds to zero at the output of all PFD . The determination of the number of the discrete interval in which the measured phase is located is carried out using an associative-positional code to a positional converter, which is explained with reference to FIG. 2 and 3. Assume that the measured phase belongs to the 2nd sampling. At the same time, at the output of the PFD) and PFDg we have a unit, at the outputs of the remaining PFD we have zero. As can be seen from FIG. 2, in this case, the unit passes only to the output of SSg, where the condition of coincidence of the inverted PFDz zero and PFD2 units is satisfied. For all other CCs, the match conditions are not met. Similarly, the converter of the associative positional code also acts for other values of the measured phase, with the exception of the zero interval, where there are no signals at all outputs of the converter simultaneously. Positional code from the output of the converter is fed to the decalcator where it is attached to a digital device. Subject of the Invention Digital phase meter for measuring the phase of high-frequency filling of pulsed radio signals in the range from 0 to 360 °, divided into 2p discrete and 1 interval of multi-phase discriminator containing a multi-phase a phase splitter, a code converter and a deflector, characterized in that, in order to increase the speed and simplify the device, the inputs n of the threshold phase discriminators are connected to tvetstvuyuschimi fazorasschepitel n outputs, n inputs other - to input "th channel of the measuring device, n outputs of the phase discriminator threshold n inputs connected to respective outputs of the transducer which is included deschifrator.

i

L.

I j. i i J J. 1

Uon

I I I

 V

W Rig 1

from P1RLP e

from PGDP 0

from shrl-} 0

about / p / TRD

omlTPAi