RU2622399C1 - Quasi-mono-pulse secondary radar - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: device contains an antenna, a block of controlled phase shifters, an adder, a transmit-receive switch, a receiver, a power divider, a controlled delay element, six keys, three decoders, three detectors, an amplitude detector and an angular discriminator connected in a specific way.

EFFECT: increasing the accuracy of measuring the angular coordinates of the aircraft by eliminating its dependence on the doppler frequency addition in the response signals.

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Description

The invention relates to the field of radar, and in particular to the field of secondary monopulse radar (MPL) and can be used in land and air-based radar systems that have a simple technical implementation and are designed to monitor the air situation.

The well-known "Monopulse radar" (RF patent №2122218, IPC G01S 13/44, publ. 11/20/1991), which contains a Doppler frequency synthesizer, connected in series with the output of the reference channel receiver, a multi-channel Doppler frequency filter, a detector and a periodometer, the output of which connected to the first input of the signal processor, connected in series with the output of the multi-channel Doppler frequency filter multiplexer, local oscillator frequency converter, the second input of which is connected to the local oscillator output, power divider and, a second mixer, the signal input of which is connected to the first output of the frequency converter, a bandpass filter, an amplifier, a phase meter, the output of which is connected to the second input of the signal processor, the second output of the power divider connected to the heterodyne input of the first mixer, the output of the measuring channel receiver connected to the second input of the phase meter, the output of the Doppler frequency synthesizer is connected to the second input of the switch, the output of which is connected to the control input of the controlled attenuation circuit, the output is passive The amplifier is connected via a controlled attenuation circuit and a calibration signal path to a communication device of the receiving antenna-feeder device and the calibration signal path, the control input of the Doppler frequency synthesizer is connected to the second output of the signal processor, the third output of which is connected to the control input of the multiplexer.

The disadvantage of this analogue is the impossibility of verifying the identity of phase shifts in the channels for measuring the angular coordinate, which can lead to a bias in its estimation, as well as the complexity of the technical implementation due to the use of the phase method of measuring the angle. Also known is the device "Multichannel radar station" (RF patent No. 94032128, IPC G01S 7/40, publ. 07/20/1996), containing an antenna made in the form of two identical channels - left and right relative to the direction of radiation, each of which is located symmetrically about the axis of the antenna, with the possibility of forming two identical independent radiation patterns with spaced phase centers, the outputs of the left and right channels of the antenna through respectively the first and second controlled phase shifters are connected to common the odes of the first and second transmit-receive switches, the transmitting outputs of which are connected to the corresponding outputs of the equal arm power divider, the input of which is the input of the transmitter signal, the receiving outputs of the said transmit-receive switches are connected respectively to the inputs of the first and second amplifiers, the outputs of which are connected to the inputs of the phase detector the output of which is connected to the information input of the automatic phase adjustment unit, the first and second outputs of which are connected to the inputs of the first and second controlled phase shifters, a control transponder (KO) used as an external control signal generator, a KO strobe driver, the output of which is connected to the gate input of the automatic phase adjustment unit, and the input is connected to the output of the antenna's angle position sensor (DUP).

The disadvantage of this device is that for its operation it requires the presence of a control transponder, taken out in a predetermined direction relative to the SLL, as well as a system for evaluating the Doppler addition of the frequency of the received signals.

In this case, the direction-finding characteristic of this device, by taking into account the phase instability of the through channels, can be stabilized only by its position relative to the equal-signal direction of the antenna. However, such changes in the bearing characteristic as the slope and violation of its symmetry by this device cannot be eliminated.

Closest to the claimed device is "Monopulse radar with through phase channels" (RF Patent No. 2232403, IPC G01S 13/44, 7/40, H01Q 3/00, publ. July 10, 2004). The device comprises an antenna made in the form of two identical channels - left and right with respect to the direction of radiation, each of which is located symmetrically with respect to the axis of the antenna, with the possibility of forming two identical independent radiation patterns with spaced phase centers, the outputs of the left and right channels of the antenna through the first and the second controlled phase shifters are connected to the common terminals of the first and second transmit-receive switches, the transmitting terminals of which are connected to the corresponding to the output outputs of the equal arm power divider, the input of which is the input of the transmitter signal, the receiving outputs of the said transmit-receive switches are connected respectively to the inputs of the first and second amplifiers, the outputs of which are connected to the inputs of the phase detector, an automatic phase adjustment unit, the first and second outputs of which are connected to the inputs the first and second controlled phase shifters, a control transponder used as an external control signal generator, and a first KO strobe driver, input One of which is connected to the output of the antenna angular position sensor, a second KO strobe driver, an analog-to-digital converter, an inclination correction unit for the direction-finding characteristic are introduced, and an automatic phase adjustment unit is made with the first and second gate inputs and an additional output, while the output of the phase detector through analog -digital converter is connected to the information input of the node correction slope direction finding characteristics, the correcting input of which is connected to the additional output of the node and the automatic phase adjustment, and the output of the direction correction slope correction unit is connected to the information input of the automatic phase adjustment unit, the first and second gate inputs of which are connected respectively to the outputs of the first and second gate formers of the control transponder, the inputs of which are interconnected.

Monopulse radar, in which the automatic phase adjustment unit is made two-channel and contains the first error calculator, the first error averager, the half-sum node, the first adder, the first code converter, the driver control circuit, the output of the first the adder through the first register of the accumulated error is connected to its additional input, the outputs of the phase shifter control circuit form the first and second outputs of the automatic tuning node phase, and in the second channel, the second error calculator, the second error averager, the half-difference node, the second adder, the second code converter are connected in series with the “output-input” terminals, while the output of the second adder is connected to its additional input through the second accumulated error register, the output of the second code converter forms an additional output of the automatic phase adjustment unit, while cross-links between the first and second channels are introduced, connecting the output of the first error averager simultaneously with by the additional input of the half-difference node, and the output of the second error averager simultaneously with the additional input of the half-sum node, the information inputs of the first and second error calculators are connected to the information input of the automatic phase adjustment, and their gate inputs form the first and second gate inputs of the automatic phase adjustment node, respectively.

A disadvantage of the known prototype device is the dependence of the accuracy of estimating the angular coordinate on the Doppler frequency addition appearing in the response signal when the secondary radar and the aircraft are mutually moved with the transponder, the inability to operate without the use of a control transponder, which excludes its installation on aircraft (LA), as well as complexity technical implementation.

These disadvantages are due to the monopulse method of measuring the angular coordinate with through phase channels used in the prototype device. This method requires constant testing of the two receiving channels for the identity of their phase characteristics, since the uneven change in time leads to a bias in the estimation of the angle of the responder. To eliminate this drawback, the prototype device requires the use of a remote control transponder with a precisely known angular azimuthal coordinate. This circumstance limits the use of the prototype device to ground-based. In addition to this drawback, the prototype device reduces the accuracy of measuring the angle in the presence of a Doppler additive in the frequency of the response signal, the value of which is never known beforehand. This disadvantage is also due to the phase measurement method used, in which the value of the angle estimate depends on the frequency of the received signals. So, to measure the angular coordinate of an aircraft in a prototype device, the phase difference of the signals received by the antenna and taken from the left and right channels relative to the radiation direction of identical channels is determined

where: α is the angular coordinate of the aircraft, measured relative to the equal-signal direction (RSN) of the antenna;

d is the distance between the phase centers of the antenna forming the two reception channels;

λ is the wavelength of the received response signals (OS).

In the presence of mutual movement of the aircraft and the MRL, the wavelength of the received OS

where: f _pr - the frequency of the received OS

where: f ₀ - frequency emitted by the respondent aircraft OS;

- доплеровская добавка частоты принимаемых сигналов;

- Doppler frequency addition of received signals;

V is the speed of mutual movement of the aircraft and the SRL.

Substituting expression (2) in (1), taking into account (3), we obtain that the phase difference of the received signals by the two antenna channels will be determined not only by the value of the angle α, but also by the value of F _d

будет вызывать смещение оценки угла α. Для ликвидации смещения необходимо получать оценку F_д, которая всегда будет отличаться от истинного ее значения. Поэтому устройство - прототип будет всегда давать смещенную оценку угла α, даже при наличии канала оценки F_д, усложняющего реализацию измерителя и увеличивающего его стоимость. Этот недостаток будет еще более выражен при установке устройства-прототипа на борту ЛА за счет увеличения взаимной скорости перемещения запросчика и ответчика по сравнению с наземным базированием вторичной РЛС.The second term in (4), for

will cause a shift in the estimate of the angle α. To eliminate the bias, it is necessary to obtain an estimate of F _d , which will always differ from its true value. Therefore, the prototype device will always give a biased estimate of the angle α, even if there is an evaluation channel F _d that complicates the implementation of the meter and increases its cost. This disadvantage will be even more pronounced when installing the prototype device on board the aircraft due to an increase in the mutual speed of the interrogator and the defendant compared to ground based secondary radar.

In addition to the listed disadvantages of the prototype device, the phase method of direction finding with end-to-end phase channels used in it requires the presence of two channels simultaneously operating at the reception and the provision of a constant analysis of their identity, using the remote control transponder for this. Errors in the operation of such a system also lead to a bias in the estimation of the angle of the aircraft. As a result, the prototype device is complicated in technical implementation, and its use is limited to ground-based.

The main objective of the claimed invention is to eliminate the dependence of the accuracy of estimating the angular coordinate on the Doppler frequency addition in the response signals, ensuring the operation of the SXR (secondary monopulse radar) located on board the aircraft, as well as reducing the complexity and cost of its implementation.

The technical result achieved by the implementation of the claimed invention is to increase the accuracy of measuring the angular coordinate of the aircraft by eliminating its dependence on the Doppler frequency addition in the response signals.

The specified technical result is achieved by the fact that in the device containing the antenna, the outputs of which are connected to the inputs of the block of controlled phase shifters, the first adder, the receive-transmit switch and the receiver are connected in series, the second output of the receive-transmit switch is connected to the input of the power divider, the outputs of which are connected to the inputs of the block of controlled phase shifters corresponding to them by number, the signal outputs of which are connected to the inputs of the first adder, an additional controlled element Arms connected in series with the first key, the first decoder, the first detector, the amplitude detector in series, the second key, the second decoder, the second detector, the third decoder and the third detector in series, as well as the third, fourth, fifth, sixth keys and an angular discriminator, the first and the second inputs of which are connected respectively with the outputs of the third and fourth keys, and the output is with the second input of the sixth key, the output of which is the output of the device, the first input of which is controlled the delay element is connected to the second inputs of the first, second and third decoders and the third input of the angular discriminator and serves as the input of the address code, the second input of the controlled delay element is connected to the first input of the block of controlled phase shifters, the first input of the first key and the output of the first detector, the output of which is connected to the first the input of the third key, the second input of which is connected to the output of the first decoder, the outputs of the second and third decoders are connected respectively to the second inputs of the fourth and fifth keys, the output of the latter is the second output of the radar, the output of the second detector is connected to the first input of the fourth key and to the second input of the block of controlled phase shifters, the output of the third detector is connected to the first inputs of the fifth and sixth keys, the output of the amplitude detector is connected respectively to the first input of the third decoder and the second the input of the first key, and its input with the output of the receiver, the output of the controlled delay element is connected to the first input of the second key, and the angular discriminator contains a split delay line, the signal input of which is the first input of the angular discriminator, and its control input is connected to the third input of the angular discriminator, the output of the controlled delay line is connected to the first inputs of the difference circuit and the second adder, the second input of the angular discriminator is connected to the second inputs of the difference circuit and the second an adder whose output is connected to the input of the divider of the ratio calculator, the input of which is divisible is connected to the output of the difference circuit, the output of the ratio calculator is the output of the angles first discriminator and the antenna is formed, for example, in the form of a phased array antenna.

The introduction of new blocks and connections into the known device made it possible to measure the angular coordinate in a quasi-monopulse method using the specifics of interval coding of the response signals received by the secondary radar and increase the measurement accuracy by eliminating the dependence of the angular coordinate estimate on the Doppler frequency shift in the response signals.

The invention is illustrated by drawings, where:

in FIG. 1 shows a structural diagram of the claimed invention;

in FIG. 2 is a block diagram of an angular discriminator block;

in FIG. 3, FIG. 4a, b, c, d, d, fig. 5a, b, c, d, e and FIG. 6 are graphs explaining the operation of the claimed device, and the following notation is introduced:

1. Antenna

2. Block controlled phase shifters

3. The first adder

4. Transmit-receive switch

5. Receiver

6. Power divider

7. The first key

8. The first decoder

9. The first detector

10. Amplitude detector

11. The second key

12. Second decoder

13. The second detector

14. Third key

15. The fourth key

16. The fifth key

17. Third decoder

18. Third Detector

19. Sixth key

20. Corner discriminator

20.1 Controlled Delay Line

20.2 Difference scheme

20.3 Second adder

20.4 Relationship Calculator

21. Controlled delay element

The quasimonopulse secondary radar contains an antenna 1, the outputs of which are connected to the inputs of the block of controlled phase shifters 2, serially connected to the first adder 3, the receive-transmit switch 4 and the receiver 5, the second output of the receive-transmit switch 4 is connected to the input of the power divider 6, the outputs of which are connected to the signal inputs of the block of controlled phase shifters 2 corresponding to them by number, the signal outputs of which are connected to the corresponding inputs of the first adder 3, connected in series with the first the first key 7, the first decoder 8, the first detector 9, the amplitude detector 10 connected in series, the second key 11, the second decoder 12, the second detector 13, the input of the amplitude detector 10 connected to the output of the receiver 5, the third key 14, the fourth key 15, the fifth key 16, the third decoder 17, the third detector 18, the sixth key 19, the second input of which is connected to the angular discriminator 20, and the output is the output of the device and the controlled delay element 21, the output of which is connected to the first input of the second key 11, are connected in series the first input is connected to the second inputs of the first 8, second 12 and third 17 of the decoders, as well as the third input of the angular discriminator 20 and serves as the input of the address code, the first input of the third decoder 17 is connected to the output of the amplitude detector 10, which is connected to the second input of the first key 7, the second input of the controlled delay element 21 is connected to the first input of the block of controlled phase shifters 2, the first input of the first key 7 and the output of the first detector 9, the outputs of the first 9, second 13 and third 18 detectors are connected, respectively with the first inputs of the third 14, fourth 15 and fifth 16 keys, and the output of the second detector 13 is connected to the second input of the block of controlled phase shifters 2, the outputs of the third 14 and fourth 15 keys are connected, respectively, with the first and second inputs of the angular discriminator 20, and the output of the fifth key 16 is the second output of the radar, the second inputs of the third 14, fourth 15 and fifth 16 keys are connected respectively to the outputs of the first 8, second 12 and third 17 decoders.

The angular discriminator 20 contains a controlled delay line 20.1, the signal input of which is the first input of the angular discriminator 20, and its control input is connected to the third input of the angular discriminator 20, the output of the controlled delay line 20.1 is connected to the first inputs of the difference circuit 20.2 and the second adder 20.3, the second input the angular discriminator 12 is connected to the second inputs of the difference circuit 20.2 and the second adder 20.3, the output of which is connected to the input of the divider of the ratio calculator 20.4, the input of which is divisible is connected to the output of the circuit ra 20.2, the output of the ratio calculator 20.4 is the output of the angular discriminator 20.

Antenna 1 is made, for example, in the form of a phased antenna array.

Antenna 1, a block of controlled phase shifters 2, a first adder 3, a receive-transmit switch 4, and a power divider 6 can be performed, for example, as separate devices, in the case of a passive phased antenna array (PAR), or can be combined in one device - active PAR (AFAR), each element of which contains both a transmitting channel and a receiving one. The implementation of each of the listed blocks is described separately, for example, [1], and when combined in the AFAR [2].

Each of the decoders: the first 8, second 12 and third 17 can be performed as delay lines with taps, the position of which corresponds to the time intervals of the OS interval codes for this requested aircraft [3].

All three detectors 9, 13 and 18 are threshold devices, the execution of which, like all keys, adders and difference schemes, has standard implementations, versions of which can be found in [4].

To solve this problem, the inventive device uses three tunable interval decoder code 8, 12 and 17, which is required for the requested aircraft.

The operation of the inventive device is as follows: BPL sends the pulses of the request code of the requested aircraft, after which the SSR switches to the mode of receiving pulses of the response code forming the response signal (OS). At this time, the bottom of the receiving antenna 1 is set to the left position relative to the RNS f1 (β) with a maximum in the direction -0β (Fig. 3). In the first decoder 8, the aircraft address code is entered, which is determined by the temporary location of the first half of the total number of pulses of the OS interval code with an even number N or the address code of the requested aircraft is entered, which corresponds to the temporary position of the first (N-1) / 2 pulses with an odd number of pulses OS interval code.

In the second decoder 12, the code corresponding to the location of the second half of the pulses of the OS interval code with an even number of pulses of the OS is N. With an odd number of pulses of the OS interval code is N, the code of the second part of the OS interval code is entered into the second decoder 12, excluding the average pulse with the number ((N-1) / 2) +1 OS code. In the third decoder 17 enter the full OS code corresponding to the temporary position of all pulses of the OS. All codes in the decoders 8, 12 and 17 are entered through their second control inputs from the address input of the inventive device, indicated in FIG. 1 as an address code. The signals removed from these taps enter the decoder adder.

In the initial position - waiting for the OS to be received - the first key 7 is open, and the keys 11, 14, 15, 16 and 19 are closed, the controlled delay element 21 with an even number of pulses OS N gives zero delay to the control pulse of the second key 11, which will come to it the input from the output of the first detector 9 when detecting the first half of the OS pulses. With an odd value of N, the controlled delay element 21 delays the control pulse of the second key 11 for opening it for a predetermined time, such that the OS pulse with the number ((N-1) / 2) + l does not arrive at the second decoder 12.

In the presence of the requested aircraft in this direction, the transponder installed on it begins to emit pulses of the OS at time t0 (Fig. 4, 5). At time t1, the first OS pulse is received by the phased array 1 VRL. The difference value t1-t0 is determined by the distance between the VRL interrogator and the aircraft responder.

The OS signals received by antenna 1 at the DN position f1 (P) (Fig. 3) having the amplitudes A f1 (βc) - (Fig. 4a) are pulses received in the time interval from t1 - the beginning of the arrival of the first OS pulse - to the time t2 - the moment of arrival of N / 2 - OS pulse for an even number of OS pulses - N. For an odd number of OS pulses, the time t2 is the moment of arrival of a pulse with the number (N-1) / 2 - (Fig. 5a) through the first public key 7 arrive at the input of the first decoder 8. The amplitudes of these pulses are the same and are determined by the power of the signals emitted by the transmitter of the transponder; by the directional coefficient (KND) of the transmitting antenna of the responder and the distance between the interrogator and the responder, which is taken into account by the coefficient A, as well as the value of the KND of the receiving antenna in its first position f1 (βц) - depending on the direction to the responder - βц - (Fig. 3).

The total signal from the output of the first decoder 8 with the amplitude (N / 2) Af1 (βц) - (Fig. 4d) is fed to the input of the first detector 9 and the second input of the third key 14. When the first detector 9 is triggered, the first N / 2 pulses of the OS are detected if N is even or the first (N-1) / 2 pulses of the OS are detected, when N is odd, the pulse is removed from the output of the first detector 9, which is fed to the first input of the third key 14 and opens it, goes to the first input of the first key 7 and closes it, - (Fig. 4b) is supplied to the first control input of the block of controlled phase shifters 2 Nam antenna translates from position 1 f1 (β) to a position f2 (β) - (Figure 3.). The same pulse, passing through the controlled delay element 21, enters the first input of the second key 11 and opens the second key 11 immediately after the detection signal is issued by the first detector 9 with an even number of pulses OS - N - (Fig. 4c). Through the second input of the open third key 14, the output total signal taken from the output of the first decoder 8 is fed to the first input of the angular discriminator 20.

With an odd number of OS pulses N, the controlled delay element 21 delays the pulse supplied to its input, and the second key 11 opens not at time t2, as it was at even N, but at time t2 '' - (Fig. 5c). In this case, the pulse with the number ((N-1) / 2) +1 arriving from the output of the amplitude detector 10 at the time t2 '- (Fig. 5a) does not pass to the input of the second decoder 12. As a result, the input of the first decoder 8 is disconnected from the output of the amplitude detector 7 - (Fig. 4b) and (Fig. 5b), and the input of the second decoder 12 is connected through the open second key 11 to the output of the amplitude detector 10, or at time t2 with even N - (Fig. 4c), or at time t2 '' with odd N - (Fig. 5c). Through the open second key 11, the second half of the OS pulses for even N - come to the input of the second decoder 12 (Fig. 4c), and for odd N all pulses, starting from the number ((N-1) / 2) +2, to the last one number N - (Fig. 5c). From the output of the second decoder 12, the second detector 13 receives the total signal with amplitude A (N / 2) f2 (βц) for even N, and for odd with amplitude A ((N-1) / 2) f2 (βц). When the second detector 13 is triggered, the pulse generated at its output goes to the first input of the fourth key 15 and opens the fourth key 15 and, entering the second control input of the block of controlled phase shifters 2, transfers the antenna bottom 1 from f2 (β) to the initial position f1 ( β). Through the open fourth switch 15, through its second input, a voltage of amplitude (N / 2) Af2 (βц) for even N or ((N-1) / 2) Af2 (βц) for odd N is supplied to the second input of the angular discriminator 20.

The third decoder 18 receives all received OS pulses. Their sum is equal to ((N / 2) Af1 (βц)) + ((N / 2) Af2 (βц)) for even N or ((N-1) / 2) Af1 (βц)) + ((N-1 ) / 2) +1) Af2 (βц)) for odd N goes to the third detector 18 and to the second input of the fifth key 16. When deciding whether to detect the output of the third detector 18, the signal is sent that goes to the first inputs of the fifth 16 and sixth 19 keys and opens the fifth 16th and sixth 19th keys. Through the open fifth key 16, the total signal received at the output of the third decoder 17 is fed to the second output of the radar, and through the open sixth key 19, the estimate of the angular coordinate β formed at the output of the angular discriminator 20 is taken.

The angular discriminator 20 implements the total-difference processing of signals taken from the outputs of the first 8 and second 12 decoders. A feature is that the total signal from the output of the first decoder 8 arrives at the first input of the angular discriminator 20 earlier than the total signal taken from the output of the second decoder 12 - (Fig. 4d and Fig. 5d). Therefore, the signal arriving at the first input of the angular discriminator 20 should be aligned in time with the moment of arrival of the total signal arriving at the second input of the angular discriminator 20. This task is performed by a controlled delay line 20.1. The amount of delay depends on the parameters of the OS interval code and is determined by the value of the time difference t3-t2 - (Fig. 4e or Fig. 5d). This value is set through the third control input of the angular discriminator 20 in accordance with a given address code of the aircraft. Using the difference circuit 20.2, the difference in the amplitudes of the signals arriving at the first and second input of the angular discriminator 20 is determined, and the sum of these signals is removed at the output of the adder 20.3. The ratio calculator 20.4 finds the ratio of the difference of the signals to their sum, which determines the estimate of the angular coordinate of the transponder βc.

When the third detector 18 is triggered through the open sixth key 19, the value of this estimate is received by the consumer.

The discriminatory characteristic generated by the angular discriminator 20 is shown in FIG. 6.

As follows from the foregoing, the achievement of a technical result, namely, an increase in the accuracy of measuring the angular coordinate of the aircraft is achieved by eliminating its dependence on the Doppler frequency shift in the response signals. In addition, the device prototype requires the formation of two simultaneously receiving radiation patterns. When implementing an antenna in the form of a PAR, the formation of two radiation patterns simultaneously requires the use of two sets of phase shifters and attenuators, the number of which in the set is equal to the number of emitters in the antenna. Typically, this amount is determined by dozens of units. The inventive device requires only one set of phase shifters and attenuators, which simplifies its implementation and significantly reduces the cost, and also makes it possible to use a secondary radar not only for ground based, but also on board the aircraft.

The proposed device can also reduce the complexity and cost of technical implementation of the secondary radar and ensure the operation of the radar (secondary monopulse radar) on board the aircraft as part of the aircraft traffic control complex.

INFORMATION SOURCES

1. Reference radar. Ed. M. Skolnik. New York, 1970. Per. from English (in four volumes) under the general ed. K.N. Trofimova. Tom. 2. Radar antenna devices. Ed. P.I. Angelica. M., "Sov. Radio", 1977, 408 S.

2. Active phased array antennas. / Under. ed. DI. Voskresensky and A.I. Kanashenkova. - M .: Radio engineering, 2004.

3. Globus I.A. Binary coding in asynchronous systems. - M.: Communication 1972

4. Rumyantsev K.E. Reception and processing of signals. - M.: Publishing Center "Academy", 2004. - 240 p.

Claims (3)

1. A quasi-monopulse secondary radar comprising an antenna, the outputs of which are connected to the inputs of a controlled phase shifter unit, a first adder, a receive-transmit switch and a receiver connected in series, a second receive-transmit switch output connected to the input of the power divider, the outputs of which are connected to their respective number the inputs of the unit controlled phase shifters, the signal outputs of which are connected to the inputs of the first adder, characterized in that the device is additionally introduced controlled a delay element connected in series with the first key, the first decoder, the first detector, the amplitude detector in series, the second key, the second decoder, the second detector, the third decoder and the third detector in series, as well as the third, fourth, fifth, sixth keys and an angular discriminator, the first and second inputs of which are connected respectively with the outputs of the third and fourth keys, and the output is with the second input of the sixth key, the output of which is the output of the device, the first input is the delay element to be connected is connected to the second inputs of the first, second, and third decoders and the third input of the angular discriminator and serves as the input of the address code, the second input of the controlled delay element is connected to the first input of the block of controlled phase shifters, the first input of the first key, and the output of the first detector, the output of which is connected to the first input of the third key, the second input of which is connected to the output of the first decoder, the outputs of the second and third decoders are connected respectively to the second inputs of the fourth of the fifth and fifth keys, the output of the latter is the second output of the radar, the output of the second detector is connected to the first input of the fourth key and to the second input of the block of controlled phase shifters, the output of the third detector is connected to the first inputs of the fifth and sixth keys, the output of the amplitude detector is connected respectively to the first input of the third the decoder and the second input of the first key, and its input with the output of the receiver, the output of the controlled delay element is connected to the first input of the second key. 2. The quasimonopulse secondary radar according to claim 1, characterized in that the angular discriminator contains a controlled delay line, the signal input of which is the first input of the angular discriminator, and its control input is connected to the third input of the angular discriminator, the output of the controlled delay line is connected to the first inputs of the circuit difference and the second adder, the second input of the angular discriminator is connected to the second inputs of the difference circuit and the second input of the second adder, the output of which is connected to the input of the divider A relationship dividend input connected to the output of the difference circuit, the output is an output ratio calculator angular discriminator. 3. The quasi-monopulse secondary radar according to claim 1, characterized in that the antenna is made, for example, in the form of a phased antenna array.

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