RU2542712C1 - Method of measuring dynamic range of radio receiver on intermodulation and device therefor - Google Patents

Abstract

FIELD: radio engineering, communication.

SUBSTANCE: method of measuring the dynamic range of a radio receiver on intermodulation includes transmitting to the input of the receiver noise emf E_N, measuring output noise voltage U_N and calculating nominal output voltage U_V, transmitting to the input of the receiver a calibration signal at frequency f₀ and establishing an output voltage U_V, using two signals to measure and calculate the dynamic range on intermodulation of the third order and determining the level of emf of one of n noise signals in the band-pass of a pre-selection filter, varying simultaneously and in steps the frequency of noise signals with frequency step of Δf_I, and at each frequency step, varying simultaneously and in steps the level of emf of noise signals with an amplitude step Δe, simultaneously measuring corresponding output voltages and detecting two maximum values each, calculating the number of pairs of noise signals in the band-pass of a pre-selection filter corresponding to each frequency step, and determining overall output voltages, using calibration signals to determine the dynamic range on intermodulation of higher orders of the type f₀=kf_(k-1)-(k-1)f_k with and without taking into account the band-pass of a pre-selection filter, from which the least are selected. A device for measuring the dynamic range of a radio receiver on intermodulation, comprising first and second generators, a matching device, a radio receiver, a voltmeter, an equivalent load, digital and fibre-optic links, an automated workstation, including a digital signal processing unit, a personal computer, an optical transceiver, an optoelectronic/electro-optical converter, connected to each other, includes a controlled switch, a noise generator and a storage device, connected to each other and other units of the device in the appropriate manner.

EFFECT: more accurate quantitative estimation of the dynamic range of a radio receiver on intermodulation.

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Description

The present invention relates to the field of radio engineering measurements and can be used to measure the dynamic range of a radio receiver by intermodulation.

These inventions are combined by a common inventive concept. A known method of measuring the dynamic range (DD) of a radio receiver by intermodulation (see GOST R 52016 - 2003 "Receivers of the main radio communication hectometer-decameter wavelength range. Parameters, general technical requirements and measurement methods). This method consists in the following, when measuring, an unmodulated calibration signal with an EMF (electromotive force) level of 0 dB · μV (1 μV) and a frequency equal to the receiver tuning frequency f _{0 is} fed to the input of the radio receiver (receiver). At the output of the receiver set the nominal voltage level of the output signal U _N. Then, the calibration signal is turned off, and the first and second unmodulated interference signals with the same EMF levels and frequencies corresponding to f _1,1 = f ₀ ± Δf and f _2,2 = f ₀ ± 2Δf, where Δf is the measurement tune-off frequency interval from f ₀ . It should be noted that the first index when designating frequencies (f _1.1 and f _2.2 ) shows the number of the interference signal, and the second index shows the number of identical measuring frequency intervals (1Δf or 2Δf) of the frequency offset of the corresponding interference signal from f ₀ . For example, the designation of the frequency f _2.2 means that this is the second interference signal, tuned from f ₀ into two frequency intervals equal to 2Δf. The Δf value is set equal to 20 kHz or another value depending on the bandwidth (PP) of the main selection filter (FOS), but it is necessary so that the interference signals with frequencies f _1,1 and f _2,2 are in the pre-selection filter PP ( FPS) and in the detention band (PZ) FOS. The EMF levels of the interference signals are increased simultaneously, maintaining the same, to such a value of E, until the voltage level of the output signal of the receiver reaches the nominal value of U _N. The value of the level E of any of two equal noise signals determines the DD by intermodulation of the form f ₀ = 2f _{1, 1-} f _2.2 with respect to 1 μV, which in decibels is determined by the formula: D _2-1 [dB] = 20 log (E / 1), where E is the value of the EMF level of one of the two interference signals in microvolts.

Measurement by this method gives a fairly accurate quantitative estimate of the receiver DD by intermodulation of the form f ₀ = 2f _1,1 -f _2,2 .

However, the method does not allow: to measure the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ , of the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _2.2 , measure and calculate the DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ taking into account the width of the FS FPS receiver, the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _2,2 taking into account the width of the FPS FPS receiver and type f ₀ = 2f _1,1 -f _2,2 taking into account the width of the FPS FPS receiver, measure and calculate the receiver DD by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , intermodulation-type DDs of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS FPS receiver, DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k- 1)} - (k-1) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2 , k} taking into account the width of the PP FPS receiver. Here k is a limited natural series of numbers 3, 4, ..., s, corresponding to the number of identical measuring frequency intervals of the frequency detuning of the second interference signal from f ₀ , s is the maximum number of measuring frequency intervals in the receiver's FPS.

This method does not provide an objective, complete and accurate quantitative assessment of the receiver DD by intermodulation.

In addition, the method does not determine and clarify the values of the boundary frequencies and the width of the PP FPS, PP and PZ FOS of the receiver, which also reduces the accuracy of measuring the receiver DD by intermodulation.

A known method of measuring the dynamic range of a radio receiver by intermodulation (see Patent for the invention No. 2472166, M. CL G01R 23/20, publ. 01.10.2013).

This method consists in the following: when measuring, an unmodulated or modulated calibration signal with an EMF level equal to E _{0 is} supplied to the receiver input, the calibration signal tuning frequency is set equal to the receiver tuning frequency f ₀ , determined by the formula: f ₀ = (f _B + f _N ) / 2, where f _B and f _N are the upper and lower boundary frequencies of the PP FPS receiver, respectively. At the receiver output, the nominal voltage level of the output signal U _{N is set} , then the calibration signal is turned off, after which the first, second and third unmodulated or modulated interference signals with the same EMF levels are fed to the receiver input, while the frequencies of the first, second and third interference signals are set respectively : f ₁ = f ₀ ± Δf ₁ , f ₂ = f ₀ ± Δf ₂ and f ₃ = f ₀ ± Δf ₃ , where Δf ₁ <Δf ₂ <Δf ₃ are the values of the measuring frequency intervals of the detunings in relation to the receiver tuning frequency, which are selected depending on the width PP FOS, but always so that the frequency of the first, second and third interference signals f _1, f _2, f _3, respectively, were PP FFF and the PP FOS, wherein Δf ₃ = Δf ₁ + Δf _2, and 2Δf ₁ <Δf ₂ , then increase the EMF levels of all three interference signals at the same time, keeping them the same, to such an EMF value equal to E _P1 , until the voltage of the receiver output signal reaches the nominal value U _N , while the ratio of the EMF level of any of the three equal in level interference signals E _P1 to E ₀ determines the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ , which in decibels it is determined by the formula: D ₁ [dB] = 20lg (E _P1 / E ₀ ), where E ₀ is the EMF value of the calibration signal in microvolts, E _P1 is the EMF value of one of three equal in level signals of interference in microvolts, in the logarithmic the scale of the levels of DD signals is determined by the formula: D ₁ [dB] = E _P1 dB · μV - E ₀ dB · μV, where E ₀ is the value of the EMF of the calibration signal in dB · μV; E _P1 - the EMF value of one of three equal in level interference signals in dB · μV, then determine the width of the FS FPS by the formula: Δf _FPS = f _V -f _N, then set the frequency interval between the signals in the FPS FS to Δf _P and calculate the total the number of interference signals in the FS FPS by the formula: n = (Δf _FPS / Δf _P ) -1. Next, determine the maximum possible number of pairs and triples of interference signals in the FS FPS, during non-linear interaction of which intermodulation (combination) components are created with a frequency equal to f ₀ , and the probability p of the occurrence of each of n independent interference signals at the corresponding frequency position in the FPS of the receiver is set p = 1. The number of pairs and triples is calculated according to the formulas n _pairs = p ² (n / 2) = n / 2, n _triples = p ³ [0.375n (n-3) +1] = 0.375n (n-3) +1, then calculate the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ taking into account the width of the FS FPS according to the formula:

D _1P = D ₁ [dB] - (⅓) 10 lg [n _triples + 0.25n _pairs ], dB,

then the frequencies of the first, second and third interference signals are set, respectively, f _1,1 = f ₀ ± Δf ₁ , f _2,2 = f ₀ ± 2Δf ₁ and f _3,3 = f ₀ ± 3Δf ₁ , where Δf ₁ is the measuring frequency the tuning interval with respect to the receiver tuning frequency, the first and second indices when designating frequencies (f _1,1 , f _2,2 , f _3,3 ) respectively show the number of the interference signal and the number of identical measuring frequency intervals (1Δf ₁ , 2Δf ₁ , 3Δf ₁ ) the frequency offset _of the corresponding interference signal from f ₀ , the value of Δf _{1 is} chosen so that the frequencies of the first, second and third signal in interference with frequencies f _1,1 , f _2,2 , f _3,3 were in the FS FPS and in the FS FOS, then the EMF levels of all three interference signals are changed at the same time, keeping them the same, to such an EMF value equal to E _PΣ until the voltage level of the output signal of the receiver reaches the nominal value U _Н , while the ratio of the EMF level of any of the three equal in level interference signals E _ПΣ to E ₀ determines the receiver DD by intermodulation of the total form f ₀ = f _1,1 + f _{2 , 2} -f _3.3 and f ₀ = 2f _1,1 -f _2,2 , which in decibels is determined by the formula: D _Σ [dB] = 20lg (E _PΣ / E ₀ ), where E ₀ is is the EMF of the calibration signal in microvolts, E _PΣ is the EMF of one of three equal in level signals of interference in microvolts, on the logarithmic scale of the signal levels DD is determined by the formula: D _Σ [dB] = E _PΣ dB · μV - E ₀ dB · μV , where E ₀ is the value of the EMF of the calibration signal in dB · μV, E _PΣ is the value of the EMF of one of the three equal in level signals of interference in dB · μV, then the receiver DD is calculated by intermodulation of the total form f ₀ = f _1,1 + f _{2 , 2} -f _3.3 and f ₀ = 2f _1,1 -f _2,2 taking into account the width of the PP FPS according to the formula:

D _ΣP = D _Σ [dB] - (⅓) 10lg [0.8n _triples + 0.2n _pairs ], dB,

then the third interference signal with a frequency of f _3.3 = f ₀ ± 3Δf _{1 is} turned off, while the frequencies of the first and second interference signals are selected, respectively, f _1,1 = f ₀ ± Δf ₁ and f _2,2 = f ₀ ± 2Δf ₁ so so that they are in the FS FPS and in the FS FOS, then the EMF levels of the first and second interference signals are changed simultaneously, keeping the same, to such an EMF value equal to E _P2 , until the voltage level of the output signal of the receiver reaches the nominal value U _H , at this ratio of the value of the EMF level of any of two equal in level of interference signals E _P2 to E ₀ divides the receiver DD by intermodulation of the form f ₀ = 2f _1,1 -f _2,2 , which in decibels is determined by the formula: D ₂ [dB] = 20lg (E _P2 / E ₀ ), where E ₀ is the value of the EMF of the calibration signal in microvolts, E _P2 - the value of the EMF of one of two equal in level signals of interference in microvolts, in the logarithmic scale of the signal levels DD is determined by the formula: D ₂ [dB] = E _P2 dB · μV - E ₀ dB · μV, where E ₀ - EMF value of the calibration signal in dB microvolts ·, E _P2 - EMF one of two equal level jamming signals in the mV · dB, then the calculated DD receiver by intermodulation of the form f ₀ = 2f _1,1 -f _2,2 with Chet width PP LRF by the formula:

D _2P = D ₂ [dB] - (⅓) 10 lg [4n _triples + n _pairs ], dB,

then from the calculated values of D _1P , D _2P , D _ΣP choose the smallest.

The method allows to measure the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ , of the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _{2 , 2} , measure and calculate the DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ taking into account the width of the PP FPS receiver, the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _2,2 taking into account the width of the FS FPS receiver and the type f ₀ = 2f _1,1 -f _2,2 taking into account the width of the PP FPS receiver, while choosing the smallest value from the measured and calculated values of the DD by intermodulation taking into account the width of the PP FPS receiver allows you to give a fairly objective quantitative assessment of the DD of the radio receiver intermodulation.

However, the method does not allow to measure and calculate the receiver DD by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , by the intermodulation DD of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS of the receiver, DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1 ) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS receiver i.e. does not provide a complete and accurate quantitative assessment of the receiver DD by intermodulation. In addition, the method does not determine and clarify the values of the boundary frequencies and the width of the PP FPS, PP and PZ FOS of the receiver, which reduces the accuracy of measuring the receiver DD by intermodulation.

This method of measuring the dynamic range of the radio intermodulation selected for the prototype.

Achievable technical result of the invention is the provision of a complete and accurate quantitative assessment of the DD of the radio receiver by intermodulation by measuring the DD of the radio receiver by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS of the receiver, DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, ( k-1)} - (k-1) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the PP FPS receiver.

This technical result is achieved by the fact that in the method of measuring the DD of the radio by intermodulation, determine the width of the PP FPS according to the formula: Δf_FPS= f_AT-f_Nwhere f_B and f_H - respectively, the upper and lower boundary frequencies of the FS FPS, then set the frequency interval between signals in the FS FPS equal to Δf_P and calculate the total number of interference signals in the FS FPS by the formula: n = (Δf_FPS/ Δf_P) -1, calculate the number of triples and pairs of interference signals, respectively, by the formulas:

отличающемся тем, что перед подачей на вход приёмника калибровочного сигнала устанавливают частоту настройки приёмника равной f₀=f_H+Δf_И/2, где Δf_И>Δf_P, а на вход приёмника подают шумовую ЭДС, при этом спектральную плотность мощности (интенсивность) шума устанавливают равной кТ, Дж, (Вт/Гц), где k - постоянная Больцмана, равная 1,38-10^-23Дж/К, Τ - абсолютная температура, в градусах Кельвина (К), которую принимают из условия: 0,01Т₀≤Τ≤60Т₀, где Т₀ - стандартная комнатная температура, равная 293К, причем уровень шумовой ЭДС устанавливают, равным Е_Ш, при этом на выходе приёмника измеряют уровень шумового напряжения U_Ш, далее вычисляют номинальное значение напряжения выходного сигнала U_H по формуле: U_H=h U_Ш, где h - заданный коэффициент, причём h>1, после чего шумовую ЭДС отключают, а на вход приёмника подают калибровочный сигнал и после определения ДД приёмника по интермодуляции вида f₀=2f_1,1-f_2,2 с учётом ширины ПП ФПС, равного D_P, вычисляют значение уровня ЭДС одного из n равных по уровню сигналов помех в ПП ФПС приёмника по формуле:where p is the probability of each of the η independent interference signals appearing at the corresponding frequency position in the receiver's FPS PP, with p = 1, after which a modulated or modulated calibration signal is fed to the radio input, the calibration signal tuning frequency is set equal to the receiver tuning frequency f₀, the EMF level of the calibration signal is changed to such a value E₀until the voltage level of the output signal of the receiver reaches the nominal value U_H, while the value of E₀ fix, then the calibration signal is turned off, after which the first and second unmodulated or modulated interference signals with the same EMF levels are fed to the input of the receiver, the frequencies of the first and second interference signals are selected respectively f_1,1= f₀+ Δf_AND and f_2.2= f₀+ 2Δf_ANDwhile the value of the measuring frequency interval Δf_AND offset in relation to the receiver tuning frequency f₀ chosen so that the frequencies f_1,1and f_2.2 were in the PP FPS and in the PZ FOS, then the EMF levels of the first and second interference signals are increased simultaneously, maintaining the same, to such an EMF value equal to E_Puntil the voltage level of the output signal of the receiver reaches the nominal value U_H, the ratio of the value of the EMF level of any of two equal in level of interference signals E_P to E₀ determines receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2, which in decibels is determined by the formula: D [dB] = 20lg (E_P/ E₀), where E₀ - EMF value of the calibration signal in microvolts, E_P - the value of the EMF of one of two equal in level signals of interference in microvolts, in the logarithmic scale of the levels of signal DD is determined by the formula: D [dB] = E_PE_P dB · μV-E₀ dB · μV, where E₀ - EMF value of the calibration signal in dB · μV, E_P - the EMF value of one of two equal in level interference signals in dB · μV, then determine the receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2 taking into account the width of the PP FPS according to the formula:

 characterized in that before applying the calibration signal to the receiver input, set the receiver tuning frequency to f₀= f_H+ Δf_AND/ 2, where Δf_AND> Δf_Pand a noise emf is applied to the receiver input, while the spectral power density (intensity) of the noise is set equal to kT,J, (W / Hz), where k-Boltzmann constant equal to 1.38-10^-23J / C, Τ - absolute temperature, in degrees Kelvin (K), which is taken from the condition: 0,01T₀≤Τ≤60T₀, where T₀ -standard room temperature equal to 293K, and the level of noise EMF set equal to E_W, while the output voltage of the receiver measures the level of noise voltage U_W, then calculate the nominal voltage value of the output signal U_H by the formula: U_H= h U_W, where h is a given coefficient, and h> 1, after which the noise emf is turned off, and a calibration signal is fed to the input of the receiver even after determining the receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2 taking into account the width of the PP FPS equal to D_P, calculate the value of the EMF level of one of n equal to the level of interference signals in the PP FPS receiver according to the formula:

then the value of E _Pn dB · μV is transferred to a linear scale of signal levels according to the formula: E _Pn μV = 10 ^{(Epn dB μV / 20)} , the values of E _Pn μV and E _Pn dB · μV are fixed, and then the frequencies of the first and the second interference signal with the same frequency step equal to the specified measuring frequency interval

Δf _AND , in this case, at each frequency step, the values of the EMF levels of the first and second interference signals at the input of the receiver are set to E ₀ , then the values of the EMF levels of the first and second interference signals are changed simultaneously and step by step with the same amplitude step equal to the given measuring amplitude interval Δe, the frequency values of the first and second interference signals corresponding to each frequency step are set according to the formulas: f _{1, (k-1),} = f ₀ + (k-1) Δf _And , f _{2, k} = f ₀ + kΔf _And , where k is a limited natural series of numbers 3, 4, ..., s, corresponding to the number of identical measuring frequency intervals Δf _{AND the} frequency detuning of the second interference signal from f ₀ , s - the number of measuring frequency intervals Δf _and in the PP FPS receiver, the value of which is determined by the formula: s≤ (Δf _FPS / Δf _И ) -1, the frequency step number is determined by the formula: i = (k-2) = 1, 2, ..., m = s-2, the values of the EMF levels of the first and second interference signals at the receiver input, corresponding to each amplitude step at each frequency step i set according to the formula:

E _{q, i} = E ₀ + qΔe = E _{1, i} = E ₀ + 1Δe, ..., E _{r, i} = E ₀ + rΔe = E _Pn , ..., E _{R, i} = E ₀ + RΔe = E _P ,

where q is a limited natural series of numbers 1, 2, ..., r, ..., R, corresponding to the number of the amplitude step at each frequency step

i = 1, 2, ..., m, is equal to q _i = 1 _{(1 ... m)} , 2 _{(1 ... m)} , r _{(1 ... m)} , ..., R _{(1 ... m)} ,

where r = (E _Pn -E ₀ ) / Δe, R = (E _P -E ₀ ) / Δe, all values of E _{q, i} are fixed, while at each amplitude step of each frequency step q _i at the corresponding EMF levels at the receiver input equal to E _{q, i} = E _{1, (1 ... m)} , E _{2, (1 ... m)} , ..., _{Er, (1 ... m)} , ..., E _{R, (1 ... m)} , simultaneously at the output of the receiver measure the levels of the corresponding output voltages equal to U _{q, i} = U _{1, (1 ... m)} , U _{2, (1 ... m)} , ..., U _{r, (1 ... m)} , ..., U _{R, (1 ... m)} , all the measured voltage values are fixed, after which from the measured voltage values in the range: U _{1, (1 ... m)} , U _{2, (1 ... m)} , ..., U _{r, (1 ... m)} , identify maximum stress values to zhdogo frequency step equal to _{U (r, i) max =} U (r, i) max, U (r, _{1) max,} U _{(r, 2) max, ..., U (r} , m) max, then from the measured voltage values in the range: U _{1, (1 ... m)} , U _{2, (1 ... m)} , ..., U _{r, (1 ... m)} , ..., U _{R, (1 ... m)} , also reveal the maximum voltage values each frequency step equal to U _{(R, i) max} = U _{(R, 1) max} , U _{(R, 2) max} , ..., U _{(R, m) max} , all maximum values are fixed, then the total voltage is calculated by the formula :

then the first and second interference signals are turned off, and a modulated or modulated calibration signal is applied to the input of the receiver, the frequency of the calibration signal is set equal to the receiver tuning frequency f ₀ , and the level of the calibration signal is changed to such an EMF value equal to E _0m , while the voltage level of the output signal of the receiver does not reach U _Σm , while the ratio of E _P to E _0m determines the receiver DD by intermodulation of the form f ₀ = kf _(k-1) - (k-1) f _k , which is determined in decibels by the formula: D _m [dB] = 20lg (E _П / E _0m ), where E _0m - EMF value of the calibration signal in microvolts, the E _P value of the EMF of one of two equal in level signals of interference in microvolts, on the logarithmic scale of the signal levels DD is determined by the formula: D _m [dB] = E _P dB · μV - E _0m dB · μV, where E _0m is the EMF value of the calibration signal in dB · μV, E _P is the EMF value of one of two equal in level signals of interference in dB · μV, then the total voltage is calculated by the formula:

after which the level of the calibration signal is changed to such an EMF value equal to E _0mn until the voltage level of the output signal of the receiver reaches U _Σmn , while the ratio of E _P to E _0mn determines the receiver DD by the sum of intermodulations of the form f ₀ = 2f _1,1 - f _2.2 and f ₀ = kf _(k-1) - (k-1) f _k , which is calculated in decibels by the formula: D _mn [dB] = 20lg (E _P / E _0mn ), where E _0mn is the value EMF calibration signal in microvolts, E _P - EMF one of two equal level jamming signal in microvolts, the signal levels in a logarithmic scale is determined by the DD pho mule: D _MH [dB] = E _n db uV - E _0mn db uV where E _0mn - value of the calibration signal EMF in dB · mV, E _P - EMF one of two equal level jamming signals in dB · uV , then, with the corresponding frequency step number equal to i = 1, 2, ..., m, an integer number of pairs of interference signals in the receiver's FPS PP is calculated by the formula: n _pairs = P ² (n / k _i ) = n / k _i , where p = 1, k _i = i + 2 = 3, 4, ..., m + 2 = s, then the total voltage is calculated by the formula:

then the calibration signal level is changed to such an EMF value equal to E _0mn until the voltage level of the receiver output signal reaches U _Σmn , while the ratio of E _Пn to E _0mn determines the receiver DD by intermodulation of the form f ₀ = kf _(k-1) - (k-1) f _k taking into account the width of the FS FPS, which in decibels is determined by the formula: D _mn [dB] = 20lg (E _Пn / E _0mn ), where E _0mn is the EMF value of the calibration signal in microvolts, E _Пn is the value EMF of one of n equal in level signals of interference in microvolts, on a logarithmic scale of signal levels DD is determined by the formula: D _mn [dB] = E _Pn dB · μV - E _0mn dB · μV, where E _{0mn is the} EMF _{value of the} calibration signal in dB · μV, E _Pn is the EMF value of one of n equal in level signals of interference in dB · μV, then calculate total voltage according to the formula:

then change the level of the calibration signal to such an EMF value equal to E _0mnn , until the voltage level of the output signal of the receiver reaches U _Σmnn , while the ratio of E _Pn to E _0mnn determines the receiver DD by the sum of intermodulations of the form f ₀ = 2f ₁ -f ₂ and f ₀ = kf _(k-1) - (k-1) f _k taking into account the width of the PP FPS, which in decibels is determined by the formula: D _mnn [dB] = 20lg (E _Pn / E _0mnn ), where E _0mnn - value of the calibration signal in microvolts emf, E _Pn - EMF one of n equal-level interfering signals in microvolts on a logarithmic scale signal levels in DD is determined from the formula: D _mnn [dB] = E _Pn db uV - E _0mnn db uV where E _0mnn - value of the calibration signal EMF in dB · mV, E _Pn - EMF one of n equal to the level of interference signals in dB · μV, then from the obtained values of D _m and D _mn , as well as from D _mn and D _mnn , the smallest are chosen.

In this case, to measure the receiver DD by intermodulation up to a given intermodulation order number, an odd number of the intermodulation order is set equal to the value of N _И , which is selected from the series N = 5, 7, ..., 2n-1, then the magnitude of the frequency measurement interval is calculated by the formula : Δf = 2Δf _{and LRF} / (N _and 3) and the first condition is checked: Δf _and ≥f _{OT 0} -f where f _OT - upper limiting frequency PP FOS further define the maximum number of measurement intervals frequency detuning of the second interference signal by f ₀ by the formula s = (N _AND +1) / 2 and check in the second condition: s≤ (Δf _FPS / Δf _I ) -1, if these conditions are not met, the value of N _{And is} reduced by two units and the calculations Δf _And and s are repeated, while the first and second conditions are repeated and so on until these conditions are met.

To measure the receiver DD by intermodulation as applied to the electromagnetic environment (EMO) at a particular receiving location, first, by empirical studies and EMO measurements at the receiving location, the probability p is determined, the value of which lies in the range: 0 <p <1, then n _pairs are calculated, n _pairs , n _triples, respectively, by the formulas:

n _pairs = p ² (n / 2), n _pairs = p ² (n / k _i ), n _triples = p ³ [0.375n (n-3) +1].

To determine and clarify the boundary frequency and PP FBS widths, PP and PP receiver FOS, and determining the value of the measuring frequency interval before measurement JD receiver by intermodulation of the receiver input tuned to a given frequency f _K is fed noise emf at a level equal to E _W , and at the receiver output measure the noise voltage level U _W , then determine the required output voltage level of the calibration signal U _K by the formula: U _D ≥U _K ≥A _З U _Ш , where A _З is the specified attenuation at the boundaries of the FOS FOS, U _D - the level of the maximum allowable voltage above which the overload of the receiving path occurs, after which the noise emf is switched off and a modulated calibration signal is supplied to the receiver input with a frequency equal to the receiver tuning frequency f _K and with such an emf level equal to E _K so that the output of the receiver set the voltage level of the output signal U _K , then increase the frequency of the calibration signal to such a value equal to f _V , at which the level of the output voltage U _K decreases by a predetermined number A ₁ time and becomes equal U _K1 = U _K / A ₁ , where A ₁ is the attenuation value at the boundaries of the PP FOS, while the frequency f _{V is} fixed, then the frequency of the calibration signal continues to increase to a value equal to f _VZ , at which the output voltage U _K decreases a predetermined number A _Z times and it will be set equal to U _KZ = U _K / A _Z , and the value of f _{OZ is} fixed, then the frequency of the calibration signal is set equal to F _K and then the frequency of the calibration signal is reduced to a value f _n at which the output voltage level U _K will decrease by a given number A ₁ time and will be set equal to U _K1 = U _K / A ₁ , while the value of f _{n is} fixed and then continue to reduce the frequency of the calibration signal to a value equal to f _NC , at which the output voltage level U _K decreases by a predetermined number A ₃ times and it will be set equal to U _KZ = U _K / A _Z , while the value of f _{NS is} fixed, then the width of the FS FOS is calculated by the formula: Δf _FOS = f _in -f _n , where f _in and f _n are the upper and lower boundary frequencies of the PP FOS at a given receiver tuning frequency f _K, f wherein f _OT and _NC - respectively top and bottom boundary e frequency PP FOS at a given receiver tuning frequency f _K value Δf _FOS is fixed, then a calibration signal is turned off, while the receiver input is fed the first and second non-modulated measurement signals with the same levels of electromotive force, and with frequencies respectively equal to f _1I = f _K + Δf _And and f _2I = f _k + 2Δf _AND , where Δf _AND is the value of the measuring frequency interval of the detuning of the measuring signal from the receiver tuning frequency f _K , which is chosen from the condition: Δf _AND ≥f _OT -f _K , the EMF levels of the measuring signals are increased simultaneously, supporting them alone kovymi, to such a maximum value E _{1I 2I} = E = E _And, while the output of the measuring receiver signal voltage level reaches predetermined value _and U, wherein U _{and W} ≥gU where r - a predetermined coefficient which is chosen from the condition: 5≤ g≤30, then simultaneously increase the frequency values of the first and second measuring signals according to the formulas: f _1I = f _K + Δf _AND + Δf _1VAR ; f _2I = f _K + 2Δf _AND + Δf _2VAR , and Δf _1VAR and Δf _2VAR = 2Δf _1VAR are the variable values of the detuning from the tuning frequency of the receiver f _K which are determined according to the formulas:

here j is the tuning step number, Δf _jvar is the value of the variable frequency tuning step of the first measuring signal, which is selected from the condition: Δf _min ≤Δf _jvar ≤Δf _max , 2Δf _jvar is the variable frequency tuning step of the second measuring signal, which is selected from 2Δf _min ≤2Δf _jvar ≤2Δf _max , for Δf _max ≥Δf _FOS Δf _min ≤Δf _FOS / d, where d is the maximum number of steps for tuning the frequencies of the first and second measuring signals, which is chosen from the condition: (f _К / Δf _FOS ) ≤d <∞, increasing the frequencies of the first and second measuring signals DYT to such values respectively equal f _1I = (f _B + f _R) / 2 and f _2I = f _B, in which the output voltage U _and decreases in a predetermined number A _1FPS times and set to U _K2 = U _And / A _{1 FPS} , here A _{1 FPS} is the attenuation value at the boundaries of the _FS FPS, the frequency value f _{B is} fixed, then the frequency values of the first and second measuring signals are set respectively f _1И = f _К -Δf _И and f _2И = f _К -2Δf _И ,

where Δf _AND is the value of the measuring frequency interval of the detuning of the measuring signal from the receiver tuning frequency f _K , which is selected from the condition: Δf _AND ≥f _K -f _NC, the EMF levels of the measuring signals are changed simultaneously, keeping them the same, to such a maximum value of E _1I = E _2I = E _AND , until the voltage level of the output measuring signal of the receiver reaches a predetermined value U _AND , then the frequency values of the first and second measuring signals are simultaneously reduced according to the formulas: f _1I = f _K -Δf _AND -Δf _1VAR ; f _2I = f _K -2Δf _AND -Δf _2VAR , where Δf _1VAR and Δf _2VAR = 2Δf _1VAR are the variable values of the detuning from the receiver tuning frequency f _K , the frequency values of the first and second measuring signals are reduced to such values, respectively, equal to f _1I = (f _K + f _N ) / 2 and f _2I = f _N at which the output voltage level U _AND decreases by a predetermined number A _{1 FPS} times and _becomes equal to U _K2 = U _AND / A _{1 FPS,} the frequency f _{N is} fixed, then calculated the width of the PP FPS according to the formula: Δf _FPS = f _B -f _N, where f _B and f _N are the upper and lower boundary frequencies of the PP FPS at a given frequency the triples of the receiver f _K , then the measuring signals are turned off, and a modulated calibration signal with an EMF level equal to E _{K is} supplied to the receiver input, the calibration signal tuning frequency is set equal to the frequency _OZ , while the output voltage level will be set equal to U _KZ , the frequency of the calibration signal is increased to a value of f _B, wherein the output voltage level should meet the condition: U _RS ≤U _K / A _W, then set equal to the calibration signal frequency f _NC, the output voltage remains tsya equal U _RS, then reduced to a value of the calibration signal frequency f _H, the output voltage level should meet the condition: U _RS ≤U _K / A _W, then calculating the width of the top and bottom PP FOS respectively by the formulas: Δf = f _{The EOI} -f _OT and Δf _НЗ = f _НЗ -f _Н , the values of the frequencies of the calibration signal in the upper and lower FZ FOS for which U _К3 > U _К / A _З are fixed and excluded from the frequency setting of the interference signals when measuring the receiver DD by intermodulation.

We explain the possibility of achieving the specified technical result by the distinguishing features of the proposed method.

Supply noise EMF to the input of the receiver and measure the noise voltage at the output of the receiver, determine the value of the nominal voltage level of the output signal, calculate the EMF level of one of the n interference signals in the FS FPS receiver, and also step by step change the frequencies of the first and second interference signals in the PP FPS receiver and at each frequency step, there is also a step-by-step change in the level of the EMF of the interference signals at the input of the receiver, while at each amplitude step, the voltage levels of the output signal of the receiver are measured and their fixation (storing), then m revealing from the measured voltage levels of the output signals of the receiver two maximum values for each frequency step, calculating the number of pairs of interference signals in the FS FPS corresponding to each frequency step, calculating the total voltage of the output signal of the receiver and then using calibration signals allows you to measure and calculate the receiver DD by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} (D _m ), intermodulation modulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the PP FPS receiver (D _mn ), the receiver DD by the sum of intermodulations of the types f ₀ = 2f _{1 , 1} -f _2.2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} (D _mn ), DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _{2, 2} and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , taking into account the width of the PP FPS receiver (D _mnн ). The choice of the smallest of the obtained values of D _m and D _mn , as well as the selection of the smallest of the obtained values of D _mn and D _mnn allows _you to give a more complete and accurate quantitative assessment of the DD of the radio receiver by intermodulation.

In addition, supplying a noise emf to the input of the receiver and measuring the noise voltage at the output of the receiver, determining the required output voltage levels of the calibration and measurement signals, using two measuring signals with predetermined levels at the input of the receiver, which simultaneously adjust in frequency with respect to the receiver tuning frequency, and simultaneously measuring the voltage level of the output measuring signal of the receiver, allows you to additionally determine and clarify the values of the boundary frequencies of the PP FPS pr the receiver, and the use of one calibration signal with a given level at the input of the receiver, which is tuned in frequency relative to the tuning frequency of the receiver and the simultaneous measurement of the voltage level of the output calibration signal of the receiver, allows you to additionally determine and clarify the values of the cutoff frequencies of the FS FOS and the values of the cutoff frequencies of the upper and lower PZ FOS receiver. The definition and refinement of the cutoff frequencies of the FS FPS, PP and FZ FOS FS provides an additional opportunity to more accurately set: the values of the receiver tuning frequencies; frequency values of calibration and measuring signals; the value of the measuring frequency interval, which allows us to further clarify the width of the FS FPS, PP and PZ FOS, the total number of interference signals and the total number of measuring frequency intervals located in the PPS FPS of the receiver, and, therefore, improve the accuracy of measuring the DD of the radio receiver by intermodulation.

The essence of the method is illustrated by drawings, in which Fig. 1 shows an example of the amplitude-frequency distribution of radio signals (ACRR) from radio emission sources (IRI) in a wide range of the radio frequency spectrum (RF) under the prevailing electromagnetic environment (EMO) at a given receiving location

Figure 2 shows the real signals from radio stations in one of the sections (for example, Δf ₂ ) of the RF band, which is configured FPS receiver.

Figure 3 shows an idealized PP model of the FPS receiver when fully loaded with ordered signals from radio stations with equal frequency spectra in width.

Figure 4 shows the amplitude-frequency distribution of the first and second measuring interference signals in the FS FPS during measurements of the dynamic range of the receiver by intermodulation, while the idealized models of the amplitude-frequency characteristics (AFC) of the FPS and FOS of the receiver are rectangular and symmetrical.

Figure 5 shows the attenuation characteristics (A) of the frequency of three FPS receiver with mutually overlapping PP.

Figure 6 shows models of the attenuation characteristics of the frequency of the FPS and FOS of the receiver.

This method is as follows.

According to Figure 1, the amplitude-frequency distribution of radio signals (AChRR) in a wide frequency range is very uneven. The radio signal levels E are different and random. The RFS range equal to Δf _RFS is divided into frequency sections Δf ₁ , Δf ₂ , Δf ₃ , Δf ₄ , Δf ₅ , Δf ₆ , Δf ₇ , Δf ₈ , Δf ₉ . The E levels of individual signal groups are significantly different from each other. There are groups of signals, for example, in the frequency sections Δf ₂ , Δf ₄ , Δf ₆ , Δf ₈ , in which the values of the levels E of individual signals and the values of the frequency intervals Δf _P between the signals are relatively close to each other, in addition, the probability p of the occurrence of each individual independent radio signal in these groups is quite high and lies in the range: 0.5 <p <1. There are groups of signals, for example, in the frequency sections Δf ₁ , Δf ₃ , Δf ₅ , Δf ₇ , Δf ₉ , in which the levels of E radio signals are significantly lower than the levels of radio signals previously considered, the frequency intervals Δf _P between the radio signals are less uniform and the probability of the appearance of the radio signal p on the data sections below and lies in the range: 0 <p≤0.5. However, ACRR is known to depend on each specific EMO at the site of administration. Therefore, the values of the probabilities (p) of the appearance of independent signals at the corresponding frequency positions of the sections of the RF range are determined empirically.

According to Figure 2, the emission frequency bands of the individual signals are commensurate with the receiver's FOS FS equal to Δf _FOS , the frequency intervals between the carrier frequencies of the signals equal to Δf _P are close to each other, while Δf _FOS ≈Δf _P. Signals with levels E _C are located in the receiver's FPS PP with a width equal to Δf _FPS = f _B -f _N , where f _B and f _N are the upper and lower boundaries of the FPS FPS, respectively. The receiver tuning frequency f ₀ is located at an arbitrary frequency position in the FS FPS. Obviously, the probability (p) of the appearance of independent signals in a given section of the RF spectrum range at the corresponding frequency positions in the FS FPS, in which as a result of the nonlinear interaction of the interference signals, combinational (intermodulation) components (noise) arise whose frequencies coincide with the frequencies in the FS FOS receiver , is quite high and lies in the range: 0.5 <p <1.

According to the model depicted in FIG. 3, the frequency response of the FPS and FOS of the receiver are rectangular and symmetrical. The frequency spectra of the signals are adjacent to each other and completely occupy the FS FPS. The frequency intervals between the carrier frequencies of the signals are the same and equal to Δf _P. The signals have the same levels equal to E _SP, and the boundaries of the frequency spectra of the extreme signals coincide with the boundaries of the FS FPS. The value of p = 1. The width of the FS FPS is Δf _FPS = f _B -f _N , where f _B and f _N are the upper and lower boundary frequencies of the PP FPS, respectively. The receiver tuning frequency is equal to the carrier frequency f _{0 of the} desired signal and is located in the center of the FS FOS, but at the edge of the FS FPS and is equal to f ₀ = f _H + Δf _P / 2. The width of the FS FOS Δf _FOS is equal to the width of the frequency spectrum of the desired signal received by the receiver and is equal to Δf _P , that is, Δf _FOS = Δf _P. With this setting of the receiver, the width of the FOS FOS is determined by the upper FOS delay band and is equal to Δf _OT = f _V - (f _H + Δf _P ). The number of ordered interference signals when the PP FPS receiver is fully loaded with signals with the corresponding frequencies f ₁ , f ₂ , f ₃ , f ₄ , f ₅ , f ₆ , f ₇ , f ₈ , f ₉ , f ₁₀ , f ₁₁ , f ₁₂ , ..., f _(n-2) , f _(n-1) , f _n , is n, which is determined by the formula:

when calculating n, the integer part of the number is taken.

The nonlinear interaction of these signals in the elements of the receiving path leads to the appearance of intermodulation components of the third and higher orders, the frequencies of which coincide with the tuning frequency of the radio receiver f ₀ . In this measurement method, intermodulation interference of odd orders higher than the third is intermodulation interference of higher orders. Third-order intermodulation interference is considered in this method as a result of the interaction of triples and pairs of interference signals of the form f ₀ = f ₁ + f ₂ -f ₃ ; of the form f ₀ = 2f ₁ -f ₂ ; of the total form f ₀ = f ₁ + f ₂ -f ₃ and f ₀ = 2f ₁ -f ₂ , higher order intermodulation interference is considered in this method as a result of the interaction of pairs of interference signals of the types: f ₀ = 3f ₂ -2f ₃ , f ₀ = 4f ₃ -3f ₄ , f ₀ = 5f ₄ -4f ₅ , f ₀ = 6f ₅ -5f ₆ , f ₀ = 7f ₆ -6f ₇ , f ₀ = 8f ₇ -7f ₈ , f ₀ = 9f ₈ -8f ₉ , f ₀ = 10f ₉ -9f ₁₀ , f ₀ = 11f ₁₀ -10f ₁₁ , f ₀ = 12f ₁₁ -11f ₁₂ , ..., f ₀ = (n-1) f _(n-2) - (n-2 ) f _(n-1) , f ₀ = nf _(n-1) - (n-1) f _n , so f ₀ = kf _(k-1) - (k-1) f _k , where k = 3 , 4, ..., 11, 12, ..., n-1, n.

The maximum numbers of triples and pairs of interference signals in the FS FPS that create third-order intermodulation interference are determined respectively by the formulas:

where p = 1, when calculating n _triples , n _{pairs, the} integer part of the number is taken.

The maximum number of pairs of interference signals in the FS FPS creating intermodulation interference of each of the higher orders (orders above the third) is determined by the formula:

where p = 1, k = _3,4 , ..., n, when calculating n _{pairs, the} integer part of the number is taken.

Obviously, the number of pairs and triples of interference signals creating intermodulation components of the third and higher orders, when the ordered radiation of the radio stations, according to the model in figure 3, completely depend on the width of the PP FPS receiver. All intermodulation components arising as a result of the nonlinear interaction of a large number of pairs and triples of interference signals in the FS FPS, folding in the FOS FS, increase the overall level of interference oscillations at the receiver output.

Known methods include measuring the DD of the radio by intermodulation only of the third order, taking into account and without taking into account the number of triples and pairs of interference signals located in the receiver's FPS. However, the known methods do not measure the intermodulation components of higher orders and calculate their sums without taking into account and taking into account the width of the PP FPS receiver, which arise as a result of the interaction of pairs of interference signals located in the PP FPS receiver. The absence of such measurements is due to the narrow FS FPS and transfer (amplitude) characteristics of the receivers, where the integral non-linearity prevails, at which the levels of intermodulation components of higher orders are small compared to the level of the intermodulation component of third order. However, in receivers with a wide FPS FS, the number of intermodulation components of higher orders is large and should be measured. In addition, in the transfer characteristics of the ADC and DAC receivers, along with integral non-linearity, differential non-linearity with local points of “kinks” and “kinks” is strongly manifested, where the derivatives (non-linearity parameters) reach high values. Therefore, under the action of signals with relatively low levels at the input, relatively high levels of intermodulation components of higher orders arise at the output of the receiver. Therefore, for a complete and accurate quantitative assessment of the receiver DD by intermodulation, measurements of intermodulation components of higher orders are necessary, and the levels of interference signals at the receiver input should be changed in order to more accurately identify local points of differential nonlinearity of the receiver transfer characteristic.

The main objective of the proposed method is the measurement and calculation of intermodulation interference in the FS FOS receiver, consisting of the sum of the intermodulation components of higher orders, the sum of the intermodulation components of higher orders and third order, without and taking into account the width of the PP FPS receiver.

To solve this problem, we use the model shown in Figure 4, according to which the receiver tuning frequency is equal to: f ₀ = f _Н + Δf _И / 2, where Δf _And is the width of the measuring frequency interval, which is chosen so that the interference signals are in PP FPS and PZ FOS, with Δf _AND ≥Δf _P. The number of measuring frequency intervals in the FS FPS receiver s is selected from the condition:

When you initially set the frequency of the interference signals, the frequencies of the first and second interference signals are respectively equal: f _1,1 = f ₀ + 1Δf _AND f _2,2 = f ₀ + 2Δf _AND . The frequency tuning of the interference signals is carried out step by step with a frequency step equal to the frequency interval Δf _AND . At the first frequency tuning step (i = 1), the frequency of the first interference signal is set equal to f _1,2 = f ₀ + 2Δf _AND , the frequency of the second interference signal is set to f _2,3 = f ₀ + 3Δf _AND . In the second frequency tuning step (i = 2), the frequency of the first interference signal is set to f _1.3 = f ₀ + 3Δf _AND , the frequency of the second interference signal is set to f _2.4 = f ₀ + 4Δf _AND . In the third frequency tuning step (i = 3), the frequency of the first interference signal is set to f _1.4 = f ₀ + 4Δf _AND , the frequency of the second interference signal is set to f _2.5 = f ₀ + 5Δf _AND and so on. At the mth step of frequency tuning (i = m), the frequency of the first interference signal is set equal to f _{1, (s-1)} = f ₀ + (s-1) Δf _And , the frequency of the second interference signal is set to f _{2, s} = f ₀ + sΔf _AND . Thus, each frequency step number i = 1, 2, 3, ..., m, corresponds to the frequencies of the first and second interference signals, respectively, f _{1, (k-1)} = f ₀ + (k-1) Δf _And and f _{2 , k} = f ₀ + kΔf _AND , where k = i + 2 = 3,4,5, ..., s = m + 2. Therefore, i = k-2, ..., m = s-2, where k is the number of frequency intervals Δf _{AND the} frequency offset of the second interference signal from f ₀ . The indices in the designation of the frequencies (f _{1, (k-1)} , f _{2, k} ) of the interference signals indicate, respectively, the number of the interference signal and the number of measuring frequency intervals Δf _{AND the} frequency offset of the corresponding interference signal from f ₀ .

The EMF levels of the interference signals also change step by step from the EMF value equal to E ₀ to the EMF value equal to E _Pn , and then to the EMF value equal to E _P with a measuring amplitude interval Δe. The number of amplitude steps q corresponding to the value of E _Pn is r = (E _Pn -E ₀ ) / Δe, the number of amplitude steps q corresponding to the value of E _P is R = (E _P -E ₀ ) / Δe. Each amplitude step q = 1, ..., r, ..., R of each frequency step i = 1, ..., m corresponds to the EMF levels of the interference signals, the values of which are determined by the formula: E _qi = E ₀ + q _i Δe, since the EMF levels the interference signals at each frequency step are changed identically, then E _qi = E _q = E ₀ + qΔe, and thus, the step-by-step distribution of the EMF levels of the interference signals is a sequence:

E ₁ = E ₀ + 1Δe, ..., E _r = E ₀ + rΔe = E _Pn , ..., E _R = E ₀ + RΔe = E _P

To measure the intermodulation components of the form f ₀ = 2f _1,1 -f _2,2 and types: f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} use one pair of interference signals. The numbers of N orders of intermodulation here are equal as the sum of the numbers of frequency intervals Δf _And , on which each of the two interference signals from f _{0 is} tuned, therefore, for third-order interference of the form f ₀ = 2f _1,1 -f _2,2 , the order number is N _{(1 + 2)} = 1 + 2 = 3, i.e. 3rd order. For higher-order interference of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k, the} numbers of orders N _{(k-1 + k)} are equal to: k-1 + k = 2k-1, i.e. (2k-1) -e orders, where k = 3, ..., s, and thus the numbers of higher orders are equal; N _(2k-1) = 5, 7, ..., 2s-1, therefore, the measured maximum highest order of intermodulation interference is: N _max = 2s-1. Since the number of the frequency step i = k-2, ..., m = s-2, the order of the measured intermodulation component depending on the number of the frequency step of the pair of interference signals is calculated by the formula: N _i = 2i + 3. Obviously, you can set any higher odd order of the measured intermodulation component from the series N = 5, 7, ..., 2k-1, then determine the number of measuring frequency intervals for the detuning of the second interference signal from f ₀ and the number of the frequency step of the interference signals for the measured order, respectively formulas: k = (N + 1) / 2, i = (N-3) / 2. Depending on the N _max, you can calculate the value of .DELTA.f _And according to the formula: Δf = 2Δf _{and FPS} / (N _max +3), in which a pair of interference signals are evenly distributed in the PP FPS, while the value of .DELTA.f _should be such that the signals interference were in the PP FPS and in the PP FOS, that is, Δf _And ≥f _OT -f ₀ .

Before measuring the DD of the receiver by intermodulation, a numerical value Δf _{P is set} according to the model shown in Fig. 3. The number of interference signals in the PP FPS radio receiver is determined by the formula (1). The number of triples (n _triples ) of interference signals is determined by the formula (2). The number of pairs (n _pairs ) of interference signals is determined by the formula (3), and when Δf _P = Δf _{AND the} number of pairs (n _pairs ) of interference signals is determined by the formula (4). However, according to FIG. 4, for Δf _AND > Δf _{P, the} intermodulation order number is determined by the frequency step number of the pair of measurement interference signals in the FPS FS. Therefore, the number of pairs of interference signals in the FS FPS that create intermodulation components of higher orders at the corresponding frequency step number, according to Figure 4, is determined by the formula:

where p = 1, k _i is the number of frequency measurement intervals Δf _{and the} detuning of the second measurement interference signal from f ₀ at the corresponding frequency step number i = 1, 2, ..., m is calculated by the formula: k _i = i + 2 = 3, 4 , ..., s = m + 2.

For a certain value of the probability of occurrence of each of n independent signals at the corresponding frequency positions in the FS FPS, at which the corresponding intermodulation components of the third and higher orders occur, lying in the range 0 <p <1, the number of triples and pairs of interference signals are determined respectively by the formulas:

The measurement process is as follows. According to FIG. 4, the receiver tuning frequency is set to f ₀ = f _H + Δf _AND / 2, while the value of the measuring frequency interval Δf _{And is} chosen so that the frequencies of the first and second interference signals, the values of which are respectively equal to f _1,1 = f ₀ + Δf _AND and f _2.2 = f ₀ + 2Δf _AND , were in PP FPS and in FZ FOS. At the input of the receiver, a noise EMF is supplied, while the spectral power density (intensity) of the noise is set to kT, J, (W / Hz), where k is the Boltzmann constant equal to 1.38 · 10 ^-23 J / K, T is the absolute temperature , in degrees Kelvin, K, while T is taken depending on the noise figure (sensitivity) of the receiver from the condition: 0.01T ₀ ≤T≤60T ₀ , where T ₀ is the standard room temperature equal to 293K (t = 20 ° C) . For example, if T = T ₀ is adopted, the noise intensity is equal to kT ₀ ≈4 · 10 ^-21 J, (W / Hz), then the noise emf level equal to E _Ш , at the receiver input to the FS FPS is determined by the formula: E _Ш = (4 R kT ₀ Δf _{ave FBS)} ^1/2, where _{R, etc.} - receiver input resistance. At the same time, at the receiver output, the noise voltage level U _{W is} measured, the value of which is fixed, then the nominal value of the voltage level of the output signal U _{N is} calculated by the formula:

where h is a given coefficient, which is determined based on the required signal-to-noise ratio at the output of the receiver, with h> 1, the value of U _{N is} fixed, after which the noise signal is turned off. Then, an unmodulated or modulated calibration signal is supplied to the input of the radio receiver, the calibration signal tuning frequency is set equal to the receiver tuning frequency f ₀ , the EMF level of the calibration signal is changed to a value of E ₀ until the voltage level of the output signal of the receiver reaches the nominal value U _N , while E ₀ is fixed, then a calibration signal is turned off, while the receiver input is fed the first and second modulated or modulated interference signals with the same levels of electromotive force, When the values of the first and second interference signals, respectively, set the frequency f _1,1 and f _2,2. Then the EMF levels of the first and second interference signals are increased simultaneously, maintaining the same, to such an EMF value equal to E _P , until the voltage level of the output signal of the receiver reaches the nominal value U _N , the value of E _{P is} fixed, while the ratio of the value of the EMF level of any of the two equal in level of interference signals E _P to E ₀ determines the receiver DD by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 , which in decibels is determined by the formula:

where E ₀ is the EMF value of the calibration signal in microvolts, E _P is the EMF value of one of two equal in level signals of interference in microvolts, in the logarithmic scale of the signal levels DD is determined by the formula:

where E ₀ is the value of the EMF of the calibration signal in dB · μV, _EP is the value of the EMF of one of two equal in level signals of interference in dB · μV. The value of D [dB] is determined mainly by the integral nonlinearity of the amplitude characteristic of the receiver. Then, the receiver DD is calculated by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 taking into account the FS FPS width, and the EMF level of one of n equal in level interference signals in the FS FPS receiver is calculated respectively according to the formulas:

and translate the value of E _Pn dB · μV in a linear scale of signal levels according to the formula:

The values of E _Pn μV and E _Pn dB · μV are fixed.

The value of E _Pn determines the maximum EMF level of each of n interference signals in the receiver's FPS PP, at which the total level of the third-order intermodulation interference voltage at the receiver output created by pairs and triples of equal interference signals in the PPS FS does not exceed the value of U _N. Therefore, the receiver DD by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 , taking into account the width of the FS FPS, is calculated by the formula:

where E ₀ is the EMF value of the calibration signal in microvolts, E _Pn is the EMF value of one of n equal in level signals of interference in microvolts, in the logarithmic scale of the levels of DD signals is determined by the formula:

where E ₀ is the value of the EMF of the calibration signal in dB · μV, E _Pn is the value of the EMF of one of n equal in level of interference signals in dB · μV. The value of D _P [dB] is fixed. Further, the frequency of the first and second measurement interference signals is changed step by step relative to the receiver tuning frequency f _0, respectively, from values equal to f _1,1 = f ₀ + 1Δf _AND and f _2,2 = f ₀ + 2Δf _AND to values equal to f _{1, (k-1)} = f ₀ + (k-1) Δf _AND and f _{2, k} = f ₀ + kΔf _AND , where k = 3, 4, ..., s is the number of measuring frequency intervals Δf _{AND the} detuning of the second interference signal from frequency f ₀ receiver settings, s is determined by the formula (5). At each step of setting the frequency i of the first and second interference signals, the levels of the interference signals are set equal to E ₀ , and then the EMF levels of the interference signals are changed simultaneously and step by step with the measuring amplitude interval Δe from the value of E ₀ to the value of E _Pn and then to the value of E _P according to the sequence : E _{q, i} = E ₀ + q _i Δe = E _{1, i} = E ₀ +1 _i Δe, ..., E _{r, i} = E ₀ + r _i Δe = E _Pn , ..., E _{R, i} = E ₀ + R _i Δe = E _P , where q _i is the number of the amplitude step at the frequency step i. The values of the emf E _0, E _Pn, E _P, Δe expressed in microvolts (uV). For each installation at the input of the receiver of the corresponding EMF level of interference signals in the range of levels from E _{1, i} to _{Er , i} = E _Pn and further to E _{R, i} = E _P inclusive, at the same time, the corresponding voltage of the output signal from U is measured at the receiver output _{1, i} to U _{r, i} and further to U _{R, i} inclusive. All values of the EMF levels at the input of the receiver and the voltage levels at the output of the receiver, corresponding to each amplitude step q _i , are recorded (remembered). Next, from the measured voltage values of the output signal for each frequency step i = 1, ..., m, the maximum values are determined. First, the maximum values from the voltage range from U _{1, i} to U _{r, i are} identified and these values are designated as U _{(r, i) max} , then the maximum values from the voltage range from U _{1, i} to U _{R, i are} identified and these values as U _{(R, i) max} . The revealed maximum voltage values are the maximum voltage values of intermodulation components of higher orders, the numbers of which, depending on the frequency step number, are determined by the formula: N _i = 2i + 3, where i = 1, 2, 3, ..., m. It should be noted that the measured values of the voltage of the output signals of the receiver contain a noise component, therefore, when calculating the voltage of the output signals, it is necessary to take into account the values of the noise voltage at the output of the receiver. The total voltage of the output signal of the receiver, which is the sum of the intermodulation components of higher orders, is calculated by the formula:

The value of the total voltage U _Σm is the sum of the maximum voltage values of the intermodulation components of higher orders, from the 5th to (2m + 3) -th, at the output of the receiver of the types f ₀ = kf _{1 (k-1)} - (k-1) f _2k excluding the width of the PP FPS.

The total voltage of the output signal of the receiver, which is the sum of the intermodulation components of higher orders and the intermodulation component of the third order, is calculated by the formula:

The value of the total voltage U _Σmn is the sum of the intermodulation components of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _(k-1) - (k-1) f _k without taking into account the width of the PP FPS receiver. By the formula (6) calculate the number of pairs of interference signals n _pairs . Next, calculate the total voltage of the output signal of the receiver, which is the sum of the intermodulation components of higher orders taking into account the width of the PP FPS receiver according to the formula:

The value of the voltage level U _Σmn is the sum of the maximum values of the voltages of the intermodulation components of higher orders at the output of the receiver of the form f ₀ = kf _{1 (k-1)} - (k-1) f _2k taking into account the width of the PP of the FPS of the receiver.

The total voltage of the output signal of the receiver, which is the sum of the intermodulation components of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _(k-1) - (k-1) f _k taking into account the width of the PP FPS receiver is calculated by the formula:

Then, the first and second interference signals are turned off, and an unmodulated or modulated calibration signal is supplied to the receiver input, the frequency of the calibration signal is set equal to the receiver tuning frequency f ₀ , and then the calibration signal level is changed to such an EMF value equal to E _0m, while the output signal voltage level receiver reaches the value U _Σm, calculated according to formula (13), the value E _0m fixed, then change the level of the calibration signal to a value of EMF equal _0mn E until the voltage level receiver output signal reaches the value U _Σmn calculated by the formula (14), the value E _0mn fixed, then change the calibration signal level to a value of EMF equal E _0mn, while receiver output voltage level reaches values UΣ _mn, calculated according to the formula (15), the value of E _{0mn is} fixed and then the level of the calibration signal is changed to such an EMF value equal to E _0mnn , until the voltage level of the output signal of the receiver reaches the value U _Σmnn calculated by formula (16), the value of E _{0mnn is} fixed. After that, the dynamic ranges are calculated by the formulas:

where E _P is the EMF value of one of two equal-level interference signals in microvolts, E _Pn is the maximum EMF level of each of n signals in the receiver's FPS PP in microvolts, E _0m , E _0mn , E _0mn E _0mnn are the EMF values of the calibration signals in microvolts (μV) at the input of the receiver, corresponding to the total voltage of the output signals, calculated respectively by the formulas: (13), (14), (15), (16). The receiver dynamic ranges D _m [dB] and D _mn [dB], calculated according to formulas (17) and (18), respectively, represent the receiver DD according to the total intermodulation of higher orders of the form f ₀ = kf _(k-1) - (k -1) f _k and DD according to the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _(k-1) - (k-1) f _k without taking into account the width of the FS of the FPS receiver. The receiver dynamic ranges D _mn [dB] and D _mnн [dB], calculated according to formulas (19) and (20), respectively, represent the receiver DD according to the total intermodulation of higher orders of the form f ₀ = kf _(k-1) - (k -1) f _k and DD according to the sum of the intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _(k-1) - (k-1) f _k taking into account the width of the FS of the FPS receiver.

On a logarithmic scale of signal levels, DDs are calculated according to the formulas:

where E _P is the value of the EMF of one of two equal in level interference signals in dB · μV, E _Pn is the maximum level of the EMF of each of n signals in the FS FPS of the receiver in dB · μV, E _0m , E _0mn , E _0mn , E _0mnn - EMF values of calibration signals in dB · μV.

Obviously, for D _m [dB] and D _mn [dB], the upper boundaries of DD are E _P μV or E _P dB · μV, the value of which is determined by direct measurement, and for D _mn [dB] and D _mnн [dB] the upper the DD boundaries are E _Pn dB · μV or E _Pn μV, the values of which are calculated according to formulas (10) and (11), respectively. However, the lower boundaries of the dynamic ranges D _m [dB], D _mn [dB], D _mn [dB], D _mnn [dB] are different, the values of which are respectively equal, E _0m , E _0mn , E _0mn , E _0mnn and are expressed either in μV, or in dB · μV.

The proposed method for measuring the receiver DD by intermodulation allows us to experimentally study both the integral nonlinearity and the differential nonlinearity of the transfer (amplitude) characteristics of the radio receiving path and its elements.

The choice of the smallest of the measured values of D _m [dB] and D _mn [dB], as well as from D _mn [dB] and D _mnn [dB] allows us to give a fairly complete and accurate quantitative estimate of the dynamic range of the receiver by intermodulation.

According to Figure 5 the switching points between passbands FPS1, FPS2, FPS3 receiver m3 and m4 is working PP FPS2, whose width is equal to Δf = f _FPSp -f _{Hp Vp} where _Vp f - value of the upper operating frequency corresponding to point m4, f _Hp - the value of the lower operating frequency corresponding to point m3. The values of f _Bp , f _Hp , Δf _FPSp are given in the technical (passport) data of the receiver, according to which they measure the receiver DD by intermodulation. It also shows the true value of the width of the FS FPS2 equal to Δf _FPS = f _B -f _N , where f _B and f _N are the values of the upper and lower boundary frequencies corresponding to the normalized attenuation of the signals in the _FS FPS equal to A _{1 FPS} . Obviously, Δf _FPS > Δf _FPSp , and therefore, a greater number (n) of interference signals are located in the true PP FPS2 receiver. Similar discrepancies can be in the characteristics of the PP and PZ FOS of the receiver. Therefore, the measurements to determine and refine the boundary frequencies and the widths of the PP FPS, PP and PZ FOS, as well as the magnitude of the measuring frequency interval Δf _And refine the measurements and calculations of the receiver DD by intermodulation.

According to the model shown in Fig.6, the FPS has a PP equal to Δf _FPS , FOS has a PP and PZ (lower and upper), respectively, equal to Δf _FOS , Δf _NC and Δf _BZ , two measuring signals with the same levels E _И1 and E _И2 equal to E _AND are located in the FS FPS and in the FS FOS, the calibration signal and the noise EMF with levels respectively equal to E _K and E _{W are} located in the FS FOS. The upper and lower boundary frequencies of the PP FPS, PP and PZ FOS are designated respectively as: f _V and f _N , f _in and f _n , f _OZ and f _NC .

When measuring the values of f _In and f _N , f _in and f _n , f _OZ and f _NC , Δf _FPS , Δf _FOS , Δf _NC and Δf _OZ , Δf _And to the input of the receiver tuned to a given frequency f _K , the noise emf is applied, the spectral power density (intensity) of the noise is set equal to kT, J, (W / Hz), where k is the Boltzmann constant equal to 1.38 · 10 ^-23 J / K, T is the absolute temperature, K, while T is set depending on the noise figure (sensitivity) of the receiver, it is chosen from the condition: 0.01T ₀ ≤T ≤60T ₀ , where T ₀ is the standard room temperature equal to 293K (t = 20 ° C). For example, in the case of adoption of T = T ₀ , the noise intensity is kT ₀ ≈4 · 10 ^-21 J, (W / Hz), then the noise emf level equal to E _Ш , at the input of the receiver in the FS FPS is determined by the formula: E _Ш = (kT ₀ 4 R Δf _{ave FBS)} ^1/2, where R _pr - the value of the input impedance of the receiver. At the same time, at the receiver output, the noise voltage level U _{W is} measured, the value of which is fixed, then the required output voltage level of the calibration signal U _{K is} determined by the formula:

where A _З is the specified value of attenuation at the boundaries of the PF FOS in times, U _D is the level of maximum permissible voltage, above which the overload of the receiving path occurs. Then the noise emf is turned off and an unmodulated calibration signal is supplied to the receiver input with a frequency equal to the receiver tuning frequency f _K , the emf level of the calibration signal is changed to such a value E _K until the voltage level of the receiver output signal reaches U _K , then the frequency of the calibration signal is increased to such a value equal to f _in , at which the level of the output voltage U _K decreases by a predetermined number A ₁ times and becomes equal according to the formula:

where A ₁ is the specified attenuation at the boundaries of the FS FOS, while the frequency f _is fixed, then the frequency of the calibration signal continues to increase to a value equal to f _OT , at which the output voltage level U _K decreases by a specified number of A ₃ times and is established equal according to the formula:

in this case, the f _O value is fixed, then the frequency of the calibration signal is set equal to f _K and then the frequency is reduced to such a value f _H at which the output voltage level U _{K will} also decrease by a predetermined number A ₁ time and become equal to U _K1 = U _K / A ₁ , while the value of f _{n is} fixed and then continue to reduce the frequency value of the calibration signal to a value equal to f _NC , at which the output voltage level U _K decreases by a predetermined number of A _Z times and becomes equal to U _KZ = U _K / A _Z , the value of f _{NC is} fixed, but m calculate the width of the FS FOS according to the formula: Δf _FOS = f _in -f _n , the calibration signal is turned off, and the first and second unmodulated measuring signals with the same EMF levels and frequencies correspondingly equal according to the formulas are fed to the receiver input:

where Δf _AND is the value of the measuring frequency interval of the detuning of the measuring signal from the receiver tuning frequency f _K , which is chosen from the condition:

the EMF levels of the measuring signals are increased simultaneously, keeping them the same, to such a value E _1I = E _2I = E _AND , until the voltage level of the output measuring signal of the receiver reaches a predetermined value U _AND , while:

where the coefficient g is chosen from the condition: 5≤g≤30, then simultaneously increase the frequency values of the first and second measuring signals according to the formulas:

moreover, Δf _1VAR and Δf _2VAR = 2Δf _1VAR are the variable values of the detunings from the receiver tuning frequency f _K , which are determined according to the formulas:

here j is the tuning step number, Δf _jvar is the value of the variable frequency tuning step of the first measuring signal, which is chosen from the condition: Δf _min ≤Δf _jvar ≤Δf _max , 2Δf _jvar is the variable frequency tuning step of the second measuring signal, which is chosen from 2Δf _min ≤2Δf _jvar ≤2Δf _max , for Δf _max ≥Δf _FOS , Δf _min ≤Δf _FOS / d, where d is the maximum number of steps for tuning the frequencies of the first and second measuring signals, which is chosen from the condition: (f _K / Δf _FOS ) ≤ d <∞, an increase in the frequencies of the first and second measurement signals odyat to such values respectively equal _1I f = (f _B + f _R) / 2 and _2I f = f _B, in which the level of the output voltage U _and reduced to a predetermined number of times _1FPS A and set to the formula:

where A _{1 FPS} is the attenuation value at the boundaries of the _FS FPS, the frequency value f _{B is} fixed, then the frequency values of the first and second measuring signals are set, respectively, according to the formulas:

where Δf _AND is the value of the measuring frequency interval of the offset from the receiver tuning frequency fK, which is chosen from the condition:

the EMF levels of the measuring signals are changed simultaneously, keeping them the same, to such a maximum value of E _1I = E _2I = E _AND , until the voltage level of the output measuring signal of the receiver reaches a predetermined value U _AND , then simultaneously reduce the frequency values of the first and second measuring signals according to the formulas :

moreover, Δf _1VAR and Δf _2VAR = 2Δf _1VAR are the variable values of the detunings from the receiver tuning frequency f _K. The frequencies of the first and second measuring signals are reduced to values corresponding to f _1I = (f _K + f _N ) / 2 and f _2I = f _N , at which the output voltage level U _AND decreases by a predetermined number A _{1 FPS} times and _becomes equal U _K2 = U _AND / A _{1 FPS} , the value of the frequency f _{N is} fixed. Then calculate the width of the FS FPS according to the formula: Δf _FPS = f _B -f _N , where f _B and f _N are the upper and lower boundary frequencies of the PP FPS at a given receiver tuning frequency f _K.

The essence of the additional measurement of the boundary frequencies f _In and f _N FPS receiver is as follows. As a result of nonlinear interaction in the receiving path of two measuring signals with the corresponding frequencies, an intermodulation component of the third order is created with a frequency equal to the tuning frequency of the receiver, which operates in the FS of the receiver, while the frequencies of the measuring signals are in the FS of the receiver.

The first and second measuring signals with the same EMF levels equal to E _1I = E _2I = E _AND , and with frequencies respectively equal: f _1I = f _K ± Δf _AND and f _2I = f _K ± 2Δf _AND , act on the input of the receiver. The EMF level of the input interference input E _BX is expressed as:

E _IN = E _{1 and} cosω _{1 and} t + E _{2 and} cosω _{2 and} t,

where ω _1И = 2πf _1И = 2πf _К ± 2πΔf _И = ω _К ± Δω _И ,

ω _2I = 2πf _2I = 2πf _K ± 2π2Δf _AND = ω _to ± 2Δω _and .

It should be noted that the EMF levels of the measuring signals are set equal to such values of E _И1 = E _2И = E _И , so that only the integral non-linearity of the transfer characteristic of the receive path is manifested.

The voltage level of the third-order intermodulation component (output measuring signal) in the receiver’s FSF arising as a result of the interaction of the input measuring signals in the receiving path with the integral non-linearity of the transfer characteristic is determined by the formula:

U _И = (S ″ / 3!) E ³ _ВХ = (S ″ / 3!) [Е _1И cos (ω _К ± Δω _И ) t + E _2И cos (ω _К ± 2Δω _И ) t] ³ ,

where S ″ is the second derivative of the steepness S at the operating point of the amplitude characteristic of the nonlinear receiving path.

Using well-known trigonometric formulas:

cos ² α = (1 + cos2α) / 2;

2cosαcosβ = cos (α + β) + cos (α-β),

we find that the EMF of the third-order intermodulation component reduced to the receiver input, the frequency of which coincides with the receiver tuning frequency ω _K = 2πf _K , is determined by the formula,

E _int = (S ″ / S8) E ² _1I E _2I cosω _K = 0,125 (S ″ / S) E ² _1I E _2I cosω _K , and the voltage level of the intermodulation component acting in the FS FOS at the receiver output is:

U _AND = (S ″ / 8) E ² _1I E _2I = 0,125 S ″ E ² _1I E _2I.

From the formula it follows that the voltage level U _AND changes in proportion to the EMF level of the second measuring signal E _2I . Thus, when the frequency of the second measuring signal reaches the cutoff frequencies f _V or f _H , then its level E _2I will decrease by A _{1 FPS} times and _become equal to E _2I / A _{1 FPS} . Therefore, the voltage level of the output measuring signal U _AND will decrease by a predetermined number A _{1 FPS} times and will be set equal to U _K2 = 0.125 S ″ E ² _1I E _2I / A _1FPS = U _AND / A _1FPS .

Then, the measuring signals are turned off, and a modulated calibration signal with an emf level equal to E _{K is} applied to the receiver input, the calibration signal tuning frequency is set equal to the frequency _OZ , while the output voltage level will be set to U _KZ , the frequency of the calibration signal is increased to f _V , in this case, during the adjustment of the frequency of the calibration signal, the output voltage level must correspond to the condition according to the formula:

Next, the frequency of the calibration signal is set equal to f _NC , while the output voltage level is set equal to U _SC , then the frequency of the calibration signal is reduced to a value of f _N , while during the tuning of the frequency of the calibration signal, the output voltage level must meet the condition according to formula (33). Then calculate the width of the upper and lower FZ FOS respectively according to the formulas:

When tuning the frequency of the calibration signal in the upper and lower FZ FOS, the frequency values at which the output voltage level does not meet the condition according to formula (33), and therefore, the output voltage level is higher than the specified value, i.e., U _К3 > U _К / A _З , fix and exclude from the frequency setting of the interference signals when measuring the receiver DD by intermodulation.

Thus, additional measurements of the upper and lower boundary frequencies of the PP FPS, PP and PZ FOS, calculating the values of the width of the PPS FPS, PP and PZ FOS of the receiver, determining the value of the measuring frequency interval Δf _AND increase the accuracy of the quantitative estimation of the receiver DD by intermodulation in real reception conditions.

A device is known for measuring the dynamic range of a radio receiver by intermodulation (see GOST R 52016-2003 “Receivers of the main radio communication of the hectometer-decameter wavelength range.” Parameters, general technical requirements and measurement methods. Adopted and enforced by Resolution of the Russian State Standard of February 6, 2003 No. 47-st. Date of introduction 2004-01-01).

The device contains: two of the same type of signal generators, matching device, receiver, voltmeter, load equivalent, while the first and second generators outputs are connected respectively to the first and second inputs of the matching device, the output of which is connected to the input of the receiver, the output of which is connected to interconnected inputs voltmeter and radio load equivalent.

The device measures the DD by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 using two of the same type of generators and gives a fairly accurate quantitative estimate of the DD receiver by intermodulation of the form f ₀ = 2f _1,1 -f _2,2 .

However, the device does not allow measuring the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ , of the total form f ₀ = f _1,1 + f _2,2 -f _3,3 , f ₀ = 2f _1,1 - f _2.2 , measure and calculate the DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ taking into account the width of the PP FPS receiver, the total form f ₀ = f _1,1 + f _2,2 -f _3,3 , f ₀ = f _1,1 -f _2,2 , taking into account the width of the FS FPS receiver and the type f ₀ = 2f _1,1 -f _2,2 , taking into account the width of the PP FPS receiver, does not allow to measure and calculate the receiver DD by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , intermodulation DD of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the PP FPS of the receiver, DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , taking into account the width of the PP FPS receiver, does not determine the boundary frequencies and the widths of the PP FPS, PP and PZ FOS receiver, determine the size of the measuring frequency interval. Thus, the device does not provide an objective, complete and accurate quantitative assessment of the receiver DD by intermodulation, in addition, the measurement process in the device is not automated.

A device is known for measuring the dynamic range of a radio receiver by intermodulation (see Patent for the invention No. 2472166, M. class G01R 23/20, publ. 10.01.2013).

The device contains: an automated workstation (AWS), a digital signal processing unit (BTsOS), a personal electronic computer (PC), the first, second, third homogeneous signal generators, matching device (SU), a radio receiver, load equivalent (EH), voltmeter, digital communication line (CLS), fiber optic communication line (FOCL), optical transceiver, optoelectronic / electron-optical converter. The workstation includes: PC, BTsOS, optoelectronic / electron-optical converter, optical transceiver. In this case, from the first to the sixth inputs / outputs of the AWP are the first to the sixth inputs / outputs of the BCOS, the input / output bus of which is connected to the output / input bus of the PC, the first signal generator, the input / output of which is connected to the first output / input of the AWP, the second and third outputs / inputs of which are connected to the inputs / outputs of the second and third signal generators, while the outputs of the first, second, third signal generators are connected respectively to the first, second, third inputs of the control system, the output of which is connected to the input of the receiver, the output of which is connected to the interconnected inputs of the electric motor and the voltmeter, the input / output of the voltmeter is connected to the fourth output / input of the AWP, the fifth output / input of which is connected to the first input / output of the radio, the second input / output of which is connected via the DLC to the sixth output to the AWP input, the third input / output of the radio receiver is connected via the FOCL to the seventh output / input of the AWP, which is the output / input of the optical transceiver, the other output / input of which is connected to the input / output of the optoelectronic / electronic-op nical converter, the other input / output of which is connected to the seventh output / input BTSOS.

The device is designed to measure DD by intermodulation in various radios that form analog, digital, optical output signals.

The device allows you to measure the receiver DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ , the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _{2 , 2} , measure and calculate the DD by intermodulation of the form f ₀ = f ₁ + f ₂ -f ₃ taking into account the width of the PP FPS receiver, the total form f ₀ = f _1,1 + f _2,2 -f _3,3 and f ₀ = 2f _1,1 -f _2,2 taking into account the width of the PP FPS receiver and the type f ₀ = 2f _1,1 -f _2,2 taking into account the width of the PP FPS receiver. The choice of the smallest value from the measured and calculated in the device values of the DD by intermodulation taking into account the width of the PP FPS receiver allows you to give an objective quantitative assessment of the DD of the radio receiver by intermodulation. The measurement process in the device is fully automated.

However, the device does not allow to measure and calculate the receiver DD by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , by the intermodulation DD of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS of the receiver, DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1 ) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS receiver. Therefore, the device does not provide a sufficiently complete and accurate quantitative assessment of the receiver DD by intermodulation, in addition, the device does not determine the upper and lower boundary frequencies of the PP FPS, PP and PZ FOS, calculates the width of the PP FPS, PP and PZ FOS receiver, determines the value measuring frequency interval, which reduces the accuracy of measuring DD by intermodulation.

This device for measuring the DD of the radio intermodulation selected for the prototype.

Achievable technical result of the invention is to expand the functionality of the device by providing the ability to measure the DD of the radio by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , by intermodulation of the form f ₀ = kf _{1, ( k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS of the receiver, DD by the sum of the intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} taking into account the width of the FS FPS receiver, as well as additionally: the measurement of the boundary frequencies of the PP FPS, PP and PZ FOS, the determination of the values of the width of the PP FPS, P P and PZ FOS of the receiver, determining the size of the measuring frequency interval.

     The achievement of the technical result is provided in the device for measuring the DD of an intermodulation radio receiver containing an automated workstation (AWS), which includes a digital signal processing unit (BTOS), a personal electronic computer (PC), an optical transceiver, and an optoelectronic / electron-optical converter, first and second signal generators, matching device (CS), radio receiver, load equivalent (EL), voltmeter, digital communication line (CLS), fiber-optic communication line (V LS), while in the AWP the first input / output bus of the PC is connected to the first output / input bus of the BCOS, from the first to sixth inputs / outputs of which are the first to sixth inputs / outputs of the AWP, the first input / output of which is connected to the output / input the first signal generator, the output of which is connected to the first input of the control system, the second input of which is connected to the output of the second signal generators, the output / input of which is connected to the second input / output of the AWP, the fourth input / output of which is connected to the output / input of the voltmeter, the input of which is connected to from a single input between the electric drive input and the output of the radio, the first input / output of which is connected to the fifth output / input of the AWP, while the radio is equipped with a second digital input / output, which is connected via the DLC to the sixth output / input of the AWP, the third optical input / output, which via FOCL it is connected to the seventh output / input of the workstation, which is the output / input of the optical transceiver, the other output / input of which is connected to the input / output of the optoelectronic / electron-optical converter, the other input / output of which о is connected to the seventh output / input of the BCOS, characterized in that a managed switch (CC), a noise generator are introduced, and a memory device (memory) is inserted into the AWP, while the first input of the CC is connected to the control unit output, and its output is connected to the radio input , the second CC input is connected to the output of the noise generator, the control and monitoring input / output of which is connected to the connected CC control and control input / output and the third output / input of the AWP and, respectively, the third output / input of the BCOS, the second input / output bus of which is connected to the first output / input bus of the memory, the second input / output bus of which is connected to the second output / input bus of the PC.

Introduction to the proposed device that implements a method for measuring the DD of a radio receiver by intermodulation, memory, CC and a noise generator allows you to measure the DD of a radio receiver by intermodulation of the form f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , by intermodulations of the form f ₀ = kf _{1 (k-1)} - (k-1) f _{2, k} taking into account the width of the FS of the FPS of the receiver, DD according to the sum of the intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - (k-1) f _{2, k} , DD by the sum of intermodulations of the types f ₀ = 2f _1,1 -f _2,2 and f ₀ = kf _{1, (k-1)} - ( k-1) f _{2, k} taking into account the width of the receiver PP FBS, and further allows to identify and clarify the boundary frequency LRF PP, PP and PP FBF value measurable tionary frequency interval and calculate the widths FBS PP, and the PP GSH FOS receiver.

This allows you to expand the functionality of the device to ensure a complete and accurate quantitative assessment of the DD of the radio receiver by intermodulation.

The block diagram of the proposed device is shown in FIG. 7, in accordance with which the device contains an automated workstation 1 (AWP), while the first through sixth inputs / outputs of the AWP 1 are the first through sixth inputs / outputs of the digital signal processing unit 2 (BTSC), the first input / output bus of which connected to the first output / input bus of a personal computer 3 (PC), the first signal generator 4, the input / output of which is connected to the first output / input of the AWP 1, the second output / input of which is connected to the input / output of the second signal generator 5 at this exits generators 4 and 5 of the signals are connected respectively to the first and second inputs of the matching device 6 (SU), the output of which is connected to the first input of the input controlled switch 7 (UK), the second input of which is connected to the output of the input noise generator 8, the input / output of which is connected to the input / output of UK 7 and the third output / input of ARM1 are interconnected, while the output of UK 7 is connected to the input of the radio receiver 9, the output of which is connected to interconnected inputs of the equivalent of 10 load (EL) and voltmeter 11, the input / output of the voltmeter 11 is connected to the fourth output / input of the workstation 1, the fifth output / input of which is connected to the first input / output of the radio 9, while the radio 9 is equipped with a second digital input / output, which is connected to the sixth output / input via a digital communication line 12 (DLC) AWP 1, the third optical input / output, which is connected via the fiber-optic communication line 13 (FOCL) to the seventh output / input of the AWP 1, which is the output / input of the optical transceiver 14, the other output / input of which is connected to the input / output of the optoelectronic / uh of an optical-optical converter 15, the other input / output of which is connected to the seventh output / input of the BCOS 2, the second input / output bus of which is connected to the first output / input bus of the storage device 16 (memory), entered into the AWP 1, the second input / output bus which is connected to the second output / input bus of the PC 3.

The device is designed to measure DD by intermodulation in various radios that form analog, digital, optical output signals.

The principle of operation of the proposed device for measuring the DD of a radio receiver by intermodulation is as follows. According to the structural diagram of the device shown in Fig.7, in the memory 16, which is entered into the AWP 1, through the PC 3 or BTSOS 2 included in the AWP 1, enter: the values of f _B and f _N , the value Δf _P , the value Δf _FOS , Δf value _And , Δe value, coefficient value h, probability value p, then using the PC 3, the receiver tuning frequency is calculated by the formula f ₀ = f _Н + Δf _И / 2, the PP FPS width is calculated by the formula Δf _FOS = f _V -f _H is calculated and the number s is chosen according to the condition (5), calculate the maximum number of frequency steps i = 1, ..., m (1 to m) by the formula m = s-2, the number n is calculated according to the formulas (1) calculating a number: n _triplets, n _pairs, n _pari respectively by the formulas (2), (3), (6) when p = 1, and respectively by the formulas (2 ^*) (3 ^*), (6 ^* ) at 0 <p <1, while all the calculated values are transferred to the memory 16. Next, using the AWP 1, set the frequency of the receiver 9 to f ₀ , then using the AWP 1 and the newly introduced CC 7, connect the output of the newly introduced noise generator 8 to the input of the receiver 9, while connecting the second input of the UK 7 with the output of the UK 7 include a noise generator 8 and the input of the receiver serves a noise emf, while the spectral power density (intensively st) the noise of the generator is set equal to kT, J, (W / Hz), where k is the Boltzmann constant equal to 1.38 · 10 ^-23 J / K, T is the absolute temperature, in degrees Kelvin, K, the value of T is taken depending from the noise figure (sensitivity) of the receiver from the condition: 0.01T ₀ ≤T≤60T ₀ , where T ₀ is the standard room temperature equal to 293K (t = 20 ° C). When T = T _{0 is} adopted, the noise intensity is equal to kT ₀ ≈ 4 · 10 ^-21 J, (W / Hz), and the level of noise EMF acting in the FS FPS at the input of the receiver 9 is equal to E _Ш = (4 kT ₀ R _Гш Δf _FFF) ^1/2, where R = R _{rm etc.} - noise generator internal resistance equal to the resistance of antenna input (input impedance) receiver 9, respectively. At the same time, at the output of the receiver 9, with the help of a voltmeter 11, the noise voltage level U _{Ш is} measured at ЭН 10 and, using the digital input / output of the voltmeter 11, the value of U _Ш is transferred to BTsOS 2, where it is processed and transmitted to PC 3 and memory 16. With a digital output the noise signal in digital form through the DLC 12 is transmitted to BTsOS 2, where it is processed, measured and transmitted to the PC 3 and the memory 16. At the optical output of the receiver, the noise signal in optical form via FOCL 13, an optical transceiver, optoelectronic / electron-optical a transmitter transmitted to BTSOS 2, where it is processed, is measured and transmitted to the PCs 3 and memory 16, then the PC 3 is calculated in the nominal value of the output signal voltage level U _H by the formula (7) and transmitted to the memory 16. Further, by using APM 1 and UK 7 disconnect the output of noise generator 8 from the input of receiver 9, while disconnecting the second input of UK 7 from the output of UK 7, and connect the first input of UK 7 to the output of UK 7, thereby connecting the output of SU 6 to the input of receiver 9, while generator 8 noise is turned off, then using AWP 1 turn on the generator 4 and set the frequency n modulated or of the modulated calibration signal equal to f _0. The calibration signal of the generator 4 through the SU 6 and CC 7 is fed to the input of the receiver 9, then using the AWP 1 change the EMF level of the calibration signal of the generator 4 to such a value of E ₀ until the voltage level of the output signal of the receiver 9 to EN 10 reaches the nominal value U _N , which is measured by voltmeter 11, and using the digital input / output of voltmeter 11, the value of U _H is transmitted to BTsOS 2, where it is processed and transmitted to PC 3 and memory 16, while the value of E _{0 is} also transmitted to PC 3 and memory 16. Then, at help arm 1, include a second generator 5 and Further, in the first 4 and second 5 generators, the frequencies of the output signals are set respectively to f _1.1 = f ₀ + Δf _AND and f _2.2 = f ₀ + 2Δf _AND , and the EMF levels are the same. The signals of the generators 4 and 5, through the control system 6 and CC 7, are fed to the input of the receiver 9. Then, using the AWP 1, the EMF levels of the generators 4 and 5 are simultaneously changed, keeping them the same, to such a value _EP , while the voltage level of the output signal of the radio receiver 9 at EH 10 it does not reach the nominal value of U _N , which is measured with a voltmeter 11, and using the digital input / output of the voltmeter 11, the value of U _H is transmitted to BTsOS 2, where it is processed and transmitted to PC 3, while the value of E _P is transmitted by PC 3 to Memory 16. Then in the PC 3 calculate the value the receiver DD by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 , D [dB], with a linear scale of generators 4 and 5 according to formula (8), with a logarithmic scale of generators 4 and 5 according to formula (8 ^* ), then calculate the receiver DD value D _P [dB], by third-order intermodulation of the form f ₀ = 2f _1,1 -f _2,2 taking into account the width of the FS FPS, using formula (9) and calculate the value of the EMF level E _{Пn of} one of n equal in level signals of interference in the receiver's FPS PP, with the logarithmic scale of generators 4 and 5 according to formula (10) and transferred to the linear scale of generators 4 and 5 according to formula (11), all techniques, are transmitted values in the memory 16. Then, the PC 3 calculates the maximum number of amplitude steps q, _Pn corresponding to the values E _n and E, respectively, by the formulas: r = (E ₀ -E _Pn) / Δe and R = (E _n -E ₀ ) / Δe. Then, using the AWP 1 in the first 4 and second 5 generators, the frequencies of the output signals are increased by one measuring frequency interval Δf _AND , that is, the first frequency step is made (i = 1), setting the frequencies of the output signals respectively to f _1,2 = f ₀ + 2Δf _AND and f _2,3 = f ₀ + 3Δf _AND , and the EMF levels of the output signals are equal to E ₀ . Then simultaneously change the EMF levels of the output signals of the generators 4 and 5 step by step with a measuring amplitude interval Δe. With each setting of the EMF level of the output signals of the generators 4 and 5 from E _{1, i = 1} = E ₀ + 1Δe to E _{r, i = 1} = E ₀ + rΔe = E _Pn and then to E _{R, i = 1} = E ₀ + RΔe = E _P inclusively at the input of the receiver 9, at the output of the receiver 9 using a voltmeter 11 measure each corresponding voltage of the output signal at the EN 10 from U _{1, i = 1} to U _{r, i = 1} and then to U _{R, i = 1,} inclusive, and using the digital input / output of the voltmeter 11, all measured values of output voltage signals, after each measurement, transmitted in BTSOS 2, where they are processed and transmitted to the PC 3 in the memory 16, all values of the level of EMF g generators of 4 and 5 at the input of the receiver 9 is also transmitted to the memory 16. Further, by using the PC 3 and the memory 16 from the measured receiver output signal voltages from 9 U _{1, i = 1} to U _{r, i = 1} identify the maximum value of U _{(r , i = 1) max} , then from the measured values from U _{1, i = 1} to U _{R, i = 1, the} maximum value U _{(R, i = 1) max} . Then, using the AWP 1 in the first 4 and second 5 generators, the frequencies of the output signals are increased by one measuring frequency interval Δf _AND , that is, the second frequency step is taken (i = 2), setting the frequencies of the output signals respectively to f _1.3 = f ₀ + 3Δf _AND and f _2.4 = f ₀ + 4Δf _AND , and the EMF levels of the output signals are equal to E ₀ and repeat the step-by-step change in the EMF levels at the input of the receiver 9 and the step-by-step measurement of the voltage values of the output signals of the receiver 9 to the electric heater 10 with a voltmeter 11 with supply their digital input / output in BTsOS 2, PC 3, memory 16, identifying When aid PC 3 and the maximum value memory 16. Thus, the measurements are as follows: each time increasing the frequencies of the output signals of the first 4 and second 5 generators by Δf _And , setting the frequencies of the output signals, respectively, from the values of f _1,1 = f ₀ + 1Δf _And and f _2,2 = f ₀ + 2Δf _AND to values equal to f _{1, (k-1)} = f ₀ + (k-1) Δf _And and f _{2, k} = f ₀ + kΔf _And , where k = 3,4, ..., s, and at each setting of the frequency of the generators 4 and 5, the EMF levels of the first 4 and second 5 signal generators are changed step by step from the EMF value equal to E ₀ to the EMF value equal to E _Pn , and then to the EMF value equal to E _P , with measuring amplitude int interval Δe. Depending on the generators 4 and 5 scale value emf E _0, E _Pn, E _P, Δe can be expressed in microvolts (uV) or in decibels relative to one microvolt (dB microvolts). With each setting of the EMF level at the output of generators 4 and 5, in the level range from E _{1, i} to _{Er , i} = E _Pn and further to E _{R, i} = E _P inclusive, at the output of receiver 9 to 10, using a voltmeter 11, each corresponding voltage of the output signal is measured, respectively, from U _{1, i} to U _{r, i} and further to U _{R, i} inclusive, using the digital input / output of voltmeter 11, each measured value of the voltage of the output signals is transmitted to BTsOS 2, where each measured value it is processed and transferred to PC 3 and to memory 16, while all the signs set using AWP 1 The values of the EMF levels of the generators 4 and 5 operating at the input of the receiver 9 are transmitted by means of a personal computer 3 to the memory 16. Using the AWP 1, the first 4 and second 5 generators are turned off. Then, using a PC 3 and a memory device 16, the voltage values measured at voltmeter 11 for 10 frequency steps i are determined by comparing maximum values for each frequency step i. First, the maximum values are revealed from the voltage range from U _{1, i} to U _{r, i} , equal to U _{(r, i) max} , then from the voltage range from U _{1, i} to U _{R, i} , equal to U _{(R, i) max} . Then, using a PC 3 and a memory 16, the total voltages U _Σm , U _Σmn , U _Σmn , U _{Σmnn are calculated} using formulas (13), (14), (15), (16), respectively. All the calculated values in the PC 3 are transferred to the memory 16. Then, using the AWP 1, turn on the first generator 4, set the frequency of the output calibration signal to f ₀ and then change the EMF level of the calibration signal of the generator 4 to a value equal to E _0m , while the voltage level is ЭН 10 of the output signal of the receiver 9, measured by a voltmeter 11, does not reach the value U _Σm calculated by the formula (13), while the value of E _0m is transmitted to the memory 16 using PC 3, then using the AWP 1 the level of the calibration signal of the generator 4 is changed to that whose EMF value is equal to E _0mn , until the voltage level at the ЭН 10 of the output signal of the receiver 9, measured by a voltmeter 11, reaches the value U _Σmn calculated by formula (14), while the value of E _0mn is transmitted using PC 3 to the memory 16, then, using the AWP 1, the level of the calibration signal of the generator 4 is changed to such an EMF value equal to E _0mn , until the voltage level at the ЭН 10 of the output signal of the receiver 9, measured by the voltmeter 11, reaches the value U _Σmн calculated by the formula (15), while the value of E _0mn is transmitted using the PC 3 in the memory 16 , then with the help of AWP 1, the level of the calibration signal of the generator 4 is changed to an EMF value equal to E _0mnн , until the voltage level on the ЭН 10 of the output signal of the receiver 9, measured by voltmeter 11, reaches the value U _Σmnн calculated by formula (16), at In this case, the value of E _0mnn is transmitted using PC 3 to the memory 16. After that, using the PC 3 and memory 16, the dynamic ranges D _m [dB], D _mn [dB], D _mn [dB], D _mnn [dB] are _calculated respectively formulas (17), (18), (19), (20) with a linear scale generators 4 and 5, or by (17 ^*) (18 ^*) (19 ^*) (20 ^*) for logarithmically scale generators 4 and 5, all of the calculated values using the personal computer 3 are transferred into the memory 16. Next, the PC 3 by means of the values D _m [dB] and D _mn [dB] and choosing the smallest of the values D _MH [dB] and D _mnn [dB] also select the smallest. The measurement results are displayed on the PC monitor 3 and simultaneously transferred to the memory 16.

For additional determination and clarification of the values of the upper and lower cutoff frequencies, as well as the values of the FS FPS, PP and PZ FOS of the receiver and the measuring frequency interval Δf _I , in PC 3 and memory 16 enter the values: f _K , A ₁ A _Z , A _{1 FPS} , U _D , g. Using AWP 1 and UK 7, connect the output of the noise generator 8 to the input of receiver 9, while the second input of UK 7 is connected to the output of UK 7. Using AWP 1, tune receiver 9 to a given frequency f _K , then using AWP 1 include a noise generator 8 and to the input of the receiver 9 serves a noise emf equal to E _W. At the same time, at the output of the receiver 9 to the EN 10, a noise voltage level U _{W is} measured using a voltmeter 11. It should be noted that all the measured values of the voltages at the ЭН 10 with the voltmeter 11, with the help of the digital input / output of the voltmeter 11, go to BTsOS 2, where they are processed and transmitted to the personal computer 3 and the memory 16. Then using the personal computer 3 and the memory 16 according to the formulas: ( 21), (22), (23), (26), (29), calculate the specified voltage levels at 10, respectively, U _K , U _K1 , U _KZ , U _AND , U _K2 and transferred to the memory 16 and the screen PC monitor 3. Then, using AWP 1 and UK 7, disconnect the output of noise generator 8 from the input of receiver 9, while the second input of UK 7 is disconnected from the output of UK 7, and I will turn off the noise generator 8 using AWP 1 tea. Then, using AWP 1 and UK 7, connecting the first input of UK 7 with the output of UK 7, connect the output of the first generator 4 through SU 6 and UK 7 to the input of the receiver 9. Using AWP 1 turn on the first generator 4 and set the frequency of the unmodulated calibration signal to f _K , then the EMF level of the calibration signal of the generator 4 is changed to such a value of E _K at the input of the receiver 9, until the output voltage level of the receiver 9 at EH 10, measured by voltmeter 11, reaches the value of U _K. Further, using the AWP 1, the frequency of the signal of the generator 4 is increased to a value equal to f _in , at which the output voltage level of the receiver 9 at the electric power meter 10, measured by the voltmeter 11, is set equal to U _K1 . In this case, the value of the frequency f _in , by means of a PC 3, is transferred to the memory 16. Then, using the AWP 1, they continue to increase the frequency of the calibration signal of the generator 4 to such a value equal to f _OW at which the output voltage level of the receiver 9 at 10, measured by voltmeter 11, is established equal to U _KZ . In this case, the value of _f3 by means of a PC 3 is transferred to the memory 16. Next, using the AWP 1, the frequency of the calibration signal of the generator 4 is set to f _K and then the frequency of the signal of the generator 4 is reduced to a value of f _n at which the output voltage level of the receiver 9 is at 10 as measured by voltmeter 11 was set to U _K1 value f _n by the PC 3 is transmitted to the memory 16. Further, by using APM 1 continue to decrease the value of the calibration signal generator 4, the frequency to a value equal to f _NC at which the output voltage level zheniya receiver 9 EN 10 measured by voltmeter 11, set to U _{RS, NS} value f is transmitted by the PC 3 in the memory 16. Then, using the PC 3, and the width of the memory 16 is calculated by the formula PP FOS: Δf = f _{FOS in} -f _n , the value of which is transmitted by PC 3 to the memory 16. Then, using the AWP 1, the second signal generator 5 is turned on and through the SU 6 and UK 7 two modulated measuring signals are supplied from the generators 4 and 5 to the input of the receiver 9. Using the AWP 1 on the first generator 4 and the second generator 5 set the same EMF levels of unmodulated measurements natural signals, and the frequencies of the first 4 and second 5 generators are set according to the corresponding formulas (24), while Δf _And is determined by the formula (25). Using AWP 1, the first 4 and second 5 generators simultaneously increase the EMF levels of the measuring signals, keeping them the same, to such a maximum value of E _1I = E _2I = E _And , while the output voltage level of receiver 9 at 10 is measured by voltmeter 11, not reaches the value of U _AND . Then, using AWP 1, the frequency values of the measuring signals of the first 4 and second 5 generators are simultaneously increased according to formulas (27), while the magnitude of the tuning step is changed according to formulas (28). The frequency values of the measuring signals of the first 4 and second 5 generators are increased to values corresponding to f _1I = (f _V + f _K ) / 2 and f _2I = f _V , at which the output voltage level of receiver 9 at 10 is measured with a voltmeter 11 is set equal to U _K2 . The value of f _B , via PC 3, is transferred to the memory 16. Next, using the AWP 1, the frequencies of the measuring signals of the first 4 and second 5 generators are set according to the corresponding formulas (30), while Δf _{And are} determined by formula (31) and the EMF levels are changed simultaneously the measuring signals of the generators 4 and 5, keeping them the same, to such a maximum value of E _1I = E _2I = E _AND , until the output voltage level of the receiver 9 at EH 10, measured by a voltmeter 11, reaches a predetermined value of U _AND . Then, using the AWP 1, the frequency values of the measuring signals of the first 4 and second 5 generators are simultaneously reduced according to formulas (32), while the tuning steps are changed according to formulas (28). The frequency values of the measuring signals of the first 4 and second 5 generators are reduced to values corresponding to f _1I = (f _K + f _N ) / 2 and f _2I = f _N , at which the output voltage level of receiver 9 at 10 is measured by a voltmeter 11 is set equal to U _K2 . The value of f _N is transmitted via PC 3 to the memory 16. Next, using the AWP 1, the second signal generator 5 is turned off and the frequency of the calibration signal is set at the first signal generator 4 to f _O3 , and the EMF level of the signal of the generator 4 at the input of the receiver 9 is set to E _K , wherein the level of the output voltage of the receiver 9 on the EN 10, measured by a voltmeter 11, is set equal to U _KZ . Then, using the AWP 1, the frequency of the calibration signal of the generator 4 is increased to a value of f _V , while at all frequencies from f _OV to f _{V of the} generator 4, the level of the output voltage of the receiver 9 at EH 10, measured with a voltmeter 11, must correspond to formula (33). Next, using the AWP 1, the frequency of the calibration signal of the generator 4 is set to f _NC , and the EMF level of the signal of the generator 4 at the input of the receiver 9 is set to E _K , while the output voltage level of the receiver 9 to the EN 10, measured by the voltmeter 11, is set equal to U _KZ . Then, using the AWP 1, the frequency of the calibration signal of the generator 4 is reduced to a value of f _N , while at all frequencies from f _NZ to f _{N of the} generator 4, the level of the output voltage of the receiver 9 at EH 10, measured with a voltmeter 11, must correspond to formula (33). Next, using the PC 3 and the memory 16, the width of the upper and lower FOS of the FOS is calculated according to formulas (34), the values of which are transmitted by the PC 3 to the memory 16. The frequencies of the calibration signal of the generator 4 located in the upper and lower PZ of the FOS of the receiver, at which condition (33) is not met, by means of a personal computer 3 are transferred to the memory 16 and by means of the workstation 1 are excluded from the frequency tuning of the signals of the generators 4 and 5 when measuring the receiver DD by intermodulation.

The principle of operation of the device for measuring DD by intermodulation of the radio 9, forming a digital output signal, is similar to the principle of operation described above. The difference lies in the fact that the output signal of the receiver 9 from the DLC 12 is supplied to the AWP 1, where the voltage of the output signal of the receiver 9 is measured directly to BTsOS 2 and transmitted to the PVEM 3 and memory 16. The control and monitoring of the receiver 9 is carried out using the AWS 1 through the DLC 12.

The principle of operation of the device for measuring DD by intermodulation of the radio 9, forming an optical output signal, is similar to the principle of operation described above. The difference lies in the fact that the optical output signal of the receiver 9 via FOCL 13 enters the AWP 1, where, after receiving in the optical transceiver 14 and converting the optoelectronic / electron-optical converter 15 into an electric digital signal, it enters the BTSOS 2, where it is measured and then transmitted to PC 3 and memory 16. Management and control of the receiver 9 is carried out using AWP 1 on fiber optic link 13.

Consider an example of the execution of the blocks of the proposed device for measuring the DD of the radio receiver by intermodulation.

UK 7 can be made on the basis of controlled high-frequency relays or switches, for example, the company "Nais" and others.

The noise generator 8 can be made on the basis of smoothly or discretely controlled noise sources and standards, manufactured, for example, by Agilent, Rohde & Schwarz and others, as well as on the basis of switchable “warm” and “cold” noise standards, at the same time, a “warm” standard can be made on the basis of resistive elements, a “cold” standard is made using cryogenic technology. The type of noise generator 8 is determined depending on the noise figure (sensitivity) of the receiver 9.

The memory 16 can be performed on the basis of hard magnetic disks (HDD), for example, IBM 81Y9774; Iomega 35448; Dell 400-23135 and others.

AWP 1, BTsOS 2, PC 3, generators 4 and 5, SU 6, receiver 9, EN 10, voltmeter 11, CLS 12, FOCL 13, optical transceiver 14, optoelectronic / electron-optical converter 15 can be performed similarly to the prototype or with using other similar elements.

Claims (5)

1. The method of measuring the dynamic range (DD) of the radio receiver by intermodulation, which consists in determining the width of the FS FPS (passband filter pre-selection) by the formula: Δf_FPS= f_B-f_Hwhere f_Band f_H - respectively, the upper and lower boundary frequencies of the FS FPS, then set the frequency interval between the signals in the FS FPS equal to Δf_P and calculate the total number of interference signals in the FS FPS by the formula: n = (Δf_FPS/ Δf_P) -1, calculate the number of triples and pairs of interference signals, respectively, by the formulas: n_triples= p³[0.375n (n-3) +1] = 0.375n (n-3) +1, n_steam= p²(n / 2) = n / 2, where p is the probability of occurrence of each of n independent interference signals at the corresponding frequency position in the receiver's FPS PP, with p = 1, then an unmodulated or modulated calibration signal is fed to the radio input, tuning frequency the calibration signal is set equal to the receiver tuning frequency f₀, the EMF level of the calibration signal is changed to such a value E₀until the voltage level of the output signal of the receiver reaches the nominal value U_H, while the value of E₀ fix, then the calibration signal is turned off, after which the first and second unmodulated or modulated interference signals with the same EMF levels are fed to the input of the receiver, the frequencies of the first and second interference signals are selected respectively f_1,1 =f₀+ Δf_AND and f_2.2= f₀+ 2Δf_ANDwhile the value of the measuring frequency interval Δf_AND offset in relation to the receiver tuning frequency f₀ chosen so that the frequencies f_1,1 and f_2.2 were in the PP FPS and in the PZ FOS (the delay band of the filter of the main selection), then the EMF levels of the first and second interference signals are increased simultaneously, maintaining the same, to such a value of the EMF equal to E_Puntil the voltage level of the output signal of the receiver reaches the nominal value U_N, the ratio of the value of the EMF level of any of two equal in level of interference signals E_P to E₀ determines receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2 ,which in decibels is determined by the formula: D [dB] = 20lg (E_P/ E₀), where E₀ - EMF value of the calibration signal in microvolts, E_P - the value of the EMF of one of two equal in level signals of interference in microvolts, in the logarithmic scale of the levels of signal DD is determined by the formula: D [dB] = E_PdB · μV-E₀dB · μV, where E₀ - EMF value of the calibration signal in dB · μV, E_P - the EMF value of one of two equal in level interference signals in dB · μV, then determine the receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2 taking into account the width of the PP FPS according to the formula:

 characterized in that before applying the calibration signal to the receiver input, the receiver tuning frequency is set to f₀= f_H+ Δf_AND/ 2, where Δf_AND> Δf_Pand a noise emf is applied to the receiver input, while the spectral power density (intensity) of the noise is set equal to kT,J, (W / Hz), where k - Boltzmann constant equal to 1.38-10^-23J / C, Τ-absolute temperature, in degrees Kelvin (K), which is taken from the condition: 0,01T₀≤Τ≤60T₀, where T₀ -standard room temperature equal to 293K, and the level of noise EMF is set equal to E_W, while the output voltage of the receiver measures the level of noise voltage U_W, then calculate the nominal voltage value of the output signal U_N by the formula: U_H= h U_W, where h is a given coefficient, and h> 1, after which the noise emf is turned off, and a calibration signal is fed to the input of the receiver even after determining the receiver DD by intermodulation of the form f₀= 2f_1,1-f_2.2 taking into account the width of the PP FPS equal to D_R, calculate the value of the EMF level of one of n equal to the level of interference signals in the PP FPS receiver according to the formula:

 then the value of E_Mon dB · μV translate into a linear scale signal levels according to the formula: E_Mon μV = 10^{(Epn dB μV / 20)}, values of E_Mon μV and E_Mon dB · μV is fixed, and then the frequencies of the first and second interference signals are changed simultaneously and step by step with the same frequency step equal to a given measuring frequency interval Δf_ANDin this case, at each frequency step, the values of the EMF levels of the first and second interference signals at the input of the receiver are set to E₀, then change simultaneously and stepwise the values of the EMF levels of the first and second interference signals with the same amplitude step equal to the specified measuring amplitude interval Δe, while the frequency values of the first and second interference signals corresponding to each frequency step are set according to the formulas: f_{1, (k-1)}= f₀+ (k-1) Δf_ANDf_{2, k}= f₀+ kΔf_AND, where k is a limited natural series of numbers 3, 4, ..., s, corresponding to the number of identical measuring frequency intervals Δf_AND frequency offset of the second interference signal from f₀, s is the number of measuring frequency intervals Δf_AND in PP FPS receiver, the value of which is determined by the formula: s≤ (Δf_FPS/ Δf_AND) -1, while the frequency step number is determined by the formula: i = (k-2) = 1,2, ..., m = s-2, the values of the EMF levels of the first and second interference signals at the receiver input, corresponding to each amplitude step at each frequency step i, set according to the formula: E_{q, i}= E₀+ qΔe = E_{1, i}= E₀+ 1Δе, ..., E_{r, i}= E₀+ rΔе = Ε_Πn, ..., E_{R, i}= E₀+ RΔe = E_P, where q is a limited natural series of numbers 1, 2, ..., r, ..., R, corresponding to the number of the amplitude step at each frequency step i = 1,2, ..., m, is q_i= l_{(1 ... m)}, 2_{(I ... m)}, ..., r_(one..._m), ..., R_{(i ... m)}, where r = (Ε_Πn-Ε₀) / Δe, R = (Ε_P-Ε₀) / Δe, all values of E_{q, i} fix, while at each amplitude step of each frequency step q_i at the corresponding amplitude steps EMF levels at the receiver input equal to E_{q; i}= E_{1, (1 ... m)}, E_{2, (1 ... m)}, ..., E_{r, (1 ... m)}, ... E_{R (1 ... m)}, simultaneously at the receiver output measure the levels of the corresponding output voltages equal to U_{q; i}= U_{1, (1 ... m)}, U_{2, (1 ... m)}, ..., U_{r, (1 ... m)}, ... U_{R (1 ... m)}, all measured voltage values are fixed, after which from the measured voltage values in the range: U_{1, (1 ... m)}, U_{2, (1 ... m)}, ..., U_{r, (1 ... m)} identify the maximum voltage values of each frequency step equal to U_{(r, i) max}= U_{(r, 1) max}, U_{(r, 2) max}, ..., U_{(r, m})_max, then from the measured voltage values in the range: U_{1, (1 ... m)}, U_{2, (1 ... m)}, ..., U_{r, (1 ... m)}, ..., U_{R, (1 ... m)}also identify the maximum voltage values of each frequency step equal to U_{(R, i) max}= U_{(R, 1) max}, U_{(R, 2) max}, ..., U_{(R, m) max}, all maximum values are fixed, then the total voltage is calculated by the formula:
$$U_{\Sigma m}={\left({\displaystyle \sum _{i=\mathrm{one}}^m{U}^2{}_{(R,i)\max }-(m-\mathrm{one})U^2{}_W}\right)}^{\mathrm{one}/2}$$

,
then the first and second interference signals are turned off, and an unmodulated or modulated calibration signal is fed to the receiver input, the frequency of the calibration signal is set equal to the receiver tuning frequency f₀, and the level of the calibration signal is changed to a value of EMF equal to E_0muntil the receiver output voltage reaches the U value_Σm, while the ratio E_P to E_0m determines receiver DD by intermodulation of the form f₀= kf_(k-1)- (k-1) f_k, which in decibels is determined by the formula: D_m[dB] = 20lg (E_P/ E_0m), where E_0m - EMF value of the calibration signal in microvolts, E_P - the value of the EMF of one of two equal in level signals of interference in microvolts, on a logarithmic scale of the levels of DD signals is determined by the formula: D_m[dB] = E_PdB · μV-E_0m dB · μV, where E_0m - EMF value of the calibration signal in dB · μV, E_P - the value of the EMF of one of two equal in level signals of interference in dB · μV, then calculate the total voltage according to the formula:
$$U_{\Sigma mn}={\left(U^2{}_N-m{U}^2{}_W+{\displaystyle \sum _{i=\mathrm{one}}^m{U}^2{}_{(R,i)\max }}\right)}^{\mathrm{one}/2},$$

after which the level of the calibration signal is changed to such an EMF value equal to E_0mnuntil the receiver output voltage reaches the U value_Σmн, while the ratio E_P to E_0mn determines receiver DD by the sum of intermodulations of types f₀= 2f_1,1-f_2.2 and f₀= kf_(k-1)- (k-1) f_k, which in decibels is calculated by the formula: D_mn[dB] = 20lg (E_P/ E_0mn), where E_0mn - EMF value of the calibration signal in microvolts, E_P - the value of the EMF of one of two equal in level signals of interference in microvolts, on a logarithmic scale of the levels of DD signals is determined by the formula: D_mn[dB] = E_P dBuV_0mn dB · μV, where E_0mn - EMF value of the calibration signal in dB · μV, E_P - the EMF value of one of two equal in level signals of interference in dB · μV, then with the corresponding number of the frequency step equal to i = 1, 2, ..., m, calculate the integer number of pairs of interference signals in the PP FPS receiver according to the formula:
n_couples= p²(n / k_i) = n / k_iwhere p = 1, k_i= i + 2 = 3,4, ..., m + 2 = s,
then calculate the total voltage by the formula:

   then change the level of the calibration signal to a value of EMF equal to E_0mnuntil the receiver output voltage reaches the U value_Σmn, while the ratio E_Mon to E_0mn determines receiver DD by intermodulation of the form f₀= kf_(k-1)- (k-1) f_k taking into account the width of the PP FPS, which in decibels is determined by the formula: D_mn[dB] = 20lg (E_Mon/ E_0mn), where E_0mn - EMF value of the calibration signal in microvolts, E_Mon - the value of the EMF of one of n equal in level of interference signals in microvolts, in the logarithmic scale of the levels of DD signals is determined by the formula: D_mn[dB] = E_Mon dBuV_0mn dB · μV, where E_0mn - EMF value of the calibration signal in dB · μV, E_Mon - the EMF value of one of n equal in level of interference signals in dB · μV, then calculate the total voltage according to the formula:

then change the level of the calibration signal to a value of the EMF equal to E_0mnнuntil the receiver output voltage reaches the U value_Σmnн, while the ratio E_Mon to E_0mnн determines receiver DD by the sum of intermodulations of types f₀= 2f_one-f₂ and f₀= kf_(k-1)- (k-1) f_k taking into account the width of the PP FPS, which in decibels is determined by the formula: D_mnн[dB] = 20lg (E_Mon/ E_0mnн), where E_0mnн - EMF value of the calibration signal in microvolts, E_Mon - the value of the EMF of one of n equal in level of interference signals in microvolts, in the logarithmic scale of the levels of DD signals is determined by the formula: D_mnн[dB] = E_Mon dBuV_0mnн dB · μV, where E_0mnн - EMF value of the calibration signal in dB · μV, E_Mon - the value of the EMF of one of n equal in level of interference signals in dB · μV, then from the obtained values of D_m and D_mn, as well as from D_mn and D_mnн choose the smallest. 2. The method according to claim 1, characterized in that for measuring the DD of the radio receiver by intermodulation up to a predetermined number of the order of intermodulation, an odd number of the order of intermodulation is set equal to the value of N _AND , which is selected from the series N = 5, 7, ..., 2n- 1, and then calculates the frequency measurement interval according to the formula: Δf = 2Δf _{and LRF} / (N _and 3) and the first condition is checked: Δf _and ≥f _OT - f _0, where f _OT - upper limiting frequency PP FOS further define the maximum the number of measuring frequency intervals of the detuning of the second interference signal from f ₀ by the formula s = (N _AND +1) / 2 and check the second condition: s≤ (Δf _FPS / f _AND ) -1, if these conditions are not met, the value of N _{And is} reduced by two units and the calculations Δf _AND and s are repeated, this repeats the verification of the first and second conditions, and so on until these conditions are met. 3. The method according to claim 1, characterized in that for measuring the receiver DD by intermodulation as applied to the electromagnetic environment (EMO) at a specific receiving site, first, by empirical studies and measuring the EMO at the receiving location, determine the probability p, the value of which lies within: 0 <p <1, then calculate the values of n _pairs , n _pairs , n _triples, respectively, by the formulas:
n _pairs = p ² (n / 2), n _pairs = p ² (n / k _i ), n _triples = p ³ [0.375n (n-3) +1]. 4. The method according to claim 1, characterized in that for determining and clarifying the boundary frequencies and widths of the PP FPS, PP and PZ FOS of the receiver, as well as determining the value of the measuring frequency interval before starting the measurement of the DD receiver by intermodulation to the input of the receiver configured to set frequency f_TOprovide noise emf with a level equal to E_Wand at the output of the receiver measure the level of noise voltage U_W, then determine the required output voltage level of the calibration signal U_TO by the formula: U_D≥U_TO≥A₃ U_Wwhere A₃ - a given amount of attenuation at the boundaries of the PP FOS, U_D - the level of the maximum allowable voltage, above which the overload of the receiving path occurs, after which the noise emf is switched off and an unmodulated calibration signal with a frequency equal to the receiver tuning frequency f is fed to the receiver input_TO, and with such an emf level equal to E_TOso that at the output of the receiver set the voltage level of the output signal U_TO, then increase the frequency of the calibration signal to a value equal to f_atat which the output voltage level U_TO decrease by a given number A_one times and will be set equal to U_K1= U_TO/ A_onewhere A_one is the amount of attenuation at the boundaries of the PP FOS, while the value of the frequency f_at fix, then continue to increase the frequency of the calibration signal to a value equal to f_OTat which the output voltage level UK decreases by a predetermined number A₃ times and will be set equal to U_KZ= U_TO/ A₃, with the value of f_OT fix, then set the frequency of the calibration signal to f_TO and further reduce the frequency of the calibration signal to such a value f_nat which the output voltage level U_TO decrease by a given number A_one times and will be set equal to U_K1= U_TO/ A_one, with the value of f_n fix and then continue to reduce the value of the frequency of the calibration signal to a value equal to f_NZat which the output voltage level U_TO decrease by a given number A₃ times and will be set equal to U_KZ= U_TO/ A₃, with the value of f_NZ fix, then calculate the width of the PP FOS according to the formula: Δf_FOS= f_at-f_nwhere f_at and f_n - respectively, the upper and lower cutoff frequencies of the FS FOS at a given receiver tuning frequency f_TO, while f_OT and f_NZ- respectively, the upper and lower cutoff frequencies of the FOS FOS at a given receiver tuning frequency f_TO, the value of Δf_FOS fix, then the calibration signal is turned off, and the first and second unmodulated measuring signals with the same EMF levels and with frequencies corresponding to f_1and= f_TO+ Δf_AND and f_2and= f_TO+ 2Δf_ANDwhere Δf_AND - the value of the measuring frequency interval of the detuning of the measuring signal from the receiver tuning frequency f_TOwhich is selected from the condition: Δf_AND≥f_OT-f_TO, the EMF levels of the measuring signals are increased simultaneously, keeping them the same, to such a maximum value of E_1and= E_2and= E_ANDuntil the voltage level of the output measuring signal of the receiver reaches the set value U_AND, while U_AND≥ă U_W, where ă is a given coefficient, which is selected from the condition: 5≤ă≤30, then simultaneously increase the frequency values of the first and second measuring signals according to the formulas: f_1and= f_TO+ Δf_AND+ Δf_1VAR; f_2and= f_TO+ 2Δf_AND+ Δf_2VAR, and Δf_1VAR and Δf_2VAR= 2Δf_1VAR - variable values of detunings from the receiver tuning frequency f_TO, which are determined according to the formulas:

here j is the number of the tuning step, Δf_jvar - the value of the variable step of tuning the frequency of the first measuring signal, which is chosen from the condition: Δf_min≤Δf_jvar≤Δf_max, 2Δf_jvar - the value of the variable pitch of the frequency adjustment of the second measuring signal, which is selected from the condition 2Δf_min≤2Δf_jvar≤2Δf_maxat Δf_max≥Δf_FOS, Δf_min≤Δf_FOS/ d, where d is the maximum number of steps for tuning the frequencies of the first and second measuring signals, which is chosen from the condition: (f_TO/ Δf_FOS) ≤d <∞, an increase in the frequencies of the first and second measuring signals is performed to such values, respectively, equal to f_1and= (f_AT+ f_TO) / 2 and f_2and= f_ATat which the output voltage level U_AND decrease by a given number A_1FPS times and will be set equal to U_K2= U_AND/ A_1FPShere A_1FPS - the attenuation at the boundaries of the PP FPS, the value of the frequency f_AT fix, then set the frequency values of the first and second measuring signals, respectively f_1and= f_TO-Δf_AND and f_2and= f_TO-2Δf_AND,
where Δf_AND - the value of the measuring frequency interval of the detuning of the measuring signal from the receiver tuning frequency f_TOwhich is selected from the condition: Δf_AND≥f_TO-f_NZ, the EMF levels of the measuring signals are changed simultaneously, keeping them the same, to such a maximum value of E_1and= E_2and= E_ANDuntil the voltage level of the output measuring signal of the receiver reaches the set value U_AND, then simultaneously reduce the frequency values of the first and second measuring signals according to the formulas: f_1and= f_TO-Δf_AND-Δf_1VAR; f_2and= f_TO-2Δf_AND-Δf_2VARwhere Δf_1VAR and Δf_2VAR= 2Δf_1VAR - variable values of detunings from the receiver tuning frequency f_TO, reducing the frequency values of the first and second measuring signals is produced to such values, respectively, equal to f_1and= (f_TO+ f_N) / 2 and f_2and= f_Nat which the output voltage level U_AND decrease by a given number A_1FPS times and will be set equal to U_K2= U_AND/ A_1FPS, frequency value f_H fix, then calculate the width of the PP FPS according to the formula: Δf_FPS= f_AT-f_Nwhere f_AT and f_N - respectively, the upper and lower cutoff frequencies of the FS FPS at a given receiver tuning frequency f_TO, then the measuring signals are turned off, and an unmodulated calibration signal with an emf level equal to E is fed to the input of the receiver_TO, the tuning frequency of the calibration signal is set equal to the frequency f_OTwhile the output voltage level is set equal to U_KZincrease the frequency of the calibration signal to f_ATwhile the output voltage level must meet the condition: U_K3≤U_TO/BUT₃then set the frequency of the calibration signal to f_NZwhile the output voltage level remains equal to U_K3, then reduce the frequency of the calibration signal to f_Hwhile the output voltage level must meet the condition: U_K3≤U_TO/ A₃, then calculate the width of the upper and lower FZ FOS respectively according to the formulas: Δf_BZ= f_B-f_BZ and Δf_NZ= f_NZ-f_N the values of the frequencies of the calibration signal in the upper and lower FOS FOS, at which U_K3> U_TO/BUT₃, fix and exclude from the frequency settings of the interference signals when measuring the receiver DD by intermodulation. 5. The device for measuring the DD of an intermodulation radio receiver containing an automated workstation (AWS), which includes a digital signal processing unit (BTOS), a personal electronic computer (PC), an optical transceiver, and an optoelectronic / electron-optical converter, the first and second signal generators, matching device (SU), radio receiver, load equivalent (EL), voltmeter, digital communication line (CLS), fiber optic communication line (FOCL), while the first input / output PC bus is connected it is connected with the first output / input bus of the central control system, from the first to sixth inputs / outputs of which are the first to sixth inputs / outputs of the AWP, the first input / output of which is connected to the output / input of the first signal generator, the output of which is connected to the first input of the control system, the second the input of which is connected to the output of the second signal generator, the output / input of which is connected to the second input / output of the AWP, the fourth input / output of which is connected to the output / input of the voltmeter, the input of which is connected to the input of the electric drive and the output of the radio receiver, the input / output of which is connected to the fifth output / input of the AWP, while the radio is equipped with a second digital input / output, which through the DLC is connected to the sixth output / input of the AWP, the third optical input / output, which is connected via the FOCL to the seventh output / input of the AWP which is the output / input of the optical transceiver, the other output / input of which is connected to the input / output of the optoelectronic / electron-optical converter, the other input / output of which is connected to the seventh output / input of the BCOS, characterized in then a managed commutator (CC), a noise generator are introduced, and a memory device (memory) is introduced into the AWP, while the first input of the CC is connected to the output of the CS, and its output is connected to the input of the radio, the second input of the CC is connected to the output of the noise generator, input / the control and monitoring output of which is connected to the connected control / monitoring input / output of the AC and the third output / input of the automated workplace and, respectively, the third output / input of the BCOS, the second input / output bus of which is connected to the first output / input bus of the memory device, the second input / output koto bus The horn is connected to the second PC output / input bus.

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