RU2345379C1 - Vhf module of superregenerative transceiver of radiosonde - Google Patents

Abstract

FIELD: physics, radio.

SUBSTANCE: invention concerns a radio engineering and can be used in aerologic radiosondes (ARS) systems of radio sounding of atmosphere for measuring of range to (ARS) using a pulsing method, direction finding on angular co-ordinates and transmissions of the telemetering information on one carrier frequency, also can be used for build-up of highly stable and economic receiving-sending devices of communication systems. SHF-module of the superregenerative transceiver containing the SHF oscilator, inertial an autobias chain, a current regulator, the busbar of a food and the zero busbar, differing is offered to that the current regulator contains the regulating transistor, the first, second, third and fourth resistors, the first, second, third and fourth condensers with following linkings: the regulating transistor is executed under the plan with the blanket emitter, and the datum of the transistor is joined to a medial point of the resistive divider executed on the first and second resistors, the divider extremities are joined to the busbar of a food and the zero busbar; the emitter of the regulating transistor through the third resistor is joined to the food busbar, and is immediate - with a collector of the transistor of the SHF oscilator: The collector of the regulating transistor through the fourth resistor is joined to datum of the target transistor and the second extremity of the fourth condenser which first extremity is an inlet of all target stage; input inertial the autobias chain contains consistently joined the sixth constant resistor, the first and second the diode in a forward direction to the zero busbar, and the point of linking of the sixth resistor and the first diode through consistently joined the fifth variable resistor and the fourth condenser is joined to datum of the SHF generator.

EFFECT: increase of stability of operation of SGH radiosondes in the conditions of destabilising factors, pinch of sensitivity, power of radiation and stability of an operating mode of the superregenerative transceiver, decrease in level of power consumption from the power supply, increase of ARS operating time; decrease of ARS mass and dimensions parameters; increase of adaptability to manufacture and manufacture depreciation.

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Description

The invention relates to radio engineering and can be used in aerological radiosondes (ARZ) of atmospheric radio sounding systems for measuring ranges to ARZ using a pulsed method, direction finding by angular coordinates and transmitting telemetric information on one carrier frequency, can also be used to build highly stable and economical transceiver devices of systems communication.

Domestic atmospheric radiosounding (SR) systems are constructed using the goniometer-range measuring method for measuring coordinates, velocity and direction of radiosonde movement in a free atmosphere. Measurement of angular coordinates: - azimuth (β), elevation angle (ε), as well as slant range (R _n ) using a pulsed method with an active response. It turned out to be especially effective when using super-regenerative transceivers (SPP) as part of radiosondes. Intensive SPP radiation provides reliable transmission of telemetric information and tracking along angular coordinates. The high sensitivity of the SPP to the pulsed interrogation signal allows generating a range response signal in the form of a short pause in the SPP emission at a reduced transmitter power of the interrogated radar radar. Ultimately, it is very important that the coordinate determination system and the telemetry information transmission channel of the radio sounding system operate at the same carrier frequency.

A common problem in the production and operation of ARZs is the creation of low-cost designs of transceiver devices that are stable in radio engineering under changing ambient temperature, supply voltage and ARZ antenna system parameters.

Known superregenerative transceiver containing serially connected generator of superimposing pulses, a capacitor, an oscillator and an antenna, a power source, the first output of which is connected to the second outputs of the oscillator and generator of the superimposing pulses, and the oscillator includes a transistor and a resonator, the inputs and outputs of which are the same inputs and the oscillator outputs, and the base, collector and emitter of the transistor are connected respectively to the first, second inputs and the second output of the resonance Ora, characterized in that, in order to increase the stability of the parameters, an average current stabilization unit is introduced into it, the first and second inputs of which are connected respectively to the second and first outputs of the power source, and the first and second outputs are connected to the second and first inputs of the oscillator (see RF patent No. 1106262. Super regenerative transceiver).

A superregenerative radiosonde transceiver is known, the microwave oscillator of which is built according to a two-cavity circuit implemented on microstrip lines. The introduction of a resonator in the emitter circuit allows, within certain limits, to regulate the module and phase of the feedback coefficient of the SPP microwave oscillator, and thereby increase the sensitivity of the SPP (see RF patent No. 2172965. Super regenerative transceiver).

A patent is known which describes the design and parameters of the ARZ antenna system equipped with a super-regenerative transceiver. The proposed design of the antenna system ARZ allows you to configure the operating frequency and sensitivity of the SPP (see RF patent No. 2214614. Transceiver system of the aerological radiosonde and its design).

A known super-regenerative radiosonde transceiver, the microwave oscillator of which is connected to the ARZ antenna system through a band-pass filter, which reduces the influence of active external interference and decouples the ARZ antenna from the collector circuit of the microwave transistor for direct current (see RF patent No. 56001 for utility model. aerological radiosonde).

A superregenerative radiosonde transceiver is known, in the microwave oscillator of which a varicap is introduced, controlled by a signal proportional to the amplitude of the microwave oscillations. This allows adjusting the signal amplitude to combine the frequency of the reception and transmission of the SPP (see RF patent No. 49283 for a utility model. Super-regenerative transceiver with a combination of reception and transmission frequencies).

A known super-regenerative radiosonde transceiver, the microwave oscillator of which is built according to the most advanced three-resonator circuit, implemented on microstrip lines. The introduction of the third resonator into the base circuit made it possible to separately regulate the module and phase of the feedback coefficient of the microwave oscillator and, therefore, adjust the sensitivity and output power of the SPP (see RF patent No. 50682 for a utility model. Super regenerative transceiver is a prototype).

The disadvantage of all known technical solutions and prototype is the significant influence of the inductances of the connecting conductors between the circuit board of the microwave oscillator and the ARZ telemetry unit. This spurious negative effect is manifested in the form of low-frequency shock oscillations arising under the action of pulses of the generator of the supervising voltage on the inductors of the connecting conductors in the control circuit of the microwave oscillator SPP. The presence of low-frequency shock vibrations leads to a decrease in the sensitivity and stability of the SPP.

An object of the invention is to increase the stability of the SPP radiosondes in conditions of destabilizing factors due to:

- creating a schematic, technical and constructive solution to reduce the level of spurious shock oscillations, thereby increasing the sensitivity, radiation power and stability of the super-regenerative transceiver;

- reducing the level of power consumption from the power source by reducing the number of active elements and increasing efficiency, i.e. ultimately an increase in the operating time of the ARZ;

- reducing the overall dimensions of the ARZ;

- improving manufacturability and reducing production costs.

To solve this problem, a microwave module of a super-regenerative transceiver is proposed, comprising a microwave autogenerator, an inertial self-bias circuit, a current stabilizer, a power bus and a zero bus, characterized in that the current stabilizer contains a control transistor, first, second, third and fourth resistors, the first, the second, third and fourth capacitors with the following connections: the control transistor is made according to the scheme with a common emitter, and the base of the transistor is connected to the midpoint of the resistive divider, complements the first and second resistors, the ends of the divider are connected to the power bus and neutral bus; the emitter of the control transistor through a third resistor is connected to the power bus, and directly to the collector of the transistor of the microwave oscillator; the collector of the control transistor through the fourth resistor is connected to the base of the output transistor and the second end of the fourth capacitor, the first end of which is the input of the entire output stage; the input inertial auto-bias circuit contains a sixth constant resistor connected in series, the first and second diodes connected in the forward direction to the zero bus, and the connection point of the sixth resistor and the first diode is connected through the fifth variable resistor and the fourth capacitor in series with the microwave generator base, and for of eliminating the parasitic circuit excitation effect in the control circuit of the SPP by the input current pulses, the condition of shock vibration damping is fulfilled in the form:

R ² C / 4L >> 1,

where R is the total series resistance of the sixth and fifth resistors of the auto-bias circuit; L is the total inductance of the connecting conductors in the control circuit of the microwave oscillator; C is the capacity of the auto-bias circuit, in this case the fourth capacity,

and to ensure the required speed of starting current establishment, the performance condition is additionally fulfilled

2L / R << T _c,

where T _c is the period of superimposing pulses U _c.

The microwave oscillator is made according to the patent of the Russian Federation No. 2291467, is made on a microstrip board with surface mounting.

To explain the essence of the invention, the following diagrams, graphs and drawings are given: Figure 1 - Structural diagram of a super-regenerative transceiver; Figure 2 - Oscillograms explaining the principle of operation of the SPP with the rigid nature of the establishment of self-oscillations; Figure 3 - Dependence of the attenuation of the circuit of the microwave oscillator from the amplitude of the oscillations; Figure 4 - (a) - The mechanism of shock excitation of the microwave circuit of the SPP pulses of the starting current of the emitter; (b) - distortion of the inrush current by pulses of the supercharging signal due to the inductance of the connecting conductors; 5 is a Functional diagram of a super-regenerative transceiver; 6 is a Functional diagram of a microwave module superregenerative transceiver; Fig. 7 is an electrical diagram of a microwave module of a super-regenerative transceiver; Fig. 8 shows a design of a microstrip board of a microwave module of a super regenerative transceiver.

The block diagram of the SPP has the following connections: the power bus Ep is connected to a current stabilizer 4 and to a generator of a supervoltage voltage 1, the input of the latter is a modulation input, and the output is connected via an inertial auto-bias circuit 2 to a current stabilizer 4 and a microwave oscillator 5, the output of a current stabilizer 4 connected to the power bus of the microwave oscillator 5, the output / input of which is connected to the transceiver antenna 6.

The structural diagram of the SPP shown in figure 1, contains: a generator of a supervising voltage (GSP) - 1; inertial auto-bias circuit - 2; microwave power supply voltage stabilizer - 3; the average current stabilizer of the microwave oscillator - 4; Microwave oscillator - 5; transceiver antenna AP3-6.

The fundamental features of the functioning of the SPP can be explained by analyzing its operation during one period of the supervising frequency T _c . Figure 2 shows: U _c is the voltage of the superimposing frequency, characterized by a period of T _s and a duration of τ _s ; δ _(t) is the law of variation of the attenuation decrement of the circuit of the microwave oscillator; - the U _rad - the envelope of the radio pulse emitted by the CPR _{and the} duration τ.

The SPP microwave self-oscillator is periodically turned on at the moment of the appearance of the super-impulse U _c and turns off when it ends in the damping interval τ _d . The operating frequency of the microwave oscillator is about 1800 MHz. The frequency of the supervising voltage is 800 kHz. The oscillation system of the SPP in the off state is characterized by its own attenuation δ ₀ . The change in the loop attenuation during the superization pulse τ _c determines the process of development and establishment of oscillations in a stationary mode.

To ensure high sensitivity in the receiving mode, it is necessary to turn on the microwave oscillator with the minimum value of the starting negative attenuation δ _p. To achieve the maximum output power proportional to A _st in SPP, it is necessary to increase the negative attenuation in the medium and large amplitudes for this type of active oscillator device . For the implementation of these conflicting requirements, it turned out to be necessary to implement a regime of rigid oscillation establishment in the NGN circuit. This result can be obtained by analyzing a simplified version of the nonlinear equation of the oscillator that does not take into account the effect of a weak external signal on the stationary amplitude:

A qualitative analysis of the equation allows you to find out the features of the behavior of the function δ (t, A) in the time domain (Figure 2) and depending on the amplitude of oscillations A (Figure 3). The study of various options for the implementation of the function δ (t, A) shows that, in contrast to the soft mode of oscillation establishment in the classical superregulator recommended in the well-known literature, it is necessary to implement a transition process in the SPP with a rigid nature of oscillation establishment [1]. In this case, the triggering of the SPP can occur with a minimum negative attenuation value δ _p , which ensures a minimum bandwidth and high sensitivity. The stationary mode is established in the region of maximum amplitudes A _st , therefore, at a high level of output power. It must be emphasized that the change in starting attenuation δ _p practically does not affect And _Art. This allows, ultimately, separately and effectively adjust the parameters of the receiving and transmitting modes of operation of the SPP by adjusting the starting current of the microwave oscillator at the time of switching on. It should be emphasized that in order to ensure a transient process with a rigid nature of the establishment of oscillations, it is necessary to control the base circuit of the microwave oscillator transistor to control the voltage pulses generated by the super-voltage generator with a low output resistance. In practice, these pulses are generated using directly biased diodes, which provide a low differential output resistance of the seeker. The maximum negative attenuation in the region of average amplitudes provides a quick transition from the receiving to the transmitting mode of operation of the SPP. This contributes to the formation of almost rectangular radio pulses and a symmetric spectrum of the SPP radiation characteristic of a sequence of radio pulses.

The superregenerative amplification effect is reduced by reducing the delay time τ _{s of the} leading edge of the microwave pulses of the microwave oscillator by Δτ _s when an external signal U _{ss appears} during the reception interval of operation τ _pr adjacent to the time of the start of the SPP. The level of the output signal of the NGN, depending on the level of the request signal in the primary response mode, can be estimated using a simplified expression:

Where

A _Σ is the effective amplitude of the noise in the NGN circuit at the time of startup; A _c is the amplitude of the external signal.

The above expressions show that the amplification effect Δτ _s is mainly determined by the value of the starting attenuation δ _p. The occurrence of self-oscillations occurs with the starting attenuation δ _p = 0, when the collector current of the active device is equal to the boundary value I _к = I _gr . The development of self-oscillations occurs when δ _p > 0, which is determined by the starting current of the self-oscillator I _p > I _gr at the time of inclusion. Therefore, by changing the value of I _p , the delay time τ _s and the gain effect are adjusted — the delay time increment Δτ _s . Thus, the SPP is a transceiver with a temporary separation of the receiving and transmitting operating modes.

It is important to emphasize that practically in the transistor microwave oscillator SPP, the starting current I _p during the receiving interval exceeds the boundary value of I _{g by} only tens to hundreds of microamps. Therefore, to reduce the effect of shock excitation of the circuit of the microwave oscillator and ensure high sensitivity, the shape of the emitter current pulses during the receiving interval should be gradually increasing from zero to the starting value of I _p (see figure 2). Further, the constant component of the emitter current I _eo (and the collector current I _ko = I _eo ) changes synchronously with the amplitude of the self-oscillations due to the hard nature of the transient process to the maximum values for this active device until the steady-state mode is established. It should be emphasized that the stationary amplitudes A _st and I _emax do not depend on the value of the starting current I _p. It should be noted that the average value of the collector direct current I _{to cf} for the period of superization is determined by the ratio of τ _s and τ _s. Since the value of τ _{s is} regulated by the starting current I _p , it turns out that adjusting the average current I _{to cp} causes a corresponding change in the starting current of the microwave oscillator. For example, by increasing the average current I increases _{to cf.} inrush current I _n, which leads to a reduction _of the delay time τ, τ radio pulse duration increase _and decrease and the sensitivity. As the average current I _{k c} decreases, the process goes in the opposite direction. Thus, the stabilization of I _{to sr} makes it possible to stabilize τ _s , therefore, the sensitivity and bandwidth in the receiving mode, as well as the duration and power of the emitted SPP radio pulses τ _and . Accordingly, the choice of the duration of superimposing pulses τ _s allows us to optimize the ratio of sensitivity and radiated average power of the SPP.

The mechanism of shock excitation of the circuit of a microwave oscillator with inrush current pulses is known (see pages 140-146 [2]) and is shown in Fig. 4 (a). Shock microwave oscillations are indicated by the number 1, self-oscillations of the microwave oscillator are indicated by the number 2. By choosing the minimum inrush current I _p <2-5 mA and the steepness of its growth, it is possible to reduce the level of shock microwave oscillations to the level of fluctuation noise of the order of minus 120-125 dB / Tue

The studies carried out in the process of working on the application materials made it possible to find out another mechanism of additional low-frequency shock vibrations that disrupt the operation of the SPP. In known devices, the GOS is connected to the SPP microwave oscillator using connecting conductors having a finite inductance value. To analyze the mechanism of additional shock vibrations, Fig. 5 shows a functional diagram of a real SPP radiosonde, comprising: a generator of a supervising voltage (GOS) - 1; microwave power supply voltage stabilizer - 2; the average current stabilizer of the microwave oscillator - 3; inertial auto-bias circuit formed by the output equivalent resistance of the seeker, the resistor - 4, the input equivalent resistance of the microwave oscillator and the capacitor - 5; Microwave oscillator - 4; the inductance of the structural conductors in the GSN output circuit, the auto-bias circuit, and the control input of the microwave oscillator is 7. The ARZ transceiver antenna is not conventionally shown.

The pulses of the current generated by the GOS, create at the inductance 7 low-frequency shock oscillations in the control circuit of the microwave oscillator. Since, as noted earlier, in fact, the difference between the boundary and starting currents of the microwave oscillator is only tens to hundreds of μA, this leads to a distortion of the shape of the starting current of the emitter I _eo during the receiving interval (see Fig. 4, b), therefore, reduce the sensitivity and stability of the NGN. An analysis of the parameters of the parasitic circuit in the control circuit of the SPP control circuit shows that in order to eliminate the effect of excitation of the parasitic circuit in the control circuit of the SPP current impulses of the seeker, it is necessary to fulfill the condition for damping low-frequency shock oscillations in the form

where R is the total series resistance of the circuit auto-bias circuit; L is the total inductance of the connecting conductors in the control circuit of the microwave oscillator; C is the capacity of the auto-bias circuit.

In practice, the values of R and C can change dozens of times from the nominal values during the adjustment of the SPP; therefore, to ensure the required rate of establishment of the starting current, it is necessary to additionally fulfill the performance condition

Thus, to ensure both requirements, it is necessary in the design of the SPP to minimize the stray inductance of the connecting conductors in the control circuit of the SPP.

The best constructive solution to this problem is achieved by placing the output stage of the GSN generating control video pulses directly on the microstrip board of the microwave oscillator. Moreover, the inductance of the connecting printed conductors is stable and minimally possible. Ultimately, in such a design, a smooth and fairly fast inrush current is established during the receive interval of the SPP, which allows you to effectively control the passband and sensitivity of the SPP, significantly improve the stability of its operation.

Figure 6 shows the functional diagram of the microwave module. It contains a GSN output circuit, a current stabilizer, and a microwave oscillator. 7 shows an electrical diagram of a microwave module of a super regenerative transceiver. One of the options for the structural combination of the output stage of the GOS, the current stabilizer and the microwave oscillator in the microstrip design is shown in Fig. 8.

As noted above, an important node of the SPP is the stabilizer of the average current of the microwave oscillator. It is also structurally located on the microwave module board. The stabilizer is as follows. The average current stabilizer of the microwave oscillator is made on the transistor VT1; resistors R1, R2, R3, R4; capacitors C1, C2, C3. Resistors R1, R2 form the bias circuit of the base of transistor VT1. On resistor R3, the average collector current I _{to cf of the} microwave oscillator VT2 creates a voltage drop that is blocking for the transistor VT1. The current value I _{to cp is} regulated by the choice of the ratio of resistors R1, R2. With increasing current I _{to cf} under the influence of destabilizing factors, the transistor VT1 will lock and reduce the base current of the microwave transistor, returning the current value I _{to cf} to the set value. With a decrease in current I _{to cf,} the stabilization process goes in the opposite direction. Capacitors C1, C2, C3 are turned on so that they provide effective filtering of the current pulses of the collector of transistor VT2 and the corresponding phase shift of the disturbing effect along the feedback circuit formed by transistor VT1 in order to minimize the effect of collector current pulses of VT2 on the receive mode of the SPD. It should be emphasized that the bias circuit R1, R2 provides correction of the current I _{to sr} when changing the supply voltage of the collector circuit E _to so that the sensitivity of the SPP remains constant. So with increasing supply voltage E _to increases the sensitivity and decreases the stability of the SPP. Since the bias voltage of the base of the transistor VT1 also rises, a corresponding increase in the collector current I _{to cf of the} transistor VT2 occurs, while the sensitivity of the SPP is stabilized. When lowering the supply voltage E _{to the} process of current regulation goes in the opposite direction and provides stabilization of the sensitivity of the SPP. It must be emphasized that the introduction of a current stabilizer greatly facilitates the configuration of the transceiver in the production environment, since the current value remains optimal for all iterative adjustment modes of the device.

GOS produces video pulses with a frequency of about 800 kHz that directly control the operation of the microwave oscillator. The output stage of the GOS is structurally located on the circuit board of the microwave oscillator in order to reduce the effect of shock excitation by the pulses of the GOS of the parasitic inductances of the connecting conductors in the base and emitter circuit of the microwave transistor. In practice, these pulses are generated using directly biased diodes VD1, VD2, which provide a low differential output resistance of the seeker. The resistor 6 determines the magnitude of the current pulses flowing through the diodes. When you configure the SPF, the output resistance of the seeker is controlled by a resistor 5 connected in series (Fig. 6).

The design of the GSN output stage and the current stabilizer on the same printed circuit board together with the SPP microwave oscillator significantly reduces the influence of the inductance of the connecting conductors of the radiosonde telemetry unit on the stability of the SPP operation, increases the manufacturability of the assembly and facilitates tuning in production conditions. As a specific example, FIG. 7 shows a complete circuit diagram of a microwave module of an SPP radiosonde. On Fig shows the placement of the structural elements of the current stabilizer, the output stage of the GOS and the microwave oscillator, made according to the patent of the Russian Federation No. 2291467 (Super regenerative transceiver). The structural elements of the microwave module depicted in Fig. 8 have the following notation: 7 — Microstrip resonator in the emitter circuit — W1; 8 - Microstrip resonator in the base circuit - W2; 9 - Input - microwave output; 10 - A quarter-wave microstrip choke in the collector circuit - W4; 11 - Resistor R3; 12 - Capacitor C3; 13 - Capacitor C1; 14 - Resistor R1; 15 - Common conductor; 16 - Transistor VT1; 17 - Resistor R2; 18 - Capacitor C1; 19 - The output of the collector power circuit E _to ; 20 - Resistor R5; 21 - Input superimposing video pulses; 22 - Resistor R6; 23 - Capacitor C6; 24 - microwave microstrip board; 25 - microwave transistor VT2; 26 - A quarter-wave microstrip choke in the emitter circuit - W3; 27 - General conductor; 28 - Resistor R4; 29 - Microstrip resonator in the collector circuit - W6; 30 - A quarter-wave microstrip choke in the base circuit - W5; 31 - Resistor R5; 32 - Diodes VD1, VD2; 33 - General conductor;

The SPI microwave module contains a control transistor VT1, an output microwave transistor VT2, a power bus Ek and a zero bus, first, second, third and fourth R1-R4 resistors, first, second, third and fourth C1-C4 capacitors with the following connections: control the transistor VT1 is made according to the scheme with a common emitter, and the base of the transistor is connected to the midpoint of the resistive divider R1-R2, made on the first and second resistors, the ends of the divider are connected to the power bus Ek and the zero bus; the emitter of the regulating transistor through the third resistor R3 is connected to the power bus Ek, and directly to the collector of the transistor VT2 of the microwave oscillator: the collector of the regulating transistor VT1 through the fourth resistor R4 is connected to the base of the output transistor VT2 and the second end of the fourth capacitor C4, the first end of which is the input the entire output stage; The microwave transistor VT2 is turned on according to a circuit with a common emitter, and the electrical circuit is made on microstrip segments, their length being obviously greater than λ / 4, and during the tuning process the length of the segments is selected depending on the values of stray capacitances and inductances of the microwave transistor VT2 and the specific topology of the oscillator, given that segments of length <λ / 4 play the role of capacitance, and> λ / 4 play the role of inductance; the first capacitor C1 is connected between the collector of the regulating transistor and the zero bus, the second capacitor C2 is between the base and the collector, the third capacitor C3 is between the emitter and the zero bus, the fourth capacitor C4 is between the base of the microwave transistor VT2 and the input of the cascade; the emitter of the regulating transistor VT1 is connected to the collector of the microwave transistor VT2 through the resistor R5 and the microstrip section W4, and the collector of the microwave transistor VT2 through the microstrip section W6-W7 is connected to the antenna of the radiosonde.

The indicated nodes of the circuit diagram can be performed on the following electro-radio elements: VT1 - bipolar transistor type p-n-p KT3129A9 (see. Author Perelman BL New transistors. Handbook, - Part 11, Solon, 1996, p.29-31); VT2 - microwave transistor type KT637A (see Semiconductor devices. Transistors of medium and high power .: Reference - 3rd ed .; Edited by A.V. Golomedov. M .: KUBK-a, 1995, p. 406-407; capacitors C1-C5 lead-free, type K10-47 V (see The reference book of the amateur radio designer, edited by P.I. Chistyakov, M, P and S, 1990, p. 403); MPL segments and chokes on microstrip lines (see the Guide to elements of strip technology, under the editorship of A.L. Fildshtein, M., Communication, 1979, p.20); resistors of the P1-12 type (see the reference book of the amateur radio designer, ed. P.I. Chistyakova, M., Radio and Communications, 1990, p. 381).

Improving the design and production technology of SPP allowed to increase its sensitivity to - 90 ÷ 100 dB / W with an average radiation power of 180-250 mW and an efficiency of at least 25%. This ARZ transceiver provides accurate measurement of the slant range of a ground-based radar to 200-300 km with an accuracy of no worse than ± 15 m, with a low level of request power. So the pulse power of the radar transmitter is 200 watts, the average is 0.2 watts. The transmission of ARZ telemetric signals is carried out at the same frequency by frequency modulation of superimposing pulses, i.e. at one carrier frequency, all ARZ coordinates are measured: elevation, azimuth, range, and telemetry signals of meteorological quantities are transmitted. Ultimately, the use of NGN can significantly reduce the cost of obtaining aerological information on the Roshydromet network of the Russian Federation.

Literature

1. Ivanov V.E., Fridzon M.B., Yesyak S.P. “Radio sounding of the atmosphere. Technical and metrological aspects of the development and use of radiosonde measuring instruments ”, ed. V.E. Ivanova. Yekaterinburg. UrB RAS. 2004.596 s. ISBN 5-7691-1513-0 (see p.551-554).

2. Superregenerators. M.K. Belkin, G.I. Kravchenko, Yu.G. Skorobutov, B.A. Stryukov; edited by M.K.Belkin. - M .: Radio and communications, 1983 .-- 248 p., Ill.

Claims (3)

1. Microwave module of a super-regenerative transceiver (SPP) of a radiosonde, comprising a microwave autogenerator, an inertial auto-bias circuit, a current stabilizer, a power bus and a zero bus, characterized in that the current stabilizer contains a control transistor, first, second, third and fourth resistors, the first , the second, third and fourth capacitors with the following connections: the control transistor is made according to the scheme with a common emitter, and the base of the control transistor is connected to the midpoint of the resistive divider made on first and second resistors, the ends of the divider are connected to the power bus and neutral bus; the emitter of the regulating transistor is connected through the third resistor to the power bus, and directly to the collector of the microwave oscillator transistor: the collector of the regulating transistor through the fourth resistor is connected to the base of the microwave oscillator transistor and the second end of the fourth capacitor, the first end of which is the input of the entire output stage. 2. The microwave module according to claim 1, characterized in that the inertial auto-bias circuit contains a sixth constant resistor connected in series, the first and second diodes in the forward direction to the zero bus, and the connection point of the sixth resistor and the first diode through the fifth variable resistor connected in series and the fourth capacitor is connected to the base of the transistor of the microwave generator, and to eliminate the effect of excitation of the parasitic circuit in the control circuit of the SPP input current pulses, the condition for damping shock waves s in the form of:
R ² C / 4L >> 1, (l)
where R is the total series resistance of the sixth and fifth resistors of the auto-bias circuit; L is the total inductance of the connecting conductors in the control circuit of the microwave oscillator; C is the capacity of the auto-bias circuit, in this case the fourth capacity, and to ensure the required speed of starting current establishment, the performance condition is additionally fulfilled
2L / R << T _s . (2),
where T _c is the period of superimposing pulses U _c . 3. The design of the microwave module according to claim 1, characterized in that it is made on a microstrip board with surface mounting.

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