RU2338306C1 - Transmitting-receiving module of active phased antenna array - Google Patents

Abstract

FIELD: radio engineering.

SUBSTANCE: invention is related to active phased antenna arrays (AFAR), which consist of transmitting-receiving modules (PPM), which are intended for application in radiolocation stations, communication systems and systems of radio countermeasures. Technical result is achieved with the help of additional phase control of PPM output signal value.

EFFECT: provision of high efficiency factor of PPM AFAR in the mode of transmission and simultaneously provision of wide range of control of radiated signal range with preservation of phase control.

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Description

The present invention relates to antenna systems of directional radiation - active phased antenna arrays (AFAR).

The most effective transceiver module (APM) AFAR can be used in airborne radars, ship and ground radars, as well as in radio countermeasures and radio relay stations.

AFAR transceiver modules are known and are 2-channel devices, the transmission channel and the reception channel of which are combined by “transmit-receive” switches, which, in turn, are connected to the air via matching devices (CS) or substitute devices, respectively, to each of N emitters forming an open AFAR.

Figure 1 shows a diagram - an analogue of the APM AFAR and its connection to 1 ... N emitters of the AFAR, as well as to the microwave signal distribution system, which distributes the power of this signal from the radar exciter in transmission (radiation) mode to each APM summarizes the received from the ether and amplified in each MRP echo signals in the receiving mode, forming the output signal of the entire AFAR at the input of the output device (see. "Active phased antenna arrays" ./ Edited by D. I. Voskresensky, A. I. Kanaschenkov M.: Radio Engineering, 2004, p. 19).

PPM - the analogue contains:

1 - controlled phase shifter for controlling the phase of the microwave signal sequentially in the transmission mode and in the reception mode using control signals, respectively, U _{φ ° per} and U _{φ ° pr} , distributed using control signal distribution systems (PC control signal);

2 - the first switch "reception-transmission" (SPT ₁ );

3 - preliminary power amplifier of the microwave signal;

4 - output power amplifier (PA);

5 - power amplifier power supply modulator, controlled by the voltage of the signal U _mod from the distribution system of the modulating signal (PC mod. Sig .; which is a device that uniformly distributes the modulating signal U _M = u (τ, T _p ) over all APM AFAR, which determines the duration of the emitted PPM pulse τ and its repetition period - T _p ;

6 - the second switch "reception-transmission" (SPT ₂ ), the "output-input" of which is connected to one of the N emitters through a matching device (SU), the input is connected to the output of the PA 4, and the output is connected to the input of the receiving channel 7 PPM, consisting of series-connected memory - protective device, low-noise amplifier LNA, F - bandpass filter. Us - amplifier, A - controlled attenuator (receiving), the output of which is connected to the input of the IFR ₁ - the first switch "reception-transmission" (2).

It can be seen from the diagram in FIG. 1 that in the signal transmission (emission) mode, when blocks 1, 2, 3, 4, 5, and 6 are involved, the amplitude (power) of the emitted signal is not controllable, because there is no control element, for example, an attenuator.

Thus, this scheme APM AFAR does not allow you to control the amplitude distribution of AFAR in the radiation mode, which is a significant drawback of the analogue.

The closest analogue (prototype) of the present invention is a module with error correction (US patent No. 5.093.667, K. Andriyakos from 03.03.1993), a block diagram of which is presented in figure 2.

This device contains:

1 - switch “reception-transmission” (into two positions: position “A” - transmission, position “B” - reception);

2 - controlled phase shifter (φ °);

3 - controlled attenuator (ATT.up);

4 - preliminary amplifier (Pr.);

5 - output power amplifier (PA) with a microwave divider at the input and a microwave adder at the output (elements 2 ... 5 form the transmitting channel PPM);

6 - circulator "reception-transmission" (C);

7 - emitter;

8 - receiving channel PPM, similar to the receiving channel PPM-analogue in figure 1.

In transmission mode, the microwave signal from the distribution system through the receive-transmit switch 1 (position “A”) is fed to the input of the controlled phase shifter 2, where it acquires the required phase shift φ °, set using the control voltage Uφ ° = f (x _n , y _n , θ °, γ °),

where x _n and y _n are the coordinates of the APM in the aperture of the AFAR, θ ° and γ ° are the azimuthal and elevation directions of the AFAR beam.

Next, the microwave signal is fed to the input of the controlled attenuator 3, in which the required attenuation of this signal is set by the control voltage U (t) _a , and from the output of the attenuator 3 to the input of the preliminary amplifier 4, the output signal of which is divided by 2 equal in power (amplitude) parts in the divider, which is shown in the patent description (without digital designation) as a splitter into 2 parallel channels, through which the signals are fed to the inputs of a 2-stroke output linear power amplifier 5, are amplified by power, and after summing common signal is input via the circulator 6 and the emitter 7 is radiated into space for the purpose of irradiation. The signals reflected from the target (echo signals) received by the emitter 7 are fed through the circulator 6 to the input of the receiving channel 8, from the output of which through the switch 1 (position “B”) - to the input of the distribution system (PC). Moreover, if the output power amplifier 5 operates in saturation mode, its efficiency (efficiency) can reach 50%, but the control range of the amplitude of the emitted signal does not exceed 6 ... 8 dB with the required usually> 30 dB.

If you put the output amplifier 5 in linear mode to increase the amplitude control range, then its efficiency will decrease to ~ 23% (US patent mentioned above, page 12), which will lead to a decrease in the radiated signal power, to an increase in the heating temperature of the AFAR, i.e. . to increase the power of the AFAR cooling system, increase the mass and price of AFAR, which is unacceptable for aircraft radar.

Thus, the disadvantage of the prototype is the inability to provide a sufficiently high PPM efficiency (≥40%) in the transmission mode with the required, usually wide (~ 30 dB), range of control of the amplitude of the emitted signal.

The objective of the invention is to eliminate the above disadvantages, namely: ensuring high efficiency PPM AFAR in transmission mode and at the same time providing a wide range of control of the amplitude of the emitted signal while maintaining phase control.

This goal is achieved by the fact that while maintaining the main functional elements of the prototype (switch, pre-amplifier, 2-stroke output power amplifier of the transmitting channel with a microwave divider and microwave adder, circulator, emitter, receiving channel) at the input of each of 2- x parallel-connected channels of the 2-stroke output power amplifier of the PPM transmitting channel, the first and second controlled phase shifters, respectively, are added, which are controlled respectively by the sum and spacing the components of the signal that controls the phase and controls the amplitude, respectively.

Figure 1 presents the block diagram of the analogue - PPM AFAR;

Figure 2 - block diagram of the prototype - APM AFAR with the correction of amplitude-phase errors in the transmitting channel;

Figure 3 is a block diagram of the proposed PPM AFAR;

Figure 4 is a vector diagram of the output signals of the MRP, controlled by amplitude and phase.

The transceiver module AFAR (figure 3) contains:

1 - switch “reception-transmission” to 2 positions: position “A” - signal transmission, position “B” - reception of an echo signal having an input-output contact, by means of which, in position “A” of switch 1, the input of the transmitter channel - pre-amplifier input the whisker is connected through the contact “output” to the distribution system, to which in position “B” the output of the receiving channel is connected through the contact “input” of switch 1;

2 - a preliminary amplifier (Pr.) Of the PPM transmitting channel, the output of which is connected to a microwave bridge power divider;

3 - microwave bridge power divider (MDM) of the output signal of the pre-amplifier with outputs: 3 ₁ - the first transmitting channel and 3 ₂ - the second transmitting channel, respectively, which are connected to the inputs of the phase shifters 4 ₁ and 4 ₂ , respectively;

4 - the first (4 ₁ ) and second (4 ₂ ) controlled phase shifters of the first and second transmitting channels, the outputs of which are connected respectively to the inputs of amplifiers of a 2-channel output power amplifier 5 ₁ and 5 ₂ ;

5 - output 2-channel (amplifiers 5 ₁ , 5 ₂ - of the first and second transmitting channels, respectively) 2-stroke non-linear power amplifier, the outputs of which are connected to the inputs of the microwave adder;

6 - microwave power adder with inputs 6 ₁ and 6 ₂ (of the first and second transmitting channels, respectively), the output of which is connected to the input of the circulator 7 "receive-transmit", the "input-output" of which is connected to the emitter 8, and the "output" - with the input of the receiving channel 9, consisting of series-connected: a protective device (memory), a low-noise amplifier (LNA), a controlled attenuator (ATT), an amplifier (CSS) and a controlled phase shifter (F _CR ), the output of which is the output of the receiving channel and connected with the input of the switch "reception-transmission" 1 (position "B the accept).

Elements (blocks) 2, 3, 4, 5, 6 form the transmitting channel PPM.

Elements 3, 4, 5, 6 form a 2-channel device for controlling the amplitude and phase of the transmitting channel.

Switch - 1 can be made according to known schemes on pin diodes in a hybrid integrated circuit (GIS) with microstrip connection lines. It has a common input-output contact connected to a distribution system that distributes microwave signals from the master oscillator to all APM AFARs through the output contact when turned on in position “A” —signals the contact “input” - position “B” Reception of an echo signal. In addition, switch-1 can also be implemented on field-effect transistors or in the form of MEMS-switches (microelectromechanical structure), known in the literature (JEEE MTT - S. Internalional Microwave Sdmposkim. Diqest. Vol. 1, 2000, p. 165-168 , Microwave Switching Devices on the Bands ”, Weissblad, M. RiSv., 1987, 120 pp.).

The preamplifier 2 can be performed on field-effect transistors with a Schottky barrier (PTSh) in a hybrid integrated design.

Its output is connected to the input of a microwave bridge power divider 3, dividing into two equal parts the power of the output signal of the pre-amplifier.

The microwave divider 3 can be made in the form of a microstrip bridge circuit (“Radio transmitting devices” ./ Under the editorship of Blagoveshchensky MV, Utkina GM M .: Radio and communications, 1982, p. 109), from the outputs (3 ₁ ) of the first and (3 ₂ ) second channels of which the signal is supplied respectively to the first - 4 ₁ and second - 4 ₂ - controlled phase shifters.

Electrically controlled phase shifters 4 ₁ and 4 ₂ can be made in the form of pin-diode switches or in the form of a microstrip integrated circuit (MIS) on Schottky field effect transistors. Control ranges 0 ° ... 360 °, phase setting discrete 3 ° (“Active phased antenna arrays” ./ Edited by D.I. Voskresensky et al., M .: Radio engineering, 2004, p. 26, 27 )

The control signal U ₁ is a digital binary code (0,1) in the form of a commonly used sequence of TTL pulses - level (transistor-transistor logic) - 4, 5 or 6-bit words (depending on the required installation accuracy) - fed to the controlled input of the first 4 ₁ phase shifter in the form of the sum U ₁ = Uφ ° + ΔU _{Δφ °} , where U _{φ °} is the phase control signal φ ° of the microwave signal, and ΔU _{Δφ °} is the control signal of the microwave signal amplitude (Definition of codes see "Antennas and microwave devices ./ Edited by D.I. Voskresensky. M .: Sov.radio, 1981, pp. 164 ... 166).

The control signal U ₂ is supplied to the control input of the second phase shifter 4 ₂ in the form of a difference U ₂ = U _{φ °} -ΔU _{Δφ °} , where U _{φ °} is the phase control signal φ _c ° of the microwave signal (exactly corresponding to the code of the phase control signal for phase shifter 4 ₁ ), and ΔU _Δφ is the microwave amplitude control signal that corresponds exactly to the code for controlling the amplitude of the microwave signal 4 ₁ , but with the opposite sign, i.e. with the opposite value of the sign discharge relative to ΔU _Δφ ° of the first phase shifter.

Thus, the control signals U ₁ and U ₂ differ in magnitude by 2ΔU _{Δφ °} , which provides an increase in the phase of the microwave signal in the first controlled phase shifter 4 ₁ to φ _c1 ° of the first channel φ _c1 ° = φ _c ° + Δφ _c ° (where Δφ _с ° - correction of the microwave signal phase due to the control voltage ΔU _{Δφ °} ) and reduction of the microwave signal phase to φ _с2 ° - in the second controlled phase shifter 4 _{of the} second channel φ _c2 ° = φ _c ° -Δφ _c ° by one and the same correction value Δφ _with ° (see figure 4).

The phase component of the 1st and 2nd channels φ _с ° determines the phase distribution of the emitted signal in the AFAR aperture, i.e. the position of the beam in space and is calculated by the control unit as a function of the location of the PMD in the aperture of the AFAR and the direction of radiation of microwave energy in the space φс ° = f (x _n , y _n , θ °, γ °), where x _n and y _n are the coordinates of the PMP on the opening AFAR;

θ ° and γ ° are the angular directions of the AFAR beam in the azimuthal and elevation plane, respectively.

The component Δφ _с ° is a quantity that depends only on the amplitude of the signal required to ensure a given amplitude distribution over the open AFAR.

The dependence of the amplitude of the emitted signal on the value Δφ _with ° at the output of the adder 6 will be determined below.

The output of the first controlled phase shifter 4 _{1 of the} first channel is connected to the input of the power amplifier 5 _{1 of the} first channel, and the output of the second controlled phase shifter 4 _{2 of the} second channel is connected to the input of the power amplifier 5 _{2 of the} second channel of a 2-stroke output nonlinear power amplifier 5.

Power amplifiers 5 ₁ and 5 ₂ can be made in the form of a microstrip integrated circuit on a PTSh-arsenidgalium field-effect transistor, for example, according to the scheme from the book "Radio transmitting devices". / Ed. M.V. Blagoveshchensky, G.M. Utkin. M.Radio and Communications, 1982, p. 107, 109.

The outputs of the amplifiers 5 ₁ and 5 _{2 are} connected respectively to the first 6 ₁ and second 6 ₂ inputs of the power adder (MC) 6, which can be performed as a bridge - adder similar to bridge divider 3.

MC6 output is connected to the “input” contact of the receive-transfer circulator - 7, the input-output contact of which is connected to the emitter 8, and the “output” contact - to the input of the receiving channel PPM - 9, the output of which is connected to the “input” contact "Switch 1" transmission ". In position "B" of switch 1 through the input-output contact, the output of the receiving channel is connected to the distribution system.

The first 4 ₁ and second 4 ₂ phase shifters are controlled by digital code signals U ₁ and U ₂ from the control unit.

The transceiver module AFAR works as follows.

In transmission mode, the signal from the output of the distribution system is fed to the input-output contact of the receive-transfer switch - 1 and through it (position "A") - to the output of the power pre-amplifier 2, where it is amplified and fed from its output to the input divider 3, where the power of the microwave signal is divided into 2 equal parts, each of which from the outputs 3 ₁ and 3 _{2 is} supplied to the inputs of the first 4 ₁ and second 4 ₂ controlled phase shifters, at the outputs of which the signal phases φc ₁ ° and φс _{2 are set} ° according to digital signals controlled U ₁ and U ₂ , the structure of which can be represented as a 6-bit word 110111, where the first unit is a + sign, if the first zero is a minus sign. The remaining elements of the binary code show one of the 64 possible values of the phase set by this code in the phase shifter, the minimum value of which is 5, 6 degrees - the price of the least significant bit. Control signals are generated using drivers (programs).

The relationship between the control signal and the magnitude of the phase change of the microwave signal U _φ ° = f (φ _c °) and ΔU _Δφ ° = f (Δφ °) is presented in the literature, for example, “Radar Reference.” / Ed. M. Skolnik, Volume 2, Moscow: Sov. radio, 1977, p. 255 or “Antennas with non-mechanical motion of the beam” A. Vendik, 1973, p. 250.

Since the phase of the microwave signal of the first channel is set equal to φ _c1 °, then in a complex exponential form, this signal at the input of the first nonlinear amplifier 5 ₁ will have the form

where U _in1 is the amplitude of the input microwave signal of the 1st channel;

φ _c1 ° - phase of the input microwave signal of the 1st channel.

Similarly, at the input of the second nonlinear amplifier 5 _{2 the} microwave signal in complex form is equal to:

where U _in2 - the amplitude of the input microwave signal of the 2nd channel;

φ _c2 ° - phase of the input microwave signal of the 2nd channel.

Given that microwave amplifiers operating in a nonlinear class B or C mode have an efficiency of> 40% (“Active PAR” Gostyukhin VL, M .: Radio and Communications. 1993, p. 190) and are quite broadband , the phase of the output signal of the first nonlinear amplifier 5 ₁ will be:

φ _s1 ° = φ _s ° + Δφ _s °

The phase of the output signal of the second nonlinear amplifier 5 ₂ :

φ _s2 ° = φ _s ° -Δφ _s °.

Given that the transmission coefficients for power K ₁ and K _{2 of} amplifiers 5 ₁ and 5 ₂ are equal (K ₁ = K ₂ = k), we obtain at the first input 6 _{1 of} adder 6 a complex input signal in the form

and at the second input 6 ₂ - a complex input signal in the form

The summation of the signals at the output of the adder 6 will determine the output (total) signal of the transmitting channel

According to Euler's formula

Substituting the result into formula (1), we obtain

From the formula (2) it is seen that the amplitude of the output signal of the adder 6 is a module of the controlled complex signal of the transmitting channel

The phase of the output signal of the adder 6 of the transmitting channel φ _with ° is determined by the required base distributor according to the open AFAR.

The amplitude in accordance with the formula of the output signal (3) varies depending on a correction amount of the microwave signal phase Δφ _c °, which in the phase shifter _{1 April} microwave signal phase increases and a phase shifter _{2 April} reduced by one and the same value Δφ _with °.

For example, the amplitude of the output signal of the transmitting channel is 0 if Δφ _c = 90 ° and reaches a maximum (2k U _in ) at

Δφ _s ° = 0 °

Thus, if this MRP, located in row x _j and column y _{j of} the AFAR opening, should emit a maximum signal, then Δφ _with ° dB is equal to zero.

и такой же - на входе 6₂) и иметь вид:Then the output signal of adder 6 will consist of 2 common-mode signal components (at input 6 ₁ -

and the same - at the input 6 ₂ ) and have the form:

The control signals Uφ ₁ and Uφ ₂ are equal, and their codes are the same (U _φ1 = U _φ2 = U _φ ).

If the implementation of the given amplitude distribution requires the amplitude of the output signal of the PPM adder U _{Σreg to be} reduced by "n" times, then, based on the value of "n", it is necessary to determine the value of the corresponding phase correction Δφ _with °.

These values are related as follows:

U _Σmax = 2k · U _in - the maximum level of the signal amplitude at the output of the adder 6.

- требуемый уровень амплитуды сигнала на выходе сумматора 6.U _Σreg = 2k · U _Rin cosΔφ

- the required level of signal amplitude at the output of the adder 6.

or

.

This means that if it is necessary to reduce the amplitude of the microwave signal at the output of the adder 6 (at the output of the PPM), for example, by half (n = 2), then the phase correction Δφ _with ° should be

Summarizing the phase value (φ _c °) and phase correction (Δφ _{c °) φ c1 ° = φ c} ° + Δφ c ° and subtracting these values _{φ c2 ° = φ c ° -Δφ} c, are the phase of the microwave signal φ _c1 ° and φ _c2 ° at the input 6 ₁ and 6 _{2 of the} adder 6.

From these values determine the values of the control voltages U ₁ = (Uφ ° + ΔU _Δφ °) and U ₂ = (Uφ ° -ΔU _Δφ °), which are supplied in the form of the codes mentioned above to the control inputs of the phase shifters 4 ₁ and 4 ₂ , in which with these voltages, the corresponding phases φ _with ° + Δφ _with ° and φ _with ° -Δφ _with ° are set, which, when summing the microwave signals in the adder 6, leads to a decrease in the amplitude of the PPM output signal relative to the amplitude of this signal at Δφ _with ° = 0 and to turn phase of this signal at an angle φ _c ° relative to the phase φ _c ° = 0. Moreover, as mentioned above, the magnitude of the control signal U _reg = U _φ ° = f (φ _c °), where

а ΔU_Δφ°=f(Δφ°), где

and ΔU _Δφ ° = f (Δφ °), where

, который разделен на 2 равные части (2 равных вектора) ОА и ОД, фаза которых сдвинута относительно вектора

управляемым фазовращателем 4₁(ОД) - до фазы φ_c1°=φ_c°+Δφ_c°, а фазовращателем 4₂ (ОА) - до величины φ_c2°=φ_c ^o-Δφ_c ^o. Предполагая для простоты изображения, что коэффициенты усиления первого и второго усилителей мощности равны 1, получим, что при суммировании в сумматоре 6, сигналы, представленные векторами ОА и ОД, образуют вектор ОС, соответствующий выходному сигналу U_Σ с фазой относительно вектора

, равной φ°, а амплитудой, меньшей, чем

т.е. как видно из рисунка

при Δφ°≠0.Figure 4 ^a (left figure) shows the input signal vector of the divider 3

, which is divided into 2 equal parts (2 equal vectors) OA and OD, the phase of which is shifted relative to the vector

controlled phase shifter 4 ₁ (OD) - up to the phase φ _c1 ° = φ _c ° + Δφ _c °, and phase shifter 4 ₂ (OA) - up to the value φ _c2 ° = φ _c ^o -Δφ _c ^o . Assuming for simplicity of the image that the amplification factors of the first and second power amplifiers are 1, we get that when summing in adder 6, the signals represented by the vectors OA and OD form the OS vector corresponding to the output signal U _Σ with a phase relative to the vector

equal to φ °, and an amplitude less than

those. as seen from the figure

at Δφ ° ≠ 0.

т.е. φ_с°=0, а амплитуда уменьшена (как и в левом рисунке) за счет Δφ_с°≠0, т. е.

Figure 4 ^a (right figure) shows the case when the phase of the output signal (OS vector) does not change relative to the phase of the signal

those. φ _с ° = 0, and the amplitude is reduced (as in the left figure) due to Δφ _с ° ≠ 0, i.e.

, так как cos0°=1 (см. формулу 2).Figure 4 ^b (left figure) shows the case when the phase of the output signal of the adder φ _с ° ≠ 0, and Δφ _с ° = 0. In this case, the amplitude of the output signal of the adder is maximum

, since cos0 ° = 1 (see formula 2).

.The right figure shows the case when the amplitude of the output signal is equal to zero for any phase value φ _с °, since cos90 ° = 0, i.e. -

.

In the receiving mode, the signal reflected from the target is received by the emitter 8 and fed through the circulator 7 to the input of the PPM 9 receiving channel, where it is amplified in the LNA, corrected in phase and amplitude by the controlled phase shifter Ф ° _pr and attenuator “ATT” and through switch 1 (in the “ B ”) is fed to the input of the PC distribution system.

The proposed technical solution provides at the same time a high efficiency of the transmitting channel APM AFAR and a wide range of control of the amplitude of the emitted signal while maintaining control of the phase of the signal in the desired range.

This provides:

- a given identity of the amplitude and phase of the PPM output signals (error correction), which increases the directivity coefficient of the AFAR;

- the required amplitude-phase distribution over the opening of the AFAR in the signal transmission mode, which allows you to control the level of the side lobes (UBL) of the directivity pattern (BF) of the AFAR in the transmission mode.

The achievement of this technical result allows to provide in the transmission mode:

- maximum radiation power;

- maximum KND AFAR;

- the required UBL DN AFAR for transmission.

When using the proposed AFAR in an airborne radar station, the range of the radar increases, the accuracy of measuring the angular coordinates of the radar increases, and the noise immunity of the radar increases.

Claims (1)

A transceiver module of an active phased antenna array (AFM AFAR), comprising a 2-position receive-transmit switch, an input-output contact of which is connected to a distribution system, and an output-contact in position A - transmission is connected to an input of a transmitting PPM channel, consisting of a preliminary power amplifier and output 2-cycle power amplifier of the transmitting channel with a microwave divider at its input and a microwave adder at the output, which is the output of the PPM transmitting channel, which is connected to the input of the circulator em-transmission ”, the“ output-input ”contact of which is connected to the emitter, and the“ output ”contact - with the input of the receiving channel, containing a protective device in series, a low-noise amplifier, a controlled attenuator, an amplifier, a controlled phase shifter, the output of which is connected to the contact“ input "switch" reception-transmission ", characterized in that the first and second outputs of the microwave power divider signal are connected respectively to the first and second inputs of the respective additionally introduced first and second controlled phases controllers, the output of each of which is connected respectively to the input of the first and second amplifiers of a 2-step output power amplifier, and control signals U ₁ and U ₂ are generated at the control input of each of the controlled phase shifters, which are formed respectively for the first phase shifter with the sum U ₁ = Uφ ° + ΔU _Δφ °, and for the second - the difference U ₂ = U _φ ° -ΔU _Δφ ° of the two components of the control signal, namely: Uφ ° component of the phase control φ _c ° of the microwave signal and ΔU _Δφ ° component of the control amplitude of the microwave signal transmitting PPM channel , and the magnitude of the component U _φ ° is determined by the coordinates x _n , y _n PPM in the aperture plane of the AFAR, as well as the direction of the beam of the AFAR in azimuth Θ ° and in elevation γ °: Uφ ° = F (x _n , y _n , θ °, γ °), and the magnitude of the component controlling the amplitude of the signal ΔU _Δφ ° = f (Δφ °) is determined by the correction Δφ _s ° of the phase of the microwave signal, depending on the ratio of the required amplitude of the output microwave signal of the transmitting channel PPM

to its maximum possible value

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