RU2195688C2 - Procedure measuring distance to objects with use of picosecond pulses and device for its realization - Google Patents

Abstract

FIELD: radio measurement technology. SUBSTANCE: invention can be employed in construction of various measuring systems determining distance to examined objects. Procedure consists in generation of periodic sequence of picosecond video pulses of sawtooth shape, in radiation of periodic sequence of picosecond video pulses in the form of train of bursts. Video pulses of picosecond length in burst are phase-manipulated according to law of pseudorandom sequence. Procedure also includes probing of examined object by radiated periodic sequence of picosecond video pulses, reception of signal reflected from object, scale-time conversion of received signal, quantization of converted signal, memorizing of quantized signal, matched filtration of memorized quantized signal, processing of memorized filtered signal and obtainment of measurement information on examined object by way of reading of indicated data, data recorded in the form of hard copy or in personal computer. Device for realization of procedure includes generator of picosecond sawtooth video pulses, transmitting antenna, receiving antenna, scale-to-time converter, storage, matched filter, processing unit, address former, first permanent storage, second permanent storage, address counter, reversible counter, former. EFFECT: enhanced measurement accuracy of distance to objects. 2 cl, 4 dwg

Description

 The invention relates to the field of radio measurement technology and can be used in the construction of various automated measuring systems for measuring the distance to the objects under study in radar, geophysics, radio navigation.

 A known method of measuring the distance to objects [1], which consists in sensing (irradiating) the object with the electromagnetic energy of the radio signal and subsequent processing of the reflected signal from the object. Method [1] consists in generating a signal, modulating it with a corresponding frequency signal into a radio signal, amplifying a modulated radio signal, emitting a modulated radio signal, probing an object under study with a generated radio signal, receiving a reflected signal, demodulating with converting the reflected signal to the fundamental frequency (near the zero frequency), processing the demodulated signal to obtain measurement information about the object under study by counting on the displayed data, data recorded annym as a hard copy or on the PC.

 The current level allows for a carrier frequency of 94 GHz to provide a frequency band of 10 GHz. The time resolution is 0.2 ns, which corresponds to a range resolution of 3 cm, and the noise temperature is 240 K.

 The disadvantages of the method are the relatively low accuracy of distance measurement and the rather large complexity of the measurement process.

 A device for measuring the distance to objects [2], which includes a continuous oscillator, the first output of which is connected to the input of the power amplifier, the second input of which is connected to the output of the modulator, and the output to the transmitting antenna, the receiving antenna is connected to the first input of the receiver, providing demodulation of the input signal, the second input of the receiver is connected to the second output of the generator, the output of the receiver is connected to the input of an indicator that provides information processing.

 The disadvantage of this device is the relatively low accuracy of distance measurement.

 The known method [3], selected for the prototype (a method of video pulse measuring the distance to objects), which consists in generating a sequence of broadband video pulses, emitting broadband video pulses, sensing the object under study, receiving a signal reflected from the object, time-scale conversion of the received signal, quantization of the converted signal , storing the quantized signal, processing the stored signal to obtain measurement information about the investigated object by counting that according to the displayed data, data recorded in the form of a hard copy or on a PC.

 The method (prototype) allows you to measure the range to values of not more than 450-1500 m with a resolution on the range of about 1.5-2 cm; noise temperature 90 K; attenuation is practically absent.

 The disadvantage of this method [3] is the low accuracy of distance measurement, since the method allows you to measure the distance to objects only at short ranges.

 A device [3] is known for measuring the distance to objects selected as a prototype. In the device, the first output of the step function generator is connected to the input of the transmitting antenna, the outputs of which are connected: the first to the object, the second to the second input of the receive antenna, the second output of the step function generator is connected to the second input of the time-scale converter, the third output of which is connected to the first processor input, the first input of the receiving antenna is connected to the object, and the output is connected to the first input of the time-scale converter, the first output of which is connected to the input of the low-pass filter, and the second output - with an input of the indicator, the lowpass filter output is connected to the input of analog-to-digital converter whose output is connected to the processor input, the second output of which is connected to the inputs of the display device and the PC, the output of which is connected to the input of a copy device.

This device has the disadvantage of low accuracy of measuring the distance to objects. This is due to the following. In order to measure any of the parameters of an object, it is necessary to irradiate it with a signal with sufficient energy at which the intensity of the reflected signal would exceed a certain minimum level, when reception and processing of the reflected signal are still possible. In this case, the signal energy is determined by the energy of one pulse E ₁ , the value of which is limited from above by a rather low value: E ₁ ≈ 0.02 mJ, which reduces the accuracy of measuring the parameters of an object located at an unknown distance. In addition, an increase in radiation power is associated with very large material costs. All this significantly limits the possibilities of using this device.

 The technical result of the invention is to increase the accuracy of measuring the distance to objects using picosecond pulses at high ranges.

 The technical result is achieved by the fact that in the method of measuring the distance to objects using picosecond pulses, which consists in generating a sequence of video pulses and emitting them, sensing the object under study, receiving a signal reflected from the object, time-scale conversion of the received reflected signal, quantizing the converted signal, storing quantized signal, processing the stored signal to obtain measurement information about the object under study by counting ind erentiable data, data recorded in a hard copy or on a personal computer, generate a periodic sequence of video picosecond sawtooth waveform, and emit picosecond video pulses in a sequence of bursts, the video pulses in a burst are phase-shifted by the law of the pseudorandom sequence, the stored signal is subjected to matched filtering.

 The technical result is achieved by the fact that in a device that implements a method of measuring the distance to objects using picosecond pulses, containing a transmitting antenna connected to the object, a receiving antenna connected to the object, a time-scale converter, the first input of which is connected to the output of the receiving antenna, processing unit, a picosecond sawtooth video pulse generator is introduced, the first output of which is connected to the input of the transmitting antenna, and the second to the second input of the time-scale converter , the first output of the time-scale converter is connected to the first input of the memory block, the output of which is connected to the first input of the matched filter, the output of which is connected to the processing unit, the second output of the time-scale converter is connected to the input of the shaper and the first inputs of the address counter and address shaper, the second the input of which is connected to the second output of the driver and the input of the reversible counter, and the output to the fourth input of the memory block, the second input of which is connected to the output of the first constant inayuschego device having an input connected to the output address counter, a second input coupled to a third output of the first output of which is connected to the third input of the storage unit, an output down counter coupled to the input of the second permanent memory unit, whose output is connected to the second input of the matched filter.

 The use of picosecond video pulses provides high range resolution at high range.

 The emission of picosecond video pulses in the form of a sequence of bursts of pulses can significantly increase the measured range to objects in comparison with the prototype.

 Thanks to the method, in principle, it becomes possible to carry out a coordinated filtering of the received (reflected from the object) signal — video pulses and to increase noise immunity by improving the signal-to-noise ratio.

 The figure 1 presents information confirming the possibility of implementing the method: considered signals and operations on them according to the method, allowing to achieve a technical result. The figure 2 presents a structural diagram of a device for implementing the method. In figures 3 and 4 presents diagrams explaining the operation of the method and device for its implementation.

The method is as follows:
- generate a periodic sequence of picosecond sawtooth video pulses;
- emit a periodic sequence of picosecond video pulses in the form of a sequence of packs, and video pulses of a picosecond duration in a packet are phase-manipulated according to the law of a pseudorandom sequence;
- probe the investigated object by the emitted periodic sequence of picosecond video pulses;
- receive a signal reflected from the object;
- subjected to the time-scale transformation of the received signal;
- quantize the converted signal;
- remember the quantized signal;
- subjected to matched filtering stored quantized signal;
- they process the stored filtered signal and obtain measuring information about the test object by counting on the displayed data, data recorded in the form of a hard copy or on a PC.

 The method is implemented as follows.

The emitted (probing) signal, the shape of which is known in advance, is a pack (sequence) of phase-manipulated (FM) video pulses of picosecond duration according to the law of a pseudorandom sequence (PSP), periodically repeated. Therefore, the received signal is an FM signal with the greatest potential noise immunity. In addition, the signal-to-noise ratio for the FM signal increases by N ^1/2 compared to a single pulse (N is the number of pulses in a packet; N >> 1 and can be of the order of 10000), which is equivalent to an increase in N times of the accuracy of range measurement to object. On the other hand, an increase in the energy of the emitted signal by a factor of N (usually N >> 2) contributes to the measurement of N times the greater range to objects (which the method is aimed at). The comparative simplicity of phase coding ensures the successful implementation of the method.

Experimental studies show that the most optimal conditions for the propagation of the probe signal and, accordingly, the content of information about the object are carried out in the range from 100-200 MHz to 10 GHz. In this range, independence from weather conditions and the lowest possible level of temperature noise during propagation are ensured. Therefore, the duration of the video pulses in the packet is selected based on this frequency range and for the upper boundary of the range it is t _imp.opt = 100 ps.

 Since the shape and parameters of the probe signal are known in advance, this method provides the possibility of coordinated filtering of the received signal, which in the prototype cannot be performed in principle. The equipment for the implementation of coordinated filtration is distinguished by its simplicity and small dependence of its performance on the accuracy of adjustments with small dimensions and weight. The process of consistent filtering itself is the "alignment" of the temporal structures of the signal and noise. In addition, the application of the principle of adaptation at reception provides additional suppression of interference [4].

The possibility of implementing the method, consider the example (figure 1):
- a probe signal in the form of a pseudo-random sequence of picosecond pulses with N = 5,
- optimal filtering of the received signal (calculation of the autocorrelation function),
- the implementation of measuring the distance to the investigated object.

 Specifically, this is expressed in the following.

 A periodic sequence of picosecond sawtooth-shaped video pulses is generated.

 The generated pulses emit and receive a probe signal, which is a sequence of packs of FM video pulses of picosecond duration (FM according to the law of the SRP) with N = 5.

This can be represented as follows. For example, picosecond video pulses of a sawtooth shape of the corresponding polarity are generated, shifted relative to each other by a constant value t _sdv equal to the duration of the front of the video pulse t _f (t _sdv = t _f ). During the emission of each picosecond video pulse, a sawtooth current pulse is converted to the field strength of the probe signal: E ~ di / dt, where E is the electric field in the far zone, i is the current in the emitter.

 Therefore, each emitted pulse will take its place in the time sequence and a packet of video pulses is formed, which is an FM signal of the required type, periodically repeated.

Denoting the positive and negative pulses in the FM signal as "+1" and "-1", we represent the probing FM signal in the form (figa)
s (t) = [+ 1 +1 +1 -1 +1].

We write the reflected signal as (figv)
s (tt _o ) = [0 0 0 +1 +1 +1 -1 +1],
where t _o is the time delay between s (t) and s (tt _o ), which carries information about the distance to the object.

The impulse response H (t) (Fig. 1b) for s (t) is a mirror image of s (t) relative to the ordinate. Consequently,
H (t) = [+ 1 -1 +1 +1 +1 +1].

 Since the shape of the probe signal is known in advance, it is received before the measurement process, discrete signal values are read at the sampling and sampling times (time-scale conversion [5]), and extended signals are amplified, quantized and stored from the selected FM signal samples.

To measure the range, the generated FM signal is emitted and the object under investigation is probed by it. The reflected signal is received, subjected to time-scale conversion, the converted signal is quantized, and the measured signal is stored, which consists of the sum of the received signal s (nT-Т _о ) (passed the time-scale conversion) and pre-sampled (time-scale conversion operation) and the stored probe signal s (nT) (Fig. 1d), where T _o is the value of t _o after the time-scale transformation (in the transformed time scale), T is the sampling period, n = 0, 1, 2, ..., k-1 .

Since the signals s (t) and s (tt _o ) are separated in time, for t> 0, the signal s (nT) is first stored, and starting from the time t = t _o , the measured signal is stored
s _o (nT) = s (nT) + s (nT-T _o ).

After the signal s _o (nT) is remembered, it is subjected to matched filtering, which can be represented in the following form.

The stored signal values s _o (nT) delay relative to themselves by a constant value τ (where τ is the duration of one pulse in the FM probing signal from the total number N in the transformed time scale, as shown in Fig. 1): the second relative to the first by τ, the third relative to the second on τ and so on. At the same time, they are inverted in accordance with the signs of the function H (t): the “+” sign is not inverted, the “-” sign is inverted. The signals obtained in this way are summed, and the total signal, in turn, is summed with accumulation (the sum of all previous values is added to this value) with the same signal, but which is delayed by τ and inverted (Fig. 1d).

The result is data that carries information about the investigated object. After that they perform an operation, for example, code-to-analog conversion, receive the measured signal in analog form and display it, for example, on the PC monitor screen, and the required parameter is directly determined from the displayed data (Fig. 1e). From FIG. 1e it can be seen that the time interval between the two main maxima of the autocorrelation function (ACF) is equal to T _o , that is, exactly corresponds to the value of t _o , but on a transformed time scale.

In this example, the value of t _o = 4τ / k was taken, and T _o turned out to be equal to 4T, where k is the transformation coefficient [5].

Since τ and T are known in advance, the desired value is obtained in the form of the value c / 2T _о , where c is the speed of light. The measurement of t _o will correspond to a change in the temporal position of the two main ACF maxima.

где mN - количество выборок; l•t_c=l(Tm) - интервал сдвига; l=0, 1, 2, .. ., k-1; k - общее число измеряемых ординат корреляционной функции.We show that this method (process) of measuring the distance to the object is optimal. The autocorrelation function (ACF) of the measured signal s _o (nT) is an expression of the form

where mN is the number of samples; l • t _c = l (Tm) is the shear interval; l = 0, 1, 2, ..., k-1; k is the total number of measured ordinates of the correlation function.

В этом выражении АКФ s_o(nT) представляет собой сумму АКФ сигналов s(nT) и s(nT-Т_о), то есть то, что представлено на фиг.1 (расстояние между главными максимумами АКФ s_o(nT) и есть искомая дальность).Given the definition of the measured signal, we obtain

In this expression, ACF s _o (nT) is the sum of ACF signals s (nT) and s (nT-Т _о ), that is, what is shown in Fig. 1 (the distance between the main maxima of ACF s _o (nT) is desired range).

 When measuring the distance to a moving object, a Doppler shift appears, the magnitude of which is determined by the direction and speed of the object. Selecting the difference signal and subjecting it to the Fourier transform, a spectrum is found near the components corresponding to the distance to the object, the width of which corresponds to the speed of the object. The technique of such measurements has been sufficiently studied and tested [1].

For an FM signal, the signal-to-noise voltage ratio is
SIGNAL / NOISE = (N • 2E ₁ / a) ^{l / 2} ,
where E ₁ is the energy of one pulse of the FM signal, and is the one-sided spectral noise density.

With an increase in N, the signal-to-noise ratio increases:
- for N = 5 it is 2.2 times greater than for one pulse,
- for N = 255 it is 16 times greater than for one pulse.

Thus, the main ACF maxima (Fig. 1f) will be N ^1/2 times more clearly distinguished from the noise background, and the signal-to-noise ratio and measurement accuracy will be N ^1/2 times greater than that of the prototype. With a frequency band of 10 GHz (t _imp = 100 ps, noise temperature 80 K), the time resolution is 0.1 ns, which corresponds to a range resolution of no more than 1-1.5 cm (attenuation is practically absent). For N = 1000, the measured range reaches 300-1500 km, which is significantly greater than that of the prototype. Thus, the technical result, which provides the proposed method, is achieved.

 The figure 2 presents a device that implements the proposed measurement method, which includes a generator 1 picosecond sawtooth video pulses (GPPVI), a transmitting antenna 2, a receiving antenna 3, a time-scale converter (MVP) 4, a memory unit (PSU) 5, a matched filter (SF ) 6, processing unit (BO) 7, address former (FA) 8, first read-only memory (ROM1) 9, second read-only memory (ROM2) 10, address counter (CA) 11, reverse counter (PC) 12, former thirteen.

 The first output of the picosecond sawtooth video generator 1 is connected to the input of the transmitting antenna 2, and the second output (sync.) Is connected to the second input of the time-scale converter 4, the first input of which is connected to the output of the receiving antenna 3, the input of which is connected to the object, which is connected with the output of the transmitting antenna 2, the first output of the time-scale converter 4 is connected to the first input of the memory unit 5, the output of which is connected to the first input of the matched filter 6, the output of which is connected to the processing unit 7, the second output is m the time-shift converter 4 (comp.) is connected to the input of the shaper 13 and the first inputs of the counter 11 and the shaper 8, the second input of which is connected to the second output of the shaper 13 and the input of the reverse counter 12, and the output to the fourth input of the memory unit 5, the second input of which is connected to the output of the first read-only memory 9, the input of which is connected to the output of the address counter 11, the second input of which is connected to the third output of the driver 13, the first output of which is connected to the third input of the memory unit and 5, the down counter output 12 is connected to the input of the second permanent memory 10, whose output is connected to the second input of the matched filter 6.

 The device operates as follows. All work can be divided into the actual measurement and the preliminary cycle.

 The latter is presented in figure 3 and figure 4. Generator 1 generates sawtooth video pulses (PVI) with picosecond front duration. The formation of PVI can be carried out by several methods. This is most easily achieved using a current or voltage drop. At present, the formation of voltage drops with a front duration of about 40-60 ps and an amplitude of 30-50 V does not present practical difficulties.

The generated positive difference in picosecond duration is summed with a negative difference in microsecond duration delayed by time t ₁ . The result is PVI, as shown in figa. The first derivative of the current E ~ di / dt is shown in Fig.3b. Since t ₁ << t ₂ , then A ₂ << A ₁ and A _{2 are} practically not taken into account, and we can say that a sequence of picosecond pulses is formed, from which the FM probe signal of the required form is “collected”.

The formed difference is delayed, inverted and summed with the original, receiving PVI (Fig. 4A). PVI current is supplied to the transmitting antenna 2 (Fig.2), which is a multifunctional phased antenna array (PAR), for example, as discussed in [6]. PVI current is applied to a specific antenna element. As a result of radiation, the current -> field strength is converted (Fig. 3b, 4b). Each element of the phased array is supplied with a current PVI with a corresponding delay: 0, t ₁ , t ₂ .... The sounding signal is generated due to the sequential radiation of the fields E ', E'',E''''... (( figv) and their summation, which provides the required FM probing signal. The delay of the signal arriving at the PAR elements can be performed on segments of transmission lines having a short length and without introducing distortion. Using the HEADLIGHTS allows you to organize a flexible measurement system, which is more preferable compared to conventional antennas.

 The emitted signal is received by the antenna 3 and fed to the input of the MEP 4. The steep front of the first pulse of the generator 1 synchronizes (synchronized) the operation of the entire device.

 Codes from the output of the profit center 4 go to the input of the first ROM1 9 (Fig.2), in which all values of the sounding signal are recorded sequentially (in the order of arrival) at the sampling times. Management of ROM1 9 is carried out by the counter of address 11, which is triggered by each signal "Exercise" at its input and determines the corresponding address for the corresponding code. At the same time, the signal from the output of the profit center 4 is fed to the input of the ROM2 10, the operation of which is controlled by the pulse counter 12. The latter is a reversible counter and does not work from each signal "Exercise" at the input, but only for one, per each video pulse in a packet of FM signal. Therefore, in ROM2 10 information is recorded about the polarity of each video pulse in a pack of "+" or "-" (ROM characters).

 During the measurement, the information from ROM210 is copied to memory block 6, but in the reverse order: what was the last at the input of ROM210 will be the first at its output, and so on, and reading information from ROM210 occurs with address inversion - in the reverse order by compared to the recording process.

 Thus, all the necessary information for the operation of the device is entered in the corresponding nodes 9 and 10 (figure 2). Note that at the output of ROM2 10 (Fig. 2) there is an element (level converter) that converts information in the form of "+" and "-" into levels of "0" and "1", respectively.

The measurement process is as follows. The generator 1 (figure 2) generates video pulses of picosecond duration, as described above, arriving at the antenna 2 in the form of a PAR, which emits a probing FM signal. The signal reflected from the object is received by the antenna 3 and fed to the input of the profit center 4. From the front of the first pulse of the generator 1, the profit center 4 is synchronized (sync.). Last with his signal "Exercise" starts the address generator 8, the driver 13, which generates a “write” signal for the memory block 5 for recording information at the corresponding addresses, and a counter 11, under the influence of the signal of which the information is rewritten from the ROM1 9 to the memory block 5. At the input of the memory block 5 is located an adder for adding signals from the outputs of the MVP 4 and ROM1 9, as a result of which a measuring signal s _o (nТ) is generated. Shaper 13 generates a signal "read" information in the memory unit 5.

 The signal from the output of the shaper 13 starts the reverse counter 12, which controls the operation of the ROM2 10, providing the output from the ROM210 of information about the signs N (t) received at the control inputs of the block 6. At the same time, the output signal of the shaper 13 is fed to the input of the block 8, providing the formation of addresses last for sequential output of information recorded in the memory unit 5. The output signal of the shaper 13 (reset) sets the initial counter address 11.

 Consistent filtering is performed by a node assembled on counters that provide a delay of τ, 2τ, ... (N-1) τ and τ.

 At the output of block 6, a signal is obtained, in analog form, shown in FIG. 1e, which enters the processing unit 7. The latter includes a PC. The processing allows you to determine the necessary parameters of the object.

 When designing the device, you can combine the first and second ROMs, a matched filter, processing unit, blocks 8, 11, 12, 13 into a single unit. If we add the profit center to this, then this part of the device can be organized on the basis of the S9-11 broadband measuring system [7], which greatly simplifies the implementation of the proposed measurement method.

 The considered possible implementation of the device based on the measurement method shows that the device blocks are built on well-known principles and are practically practicable. All this simplifies the application of the proposed method.

 Thus, the industrial application of the method shows the following.

 The use of a special form of the generated signal and the probe signal as a sequence of FM picosecond video pulses with an appropriate choice of the duration of each pulse within the specified limits and the possibility of coordinated filtering operations lead to a significant increase in the accuracy of measuring the distance to objects. The use of a phased array during radiation operation allows you to summarize the power from separate identical antenna elements and can lead to an increase in the power of the probing signal. During the measurement process, it is possible to combine the operations of the time-scale transformation, quantization, and matched filtering, since they are performed by a single device of type C9-11.

 This method provides an increased measuring range characteristic of a long pulse (like an analogue), while maintaining the high resolution inherent to short probe pulses (like a prototype), but is not the sum of the prototype and analogue, and all this with high accuracy of measurements due to the effective noise reduction.

 Periodic video-pulse FM signals of picosecond duration with FM according to the law of the SRP allow to increase the level of reliability of detection and measurement of distance. Such signals allow to solve these problems at a qualitatively new level, increasing the capabilities of measuring systems based on the proposed method. It should be noted the possibility of full automation of the entire measurement process and the application of secondary data processing (during the processing operation), aimed not only at improving the quality of measurements, but also at solving a wider range of tasks when performing a wide variety of measurements.

 The method with high measurement accuracy provides a high energy density, good interaction with the probed object, low cost of hardware implementation.

 The picosecond pulse in the FM probing signal, having a wide spectrum, provides additional noise immunity of the method.

 It is easier to form a sawtooth signal (generation operation) than a rectangular one.

 When using a probing FM signal with a video pulse duration of 100 ps, the resolution of the measurements is no worse than 1-1.5 cm.

 The method allows to determine the speed, acceleration and derivative speeds of a higher order from the measured range, which increases the amount of information about the object.

 Compare this method with an analog and prototype.

For the analogue, the current level of development allows providing a frequency band of 10 GHz at a carrier frequency of 94 GHz. The resolution is 2 times worse, and the noise temperature is 3 times higher than in the case of measurements without a carrier. Therefore, the useful range and range accuracy is half that of the non-carrier method. Compared with the prototype, the measurement accuracy, based on the signal-to-noise ratio (N • 2E ₁ / a) ^1/2 / (2E ₁ / a) = N ^1/2 , increased by N ^1/2 times for N> 1. In this case, the range due to an increase in the signal energy increased N times.

The presence of a powerful probe pulse as in [1] is not necessary in this case, since this method allows one to generate a probe signal of a sufficiently large length (packet length) with an energy of N • E ₁ , and the received signal can undergo such operations that, as a result, narrow enough pulses (figure 1), reducing the dependence on radiated power.

 In this case, the great value of the product of the duration by the width of the spectrum is provided, and the amount of information that the signal can transfer increases in proportion to its duration and the width of the occupied frequency band (which is at least 2 times better than that of the prototype and analog).

 Thus, the proposed method has several significant advantages over the prototype.

The proposed method can be used as a basis for the development of measuring devices and systems that will find wide application:
- for introscopy of the bowels of the earth (underground research) - detection of cavities in the soil (sounding in mines), operational display of soil profiles;
- as an all-weather locator;
- to measure the thickness of ice, search for landing sites (ice reconnaissance);
- to accompany various objects - ensuring the safety of freight traffic.

Literature
1. The use of digital signal processing. / Ed. E. Oppenheim. M .: World. - 1980 .-- 550 s. (p. 272-275).

 2. Skolnik M. Introduction to the technique of radar systems. M.: Mir, 1965 .-- 748 p. (p. 16, 113, 118-121, 125, 126, 146).

 3. Bennett S.L., Ross J.F. Time-pulsed electromagnetic processes and their application. // TIIER. - 1978. - T. 66. - 3. - P.35-57 (prototype), (p.40, Fig. 7).

 4. Compton R. T. Adaptive antenna array in a broadband communication system. // TIIER. - 1978. - T. 66. - 3. - P.23-34.

 5. Ryabinin Yu.A. Stroboscopic oscillography. M .: Sov. Radio, 1972.- 272 p. (p. 6-10).

 6. Bosch B.G. Gigabit electronics. Overview. // TIIER. - 1979. - T. 67. - 3. - S.5-50.

 7. Andriyanov A.V., Shpak I.I. Digital information processing in measuring instruments and systems. - Mn .: Vysh. school., 1987. - 176 p. (p.126-133).

Claims (2)

 1. The method of measuring the distance to the object using picosecond pulses, which consists in generating a sequence of video pulses, emitting them, sensing the object under study, receiving a signal reflected from the object, time-scale conversion of the received reflected signal, quantizing the converted signal, storing the quantized signal, processing the stored signal to obtain measuring information about the object under study by counting on the displayed data, data recorded in the form a hard copy or PC, characterized in that a periodic sequence of video pulses of picosecond sawtooth duration is generated, picosecond video pulses are emitted in the form of a sequence of bursts of pulses, the video pulses in the packet being phase-manipulated according to the law of a pseudorandom sequence, the stored signal is subjected to matched filtering.  2. A device for implementing a method of measuring the distance to objects using picosecond pulses, comprising a transmitting antenna coupled to the object, a receiving antenna coupled to the object, a time-scale converter, the first input of which is connected to the output of the receiving antenna, a processing unit, characterized in that, a picosecond sawtooth video pulse generator is introduced into it, the first output of which is connected to the input of the transmitting antenna, and the second to the second input of the time-scale converter, the first output of the head-time converter is connected to the first input of the memory block, the output of which is connected to the first input of the matched filter, the output of which is connected to the processing unit, the second output of the time-scale converter is connected to the input of the shaper and the first inputs of the address counter and address shaper, the second input of which is connected with the second output of the driver and the input of the reversible counter, and the output with the fourth input of the memory block, the second input of which is connected to the output of the first permanent storage device two, the input of which is connected to the output of the address counter, the second input of which is connected to the third output of the driver, the first output of which is connected to the third input of the memory block, the output of the reverse counter is connected to the input of the second permanent storage device, the output of which is connected to the second input of the matched filter.

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