RU2138887C1 - Stripline nonreflecting band-elimination filter ( variants ) - Google Patents

Abstract

FIELD: SHF equipment, frequency-selective circuits. SUBSTANCE: in agreement with first variant filter is based on asymmetrical stripline. It includes dielectric plate with grounding base. First, quarter-wavelength, and second conductors are deposited on dielectric plate and are connected in series. Two more conductors some ends of which are linked via capacitive gaps to ends of quarter-wavelength conductor and which other ends are interconnected via parallel inductive rod are deposited on dielectric plate. There are presented nine structural variants of band-elimination filter based on transmission striplines. EFFECT: enhanced attenuation on central frequency of rejection band with simultaneous maintenance of low level of mismatch on this frequency. 10 cl, 30 dwg

Description

 The invention relates to microwave equipment, in particular to frequency-selective devices, and can be used in communication, radar, radio navigation, and measuring equipment.

 Known non-reflective microwave filter described in article E.G. Cristal "A method for the design of nonreflecting high power microwave bandpass filter", Microwave Journal, v. 9, N 6, p. 69-74, 1966.

 This filter contains an input transmission line, two channels connected in parallel to it, one of which contains resonators of a reflective band-stop filter (PFZ), the other contains resonators of a reflective band-pass filter (PPF) and an absorbing load. The filter is designed on a waveguide, but its circuit can be implemented on any transmission lines, including strip lines. Depending on the choice of one of the two parallel-connected channels as the output channel to which the output (receiving) transmission line is connected, a known non-reflective filter (the filter can be used either as a non-reflective PPF or as a non-reflective PZF. If the output transmission line is connected to the channel, which contains the reflective PZF, and the channel containing the reflective PFZ is loaded on the absorbing load, in this case the known filter has a frequency response characteristic attenuation corresponding to the characteristic zhayuschego NRF. signal energy at frequencies in a consistent barrier absorbed absorbing load. (The absorbent capacity is a necessary element in the kit form of the filter and without filter ceases to be non-reflective).

The specified non-reflective band-stop filter has the following disadvantages:
- has a low level of attenuation at the center frequency of the fence;
- has a high level of mismatch at the center frequency;
- to absorb signal energy, a component is needed - a coordinated load.

The electrical parameters of the known non-reflective PZF are obtained by analyzing a PC circuit of it, and for greater generality, instead of specific resonators, their equivalent circuits are considered - resonant R, L, C circuits. For a circuit containing a parallel circuit in the serial branch of the output channel, and a serial circuit loaded on the absorbing load in the serial branch of another channel, the following values of the main electrical parameters are obtained. At the central (resonant) frequency, the maximum attenuation (L _max ) and characterizing the level of mismatch - the maximum standing wave coefficient (KST _max ) are respectively:
At Q ₀ = 100, L _max = 6.72 dB, KST _max = 1.6
Q ₀ = 200, L _max = 9.16 dB, KST _max = 1.42
Q ₀ = 10000, L _max = 40.1 dB, KST _max = 1.01
Q ₀ = ∞, L _max = ∞, KST _max = 1
(Q _{0 is the} intrinsic Q factor, which characterizes dissipative losses in the circuits).

For all values of Q _{0, the} inductive and capacitive resistances of the circuits were varied so that the amplitude-frequency characteristic (AFC) had a band of V ₃ = 1% calculated at a level of 3 dB.

The presented numerical data allow us to draw the following conclusions. In the absence of losses in the circuits (Q _o = ∞), i.e. in an ideal reactive known PZF, there is a complete resonant energy absorption in the absorbing load. (The term “full” means the infinite attenuation and the absence of reflection at the center frequency, the term “resonant” means the resonant nature of the frequency response). For small dissipative losses in the circuits (which corresponds to waveguide resonators), the maximum attenuation is large, but not infinite. There is no complete absorption of energy in the absorbing load due to a mismatch caused by the presence of a finite value of the active component of the impedance of the parallel circuit in the output channel. As the dissipative losses increase (with decreasing Q ₀ ), which corresponds to low-Q strip resonators, the mismatch increases and the maximum attenuation decreases sharply. If the absorbing load is not used, then the known filter instead of the "non-reflective" becomes reflective.

 Thus, the known non-reflective band-stop filter, when implemented on strip lines, has a low attenuation at the center frequency of the obstacle band, a large level of mismatch at this frequency, and furthermore contains an absorbing load.

 The closest in technical essence to the proposed strip non-reflective band-stop filter is the strip non-reflective band-stop filter described in the book of D. L. Matthew, L. Young, E.M.T. Jones, “Microwave Filters, Matching and Communication Circuits,” translated from English, Moscow, “Communication, vol. 2, pp. 280-283, 298-302, 315-317, 1972.

 The prototype filter described in this book is designed on a symmetrical air stripe line containing two outer metal plates. By known methods, its parameters can be calculated for implementation on an asymmetric strip line containing a dielectric plate, on one side of which there is a grounding base.

 The prototype filter contains a dielectric plate, on one side of which there is a grounding base. On the other side of the dielectric plate are the conductors of the input and output transmission lines, a quarter-wave conductor, the first and second conductors open at the ends, and a connecting conductor. The filter also contains an absorbing load. The ends of the quarter-wave conductor are connected directly to the conductors of the input and output transmission lines, respectively. The first and second conductors have a length of more than one quarter of the wavelength and their one ends are capacitively connected to the ends of the quarter-wave conductor, respectively. In addition, the first and second conductors are interconnected by means of a connecting conductor having a length equal to three quarters of the wavelength, while the other ends of the first and second conductors are capacitively connected to the ends of the connecting conductor, respectively. One end of the connecting conductor is open, and the other end is conductively connected to the absorbing load. (The first and second conductors of the prototype filter form half-wave resonators. Hereinafter, as is customary, we will call strip resonators, depending on the length of the conductors forming the resonators, “half-wave” and “quarter-wave”. In fact, due to the reactive coupling of the resonators with external circuits, for half-wave resonators, the length of the conductors is more than one quarter of the wavelength, but less than one half of the wavelength, and for “quarter-wave” resonators, the length of the conductors is less than one quarter of the wavelength).

 Among the listed features of the prototype common to him and the proposed filter, made according to the first embodiment, there are the following significant features: the presence of a dielectric plate, on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are capacitively connected to the bottom and other ends of the quarter-wave conductor, respectively, and the other ends are interconnected.

 The disadvantages of the prototype are the low level of attenuation at the center frequency of the boom strip and the presence of an absorbing load. This is due to the following considerations. The prototype filter is a four-arm device (eight-pole device), the insertion loss characteristics of which, depending on the choice of output arm, correspond to either non-reflective PPF or non-reflective PZF. In the application materials, a strip non-reflective filter prototype is considered as a non-reflective PZF, therefore, the arm to which the signal power is transmitted with attenuation corresponding to the characteristic of the PZF is selected as the output, the third arm is open and the fourth is loaded on the absorbing load. This consideration is in agreement with the possible use of a prototype filter. The signal power at the boom frequencies is absorbed in the matched absorbing load. The low level of attenuation at the resonant frequency and the necessary presence in the filter kit prototype of the absorbing load can be explained on the basis of the physical principles of its operation.

Under the ideal condition that there are no losses in half-wave resonators containing the first and second conductors and due to the presence of a quarter-wave conductor and a connecting conductor with a length of three quarters of the wavelength in the prototype filter structure, it is possible to completely absorb energy in the load at the resonant frequency. But, since the dissipative losses in the resonators are significant and ideal conditions are not satisfied, there is no complete absorption in the load. Indeed, dissipative losses lead to the fact that at the resonant frequency f _{0 the} input impedance of the resonators R _{in is} not equal to unity and part of the signal power, bypassing the resonators by means of a quarter-wave conductor, is transmitted from the input to the output of the prototype filter, reducing its attenuation. The analysis methods calculated the electrical characteristics of the strip non-reflective PZF - prototype. In the analysis, the following parameters were varied.

X _C - capacitance, characterizing the capacitive coupling of the ends of the first and second conductors with the ends of the quarter-wave and connecting conductors, respectively,
l ₀ , ρ _o ,, Q ₀ - geometric length, wave impedance, and intrinsic Q factor of a strip line segment containing a quarter-wave conductor
l ₁ , ρ ₁ ,, Q ₀ - geometric length, wave impedance and intrinsic Q factor of the strip line segments containing the first and second conductors;
l ₂ , ρ ₂ ,, Q ₀ is the geometric length, wave impedance, and intrinsic Q factor of the strip line segment containing the connecting conductor.

The following main electrical parameters are obtained for the frequency response with a 3 dB bandwidth V ₃ = 1%;

At Q ₀ = 100, L _max = 5 dB, KST _max = 1.016
Q ₀ = 200, L _max = 8.15 dB, KST _max = 1.006
Q ₀ = 500, L _max = 14.3 dB, KST _max = 1.005
From the presented data it can be seen that the prototype filter has small attenuation values at the center frequency, but it has a low level of mismatch.

 Therefore, the strip non-reflective bandpass filter selected as a prototype has a low attenuation at the center frequency of the obstacle strip and contains an absorbing load.

 The aim of the invention is the creation of a strip non-reflective band-stop filter, providing increased attenuation at the center frequency of the boom band while maintaining a low level of mismatch at this frequency and over a wide frequency range and not containing absorbing load. The goal is the same for all variants of the proposed strip non-reflective band-stop filter. The problem is solved essentially in the same way, which is confirmed by the matrices (1), (4), (5) given below in the text and the relations (2) between the matrix elements that are common for all variants of the proposed PZF. This goal is achieved by the fact that in the first embodiment, in a strip non-reflective bandpass filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side there are conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly with the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which have capacitive coupling with one and the other ends of the quarter-wave the superconductor, respectively, and the other ends interconnected, according to the invention the first and second conductors have a length less than one-quarter wavelength, while their other ends are interconnected through the further inductive inputted parallel rod.

 The invention is illustrated by the following description and the attached drawings.

In FIG. 1 shows the design of the proposed filter, made according to the first embodiment;
in FIG. 2 - equivalent circuit of the proposed filter, made according to the first embodiment;
in FIG. 3 - calculated frequency response and CTF of the proposed filter, made according to the first embodiment.

In FIG. 1,2 and in the text the following notation:
1-dielectric plate;
2 - grounding base;
3.4 - conductors of the input and output transmission lines;
5 - a quarter-wave conductor;
6.7 - the first and second conductors;
8 - additionally introduced parallel inductive rod.

(According to the terminology adopted in the microwave technology, the term "parallel inductive rod" means a metal rod connecting the current-carrying conductor to the grounding base and introducing into the transmission line an inhomogeneity equivalent to the inductance connected in parallel. See, for example, "The Guide to Elements of Strip Technology under the General Edition A. L. Feldstein, Moscow, “Communication” 1979, p. 197.)
i is a conditionally selected section in which one end of the quarter-wave conductor 5 is directly connected to the conductor 3 of the input transmission line;
i 'is a conditionally selected section in which the other end of the quarter-wave conductor 5 is directly connected to the conductor 4 of the output transmission line;
S - capacitive gaps between the ends of the quarter-wave conductor 5 and one ends of the first 6 and second 7 conductors, respectively;
L is the equivalent inductance formed by a parallel inductive rod 8.

 C is the equivalent capacitance characterizing the capacitive coupling of the ends of the quarter-wave conductor 5 with the ends of the first 6 and second 7 conductors.

 The proposed strip non-reflective band-stop filter according to the first embodiment is made on a strip line (microstrip or symmetrical).

 In the microstrip design, the filter according to the first embodiment contains a dielectric plate 1 with a grounding base 2. Conductors 3, 4 of the input and output transmission lines, a quarter-wave conductor 5, the ends of which are directly connected in sections i, i 'with conductors 3, 4 are applied to the dielectric plate 1 input and output transmission lines, respectively. The first 6 and second 7 conductors are also deposited on the dielectric plate 1, one ends of which through capacitive gaps S are capacitively connected to one and the other ends of the quarter-wave conductor 5, respectively. The other end of the first conductor 6 is connected to the other end of the second conductor 7 through an additionally introduced parallel inductive rod 8.

Strip non-reflective band-stop filter according to the first embodiment works as follows. The microwave signal coming through the input transmission line 3 at a given frequency fo does not pass to the output transmission line 4 and is not reflected in the input. The electromagnetic energy of the signal is completely absorbed, being converted into thermal energy in the structural elements due to the presence of "natural" ohmic losses in the conductors and dielectrics. The filter attenuation has a resonant character, and at the resonant frequency f ₀ the transmission coefficient has a pole. Outside the resonance absorption band, in a wide frequency band, a signal with a small attenuation (L ₀ ≈ 0.1 dB) passes from input 3 to output 4. There is no reflection at the resonant frequency (CCT = 1); outside the absorption band of CTC, it slightly differs from unity (CTC ≈ 1.08). For brevity, we will call the “full resonance absorption effect” the properties of a four-pole circuit to completely absorb energy at a given frequency, while at the same time ensuring a low level of mismatch and loss in a wide frequency band outside the absorption band, without the use of special absorbing elements.

To explain the presence of the effect of full resonance absorption, we will analyze the filter equivalent circuit, which is shown in the attached FIG. 2. It contains input 3 and output 4 transmission lines, quarter-wave segment 5, the first 6 and second 7 segments of the transmission line with a quasi T-wave and concentrated L, C elements. We emphasize that in the filter structure there are no absorbing loads and nonreciprocal elements. The circuit shown in FIG. 2, is a passive linear reversible symmetrical 4 ^x -pole formed by parallel connection of two components of 4 ^x -poles.

The first component 4 ^x -polyusnik comprising segments 6, 7 of the transmission line, one ends of which are connected via the capacitance C to the ends 5 of the quarter segment, and the other ends are interconnected through inductance L, as follows from analysis is an inverter resistance with the parameter K ₁ = 0.5. This inverter gives a frequency shift of φ = -90 ^° at frequency f ₀ . Since the lengths of the segments 6, 7 are slightly less than one quarter of the wavelength, in addition to the inverter parameters, the first component of the 4 ^x- terminal also carries out frequency selection of the signal corresponding to the two-cavity reflective PPF with the following parameters: at the center frequency f _0, dissipative losses L ₀ = 7.9588 dB, KST = 1.5: input impedance active (R _e Z _I = 0.6667; I _m Z _I = 0). Dissipative losses are caused by distributed losses in the conductors and dielectrics of a two-cavity PPF, or in other words, the losses are determined by the finite value of the intrinsic Q factor Q _{0 of} two resonators connected through the inductance L.

The second component 4 ^x -pole, containing the quarter-wave conductor 5, is another resistance inverter with the parameter K _o = ρ _o (ρ _o is the wave impedance of the quarter-wave segment). Another inverter at a frequency f ₀ gives a phase shift of φ = +90 ^° . With the parallel connection of the two 4 ^x considered poles, with the marked properties and the listed parameters, a short circuit mode is provided at the frequency f ₀ at the output of the claimed filter, and this explains the existence of the transmission coefficient pole. The input impedance of the resulting 4 ^x - pole is active and is equal to R _e Z _in = 1 (I _m Z _in = 0) - and this explains the ideal matching mode (KST = 1). The presence of dissipative losses (L ₀ = 7.9588dB) in the resonators provides complete absorption (thermal dissipation) of the signal energy. Note that dissipative losses in the prototype filter, on the contrary, are the cause leading to a low level of attenuation at the center frequency. Beyond resonance absorption band, the signal from input to output is transmitted filter "essentially" means quarterwave length, bypassing the first constituent 4 ^x -polyusnik because at these frequencies it has a large reactive component of the input impedance. This ensures a low level of mismatch and loss in a wide frequency band.

Thus, the structure under study ensures the existence of a transmission coefficient pole at a given frequency f ₀ , perfect matching at this frequency and a low level of mismatch and loss in a wide frequency band outside the absorption band, and the filter structure does not have absorbing loads and nonreciprocal elements.

 The quantitative relations between the parameters necessary for calculating the filter can be found using classical transfer matrices.

матрица передачи первого составляющего 4^х-полюсника,

матрица передачи второго составляющего 4^х-полюсника
Тогда параллельное соединение этих 4^х-полюсников описывается матрицей

Требования существования полюса на заданной частоте f₀ и одновременно отсутствие отражения на этой частоте, приводят к следующим соотношениям между элементами матриц:
A'₁₂=-A''₁₂; A'₁₁=A''₁₁-A''₁₂ (2)
Для схемы фиг. 2 аналитические выражения элементов матриц имеют вид:

где

постоянная распространения четвертьволнового отрезка 5 (см. фиг. 2);

постоянная распространения отрезков 6, 7;
Q'₀Q''₀ - собственная добротность отрезков 6, 7, 5.Let be

transfer matrix of the first component 4 ^x -pole,

transfer matrix of the second component 4 ^x -pole
Then the parallel connection of these 4 ^x- terminals is described by the matrix

The requirements for the existence of a pole at a given frequency f ₀ and at the same time the absence of reflection at this frequency lead to the following relationships between the elements of the matrices:
A _'12 = -A'_'12; A _'11 = A'_'11-A'_'12 (2)
For the circuit of FIG. 2 analytical expressions of matrix elements are of the form:

Where

the propagation constant of the quarter-wave segment 5 (see Fig. 2);

propagation constant of segments 6, 7;
Q ' ₀ Q'' ₀ - intrinsic Q factor of segments 6, 7, 5.

In the future, we take Q ' ₀ = Q'' ₀ - Q ₀
The intrinsic quality factor of a strip line can vary widely by changing the intrinsic quality factor of a dielectric and the intrinsic quality factor of conductors.

- нормированная индуктивная проводимость;

R - нормирующее сопротивление (R=1);

нормированное емкостное сопротивление;

Соотношения (2) и трансцендентные выражения (3), являющиеся функциями комплексной переменной, непосредственно сложно применить для получения расчетных формул. Вместе с тем задачу по расчету фильтра можно упростить, рассматривая схему замещения (фиг. 2) и составляющие ее 4^х-полюсники при различных условиях работы. Так методами анализа определено, что на центральной частоте при отсутствии потерь первый составляющий 4^х-полюсник описывается матрицей:

(4)
при наличии потерь L₀=7,9588 дБ в двух резонаторах первого составляющего 4^х-полюсника, его матрица имеет вид:

(5)
Используя аналитические выражения (3) и найденные матрицы (4), (5) находим следующие расчетные формулы:

(6)

(7)

(8)

(9)
В формулах (6), (7), (8), (9) определены взаимосвязи между параметрами l₁/λ_o, X_C, X_L при l_o/λ_o= 0,25.
Собственная добротность, характеризующая диссипативные потери в резонаторах, определяется из равенства:

(10)
Полоса заграждения (V₃) по уровню L = 3 дБ вычисляется по формуле:

(11)
Предлагаемый фильтр по первому варианту может быть использован при относительных полосах заграждения изменяющихся от 0,5% до 5%.l _o , ρ _o - geometric length and impedance of the quarter-wave segment 5;
l ₁ , ρ ₁ - geometric length and wave impedance of the same segments 6, 7,
wave impedances ρ _o and ρ _{1 /} consider active)
Ω = f / f _o - relative frequency;
f is the frequency variable; f ₀ is the given frequency;
λ _o - wavelength in segments of the transmission line corresponding to the frequency f ₀ ;

- normalized inductive conductivity;

R is the normalizing resistance (R = 1);

rated capacitance;

Relations (2) and transcendental expressions (3), which are functions of a complex variable, are directly difficult to apply to obtain the calculation formulas. At the same time, the task of calculating the filter can be simplified by considering ^the equivalent circuit (Fig. 2) and its 4 ^x -polar components under various operating conditions. Thus, it was determined by analysis methods that at the central frequency in the absence of losses, the first component of the 4 ^x- terminal is described by the matrix:

(4)
in the presence of losses L ₀ = 7.9588 dB in two resonators of the first component of the 4 ^x- terminal, its matrix has the form:

(5)
Using analytical expressions (3) and found matrices (4), (5) we find the following calculation formulas:

(6)

(7)

(eight)

(nine)
In formulas (6), (7), (8), (9), the relationships between the parameters l ₁ / λ _o , X _C , X _L at l _o / λ _o = 0.25 are determined.
The intrinsic Q factor characterizing dissipative losses in the resonators is determined from the equality:

(ten)
The barrage band (V ₃ ) at the level of L = 3 dB is calculated by the formula:

(eleven)
The proposed filter according to the first embodiment can be used with relative barrage bands varying from 0.5% to 5%.

 The presented formulas (6-11) make it possible to calculate the claimed strip non-reflective PZF according to specified requirements. We illustrate this with an example.

Let it be given: the barrage band at the level L = 3 dB is equal to V ₃ = 1%; center frequency Ω = 1; attenuation at the center frequency L _max ≥ 50 dB, KST ≤ 1.05; the filter must be made on a microstrip line having Q ₀ = 200 (material - polycor).

We take the wave impedances of the quarter-wave segment 5, the first 6 and second 7 segments of the strip line the same and equal ρ ₁ = ρ _o = ρ = 1 (we recall that in the calculation formulas all parameters are normalized). By the formulas (6-11) we find X _C = 11.5422; X _L = 0.00374; l ₁ / λ _o = 0.2356499; l _o / λ _o = 0.25.
So, all parameters are calculated, then the structural dimensions are determined by known methods.

 Using the found parameter values using a PC, the AFC and the frequency dependence of the CTF are constructed, which are shown in the attached FIG. 3 (curves 1 and 2, respectively).

 The calculated curves illustrate the existence of the transmission coefficient pole at a given frequency Ω = 1, ideal matching at this frequency and a low level of mismatch and loss in a wide frequency band.

Clarification is needed on the attainable attenuation values at the resonant frequency. The calculated curves shown in FIG. 3, obtained at the values of the parameters calculated by the formulas (6-11). These formulas were derived under the assumption that, compared with the losses L ₀ = 7.9588 dB in the resonators of the first component of the 4 ^x- terminal, the losses in the second component of the 4 ^x- terminal (in the quarter-wave segment) are negligible and its intrinsic Q factor Q _o = ∞. In this case, the transmission coefficient has a pole, and KCT = 1. If we take into account the losses in the quarter-wave segment, then the attenuation L _{max is} large (L _max ≈ 100 dB), calculated using formulas (6-11), but not infinitely. Nevertheless, the analysis on a PC shows that when losses are taken into account, with a small correction of the calculated parameter values, it is possible to obtain very large attenuation values (L _max = 200 - 300 dB at KST = 1).

 Obviously, in the structure of the proposed non-reflective PZF there are no restrictions for achieving any arbitrarily large attenuation at the resonant frequency and at the same time a low level of mismatch at this frequency and in a wide frequency band.

 In order to verify the practical feasibility of the proposed filter and experimentally determine the values of the main electrical parameters, filter mock-ups were made and tested. Test report attached. The protocol contains information on the design parameters and measured values of the main electrical parameters of the two types of microstrip non-reflective PZF, one made according to the first option, and the other non-reflective PZF made according to the second option (this filter will be considered below as the second version of the PZF). The data presented in the protocol show that the filters have high electrical parameters and technological feasibility.

 In the second embodiment, in a strip non-reflective band-pass filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side there are conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the input and output conductors transmission lines, respectively, the first and second conductors, open at the ends and connected to each other, and their one ends are capacitively connected to one and the other ends of the quarter respectively, according to the invention, the first and second conductors are capacitively coupled to one another and implemented between the other end of the first one and one end of the second.

 For the second variant of PZF, the analogue and filter prototype are the same as for the first variant of PZF.

 The second embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 4 shows the design of a strip non-reflective band-stop filter made in the second embodiment.

 In FIG. 5 - equivalent circuit of the proposed filter, made according to the second embodiment.

 In FIG. 6 - calculated frequency response and CTF of the proposed filter, made according to the second embodiment.

 The difference between the strip non-reflective PZF in the second embodiment and the PZF in the first embodiment is that it does not contain a parallel inductive rod; the length of the first and second conductors is one quarter of the wavelength longer than that of the same conductors in the first embodiment; the connection of two conductors with each other is capacitive, and not through a parallel inductive rod; communication is made between the other end of the first conductor and one end of the second, and not between the other ends.

In FIG. 4, 5 and in the text the following additional designations are adopted according to the second option:
S is the capacitive gap between one end of the first conductor and one end of the quarter-wave conductor;
S ₁ - capacitive gap between the other end of the first conductor and one end of the second conductor;
S ₂ is the capacitive gap between one end of the second conductor and the other end of the quarter-wave conductor;
C, C ₁ , C ₂ are equivalent capacities characterizing capacitive coupling realized by capacitive gaps S, S ₁ , S _2, respectively.

 The principle of operation of the strip non-reflective PZF according to the second variant is no different from the principle of its operation according to the first variant. Matrices (1), (4), (5) and relations (2) between the elements of the matrices remain unchanged, which confirms the solution of the problem in the same way.

 The equivalent scheme of the FZP performed according to the second variant is difficult for an analytical description, therefore, for the PZF according to the second and subsequent third to tenth options, the numerical values of the parameters corrupted by PC analysis for three different obstacle bands are presented.

 For other required fence bands, parameter values can be obtained by interpolation methods.

Below are the values of the PZF parameters according to the second embodiment for three V ₃ obstacle bands at a level of 3 dB.

Q₀ = 206.For V ₃ = 0.97% X _C = X _C2 = 8; X _C1 = 128.5;

Q ₀ = 206.

Q₀ = 390.For V ₃ = 0.51% X _C = X _C2 = 11; X _C1 = 242.7;

Q ₀ = 390.

Q₀ = 1000.For V ₃ = 0.2% X _C = X _C2 = 18; X _C1 = 648;

Q ₀ = 1000.

Q₀ = 206.The characteristics shown in FIG. 6 are built with the following parameter values:
X _C = X _C2 = 8; X _C1 = 98;

Q ₀ = 206.

 PZF according to the second option can be used with relative barriers, varying from 0.2% to 7%.

 The attached test report shows the measured values of attenuation at the resonant frequency and KST in a wide frequency range of three filter mock-ups made on various dielectric materials. The experimental data show the highest achievable values of the main electrical parameters of the strip non-reflective PZF, performed according to the second option.

 Comparison of the PZF performed according to the first and second options shows that due to capacitive coupling between the first and second conductors, the PZF according to the second option has the advantage of implementing narrower barriers.

 In the third embodiment, in a strip non-reflective bandpass filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side there are conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the input and output conductors transmission lines, respectively, the first and second conductors, one ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, and the other ends are connected ezhdu is, according to the invention linkage one ends of the first and second conductors with the ends of the conductor quarterwave direct conductive, and the other ends are interconnected through the further inductive inputted parallel rod.

 For the third version of the PZF analogue and filter prototype are the same as for the first version of the PZF.

 A third embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 7 shows the design of a strip non-reflective band-stop filter made in the third embodiment.

 In FIG. 8 - equivalent circuit of the proposed filter, made according to the third embodiment.

 In FIG. 9 - calculated frequency response and CTF of the proposed filter, made according to the third embodiment.

 The difference between the strip non-reflective PZF in the third embodiment and the PZF in the first embodiment is that the length of the first and second conductors is one quarter wavelength longer than the same conductors in the first embodiment, the connection of one end of both conductors with the corresponding ends of the quarter-wave conductor conductive rather than capacitive.

 The principle of operation of the strip non-reflective PZF according to the third embodiment is no different from the principle of its operation according to the first embodiment.

Q₀ = 11.2.PZF according to the third embodiment has the following parameter values:
For V ₃ = 18% X _L = 0.55;

Q ₀ = 11.2.

Q₀ = 13.For V ₃ = 15.6% X _L = 0.548;

Q ₀ = 13.

Q₀ = 15.For V ₃ = 13.6% X _L = 0.535;

Q ₀ = 15.

Q₀ = 15.Depicted in FIG. 9 characteristics are built with the following parameter values:
X _L = 0.535;

Q ₀ = 15.

 The FZP according to the third embodiment can be used with relative barrage bands varying from 5% to 15%.

 A PZF made according to the third embodiment, compared to a PZF made according to the first embodiment, has the advantage that its barrier band is wider due to the conductive coupling of the ends of the first and second conductors with the corresponding ends of the quarter-wave conductor.

 In the fourth embodiment, in a strip non-reflective band-stop filter containing a dielectric plate on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output lines the transmission, respectively, the first and second conductors, open at the ends, and their one ends have capacitive coupling with one and the other ends of the quarter-wave conductor co accordingly, the connecting conductor connecting the first and second conductors to each other, according to the invention, the connecting conductor has a length of less than one quarter of the wavelength and it connects the first and second conductors conductively, and in their middle part.

 For the fourth version of the PZF analogue and filter prototype are the same as for the first version of the PZF.

 A fourth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 10 shows the construction of a strip non-reflective band-stop filter made in the fourth embodiment.

 In FIG. 11 is an equivalent circuit of the proposed filter, made according to the fourth embodiment.

 In FIG. 12 - calculated frequency response and CTF of the proposed filter, made according to the fourth embodiment.

 The difference between the strip non-reflective PZF in the fourth embodiment and the PZF in the first embodiment is that the length of the first and second conductors is one quarter wavelength longer than the same conductors in the first embodiment; the connection of both conductors with each other is conductive and is carried out by means of a connecting conductor 8 having a length of less than one quarter of the wavelength, and not through a parallel inductive rod; the connection between the first and second conductors is carried out in their middle part, and not between their other ends.

 The principle of operation of the strip non-reflective PZF in the fourth embodiment is no different from the principle of its operation in the first embodiment.

Below are the values of the PZF parameters according to the fourth embodiment for three V ₃ barrier bands at a level of 3 dB.

Q₀ = 50;
Для V₃ = 1% X_C = 7.44;

Q₀ = 200;
Для V₃ = 0,4% X_C = 12.69;

Q₀ = 494;
Представленные на фиг. 12 расчетные АЧХ и КСТ построены при значениях параметров.For V ₃ = 4% X _C = 3.35;

Q ₀ = 50;
For V ₃ = 1% X _C = 7.44;

Q ₀ = 200;
For V ₃ = 0.4% X _C = 12.69;

Q ₀ = 494;
Presented in FIG. 12 calculated frequency response and KST are constructed at parameter values.

Q₀ = 200;
ПЗФ по четвертому варианту может быть использован при относительных полосах заграждения, изменяющихся от 0,5% до 10%.X _C = 7.598;

Q ₀ = 200;
The FZP in the fourth embodiment can be used with relative barrage bands varying from 0.5% to 10%.

 Comparison of the PZF performed according to the first and fourth options shows that, due to the conductive coupling between the first and second conductors, the PZF according to the fourth option has a wider range of variation of the obstacle band.

 In the fifth embodiment, in a strip non-reflective band-stop filter containing two external metal plates, the conductors of the input and output transmission lines are symmetrically between them, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, some ends of which are connected to one and the other ends of the quarter-wave conductor, respectively, and others are open, the connecting conductor the first and second conductors to each other, according to the invention, the first, second and connecting conductors have a length of less than one quarter of the wavelength, two parallel inductive rods are added that connect one ends of the first and second conductors to two outer metal plates, respectively, one ends of the first and the second conductors are connected to the ends of the quarter-wave conductor conductively through one and the other introduced conductors, and the connecting conductor connects the first and second conductors ki conductive, and their one ends.

 For the fifth variant of the PZF, the analogue and filter prototype are the same as for the first variant of the PZF.

 A fifth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 13 shows the construction of a strip non-reflective band-stop filter made in the fifth embodiment.

 In FIG. 14 is an equivalent circuit of the proposed filter, made according to the fifth embodiment.

 In FIG. 15 - calculated frequency response and CTF of the proposed filter, made in the fifth embodiment.

 The difference between the strip non-reflective PZF according to the fifth embodiment and the PZF according to the first embodiment is that it does not contain a dielectric plate and is made on a symmetrical air stripe line containing two outer metal plates. The first and second conductors are connected at one end to the ends of the quarter-wave conductor conductively through one and the other inserted conductors, and not capacitively. The other ends of the first and second conductors are open and not connected. The connection of the first and second conductors with each other is carried out between their one ends conductively by means of a connecting conductor, and not between the other ends through a parallel inductive rod. Additionally introduced two parallel inductive rods that connect one end of the first and second conductors with two outer metal plates, respectively.

In FIG. 13, 14 and in the text the following additional designations are adopted according to the fifth embodiment:
1,2 - external metal plates;
8 - connecting conductor;
9, 10 - additionally introduced parallel inductive rods;
11, 12 - one and the other introduced conductors;
L is the equivalent inductance formed by each parallel inductive rod 11, 12.

 The principle of operation of the strip non-reflective PZF in the fifth embodiment is no different from the principle of its operation in the first embodiment.

 The FZP in the fifth embodiment has the following parameter values.

Q₀ = 1012;
Для V₃ = 0.126% X_L = 0.031;

Q₀ = 1590;
Для V₃ = 0.08% X_L = 0.025;

Q₀ = 2480;
l₃ - длина одного и другого введенных проводников 11, 12.For V ₃ = 0.2% X _L = 0.039;

Q ₀ = 1012;
For V ₃ = 0.126% X _L = 0.031;

Q ₀ = 1590;
For V ₃ = 0.08% X _L = 0.025;

Q ₀ = 2480;
l ₃ - the length of one and the other introduced conductors 11, 12.

Q₀ = 1960;
ПЗФ по пятому варианту может быть использован при относительных полосах заграждения, изменяющихся от 0,07 до 1,5%.The characteristics shown in FIG. 15 calculated at parameter values:
X _L = 0.028;

Q ₀ = 1960;
The FZP according to the fifth embodiment can be used with relative barrage bands varying from 0.07 to 1.5%.

 The FZP in the fifth embodiment, compared with the PZF made in the first embodiment, has the advantage of implementing narrower barriers.

 In the sixth embodiment, in a strip non-reflective bandpass filter containing two outer metal plates, the conductors of the input and output transmission lines are symmetrically between them, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting the other ends of the first of the first and second conductors to each other, according to the invention, four parallel inductive rods are additionally introduced, which connect one and the other ends of the first and second conductors to two outer metal plates, respectively, one ends of the first and second conductors are connected to the ends of the quarter-wave conductor through one and the other introduced conductors, and the connecting conductor has a length of less than one quarter of the wavelength and connects the other ends of the first and second conductors conductively.

 For the sixth variant of the PZF analogue and filter prototype are the same as for the first variant of the PZF.

 The sixth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 16 shows the construction of a strip non-reflective band-stop filter made in the sixth embodiment.

 In FIG. 17 is an equivalent circuit of the proposed filter, made according to the sixth embodiment.

 In FIG. 18 - calculated frequency response and CTF of the proposed filter, made in the sixth embodiment.

 The difference between the strip non-reflective PZF according to the sixth embodiment and the PZF according to the first embodiment is that it does not contain a dielectric plate and is made on a symmetrical air stripe line containing two outer metal plates. The length of the first and second conductors is one quarter of the wavelength longer than that of the same conductors in the first embodiment and they are connected at one end to the ends of the quarter-wave conductor conductively through one and the other inserted conductors, and not capacitively. The other ends of the first and second conductors are connected conductively by means of a connecting conductor, and not through a parallel inductive rod. Additionally introduced four parallel inductive rods that connect one and the other ends of the first and second conductors with two outer metal plates, respectively.

In FIG. 16, 17 and in the text the following additional designations are adopted according to the sixth embodiment:
1, 2 - outer metal plates;
8 - connecting conductor;
9,10, 11, 12 - additionally introduced parallel inductive rods;
13, 14 - one and the other introduced conductors.

 L is the equivalent inductance formed by each parallel inductive rod 9, 10, 11, 12.

 The principle of operation of the strip non-reflective PZF according to the sixth embodiment is no different from the principle of its operation according to the first embodiment.

 PZF according to the sixth embodiment has the following parameter values.

Q₀ = 475;
Для V₃ = 0.16% X_L = 0.05;

Q₀ = 1225;
Для V₃ = 0.06% X_L = 0.03;

Q₀ = 3435;
l₃ - длина одного и другого введенных проводников 13, 14.For V ₃ = 0.42% X _L = 0.08;

Q ₀ = 475;
For V ₃ = 0.16% X _L = 0.05;

Q ₀ = 1225;
For V ₃ = 0.06% X _L = 0.03;

Q ₀ = 3435;
l ₃ - the length of one and the other introduced conductors 13, 14.

 The frequency response and CTF shown in FIG. 18 are constructed with parameter values.

Q₀ = 3435;
ПЗФ по шестому варианту может быть использован при относительных полосах заграждения, изменяющихся от 0,08% до 2%.X _L = 0.03;

Q ₀ = 3435;
The PZF according to the sixth embodiment can be used with relative barrage bands varying from 0.08% to 2%.

 The PZF in the sixth embodiment, compared to the PZF made in the first embodiment, has the advantage of implementing narrower barriers and, in addition, has the advantage of a higher level of transmitted power.

 In the seventh embodiment, in a strip non-reflective band-stop filter containing two external metal plates, the conductors of the input and output transmission lines are symmetrically between them, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, and the other are interconnected, according to the invention three parallel inductive rods have been introduced, two of them connecting one ends of the first and second conductors with two external metal plates, respectively, and one of them connects the other ends to each other and connects them to two external metal plates, and one ends of the first and second conductors connected to the ends of the quarter-wave conductor conductively through one and the other introduced conductors.

 For the seventh variant of the PZF analogue and filter prototype are the same as for the first version of the PZF.

 The seventh embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 19 shows the construction of a strip non-reflective band-stop filter made in the seventh embodiment.

 In FIG. 20 is an equivalent circuit of the proposed filter, made according to the seventh embodiment.

 In FIG. 21 - calculated frequency response and CTF of the proposed filter, made in the seventh embodiment.

 The difference between the strip non-reflective PZF in the seventh embodiment and the PZF in the first embodiment is that it does not contain a dielectric plate and is made on a symmetrical air stripe line containing two outer metal plates. The length of the first and second conductors is one quarter of the wavelength longer than that of the same conductors in the first embodiment and they are connected at one end to the ends of the quarter-wave conductor conductively through one and the other inserted conductors, and not capacitively. Additionally introduced parallel inductive rods that connect one end of the first and second conductors with two outer metal plates, respectively.

In FIG. 19, 20 and the text adopted the following additional designations for the seventh embodiment:
1, 2 - outer metal plates;
8, 9, 10 - additionally introduced parallel inductive rods;
11, 12 - one and the other introduced conductors.

L ₁ - equivalent inductance formed by parallel inductive rods 8.10;
L ₂ - equivalent inductance formed by a parallel inductive rod 9.

 The principle of operation of the strip non-reflective PZF in the seventh embodiment is no different from the principle of its operation in the first embodiment.

 Below are the parameter values for the PZF in the seventh embodiment.

Для V₃ = 0.2% X_L1 = 0.055; X_L2 = 0.0015;

Q₀ = 1010
Для V₃ = 0.1% X_L1 = 0.04; X_L2 = 0.0008;

Q₀ = 2000.For V ₃ = 0.33% X _L = 0.07; X _L2 = 0.0024;

For V ₃ = 0.2% X _L1 = 0.055; X _L2 = 0.0015;

Q ₀ = 1010
For V ₃ = 0.1% X _L1 = 0.04; X _L2 = 0.0008;

Q ₀ = 2000.

l ₃ - the length of one and the other introduced conductors 11, 12.

Q₀ = 2000.Depicted in FIG. 21 characteristics are calculated at parameter values:
X _L1 = 0.04; X _L2 = 0.0008;

Q ₀ = 2000.

 The FZP according to the seventh embodiment can be used with relative barrage bands varying from 0.05% to 0.5%.

 The PZF in the seventh embodiment, compared with the PZF made in the first embodiment, has the advantage of realizing narrower barriers and, in addition, has the advantage of a higher level of absorbed power.

 In the eighth embodiment, in a strip non-reflective band-stop filter containing two external metal plates, the conductors of the input and output transmission lines are symmetrically between them, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are capacitively coupled to one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting according to the invention, the first, second and connecting conductors have a length of less than one quarter of the wavelength, two parallel inductive rods are added that connect the other ends of the first and second conductors with two outer metal plates, respectively, and the connecting conductor connects the other ends of the first and second conductors with each other conductively.

 For the eighth version of the PZF analogue and filter prototype are the same as for the first version of the PZF.

 The eighth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 22 shows the construction of a strip non-reflective band-stop filter made in the eighth embodiment.

 In FIG. 23 is an equivalent circuit of the proposed filter, made according to the eighth embodiment.

 In FIG. 24 - calculated frequency response and CTF of the proposed filter, made in the eighth embodiment.

 The difference between the strip non-reflective PZF in the eighth embodiment and the PZF in the first embodiment is that it does not contain a dielectric plate and is made on a symmetrical air stripe line containing two outer metal plates. Additionally introduced two parallel inductive rods that connect the other ends of the first and second conductors with two outer metal plates, respectively. The other ends of the first and second conductors are connected conductively by means of a connecting conductor, and not through a parallel inductive rod.

In FIG. 22, 23 and in the text the following additional designations for the eighth option are adopted:
1, 2 - outer metal plates;
8 - connecting conductor;
9, 10 - additionally introduced parallel inductive rods;
L are equivalent inductances formed by parallel inductive rods 9, 10.

 The principle of operation of the strip non-reflective PZF in the eighth embodiment is no different from the principle of its operation in the first embodiment.

Q₀= 1000.For the PZF in the eighth embodiment, the following relationships between the parameters were obtained:
For V ₃ = 0.2% X _C = 24.98; X _L = 0.028;

Q ₀ = 1000.

Q₀ = 2000.For V ₃ = 0.1% X _C = 34.6, X _L = 0.02;

Q ₀ = 2000.

Q₀ = 2510.For V ₃ = 0.08% X _C = 39.9; X _L = 0.018;

Q ₀ = 2510.

Q₀ = 1000.The calculated frequency response and CTF shown in FIG. 24 obtained with parameter values:
X _C = 24.98; X _L = 0.028;

Q ₀ = 1000.

 The FZP in the eighth embodiment can be used with relative barrage bands varying from 0.08% to 2%.

 The PZF in the eighth embodiment, compared with the PZF made in the first embodiment, has the advantage that its frequency response does not have spurious barriers.

 In the ninth embodiment, in a strip non-reflective bandpass filter containing two external metal plates, the conductors of the input and output transmission lines are symmetrically between them, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are capacitively coupled to one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting the first and second conductors to each other, according to the invention, the first, second and connecting conductors have a length of less than one quarter of the wavelength, the other ends of the first and second conductors are short-circuited by the inserted metal plate, conductively connecting the two outer metal plates, and the connecting conductor connects the first and second conductors between each other conductively, moreover, in cross sections spaced from their short-circuited ends at a distance less than one sixteenth of the wavelength.

 For the ninth variant of the PZF analogue and filter prototype are the same as for the first variant of the PZF.

 The ninth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 25 shows the construction of a strip non-reflective band-stop filter made in the ninth embodiment.

 In FIG. 26 is a equivalent circuit of the proposed filter, made according to the ninth embodiment.

 In FIG. 27 - calculated frequency response and CTF of the proposed filter, made according to the ninth embodiment.

 The difference between the strip non-reflective PZF in the ninth embodiment and the PZF in the first embodiment is that it does not contain a dielectric plate and is made on a symmetrical air stripe line containing two outer metal plates. The other ends of the first and second conductors are short-circuited by means of an inserted metal plate, conductively connecting the two outer metal plates, and not loaded onto a common parallel inductive rod. The first and second conductors are connected conductively by means of a connecting conductor, and not through a parallel inductive rod.

In FIG. 25, 26 and in the text the following additional designations for the ninth embodiment are adopted
1, 2 - outer metal plates;
9 - introduced metal plate, conductively connecting the outer metal plate 1 and 2 to each other;
l ₃ is the distance from the metal plate 9 to the cross sections of the first 6 and second 7 conductors, in which the conductors are interconnected by means of a connecting conductor 8.

 The principle of operation of the strip non-reflective PZF in the ninth embodiment is no different from the principle of its operation in the first embodiment.

Q₀ = 500.For the PZF in the ninth embodiment, the following parameter values were obtained:
For V ₃ = 0.4% X _C = 17.5;

Q ₀ = 500.

Q₀ = 1000.For V ₃ = 0.2% X _C = 24.95;

Q ₀ = 1000.

Q₀ = 2000.For V ₃ = 0.1% X _C = 36;

Q ₀ = 2000.

Q₀ = 1000.Depicted in FIG. 27 characteristics are calculated at the following parameter values:
X _C = 24.94;

Q ₀ = 1000.

 PZF according to the ninth embodiment can be used with relative barrage bands varying from 0.1% to 2.5%.

 The PZF in the ninth embodiment, compared with the PZF performed in the first embodiment, has the advantage that its frequency band with a low attenuation level is wider.

 In the tenth embodiment, in a strip non-reflective bandpass filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side there are conductors of the input and output transmission lines, the first and second conductors are connected to each other, and their ends are open, according to the invention, conductors directly connected to the grounding base are applied to the end sides of the dielectric plate, two transmitting conductors are introduced, one ends of which are directly connected are connected to the conductors of the input and output transmission lines, respectively, and their other ends are open and capacitively connected to each other, the open ends of the first and second conductors are capacitively connected to the transmitting conductors, respectively, and, in addition, capacitively connected to each other, and the other ends of the first and second conductors directly connected to a conductor deposited on one end side of the dielectric plate, two additional conductors are introduced, conductively connecting one ends of the transmitting conductors, respectively venno with a conductor deposited on the other face of the dielectric plate.

 For the tenth variant of the PZF analogue and filter prototype are the same as for the first variant of the PZF.

 A tenth embodiment of the invention is illustrated by the following description and the attached drawings.

 In FIG. 28 shows the construction of a strip non-reflective band-stop filter made in the tenth embodiment.

 In FIG. 29 - equivalent circuit of the proposed filter, made according to the tenth embodiment.

 In FIG. 30 - calculated frequency response and CTF of the proposed filter, made in the tenth embodiment.

 The difference between the strip non-reflective PZF in the tenth embodiment and the PZF in the first embodiment is that the input and output transmission lines are interconnected by two transmitting conductors, one ends of which are directly connected to the conductors of the input and output transmission lines, respectively, and their other ends are open and capacitively connected to each other, and not through a quarter-wave conductor, conductors are directly applied to the two ends of the dielectric plate, directly connected to the ground by; the connection between the first and second conductors is capacitive, and between their one ends, and not between the other ends through a parallel inductive rod; the other ends of the first and second conductors are directly connected to the conductor deposited on one end side of the dielectric plate, and are not interconnected; two additional conductors are introduced, conductively connecting one ends of the transmitting conductors, respectively, with a conductor deposited on the other end side of the dielectric plate.

In FIG. 28, 29 and in the text the following additional designations are adopted according to the tenth embodiment:
5, 6 - the first and second conductors;
7, 8 - conductors deposited on the end sides of the dielectric plate;
9, 10 - transmitting conductors;
11, 12 - additional conductors;
S is the capacitive gap between the transmitting conductors 9, 10;
S ₁ - capacitive gap between conductors 5, 6 and conductors 9, 10, respectively;
S ₂ - capacitive gap between the open ends of the first 5 and second 6 conductors;
C, C1, C2 are equivalent capacities characterizing capacitive coupling realized by capacitive gaps S, S ₁ , S _2, respectively.

 The principle of operation of the strip non-reflective PZF in the tenth embodiment is no different from the principle of its operation in the first embodiment.

Q₀ = 56.PZF according to the tenth embodiment has the following parameters:
For V ₃ = 3.6% X _C = 1.23; X _C1 = 96.3; X _C2 = 7;

Q ₀ = 56.

Q₀ = 162.For V ₃ = 1.23% X _C = 1.1; X _C1 = 244; X _C2 = 11;

Q ₀ = 162.

Q₀ = 280.For V ₃ = 0.71% X _C = 1.19; X _C1 = 454; X _C2 = 15;

Q ₀ = 280.

l ₀ - the length of the transmitting conductors 9, 10.

l ₃ - the length of the additional conductors 11, 12.

Q₀ = 162.The characteristics shown in FIG. 30 were obtained with the following parameter values:
X _C = 1.1; X _C1 = 244; X _C2 = 11;

Q ₀ = 162.

 PZF according to the tenth embodiment can be used with relative barrage bands varying from 0.5% to 10%.

The FZP according to the tenth embodiment, compared with the PZF performed according to the first embodiment, has the advantage that it allows one to additionally block the spectral components in the frequency band 0 ≤ Ω ≤ 0.9.
From a comparison of strip non-reflective band-stop filters made according to the proposed schemes of the first to tenth variants and the prototype scheme, it is seen that the attenuation at the center frequency of the obstacle strip of the proposed filter is 10 times or more (decibels) higher than that of the prototype filter, the mismatch levels of the compared filters are approximately the same. The proposed filter does not contain an absorbing load and the absorption of signal energy is carried out in the filter elements due to the presence of natural dissipative losses in them.

 Thus, the use of the invention will increase the attenuation at the center frequency of the obstacle strip while maintaining a low level of mismatch at this frequency and in a wide range of frequencies without absorbing load. This conclusion is the same for all variants of the proposed strip non-reflective band-stop filter.

Claims (10)

 1. Strip non-reflective band-stop filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines respectively, the first and second conductors, one ends of which are capacitively coupled to one and the other ends of the quarter-wave conductor, respectively, and the other ends are interconnected d, characterized in that the first and second conductors have a length of less than one quarter of the wavelength, and their other ends are interconnected via an additionally introduced parallel inductive rod.  2. Strip non-reflective band-stop filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines respectively, the first and second conductors, open at the ends and connected to each other, with one of their ends being capacitively connected to one and the other ends of the quarter-wave conductor with Responsibly, characterized in that the first and second conductors are capacitively coupled to one another and implemented between the other end of the first of them and one end of the second.  3. Strip non-reflective band-stop filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines respectively, the first and second conductors, one ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, and the other ends are interconnected, I distinguish iysya in that the connection ends of one of the first and second conductors with the ends of the conductor quarterwave direct conductive, and the other ends are interconnected through the further inductive inputted parallel rod.  4. Strip non-reflective band-stop filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side - conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines respectively, the first and second conductors, open at the ends, with one of their ends being capacitively coupled to one and the other ends of the quarter-wave conductor, respectively, will connect an integral conductor connecting the first and second conductors to each other, characterized in that the connecting conductor has a length of less than one quarter of the wavelength and it connects the first and second conductors conductively, and in their middle part.  5. Strip non-reflective band-stop filter containing two outer metal plates, symmetrically between which are the conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, some ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, and others are open, a connecting conductor connecting the first and second conductors with each other, characterized in that the first, second and connecting conductors have a length of less than one quarter of the wavelength, two parallel inductive rods are added that connect one ends of the first and second conductors with two outer metal plates, respectively, one ends of the first and second conductors connected to the ends of the quarter-wave conductor conductively through one and the other introduced conductors, and the connecting conductor connects the first and second conductors conductively, When in use, their one ends.  6. Strip non-reflective band-stop filter containing two outer metal plates, symmetrically between which are the conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting the other ends of the first and second wires interconnectors, characterized in that four parallel inductive rods are additionally introduced, which connect one and the other ends of the first and second conductors to two outer metal plates, respectively, one ends of the first and second conductors are connected to the ends of the quarter-wave conductor conductively through one and the other introduced conductors and the connecting conductor has a length of less than one quarter of the wavelength and connects the other ends of the first and second conductors conductively.  7. Strip non-reflective band-stop filter containing two external metal plates, symmetrically between which are the conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, some ends of which are connected with one and the other ends of the quarter-wave conductor, respectively, and others are interconnected, characterized in that three are introduced in parallel inductive rods, and two of them connect one ends of the first and second conductors with two outer metal plates, respectively, and one of them connects the other ends with each other and connects them with two outer metal plates, and one ends of the first and second conductors are connected with the ends of the quarter-wave conductor conductively through one and the other introduced conductors.  8. Strip non-reflective band-stop filter containing two outer metal plates, symmetrically between which are the conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which have capacitive coupling with one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting the other ends of the first and the second conductors to each other, characterized in that the first, second and connecting conductors have a length of less than one quarter of the wavelength, two parallel inductive rods are added that connect the other ends of the first and second conductors to two outer metal plates, respectively, and the connecting conductor connects the other the ends of the first and second conductors to each other conductively.  9. Strip non-reflective band-stop filter containing two outer metal plates, symmetrically between which are the conductors of the input and output transmission lines, a quarter-wave conductor, one and the other ends of which are connected directly to the conductors of the input and output transmission lines, respectively, the first and second conductors, one ends of which have capacitive coupling with one and the other ends of the quarter-wave conductor, respectively, a connecting conductor connecting the first and second wires nicknames to each other, characterized in that the first, second and connecting conductors are less than one quarter of the wavelength, the other ends of the first and second conductors are short-circuited by means of an inserted metal plate, conductively connecting two outer metal plates, and the connecting conductor connects the first and second conductors between itself conductively, and in cross sections spaced from their short-circuited ends at a distance less than one sixteenth wavelength.  10. Strip non-reflective band-stop filter containing a dielectric plate, on one side of which there is a grounding base, and on the other side are the conductors of the input and output transmission lines, the first and second conductors are interconnected, and their one ends are open, characterized in that conductors are directly connected to the grounding base on two end sides of the dielectric plate, two transmitting conductors are introduced, one ends of which are directly connected to the conductors the input and output transmission lines, respectively, and their other ends are open and capacitively connected to each other, the open ends of the first and second conductors are capacitively connected to the transmitting conductors, respectively, and capacitively connected to each other, and the other ends of the first and second conductors are directly connected to the conductor deposited on one end side of the dielectric plate, two additional conductors are introduced, conductively connecting one ends of the transmitting conductors respectively with the conductor, deposited to the other end side of the dielectric plate.

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