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Electric power converter
The present invention relates to an electric power converter, in particular an opposed current converter, also referred to as current amplifier.
Opposed current converters are used for high precision stepper drivers, voice coil actuator positioning systems and ultra low distortion amplifiers. For these applications a very low output distortion is desired. The known converters usually comprise a first branch, comprising a first switch and a first diode connected in series, oriented such that 10 both can conduct a current to a first common node, a second branch, arranged in parallel to the first branch, and comprising a second switch and a second diode connected in series, oriented such that both can conduct a current from a second common node, a first inductance component, with a first end coupled to the first common node, a second inductance component, with a first end coupled to the second common node, a coupling 15 of the respective second ends of the first and second inductance component forming an output connection for a load. The first and second parallel branches are arranged in parallel to a voltage source, and the load is coupled between the output connection and a common ground with the voltage source.
20 State of the art converters are the half/full bridge converter and the opposed current converter.
One disadvantage of the half/full bridge converters according to the state of the art, is that they require a dead-time in switching, that is, a safe margin in their switching 25 control signal for avoiding short circuitry as a result of both switches being switched on.
Disadvantages of the opposed current converter are a bias current that is relatively expensive to measure, and that is relatively high, causing RMS losses and requires high peak current rated output inductors. A bias current is to be understood as current out of 30 the first common node flowing into the second common node.
It is therefore a goal of the present invention to propose an opposed current converter that takes away the above disadvantages of the prior art, and/or to provide a useful alternative.
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The present invention thereto provides an electric power converter, comprising a first branch, comprising a first switch and a first diode connected in series, oriented such that both can conduct a current to a first common node, a second branch, arranged in parallel 5 to the first branch, and comprising a second switch and a second diode connected in series, oriented such that both can conduct a current from a second common node, a first inductance component, with a first end coupled to the first common node, a second inductance component, with a first end coupled to the second common node, a coupling of the respective second ends of the first and second inductance component forming an 10 output connection for a load, and at least a third inductance component, coupled between the first and the second common node.
In use, the first and second parallel branches are arranged in parallel to a voltage source, and the load is coupled between the output connection and a common ground with the 15 voltage source. The voltage source is oriented such that the switch of the first branch is coupled to the positive connection of the power source, and the diode of the first branch to the negative power source.
The third inductance component connects both branches, and enables a current to flow 20 between them. In a situation where both switches are “on”, that is, in a conducting situation, this inductance component is in parallel with the series connection of the first and second inductance components. As a result, a part of the bias current flows through the third inductance component instead of the first and second inductance component.
25 One advantage of the topology according to the invention is that distortion is less than distortion in half/full bridge converter, as it is in a majority of opposed current convertors. Distortion caused by unbalance of output inductors in the opposed current converter, which creates a coupling from bias current to output voltage, is even less in the extra inductor opposed current converter (ELOCC), as the invention will be referred 30 to as well.
In a preferred embodiment, the third inductance component has a lower impedance than the series connection of first and second inductance components, so that a majority of the bias current flows through the third inductance component.
3 A controller is used for controlling the switches, each with a duty cycle, interleaved such that there is a minimum voltage ripple across the third inductance component, and also controlled such that there is a desired average current through the third inductance 5 component such that the current out of the first branch, and into the second branch is always larger than zero.
The output connection may be coupled to a common ground by a capacitor.
10 In order to be able to create both positive and negative currents, a pair of two parallel converters as described above may be applied, wherein two respective output connections form connections for a load. Even a configuration of two quad inductor opposed current converters may be applied, wherein the two respective output connections of the first pair of power converters is coupled and forms a first output 15 connection for a load, and wherein the two respective output connections of the second pair of power converters is coupled and forms a second output connection for a load.
The invention will now be elucidated into more detail with reference to the following figures. Herein: 20 - Figure 1 shows a first embodiment of a converter according to the invention; - Figure 2 shows wave shapes for the converter in figure 1, with for illustrational purposes a non zero resistance used for the Lbx inductor; - Figures 3a-d show the active parts in the converter during various intervals; - Figure 4 shows a full bridge embodiment of the converter according to the 25 present invention; - Figure 5 shows a half-bridge equivalent of a quad inductor opposed current converter according to the present invention; - Figure 6 shows a full bridge embodiment of the quad inductor opposed current converter according to the present invention; 30 - Figure 7 shows wave shapes for the converter in figure 6.
Figure 1 shows a first embodiment of a voltage source Udc to which power converter according to the present invention is coupled, showing a first branch, comprising a first switch Six and a first diode Dix connected in series, oriented such that both can conduct 4 a current to a first common node, having a voltage usnix; a second branch, arranged in parallel to the first branch, and comprising a second switch S2X and a second diode Ü2X connected in series, oriented such that both can conduct a current from a second common node. The converter further comprises a first inductance component Lfix, with 5 a first end coupled to the first common node, that has an output voltage uout and a second inductance component Lnx, with a first end coupled to the second common node, having a voltage usn2x The converter is characterised by a third inductance component Lbx, coupled between the first and the second common node.
10 In the converter according to the state of the art, the bias and output current both flow through the output inductors Lnx and Lf2X. Depending on the phase shift between the PWM switch control signals within a switching cell the current ripple can be moved from the output to the bias current. With the present invention, the bias and output current path are separated by adding an extra inductor Lbx.
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The impedance of Lbx should be lower than the impedance of Lnv + Lf2*. In this case the major part of the bias current flows through the bias inductor only. This can be easily measured with a single current sensor, measuring the current though Lnx and Lnx is not necessary.
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Figure 2 shows various waveshapes for the converter in figure 1. From the figure, it becomes clear that a part of the current continuously flows through Lbx, and that a voltage is over Lbx when both switches are on.
25 Figures 3a-d show the active parts in the converter during various intervals. It is remarked that the state where Ubias is negative does not occur in steady state but it may occur when dynamically adjusting the bias current.
Figure 4 shows a full bridge equivalent converter with an inductor Li and resistor Ri as 30 load. Like numerals refer to like parts. Once can see that the circuit comprises of two converters as shown in figure 1. The first converters components have been marked with a “p”, the second converters components with an “n”.
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Figure 5 shows a half-bridge equivalent of a quad inductor opposed current converter according to the present invention. The circuit comprises of a converter as shown in figure 1 but with separated bias control for leg 1 and leg 2. In this configuration, the currents can be further decoupled, providing separate bias control for both legs and fully 5 decoupled bias/output currents. The separate switching leg allows for non-interleaved switching in the bias path (Lbix and Lb2X) to have a minimum voltage ripple across the bias inductors, and interleaved switching in the output path to have a minimum current ripple through the output capacitor. Using interleaved switching for the output path results in a minimum voltage/current ripple at the output. Using non-interleaved 10 switching in the bias path results in a minimum of required inductance in the bias path. When aiming for an equal voltage or current ripple on the output, compared to the configuration from figure 1, the total inductive volume of the converter from figure 5 can be lower.
15 Figure 6 shows a full bridge equivalent quad inductor opposed current converter with an inductor Li and resistor Ri as load. Like numerals refer to like parts. Once can see that the circuit comprises of two converters as shown in figure 5. The first converters components have been marked with a “p”, the second converters components with an “n”.
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In theory all OCC variants are derived from this QLOCC topology. Removing the bias inductors and the bias switching legs results in the standard OCC topology. Leaving only the bias switching legs out and connecting the two separate bias inductors together results in the ELOCC topology.
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Figure 7 shows wave shapes for the converter from figure 6.