MXPA99009565A - Synchronization of forward link base station power levels during handoff between base station sectors in a mobile radio communication system - Google Patents

Abstract

A method and apparatus for controlling the transmit power levels of first and second base station transceivers, wherein the first and second base station transceivers are respectively associated with first and second sectors of a cell. The received signal strength of a communication signal arriving at the mobile station is initially determined. A power control value that is based on the received signal strength is then transmitted from the mobile station to the first and second base station transceivers. A first received power control value is next generated by attempting to receive the transmitted power control value at the first base station transceiver, and a second received power control value is generated by attempting to receive the transmitted power control value at the second base station transceiver. A common transmit power value is calculated at a base station controller for the first and second base station tranceivers when the first and second received power control values are unequal. The communication signal is then transmitted from the first and second base station transceivers in accordance with the common transmit power value.

Description

SYNCHRONIZATION OF POWER LEVELS OF DIRECT LINK STATIONS DURING THE TRANSFER BETWEEN THE SECTORS OF THE BASE STATION IN A MOBILE RADIOCOMMUNICATION SYSTEM This application claims the priority of the United States Provisional Patent Application serial number 60 / 075,211, filed on February 19, 1998, which is pending.

BACKGROUND DB THE INVENTION I. FIELD OF THE INVENTION The present invention relates generally to communications, and in particular to synchronized power control in a multiple access communications system.

II. Description of the Related Art The use of multiple access modulation techniques with code division (CDMA) is one of several techniques for facilitating communications in which a large number of users of the system are present. Although other techniques are known such as multiple access with time division (TDMA), multiple access with frequency division (FDMA) and AM modulation schemes such as the individual sideband, compressed-expanded in amplitude (ACSSB), CDMA has significant advantages over these other modulation techniques. The use of CDMA techniques in a multiple access communication system is described in U.S. Patent No. 4,901,307 entitled "SPREAD SPECTRUM MULTIPLE ACCESS COMMUNICATION SYSTEM USING SATELLITE OR TERRESTRIAL REPEATERS", assigned to the assignee of the present invention and the description of which is incorporated as a reference in the present. In the patent mentioned above, a multiple access technique is described, wherein a large number of users of a mobile telephone system, each having a transceiver, communicating through satellite repeaters or land base stations ( also known as cellular base stations, or cell sites) using the extended spectrum communication signals of CDMA. By using CDMA communications, the frequency spectrum can be re-used several times, thus allowing an increase in the user's capacity of the system. The use of CDMA techniques results in greater spectral efficiency than can be achieved using other multiple access techniques. In conventional cell phone systems that use analog FM modulation, the available frequency band is divided into channels typically of 30 KHz bandwidth. The service area of the system is divided geographically into cells of variable size. The available frequency channels are divided into sets with each set that usually contains an equal number of channels. The frequency sets are assigned to the cells in such a way as to minimize the possibility of interference between co-channels. Transfer schemes in conventional cellular systems are proposed to allow a call or other type of connection, for example a data link, to communicate with a mobile station across the boundary between the two cells. The transfer from one cell to another is initiated when the receiver in the cellular base station that transfers the call or the connection, notifies that the intensity of the signal received from the mobile station falls below a predetermined threshold value. When the signal level drops below a predetermined threshold value, the base station asks the system controller to determine if a neighbor base station receives the signal from the mobile station with higher signal strength than the current base station. The system controller answers the question of the current base station by sending messages to neighboring base stations with a transfer request. Neighboring base stations then use special scanning receivers to search for the signal from the mobile station in the specified channel. If a transfer is attempted, one of the neighboring base stations must report an appropriate signal strength to the system controller. In a conventional system, a call is discontinued if the transfer to the new base station is unsuccessful. There are many reasons why transfer failure may occur. For example, if there is no unoccupied channel available in the neighbor cell to communicate the call, the transfer fails. Likewise if the neighboring base station reports that it hears the mobile station, but actually actually hears another mobile unit using the same channel in a completely different cell, the transfer fails. The transfer may also fail where the mobile station fails to receive an order signal to switch to a new channel in the neighboring cell. Still another transfer problem in conventional cellular systems occurs when the mobile unit approaches the edge between the two cells. In this situation, the signal level of the mobile station tends to fluctuate in both base stations, thereby creating a "ping-pong" effect. Repeated requests are made to transfer the call back and forth between the two neighboring base stations.

In U.S. Patent No. 5,101,501, entitled "METHOD AND SYSTEM FOR PROVIDING A SOFT HANDFAR IN COMMUNICATIONS IN A CDMA CELLULAR TELEPHONE SYSTEM", assigned to the assignee of the present invention, the description of which is incorporated by reference herein. , a method and system for providing communication with the mobile station through more than one cellular base station during the transfer is described. In this environment, the communication is not interrupted by the transfer of the base station of the cell, the mobile station is going out to the base station of the cell, the mobile unit is entering. That type of transfer can be considered a smooth transfer in communications between cellular base stations because the two or more base stations or sectors of an individual base station transmit in a concurrent manner to the mobile station during the transfer. In the United States patent number ,267,261, entitled "MOBILE STATION ASSISTED SOFT HANDOFF IN TO CDMA CELLULAR COMMUNICATIONS SYSTEM" assigned to the assignee of the present invention, the description of which is incorporated herein by reference, describes an improved soft transfer technique. In the improved technique of the above patent, the mobile station inspects the signal strength of the pilot signals transmitted by the neighboring base stations within the system. When the measured force of the signal exceeds a given threshold, the mobile station sends a signal strength message to a system controller via the base station through which the mobile station is communicating. Command messages from the system controller to a new base station and to the mobile station establish contemporaneous communication through the new base station and the current base station. When the mobile station detects that the signal strength of a pilot corresponding to at least one of the base stations through which the mobile unit is currently communicating has fallen below a predetermined level, the mobile station reports the force measurement of the signal indicative of the base station corresponding to the system controller via the base stations through which it is communicating. Command messages from the system controller to the identified base station and the mobile station terminate communication through the corresponding base station while communications continue through the other base station or other base stations. A typical cellular or personal communication system also contains some base stations within a cell that has multiple sectors.

A multi-sector base station comprises multiple independent transmit and receive antennas or transceivers, each of which covers an area that is smaller than the total coverage area for the base station. However, the coverage areas of the individual sectors within the cell are not mutually exclusive, and typically there are areas within the cell where the sectors overlap. In general, a cell is divided into sectors to reduce the total interference power to the mobile units located within the cell. The use of sectors also increases the number of mobile units that can communicate through the individual base station. The method of soft transfer between neighboring base stations described above can also be applied to a multi-sector base station as described in U.S. Patent No. 5,625,876 entitled "METHOD AND APPARATUS FOR PERFORMING HANDOFF BETWEEN SECTORS OF A COMMON BASE STATION ", assigned to the assignee of the present invention, the description of which is incorporated by reference herein. Each sector of a common base station is treated as a separate and independent base station. Each sector of the base station combines and decodes multipath signals from a common mobile unit. The decoded data is sent directly to the communication system controller, personal or cellular, for each sector of the base station. Alternatively, the data is compared and selected at the base station and the result is sent to the cellular or personal communication system controller. Thus, in a base station having three sectors Sl, S2 and S3, smooth transfer between the sectors can occur as follows: 1. The mobile unit can communicate with the base station through a transceiver of the SI sector; 2. The mobile unit can detect that the intensity of the pilot signal of the transceiver of sector S2 of the base station exceeds a predetermined threshold value; 3. The mobile unit informs the controller of the base station through the transceiver of sector 1 of the base station that the intensity of the pilot signal of the transceiver of sector S2 of the base station exceeds the threshold value; 4. The controller of the base station determines the availability of the resources in the sector S2 of the station and sends order signals to the mobile unit through the transceiver of the sector Sl and the transceiver of the sector S2; 5. The mobile unit then begins simultaneous communications with the base station through the transceivers of sectors Sl and 2 of the base station; 6. The base station combines the signals received from the mobile unit through its transceivers of the sector Sl and S2 until either or both of the pilot signal strengths of the sectors fall below a predetermined threshold value and the communication is terminated. through the transceivers of sector Sl and S2 by the controller of the base station.

U.S. Patent Nos. 5,267,261 and 5,383,219 entitled "FAST FORWARD LING" POWER CONTROL IN A CODE MULTIPLE ACCESS DIVISION SYSTEM "assigned to the assignee of the present invention, the descriptions of which are incorporated by reference herein, describe a process that allows a mobile unit to update on a frame-by-frame basis the base station or stations through which communicates by measuring the speed at which the mobile unit correctly or incorrectly decodes each front frame, however, problems may occur during soft transfer where a mobile unit communicates with more than one receiver of a base station in several sectors In this mode, it is likely that not all transceivers of the base unit in active communication with the mobile unit correctly decode the power control data of the mobile station.When this is presented, the gain settings of each transceiver the base station in active communication by the mobile unit can not be synchronized or can still be divergent. This way, because each transceiver in a multi-sector base station transmits on the same PN channel, when the gain settings of the active communication transceivers diverge, it becomes more difficult for the mobile unit to properly combine the Direct link communication signals it receives from each transceiver of the base station of several sectors. Therefore, some mechanisms are necessary to maintain the front frame gain settings of the base station transceivers of various sectors, synchronized during the transfer between the sectors.

SUMMARY OF THE INVENTION The present invention allows two or more transceivers in a base station of several sectors to update the power level to which each transceiver transmits to a mobile station in a direct communication link, in cases where otherwise the The gain of two or more transceivers would be divergent. In particular, the present invention is directed to a method and apparatus for controlling the transmit power levels of the first and second base station transceivers, wherein the first and second base station transceivers are respectively associated with the first and second sectors of a base station. cell. The intensity of the signal received from a communication signal arriving at the mobile station is determined in an initial manner. A power control value that is based on the intensity of the received signal is then transmitted from the mobile station to the first and second base station transceivers. A first power control value received is then generated when trying to receive the power control value transmitted in the first base station transceiver, and a second power value received is generated when trying to receive the power control value transmitted in the second base station transceiver. A common value of transmission power is calculated in the controller of the base station for the first and second base station transceivers when the received first and second power values are not equal. The communication signal is then transmitted from the first and second base station transceivers according to the common value of transmission power.

By implementing this technique, the levels at which the transceivers in active communication with an individual mobile unit are transmitting can be synchronized, minimizing in this way or eliminating the problems that may arise when a mobile station attempts to combine the communication signals that they arrive from the transceivers with divergent levels of power.

BRIEF DESCRIPTION OF THE FIGURES The features, objects and advantages of the present invention will become clear from the detailed description set forth below in conjunction with the drawings in which the reference characters are identified correspondingly throughout the length and in where: Figure 1 shows the illustration and example of the cell phone system; Figure 2 shows a structure of the coverage area of the example base station; Figure 3 shows the communication links, direct and return (or inverse) between a mobile station and a base station of two sectors, for example; Figure 4 shows an encoder for encoding the information of the direct link traffic channel transmitted by a transceiver of the base station, according to the present invention.

Figure 5 shows a modulator that modulates and adjusts the gains of the coded, direct link traffic information transmitted by a transceiver of the base station, according to the present invention. Figure 6 is a diagram showing the synchronization of a direct link power control sub-channel implemented using the first and second sets, according to the present invention. Figure 7 is a diagram showing the synchronization of a direct link power control sub-channel implemented using the third and fourth speed sets, in accordance with the present invention. Figure 8 is a diagram showing the synchronization of a direct link power control sub-channel implemented using the fifth and sixth speed sets, according to the present invention. Fig. 9 is a diagram showing the synchronization of delays in a closed loop, reverse link power control circuit implemented in accordance with the present invention. Fig. 10 is a block diagram showing the structure of a reverse link power control sub-channel punched in a reverse link pilot channel, according to the present invention. Figure 11 shows an encoder for encoding information of the reverse link traffic channel transmitted by a mobile station according to the present invention. Figures 12 and 13 show two views of a modulator for modulating the control and traffic channels, reverse link pilots, according to the present invention.

DESCRIPTION OF THE PREFERRED MODALITY An example illustration of a cell phone system is provided in Figure 1. The system illustrated in Figure 1 may use various multiple access modulation techniques to facilitate communications between a typically large number of mobile stations or mobile phones, and at base stations, including extended spectrum modulation of CDMA. In the typical CDMA system, each base station transmits a unique pilot signal comprising the transmission of a pilot carrier in a corresponding pilot channel. The pilot signal is an extended-spectrum, unmodulated, direct-sequence signal transmitted at all times by each base station using a common pseudo-random noise (PN) propagation code. The pilot signal allows mobile stations to obtain an initial synchronization of the system. In addition to the synchronization, the pilot signal provides a phase reference for coherent demodulation and a reference for the signal strength measurements used in the determination of the transfer. The pilot signal as transmitted by the different base stations may be the same PN propagation code with different phase shifts of the code phase. Figure 1 shows a system controller and switch 10 also referred to as a mobile switching center (MSC), which typically includes the set of interface and processing circuits to provide control of the system to the base stations. The controller 10 also controls the routing of telephone calls from the public switched telephone network (PSTN) to the appropriate base station for transmission to the appropriate mobile station. The controller 10 also controls the routing of calls from the mobile stations and at least one base station to the PSTN. The controller 10 can be coupled to the base stations by various means such as dedicated telephone lines, fiber optic links or by microwave communication links. In Figure 1, 3 example base stations 12, 14 and 16 are illustrated together with an exemplary mobile station. The mobile station 18, typically a cellular telephone, consists of at least one receiver, a transmitter, and a processor. Base stations 12, 14 and 16 typically include the processing circuitry to control the functions of the base stations (base station controller or BSC), and the interface circuitry to communicate with both the mobile station and the system controller. The arrows 20A-20B define the possible communication links between the base station 12 and the mobile station 18. The arrows 22A-22B define the possible communication links between the base station 14 and the mobile station 18. Similarly the arrows 24A -24B define the possible communication links between the base station 16 and the mobile station 18. The service areas of the base station or cells are designed in geometric shapes such that the base station will normally be closer to a base station. Figure 2 shows the example coverage area of the base station. In the example coverage, hexagonal base station coverage areas adjoin each other in a symmetrically interwoven array. Each mobile station is located within the coverage area of one of the base stations. For example, the mobile station 10 is located within the coverage area of the base station 20. In a cellular communication or personal CDMA telephone system, a common frequency band is used for communication with all base communications in the system , thus allowing simultaneous communication between a mobile station and more than one base station. The mobile station 10 is located very close to the base station 20, and therefore, receives a large signal from the base station and relatively small signals from the surrounding base stations. However, the mobile station 30 is located in the coverage area of the base station 40, but is close to the coverage area of the base stations 100 and 110. The mobile station 30 receives a relatively weak signal from the base station 40 and signals of similar size from the base stations 100 and 110. The mobile station 30 may be in soft transfer with the base stations 40, 100 and 110. The structure of the coverage area of the example base station illustrated in figure 2 is highly idealized In an actual cellular or personal communication environment, the coverage areas of the base station may vary in size and shape. The coverage areas of the base station may tend to overlap with the boundaries of the coverage area that define different coverage area shapes than the ideal, hexagonal shape. Additionally, the base stations can also be divided into sectors such as between sectors, as is well known in the art. The base station 60 is shown as a base station of three sectors, however, base stations with fewer numbers of sectors are contemplated. The base station 60 of FIG. 2 represents an idealized 3-sector base station. The 3 sectors of the base station 60 each cover more than 1202 of the coverage area of the base station. Sector 50, which has a coverage area indicated by broken lines 55, overlaps the coverage area of sector 70 that has a coverage area indicated by thick broken lines 75. Sector 50 also overlaps the coverage area of sector 80, which has a coverage area indicated by fine broken lines 85 For example, location 90 as indicated by X is located both in the coverage area of sector 50 and sector 70. In general, a station The base is divided into sectors in order to reduce the total interference power to the mobile stations located within the coverage area of the base station while increasing the number of mobile stations that can communicate through the base station. For example, sector 80 will not transmit a proposed signal for a mobile unit at location 90. Therefore, a mobile station at location 90 will receive power from only sectors 50 and 70. For a mobile station placed in station 90, the total interference has contributions from sectors 50 and 70 and from base stations 20 and 120. A mobile unit at location 90 may be in soft transfer with base stations 20 and 120. A mobile unit at location 90 may be in soft transfer with sectors 50 and 70 also. Referring now to Figure 3, the direct and inverse communication links between a mobile station and a base station of two example sectors are illustrated. The base station 300 is comprised of a base station controller (BSC) 310, base station transceiver 320 (BTS1), and base station transceiver 330 (BTS2). Each base station transceiver 320, 330 provides service to a sector in the coverage area of the two base stations. The arrows 350a and 360a represent the direct communication links between the base controllers 310 and the base station transceivers 320 and 330. Equally the arrows 350b and 360b represent possible direct communication links between the base station 300 and the mobile station 340. The arrows 370a and 380a represent the possible reverse communication links between the mobile station 340 and the base station 300. The arrows 370b and 380b represent the reverse communication links between the base station transceivers 320 and 330 respectively and the base station controller 310.

If in a base station divided into sectors or not divided into sectors, a set of multipath signals from an individual mobile unit is demodulated and then combined separately before the decoding process. Therefore, the decoded data output of each base station is based on all available routes or advantageous signals of the mobile unit. The decoded data is then sent to the communication system controller, cellular or personal, of each base station in the system. In this way, for each mobile station operating in soft transfer in the system, the cellular or personal communication system controller receives the decoded data from at least two base stations. In accordance with the present invention, CDMA communications can be presented both on the forward and reverse links at various data rates which are grouped into six speed sets based on a number of criteria. The six speed sets are then further divided into three groups: sets 1 and 2 speed, sets 3 and 4 speed, and sets 5 and 6 speed. The blocks of speed sets 3 and 5 contain the same number of information bits as the blocks of speed set 1. The blocks of speed set 4 and 6 contain the same number of information bits as the blocks of speed set 2. Different speed sets can be used on the direct or reverse links, provided that the speed sets come from the same group. The sets 1 and 2 of speed correspond to the sets 1 and 2 of speed described in the Interim TIA / EIA standards entitled "Mobile Station - Base Station Compatibility Standard for Dual-Mode Wideband Spread Spectrum Cellular System", TIA / EIA / IS- 95A and TIA / EIA / IS-95B, (subsequently, IS-95A and IS-95B), the contents of which are incorporated herein by reference. The details of the numerology of the direct link encoder for the set 3, 4, 5 and 6 of speed are shown in Tables 1-4 below: TABLE 1. NUMEROLOGY OF THE DIRECT LINK ENCODER FOR THE TABLE 2. NUMEROLOGY OF THE DIRECT LINK ENCODER FOR THE Referring now to Figure 4, a block diagram of an encoder 400 is shown to encode the information bits of the direct link traffic channel transmitted by the base station transceiver, according to the in ni "fsp? Fe invention The encoder 400 receives as its input blocks the information bits of the traffic channel to be transmitted from a base station transceiver to a mobile station in a direct link In a general view, the encoder 500 append to the cyclic redundancy check (CRC) bits to the information bits, attach the end bits to the block code, encode with a convolutional encoder, repeat to increase the symbol speed to at least the speed to the speed symbol complete, converts with Walsh to make the octagonal velocities, drills to reduce the symbol to a number that can be carried on one or more channels of code di straight, interspersed with a reverse block interleaver, bit inversion, mixes the symbols, and optionally unlocks 50% of the symbols. The CRC block 410 append the CRC bits to the input information blocks as follows. The input blocks of the speed sets 1, 3 and 5 have the CRC of 8 and 12 bits in the blocks of speed 1/2 and speed 1, respectively. The blocks of the sets 2,4 and 6 of speed have the CRC of 6 bits, 8 bits, 10 bits and 12 bits in the blocks of speed 1/8, speed 1/4, speed 1/2 and speed 1, respectively . The polynomials used to generate the CRC bits are shown in Table 5 below. Initially, the used CRC generators are loaded with all 1 TABLE 5. DIRECT LINK CRC GENERATORS After the CRC bits are added to the input information blocks and the end bits are appended by the end bit encoder 420 to the block code, the output of the end bit encoder 420 is alternatively provided. to one of the two convolutional encoders 430 depending on the speed set that is used. The speed coder 1, 2, 5 and 6 is a convolutional speed coder 1/2 of restriction length 9. The convolutional encoder of speed sets 3 and 4 is a 1/4 speed convolutional encoder of restriction length 9. The generator functions for both encoders 430 are shown in table 6 below, and minimum free distances for the encoders are shown in table 7 below.

TABLE 6 GENERATORS OF THE DIRECT LINK CONVOLUTIONAL ENCODER TABLE 7. MINIMUM FREE DISTANCE OF THE DIRECT LINK CONVOLUTIONAL ENCODER Each encoder 430 is locked on a base per block by initializing the state of the encoder with zero and queuing each block with an 8 bit zero encoder end. The output of the encoder 430 is provided to the symbol repetition unit 440, which repeats the symbols 8, 4, 2 and 1 time for the blocks of speed 1/8, speed 1/4, speed 1/2 and speed l, m respectively. After the symbols are repeated, they are provided to the cover unit 450, where the symbols of the speed sets 3, 4, 5 and 6 are covered with a Walsh code dependent on the speed that runs at the symbol speed . The speed-dependent Walsh codes are shown in Table 8 below, where W '' x represents the Walsh code x of a n-ary Walsh code space. The chosen Walsh codes are from an 8-year Walsh code space. The codes are chosen for two reasons. First, allocations are chosen so that speeds less than 1 are mutually orthogonal. There are less orthogonality losses due to the perforation that follows. However, drilling before the repetition of the symbol in order to maintain orthogonality degrades the performance of the convolutional decoder / decoder. Therefore, some orthogonality is sacrificed. Second, the assignments are chosen so that the speed code 1 is mutually orthogonal to all other codes when the speed frame 1 contains a run of 0 or 1. As a result of the Walsh code coverage, the decoding will be less You are likely to make a mistake in a higher speed block that runs from 0 or 1 for a lower speed block that runs from 0 or 1. This may be important during data transmission, since runs of 0 or 1 occur in a disproportionate frequently during the transmission of uncompressed and unencrypted data. In addition, the decoder will be much less likely to decode a block of less than speed 1 as another block of less than speed 1.

TABLE 8. WALSH COVERAGE DEPENDENTS OF THE DIRECT LINK SPEED FOR SET 3, 4, 5 AND 6 OF VELOCITY For speed sets 2, 4 and 6 the block has 50% more symbols than the blocks of speed sets 1, 3 and 5 respectively. In order to reduce the number of symbols so that a speed set block 2, 4, 6 can be transmitted using the same number of direct code channels as a block of speed set 1, 3 or 5, it must be drilled the stream of symbols. In this way, the outlet of the cover unit 450 is provided to the drilling unit 460. The drilling patterns used by drilling unit 460 are shown in table 9, where a 1 means transmitting the symbol and a 0 means drilling zero.

TABLE 9. DIRECT LINK PERFORATION PATTERNS The output of the drilling unit 460 is alternatively provided to one of the two interleavers 470 depending on the speed set that is used. The interleaver of speed sets 1, 2, 5 and 6 is an interleaver of bit inversion blocks with 64 fibers and 64 columns. The interleaver writes the column first using a column counter in order. The interleaver reads the rows first, using a row counter in a reverse order of bits. That is, if the row counter indicates bsbíbsb? Bibo, then the row of Joi > ? J2J3J4Js. The interleaver of speed sets 3 and 4 is an interleaver of bit inversion blocks with 128 rows and 6 columns. These interleavers have two useful properties. First, they create a pseudo-random temporal separation between the adjacent code symbols. This makes them stronger over a variety of channel conditions. Second, for block less than speed 1, the bit inverter interleaver results in uniformly separated copies of the repeated symbols. This is useful during the unlocking of the frame, because it ensures that the unlocking will distribute exactly half of the repeated symbols and will retain the orthogonality properties of the Walsh coverage of symbols. The output of interleaver 470 is provided to a coding unit 480, which encodes the symbol stream in the same manner as cited in IS-95-A, incorporated herein by reference. The output of the coding unit 480 is provided to an unlocking unit 490. In the present invention, the unlocking is supported for the speed sets 3, 4, 5 and 6. When a block is unblocked, it is only transmitted to the symbols within the second half of the block. For sets 3 and 4 of speed, this means that the symbols from 384 to 767 are transmitted. For speed sets 5 and 6, this means that symbols 192 through 383 are transmitted. During unlocking, the maximum frame speed is speed 1/2. Normally, the traffic information boxes are transmitted on the direct link using continuous transmission. However, speed sets 3, 4, 5 and 6 can be sorted in a way where they are only transmitted to the 1/8 speed, 1/4 speed and 1/2 speed frames, they are transmitted using the unlocked transmission. This mode is used to give the mobile station time to retune its receiver and search the systems using other frequencies and / or other technologies (in particular AMPS and GSM). A mobile station ordered in the unlocked search mode will be sorted to unlock N frames of the M frames, starting at system time T. The values of N and M depend on the technology searched and the number of channels searched. Referring now to Figure 5, a modulator 500 is shown to modulate and adjust the gain of the forward link traffic information output by the encoder 400 in accordance with the present invention. The numerology for the modulator 500 is shown in table 10 below. This table shows the number of direct channels (128-year Walsh codes) needed to transmit each speed set.

TABLE 10. NUMEROLOGY OF THE DIRECT LINK MODULATOR For speed sets 3, 4, 5 and 6, the modulator 500 transmits a QPSK waveform, alternating the transmission of the code symbols between the phase and the quadrature phase. This reduces the symbol rate per phase by a factor of two, doubling the number of direct code channels. For speed sets 1, 2, 3 and 4, 128-year-old Walsh codes are used. When a link is assigned to the code channel x (with x between 0 and 63), the Walsh code is used.

W ?. { W ™, W ™} For speed sets 5 and 6, a 128-year-old Walsh code is used. When a link to the code channel x is cited with (x between 0 and 127), the Walsh W ™ code is used. Table 11 shows how to interpret the CODE_CHAN field of IS-95 with the addition of 64 Walsh codes when used in accordance with the present invention. Bit 6 will not be a 1, if set 1 of speed, set 2 of speed, speed set or set 4 of speed is used.

TABLE 11. INTERPRETATION OF CAMPO CODE CHAN Bitio subfield Referring again to Figure 5, when allowed by the control signals 505, the symbol divider (splitter marked 510) in the modulator 500 toggles the input symbols between the upper and lower outputs 520, 522, starting with the first symbol that is sent to the top exit. When disabled, the splitter 510 sends all the input symbols, to the upper output 520 and sends 0 to the lower output 522. When enabled via the signals of the control 506, the symbol repeaters 524, 526 (marked "2x" and "64x") repeat the symbols the number of times indicated by the mark. When disabled, symbol repeaters 524, 526 do not repeat the symbols. The complex multiplier 530, (marked "complex multiplier") computes its output according to equations (1) and (2) below: Salidaí = Pj .. Inputí - P4. Entrance (1) Outputq = Pq. Entry ^ + P. Entrance (2) The Walsh Wj code provided to the mixers 532,534 corresponds to bit 6 of the CODE_CHAN field described above, and the Walsh code WXM provided to mixers 536, 538 corresponds to bits 5 through 0 of the CODE_CHAN field described above. In the present invention, the base stations transmit power control information (i.e., commands to increase power, decrease power, and maintain power, more fully discussed later) to the mobile stations in use and link power control channel direct. The direct link power control sub-channel is drilled in the fundamental block of the direct traffic channel. In a particularly preferred embodiment, every 1.25 milliseconds, one or two PN words is punched (one PN word is 63 PN segments) of the fundamental block. The alignment and duration of the perforation is chosen such that one or more complete modulation symbols are pierced. As explained in more detail below, in order to determine the information to be transmitted in the direct link power control sub-channel, a base station measures the strength of a reverse traffic channel signal received from a mobile station. , and then convert the measurement into a bit of power control. Figure 6 shows the synchronization for the power control sub-channels of speed sets 1 and 2. Each block is divided into 16 power control groups. Each power control group is divided into 24 PN words. The PN words align to the BPSK modulation symbols of the traffic channel. The power control sub-channel of the speed sets 1 and 2 randomizes the start of the power control command on the 16 PN words, starting at word PN 0 of the power control group n + 2. The starting position of the power control command in the fundamental block current is determined by bits 23, 22, 21 and 20 b23, b ?? rb? I, and b? O) of the previous group coding sequence of power control (power control group n + 1). The starting position of the power control group is the word PN ((b? 3, b ??, b? I, b? O) 2 of the power control group n + 2. Once the position is determined At the start of the power control command, a BPSK symbol representing the power control command is inserted in the place of the punched symbols.A '+1' represents an ascending order (that is, an order indicating that the mobile station must increase its transmit power by a predetermined amount.) A '-1' represents a descending order (ie, an order that indicates that the mobile station must decrease its transmit power by a predetermined amount). 1 speed, the BPSK symbol is 2 PN words of duration For the 2 speed set, the BPSK symbol is 1 PN word of duration Figure 7 shows the synchronization for the power control sub-channels of the sets 3 and 4 of speed. The synchronization for the power control sub-channels of sets 3 and Speed 4 is similar to synchronization for the power control sub-channels of speed sets 1 and 2 with the exception that synchronization is advanced by 12 PN words. This is done in order to reduce the delay of the power control circuit. In this way, by ensuring that the intensity of the received signal is measured during the power control group n, the power control command is initiated in the last 1/2 of the power control group n + 1 instead of the first 1/2 of the power control group n + 2. This synchronization reduces the average delay when sending the power control command from 1 1/3 power control groups to 1 5/6 of a power control group. In addition, by reducing the time taken by the mobile station to make the power control setting from 1/2 of a power control group to 1/6 of the power control group, the delay of the power control group is reduced from an average of 1 5/6 power control groups to 1 1/6 power control groups. As shown in Figure 7, each block in the direct traffic channel is divided into 16 power control groups. Each power control group is divided into 24 PN words. Again, the PN words align to the QPSK modulation symbols of the traffic channel. The power control sub-channel of the speed sets 3 and 4 randomizes the start of the power control command on the 16 PN words, starting at the word PN 16 of the power control group n + 1. The starting position of the power control command in the traffic channel stream is determined by bits 23, 22 21 and 20 ((b? 3, b ??, b? I, and b? O) of the sequence coding of the previous power control channel (power control group n) The starting position of the power control command is the PN words (12 + b23, b22 / b2 ?, and b2o) 24 of the group of power control n + l + [< 12 + b23b22b2? b20 &24] / With reference still in Fig. 7, once the starting position of the power control command is determined for sets 3 and 4 of velocity, a QPSK symbol representing the power control order is inserted in place of the punched symbols, A '(+ 1, + 1)' represents an ascending order, and a '(-1, -1)' represents a descending order For sets 3 and 4 of speed, the symbol QPSK is 2 PN words of duration Figure 8 shows the synchronization for the sub-channels of power control of the co njunto 5 and 6 of speed. The timing for the power control sub-channels of the speed sets 5 and 6 is similar to the timing for the power control sub-channels of the speed sets 3 and 4 with the exception that the perforation is aligned in still PN words and is an even number of PN words of duration. This is done because the traffic channel symbols are 2 PN words (128 PN segments) of duration. As shown in Figure 8, each block in the direct traffic channel is divided into 16 power control groups, and each power control group is divided into 24 PN words. The power control sub-channel in the speed sets 5 and 6 randomizes the start of the power control command over the 16 PN words, starting in the word PN 16 of the power control group n + 1. In the starting position of the power control command in the traffic channel stream is determined by bits 23, 22 and 21 b23, b22, and b? I) of the coding sequence of the previous power control group ( power control group n). The starting position of the power control command is the word PN < 12+ (b23, b22 / b2 ?, 0> 24 of the power control group n + l + [< 12+ (b23, b22 / b2? 0> 0> 24. Still referring to figure 8 , once the starting position of the power control command for speed sets 5 and 6 is determined, a QPSK symbol that represents the power control order is inserted instead of the punched symbols. A '(+ 1 / + D1 represents an ascending order.) A' (-1, -1) 'represents a descending order.For sets 5 and 6 of speed, the symbol QPSK is 2 PN words of duration. a diagram illustrating the timing of the delays in the power circuit, closed circuit, reverse link circuit of the present invention is shown in Figure 9. The power control circuit, closed link, reverse link uses the direct link power control sub-channels (described above in conjunction with Figures 6-8) to control the transmission power of the mobile stations on the reverse link Figure 9 summarizes the accumulation of power control delays reverse link closed circuit Assuming a round trip delay of the worst case of 512 PN segments, it is safe to assume that the worst way over air delay is less than 256 PN segments, since the longitude power control bit maximum is 2 PN words (128 PN segments) of duration, the worst case mobile station receiving time is 128 PN segments. About 256 additional PN segments (approximately 200 microseconds) are allocated for the mobile station to decode and act on the power control command. Since the base station measures the power in a complete power control group, the receive time of the base station is 1536 PN segments. About 256 additional PN segments (approximately 200 microseconds) are assigned to the base station to measure the received signal strength and rotate the power control command. Therefore, in the worst case, the power control command associated with the power control group n can be sent 768 PN segments before the start of the power control group n + 2 or 768 PN segments after the start of the power control group. power control group n + 1. In order to allow the same amount of randomization use for speed set 1 and 2, the power control commands of speed sets 3, 4, 5 and 6 are randomized over the last 12 PN words of the control group of power n + 1 and the first 4 PN words of the power control group n + 2. This results in an average delay of the power control command of 1 5/6 power control groups, including the measurement range. In addition, it results in an average delay of the power control circuit of 2 1/6 power control groups, including the measurement range. The pilot channel used in the forward link in the present invention is the same as the pilot channel set forth in IS-95-B, incorporated herein by reference. In this way, the pilot channel uses the Walsh code W¿ * =. { W ™, W ™} . Although the pilot channel does not provide data and therefore is effectively the Walsh W ™ code, not using the code Walsh W0M =. { W0128, W3428} for less than 128 segments. Therefore the Walsh code W064 = is used. { W ™, W ™} . The synchronization channel used in the forward link in the present invention is the same as the synchronization channel set forth in IS-95-B, incorporated herein by reference. In this way, the synchronization channel uses the Walsh code In a CDMA system operating in accordance with the present invention, direct link power control (power level control of the traffic signal sent from the transceiver of the base station to a mobile station in direct link) is triggered General by the frame erasure information sent from the mobile station to the transceiver of the base station when the reverse link is operating in the speed set 1. When the reverse link is the speed set 2, the direct link power control is also driven by the erasure information of the frame sent from the mobile station to the transceiver of the base station. When the reverse link speed set is 3, 4, 5 or 6, however, the direct link power control is driven by the data representing the noise signaling relationship of the direct traffic frames. When the reverse link speed set is 3, 4, 5 or 6, the direct link power control information is sent from the mobile station to the base station in a reverse link power control sub-channel. As fully explained below, the reverse link power control sub-channel is created by drilling the power control information in the selected power control groups of the reverse pilot channel. As mentioned above, the direct link power control when the reverse link is the speed set 3, 4, 5 or 6, is a power control based on the frame-to-noise ratio. As a general view, this direct link power control system operates as follows. Each frame of the mobile station measures the signal-to-noise ratio (Es / Nt) and subtracts from this the expected Es / Nt. The mobile station reports this delta of the noise signaling relationship (FWD_SNR_DEL A) to the base station in the power control inverse sub-channel. The base station then uses this delta of the signaling noise ratio to adjust the transmission gain for the next frame, usually changing the transmission gain by a factor inversely proportional to the delta. During the smooth transfer, because the transmission gains of the base station may become out of synchronization, the base station controller resynchronizes the base station's transmission gains once per frame. The mobile station preferentially chooses the expected symbol-to-noise signal ratio (Is / Nt) such that a target frame erase speed (FWD_FER) is achieved while minimizing the required signal to symbol to noise ratio. In one embodiment, the mobile station generates the expected signal-to-noise ratio Is / Nt) as follows. The mobile station adjusts the expected, initial Es / Nt to the Es / Nt of the first frame that is successfully decoded. After this, the base station does the following for each frame. If the fundamental block is deleted, then the mobile station increases the expected Es / Nt. Otherwise, the mobile station decreases the expected Es / Nt. As discussed in equations (3) and (4) below, the size of the increment step (Pincrement) and the size of the decrease (P decrease) are governed by the speed of erasure of the desired, direct link fundamental block ( FWD_FER) and the desired Es / Nt velocity, maximum increment (increment, max) • FWD _ FER dis min tion V JTVtfT? TGT7O _ 1 '"cremento.tmx *' i o P = () P (4) incremnto V ETI / r) 17? 7? i ^ 's mln ucion where P increase, max- 0. 5 . It will also be understood that other methods can be used to calculate a representative signal of the intensity of the signal received with the invention. For example, the mobile station can perform the combination of the maximum ratios of the reception routes using the received pilot signal and the received traffic signal. The mobile station can also calculate the FWD_SNR_DELTA using the expected and received signal-to-noise ratios, normalized by frame. As mentioned above, for direct link power control, the station The mobile signal sends the resulting difference between the measured and expected values of the signal-to-noise ratio in decibels (FWD_SNR_DELTA) to the transceiver of the base station in the reverse link power control sub-channel. Specifically, the FWD_SNR_DELTA for the direct frame n-1 is sent by the mobile station to the base station in the power control sub-channel of the reverse frame n. According to one embodiment, table 12 shows the relationship between the FWD_SNR_DELTA values transmitted by the mobile station, the signal-to-noise ratio, per symbol (Es / Nt) measured by the mobile station for one frame, and the expected ratio of signal to noise (Is / Nt) calculated by the mobile station.

TABLE 12. TRANSMISSION CORRELATION OF FWD SNR DELTA In the preferred embodiment, the transceiver of the base station initially uses the value of FWD_SNR_DELTA sent to it by the mobile station in the appropriate sub-channel of power control n to adjust the direct gain (FWD_GAIN), applies it to the direct box n + 1. If the power control sub-channel FWD_SNR_DELTA is not cleared by the base station, the "delta marking of the signal-to-noise ratio, direct by symbols" (FWD_SNR_VALID) on the transceiver of the base station is set to 1. In another mode, the transceiver of the base station will adjust the values of FWD_SNR_DELTA_ and FWD_SNR_VALID to 0. On reception on the base transceiver, the FWD_SNR_DELTA is converted to a decibel value according to table 13 below: TABLE 13. CORRELATION OF RECEIPT OF FWD SNR DELTA The direct gain initially applied by the transmitter of the transceiver from the base station to the direct transmission frame n + 1 is then calculated according to equation (5) below: FWD_GAIN [N + l] = FWDJ3AIN_MIN. where FWD GAINADJ < FTOjGAIN_MIN. FWDJ3M3 I? X. where FWDJSAINHXG < FWDj3AIN_MAX F Dj AINj LTJ fAnj otherwise (5) where FWDJSATJSIMXG =. FWD GAIN [N] * 10 ( { ^ 2- ^ -U1 ^? +? 2. (iroj ^ vft iD < n)] = damping factor that can be nominally equal to 1/6, and FWD_SNR_DELTA is assumed to be a 2-bit complement number 2. It will be understood that other methods are contemplated to calculate the FWD_GAIN. However, in cases such as a smooth transfer where a mobile station is communicating with more than one of the transceivers in a multi-sector base station, all transceivers of the base station in active communication with the mobile station can not correctly decode the information contained in the reverse link power control sub-channel transmitted by the mobile station. When this occurs, the FWD_GAIN applied by each of the transceivers in active communication with the mobile station can not be synchronized and may still be divergent. In this way, a means is needed to restore the FWD_GAIN values to a synchronized state to prevent the mobile station in soft transfer from experiencing undue difficulty in combining the CDMA signals with divergent gains that have been transmitted with the same code. propagation of PN for each of the transmitters of the base station divided into sectors. According to the invention, this asynchronization problem is solved as follows. First, as explained above, each transceiver of the base station divided into sectors uses any value of FWD_SNR_DELTA not erased that was sent to it by the mobile station in the sub-channel of power control of frame n to adjust the direct gain (FWD_GAINrea? ) and applies to the direct table of n + 1 according to equation (5) above. In addition, each transceiver of the base station divided into sectors sends the values of FWD_SNR_DELTA and FWD_SNR_VALID which it receives in conjunction with the reverse frame n to the controller of the base station with the decoded traffic information. The controller of the base station then selects an individual value of FWD_SNR_DELTA of all the values it receives from the reverse frame n of each transceiver divided into sectors as follows:1. For all cases where the value FWD_SNR_VALID received from the sector is 0, the corresponding FWD SNR DELTA value is discarded; 2. If any value of FWD_SNR_DELTA remains, the base station controller selects the maximum FWD_SNR_DELTA; 3. If no FWD_SNR_DELTA value remains, the base station controller adjusts the values of FWD_SNR_DELTA and FWD_SNR_VALID to 0. The controller of the base station then sends the individual FWD_SNR_DELTA value calculated in accordance with steps 1-3 above back to each transceiver of the base station divided into sectors, and each transceiver of the station calculates the value of FWD_GAIN that must be applied to the direct square n + 1 for each of the transceivers of the base station divided into sectors (it is say FWD_GAIN0bj? tivo) by applying the individual FWD_SNR_DELTA value calculated in accordance with steps 1-3 above to equation (5) above. Each transceiver of the base station divided into sectors then compares the FWD_GAinrea? That was previously applied to the direct square n + 1 to the value of FWD_GAIN0object that must have been applied to the direct square n + 1 (as determined in accordance with steps 1-3 above). The difference (FWD_GAIN < aif) between the values of FWD_GAINreai and FWD_GAIN0objective are applied to adjust up and down the gain applied to the next direct frame sent by each transceiver of the base station divided into sectors (this next frame denotes frame n + 2 + Tbac haul, where Tbackhaul represents the processing delay in the frames for the base station controller to calculate FWD_GAIN0object and send it back to the transceivers of the base station divided into sectors). In this way, the direct gain applied by each transceiver of the base station divided into sectors during the direct frame n + 2 + Tbackhaul will represent the sum of the value FWD_GAIN if (which was calculated as described above by calculating the values of FWD_SNR_DELTA sent by the mobile station during reverse frame n) and a value of FWD_GAinrea? additional that is calculated by the transceiver of the base station divided into sectors using the FWD_SNR_DELTA value sent by the mobile station during the reverse frame n + 1 + Tbackhaul. In one embodiment, each transceiver of the base station sends the values of FWD_SNR_DELTA and FWD_SNR_VALID for each frame to the controller of the base station in a reverse traffic packet having the format shown in Table 14 below, and the controller of the base station sends the values of FWD_AGAIN0object discussed above for each frame to the transceivers of the base station in a packet of direct traffic having format shown in the following table 15.

TABLE 14 FORMAT OF THE INVERSE TRAFFIC PACKAGE OF THE BASE STATION TABLE 15 FORMAT OF THE DIRECT TRAFFIC PACKAGE OF THE BASE STATION Referring now to Figure 10, a block diagram of the power control inverse sub-channel that is drilled in the selected power control groups in the reverse link pilot channel is shown. As mentioned above, in the speed sets 3, 4, 5 and 6, the difference between the signal to noise ratio, per symbol, measured direct (FWD_SNR_DELTA) is sent from the mobile station once per frame in the subchannel of reverse link power control. It is a reverse link power channel that is triggered by drilling the 3-bit values of FWD_SNR_DELTA into a fundamental block of the reverse pilot channel. More particularly, the numbering of the power control groups in the reverse pilot channel from 0, the power sub-channel is drilled in the pilot channel during power channel groups 9, 10, 11, 12, 13 and 14. Each power control group is divided into 24 PN words. Numerating the PN words in a power control group from 0, the power control sub-channel is punched in the PN words 10, 11, 12 and 13 of the power control groups 9, 10, 11, 12, 13 and 14. An example power control group with the perforated power control inverse sub-channel is shown in Figure 10. The reverse power sub-channel is drilled in the power control groups 9, 10, 11, 12, 13 Y 14 for the following reasons. First, the power control sub-channel must be drilled in the power control groups that are transmitted during unlocking. If the power control sub-channel is not going to be placed like this, then it will not be sent during unlocking. Therefore, only the power control groups 8, 9, 10, 11, 12, 13, 14 and 15 can be used. Second, the power sub-channel can not be transmitted during the last power control group. If the power control sub-channel was transmitting during the last control group, then the base station will not be able to adjust the transmission level before the next frame starts. Therefore, only control groups 8, 9, 10, 11, 12, 13, and 14 can be used. However, if 7 power control groups are used, numerology will not work well (shown in table 14). later). Therefore, 6 power control groups are used. The power control group 8 is not used in order to give the mobile station more time to determine the FWD_SNR_DELTA. Finally, the power control sub-channel is drilled in the center of the power control group in order to minimize polarization in the time and frequency tracking circuits that are driven by the estimators derived from the pilot block filters about a power control group. In a preferred embodiment, the values of FWD_SNR_DELTA are transmitted on the transmitted sub-channel of interference sent using bi-orthogonal modulation. The FWD_SNR_DELTA message is encoded in a bi-orthogonal symbol. The 3-bit value t = t2t? To, correlates in the code job (-l) < W4zn0 The code word is repeated 96 times. The code word in place of the modulation symbols is repeated in order to provide time diversity for the code symbols. Numerology plays the inverted power subchannel shown in Table 16 below: Referring now to Figure 11, it is shown in the block diagram of an encoder 1100 for encoding the information of the reverse link traffic channel transmitted by a mobile station, according to the present invention. The sets 3, 4,5 and 6 of speed support the transmission of channel speeds 1/8, 1/4, 1/2, 1, 2, 4 and 8. reverse link. Speeds above speed 1 are created by packing multiple speed blocks in an individual frame. The coding and interleaving are done on this packed box. As a general view, the encoder 1100 takes the reverse traffic information bits as its input, appends a CRC, appends the end bits to the block frame, encodes with a convolutional encoder, repeats to increase the symbol rate at least 6144 symbols, converts with Walsh, to make orthogonal speeds, drills to reduce the number of symbols to 6144, intersperses with a bit inverter block interleaver, and optionally unlocks 50% of the symbols. The numerology details of the reverse link encoder for sets 3, 4, 5 and 6 of speed are given in Tables 17-20 below: TABLE 17. NUMEROLOQY OF THE INVERSE LINK ENCODER FOR THE 3, 5 SPEED SETS TABLE 18. NUMEROLOQY OF INVERSE LINK ENCODER FOR TABLE 19. NUMEROLOGY OF INVERSE LINK ENCODER FOR TABLE 20. NUMEROLOQY OF INVERSE LINK ENCODER FOR SETS 4 AND 6 OF SPEED, SPEED AVERAGE DATA In a preferred embodiment, the blocks of speed sets 3 and 5 contain the same number of information bits as the blocks of speed set 1, and the blocks of speed set 4 and 6 contain the same number of information bits as the blocks of set 2 of speed. Still referring to Figure 11, the CRC blocks 1110 append the CRC bits to the input information blocks as follows. The blocks of sets 1, 3 and 5 of speed have CRC of 8 and 12 bits in the blocks of speed 1/2 and speed 1, respectively. The blocks of the speed sets 2, 4 and 6 have CRC of 6, 8, 10 and 12 bits in the blocks of speed 1/8, speed 1/4, speed 1/2 and speed 1, respectively. The polynomials used to generate the CRC bits are shown in Table 1 below. Initially, the used CRC generators are loaded with all 1.

TABLE 21. INVERSE LINK CRC GENERATORS After the CRC bits are added to the input information blocks the end bits are appended to the block code, the output of the multiplexer 1120 is alternatively provided to one of the three convolutional encoders 1130 depending on the speed set that is used. The convolutional encoder of speed set 1 is a convolutional speed coder 1/3 of restriction length 9. The convolutional encoder of speed set 2 is a convolutional speed encoder 1/2 of restriction length 9. The convolutional encoder of speed sets 3, 4, 5 and 6 is a convolutional speed coder 1/4 of constraint length 9. The functions of the generators for the encoders 1130 are shown in table 2 below, and the minimum free distances for the encoders are shown in table 23 below TABLE 22 GENERATORS OF THE INVERSE LINK CONVOLUTIONAL ENCODER TABLE 23 MINIMUM FREE DISTANCE OF THE INVERSE LINK CONVOLUTIONAL ENCODER Joint 1 of joint 2 of joint 3, 4, 5 and speed speed 6 of speed 18 12 24 The encoder 1130 is locked on a base per block by initiating the state of the encoder with zero and terminating each block with a zero encoder end of 8 bits. The output of the encoder 1130 is provided to the symbol repetition unit 1140, which repeats the symbols 64, 32, 16, 8, 4, 2 and 1 times for the blocks of speed 1/8, speed 1/4, speed 1 / 2, speed 1, speed 4, and speed 8, respectively. After the symbols are repeated, they are provided to the cover unit 1150, where the symbols of the speed sets 3, 4, 5 and 6 are covered with a Walsh code dependent on the speed that runs at the symbol speed . The speed-dependent Walsh code is Wrrl2, where W "represents the Walsh code x of a n-ary Walsh code space and R represents the state of symbol repetition.The Walsh codes chosen are from a space of Walsh. 64-year-old Walsh code For speed sets 2, 4 and 6, the block has 50 percent more symbols than the blocks of speed sets 1, 3 and 5, respectively, in order to reduce the number of symbols so that a block of speed set 2, 4 or 6 can be transmitted using the same number of symbols as a block of speed set 1, 3 or 5, the symbol stream must be drilled. the cover unit 1150 is provided to the punch unit 1160. The punching patterns used by the punch unit 1160 are shown in the inlet 24, where 1 means symbol transmission and a 0 means punching the symbol.

TABLE 24. PERFORATION PATTERNS OF THE LINK ENCODER The output of the drilling unit 1160 is alternatively provided to one of the two interleavers 1170 depending on the speed set that is used. The interleaver of set 1 and 2 of speed is the same as the interleaver for set 1 and 2 of speed described in the standard IS-95B, incorporated herein by reference. The interleaver of the sets 3, 4, 5 and 6 of speed is an intercalator of blocks of emission of bits with 128 rows and 48 columns. The interleaver writes the column first, using a column counter in order. The interleaver reads the row first, using a row counter in the reverse order of bits. That is, if the row counter indicates bbsbsb bsb? Bibo, then it is read from row bobi b? Bsb bsb? • The output of interleaver 1170 is provided to an unlocking unit 1180. In the present invention, deblocking is supported by sets 3, 4, 5 and 6 of speed. When a frame is unlocked, only the symbols within the second half of the frame are transmitted. During unlocking, the maximum frame speed is 1/2 speed. Normally, traffic information frames are transmitted on the reverse link using continuous transmission, with the exception of the 1/8 frame that is blocked. However, speed sets 3, 4, 5 and 6 can be ordered in a mode where only the 1/8 speed frames, 1/74 speed, 1/2 speed are transmitted and transmitted using the unlocked transmission. This mode is used to give the mobile station time to retune its receiver and search the systems using other frequencies and / or other technologies (in particular AMPS and GSM). A mobile station ordered in the unlocked search mode will be sorted to unlock N frames of the M frames, starting at the time of the T system. The values of N and M depend on the technology searched and the number of channels searched . This unlocking is synchronous with the direct link unlocking. Figures 12 and 13 show two views of a modulator for modulating the pilot, control and traffic channels, reverse link, according to the present invention. The reverse traffic channel information provided to the modulators in Figures 12 and 13 corresponds to the output of the encoder 1100. In the present invention, the power control in the reverse link (i.e. control of the power of the transmissions from the mobile station to a base station), is analyzed as follows. The base station measures the pilot to interference signal ratio (Ep / Io) of the inverse pilot over a power control group. This value is compared to a threshold. If the value of Ep / Io is more than 0.5 decibels below the threshold, then the base station sends a symbol representing an order to decrease power to the mobile station (ie, an order indicating to the mobile station that it must increase your transmission power by a predetermined amount). If the value of Ep / Io is within 0.5 decibels of the threshold, then the base station sends a symbol representing an order to maintain power to the mobile station (i.e., an order indicating that the mobile station must maintain constant its potency of transmission) . If the value of Ep / Io is more than 0.5 decibels above the threshold, then the base station sends a symbol representing a decrease order to the mobile station (i.e., an order indicating that the mobile station must decrease its power of transmission by pn anan? H to H nroH or i- fi vm i na Ha T a ca? HQ? ac l _a ai -? m __ »tt - ^ t of power, power reduction and power maintenance are sent by the base station in the direct link power control sub-channel discussed above.The base station determines what action to take when choosing the received power control command that will result in the lowest transmit power.Thus, without any base station sends a decrease order to the mobile station, then the mobile station will adjust its transmission power downwards, if any base station sends a maintenance order and no base station sends one or decrease rate, then the mobile station will not change its transmit power. If all base stations send increase orders, then the base station will adjust its transmitter upward. The description of the preferred embodiments of this invention is provided to enable a person skilled in the art to make or use the claimed invention herein. The various modifications to these modalities will be readily apparent to those skilled in the art, and the principles described may be applied to other modalities without the use of any inventive faculty. Therefore, the present invention is not to be limited to the specific embodiments described, but rather will be in accordance with the broader scope consistent with the principles and new features described herein.

Claims (10)

1. NOVELTY OF THE INVENTION Having described the present invention, it is considered as a novelty and, therefore, property is claimed as contained in the following CLAIMS I 1. In a telephone system having a base station controller associated with a divided cell in sectors, a first transceiver of the base station associated with a first sector of the cell and a second transceiver of the base station associated with a second sector of the cell and a mobile station, a method for controlling the transmission power level of the first and second transceivers of the base station, comprising the steps of: (a) determining the intensity of the signal received from a communication signal arriving at the mobile station; (b) transmitting a power control value based on the intensity of the received signal, to the first transceiver of the base station and to the second transceiver of the base station. (c) generating a first power control value received when attempting to receive the power control value transmitted in the first transceiver of the base station; (e) generating a second power control value received when attempting to receive the power control value transmitted from the mobile station in the second transceiver of the base station; (e) calculating, in the controller of the base station, a common transmit power value for the transceivers, if the first and second power control values received are not equal; and (f) transmitting the communication signal from the first and second transceivers of the base station according to the common value of transmission power. The method according to claim 1, wherein the intensity of the received signal is determined by measuring the difference between an expected signal-to-noise ratio and a real signal-to-noise ratio. The method according to claim 1, wherein the base station also communicates to the controller if the received signal strength is valid. 4. The method according to claim 3, wherein the common transmission power value is not changed if the received signal strength is not valid. The method according to claim 1, wherein the received signal strength communicated to the controller with a reverse frame n is used by the controller to generate the common value of transmit power communicated to the first and second transceivers of the base station for a direct box n + 2 + Tbackhaul, where Tbackhaul represents a processing delay in the frames, caused by the base controller. The method according to claim 1, wherein the common value of transmission power corresponds to a gain applied to the communication signal sent from the first and second transceivers of the base station. The method according to claim 1, wherein step (c) further comprises adjusting, during a first frame, a gain of the communication signal transmitted from the first transceiver of the base station according to the first power control value received, and step (f) further comprises adjusting, during a second frame subsequent to the first frame, the gain of the communication signal transmitted from the first transceiver of the base station according to a difference between the common value of transmission power and the first control power value received. The method according to claim 7, wherein step (c) further comprises adjusting, during the first frame, a gain of the communication signal transmitted from the second transceiver of the base station according to the second control value of received power, and step (f) further comprises adjusting, during the second frame subsequent to the first frame, the gain of the communication signal transmitted from the second receiver of the base station according to a difference between the common value of the power of transmission and the second power control value received. 9. In a system in a cellular communication system that has a controller of a base station associated with a cell divided into sectors, a first transceiver of the base station associated with a first sector of the cell and a second transceiver of the base station associated with a second sector of the cell, a mobile station, an apparatus for controlling the transmission power level of the first and second transceivers of the base station, comprising: (a) means for determining the intensity of the received signal of a communication signal arriving at the mobile station; (b) a means for transmitting a power control value based on the intensity of the received signal, to the first transceiver of the base station and to the second transceiver of the base station; (c) a means for generating a first power control value received when attempting to receive the power value transmitted from the mobile station in the first transceiver of the base station; (d) a means for generating a second power control value received when attempting to receive the power control value transmitted from the mobile station in the second transceiver of the base station; (e) a means for calculating in the controller of the base station, a common value of transmission power for the first and second transceivers of the base station if the first and the second power control values received are not equal; and (f) a means for transmitting the communication signal from the first and second transceivers of the base station according to the common value of transmission power. 10. In a cellular or personal communication system having a base station controller associated with a cell divided into sectors, a first transceiver of the base station associated with a first sector of the cell and a second transceiver of the base station associated with a second sector of the cell transceiver, and a mobile station, an apparatus for controlling the transmission power level of the first and second transceivers of the base station, comprising: (a) a processor in the mobile station that determines the intensity of the received signal and a communication signal arriving at the mobile station; (b) a transmitter that transmits a power control value based on the intensity of the received signal, to the first transceiver of the base station and to the second transceiver of the base station; (c) a processor in the first receiver that generates a first power control value received in response to the power control value transmitted from the mobile station; (d) a processor in the second receiver that generates a second power control value received in response to the power control value transmitted from the mobile station; (e) a set of processing circuits in the controller of the base station that generates a common value of transmission power for the first and second transceivers of the base station if the first and second received power control values are not equal; and (f) a transmitter in the first transceiver of the base station and a transmitter in the second transmitter of the base station that transmits the communication signal according to the common value of transmission power.