MXPA97009707A - Open roll antenna - Google Patents

Abstract

The present invention relates to an electromagnetic antenna for use with an antenna signal, the electromagnetic antenna comprises: a multiplely connected surface, the first insulated conductor means extending in a first conductive path generally helical, around and at least partially on the surface multiplely connected with at least one first direction of helical pitch or inclination, the second insulated conductor means extending in a second conductive path generally helical, around and at least partially on the surface multiplely connected, with at least one second helical pitch direction, which is opposite to the first helical pitch direction, so that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the multiple connected surface; and second signal terminals respectively connected the ctricamente the first and second conductive means isolated, and reflector means for directing the antenna signal with respect to the multiply connected surface for reception or transmission of the signal to

Description

OPPOSITE ROLLING ANTENNA TECHNICAL FIELD This invention relates to transmit and receive antennas, and in particular, helically wound antennas.

BACKGROUND OF THE INVENTION The efficiency of the antenna at an excitation frequency is directly related to the effective electrical length, which is related to the speed of propagation of signals by the well-known equation that uses the speed of light C in free space, the length wave?, and the frequency f: ? = C / f As is known, the electrical length of the antenna must be a wavelength, half a wavelength (a dipole) or a quarter of a wavelength with a ground plane to minimize all but the actual impedance of the antenna. When these characteristics are not met, the impedance of the antenna changes creating standing waves on the antenna and feeding the antenna (transmission line), increasing the proportion of standing waves producing all energy loss and lower radiated energy. A typical vertical telescopic antenna (a monopole) has a vertically polarized, omnidirectional pattern, and such an antenna can be comparatively small at high frequencies, such as UHF. However, at lower frequencies the size becomes problematic, leading to very long lines and to the towers used in the LF and MF bands. The large-range transmission qualities in the lower frequency bands are advantageous but the antenna, especially a directional array may be too large to have a compact portable transmitter. Even at high frequencies, it may be advantageous to have a physically smaller antenna with the same efficiency and performance as a conventional monopole or dipole antenna. Over the years different techniques have been treated to create compact antennas with directional characteristics, especially vertical polarization, which has been found to be more efficient (large range) than horizontal polarization, being the reason that horizontally polarized antennas support more losses of terrestrial wave. In terms of the directional characteristics, it is recognized that with certain antenna configurations it is possible to negate the magnetic field produced in the antenna in a particular polarization, and at the same time increase the electric field, which is normal for the magnetic field. Similarly, it is possible to negate the electric field and at the same time increase the magnetic field. The principle of equivalence is a well-known concept in the field of electromagnetic techniques, stating that two sources that produce the same field within a given region are said to be equivalent, and that equivalence can be shown between sources of electric current and the corresponding magnetic current sources. This is explained in section 3-5 of the 1961 reference Time Harmoni or The ectromagne ti c Fi the ds by R.F. Harrington. In the case of a linear bipolo antenna element which has linear electric currents, the equivalent magnetic source is given by a circular azimuth ring of magnetic current. An electric current solenoid is an obvious way to create a linear magnetic current. An electric current solenoid placed on a toroidal surface is a way to create the necessary circular azimuthal ring of the magnetic current. The helical, toroidal antenna, consists of a helical conductor wound in a toroidal shape and offers the characteristics of radiating electromagnetic energy in a pattern that is similar to the pattern of an electric dipole antenna with an axis that is normal to the plane of and concentric with the center of the colloidal form. The effective impedance of the transmission line of the helical conductor delays, in relation to the speed of propagation in the free space, the propagation of the waves coming from the conductor feeding point around the helical structure. The reduced circular velocity and current in the structure makes it possible to construct a toroidal antenna as much as an order of magnitude or smaller than the size of a corresponding resonant dipole (linear antenna). The toroidal design has a low dimensional proportion, since the toroidal helix design is physically smaller than the simple resonant dipole structure, but with similar electrical radiation properties. A simple, single-phase power configuration will give a radiation pattern comparable to a half-wavelength dipole, but in a much smaller package. In this context, US Patents Nos. 4,622,558 and 4,751,515 and European Patent Application No. EP-A-0, 043, 591, discuss certain aspects of toroidal antennas as a technique for creating a compact antenna, by relocating the conventional linear antenna with a self-resonating structure that produces vertically polarized radiation that will propagate with minor losses when it propagates over the earth. For low frequencies, vertical self-resonating linear antennas are not practical, as noted previously, and the self-resonating structure explained in these references will somewhat diminish the problem of physically unmanageable and electrically inefficient vertical elements at low frequencies. The aforementioned references initially discuss a monofilament toroidal helix as a building block for more complex directional antennas. These antennas may include multiple conduction paths fed with signals whose relative phase is controlled either with external passive circuits or due to specific self-resonating characteristics. In a general sense, the references discuss the use of so-called toroidal windings of the lamellar winding at opposite ends, to provide vertical polarization. The toroidal windings of the opposite pole discussed in these references are of an unusual design, having only two terminals, as described in the reference Birdsall, CK, and Everhart, TE, "Modified Contra-Wound Helix Circuits for High- Po eR Traveling Wave Tubes ", IRÉ Transactí ons on The Ec tron Devi ces, October 1956, p. 190. References point out that the distinctions between magnetic and electric / current fields and extrapolations that physically superimpose two monofilament circuits that are wound opposite each other on a toroid, can be created a vertically polarized antenna using a signal input of two doors. The basis for the design is the ineal helix, the design equations for which they were originally developed by Kandoian &; Sichak in 1953 (mentioned in the North American Patent No. 4, 622,558). The prior art, such as the aforementioned references, speaks in terms of elementary toroidal modalities as elementary building blocks for more complex structures, such as two toroidal structures oriented to simulate opposite winding structures. For example, the aforementioned patent discusses a bull (complex or simple) that is designed to have an integral number of wavelengths guided around the circumference of the circle defined by the minor axis of the bull. European Application EP-A-0, 043, 591 illustrates toroids in which the greater radius a is clearly greater than zero and the minor radius b is clearly not greater than the greater radius a. However, in that application, the equations defined "1" and "N" on page 12, line 14, could both be zero or approximately zero for the undescribed case of a spherical or generally spherical surface in which the The main radius or greater a is zero or approximately zero. In this way N, the "number of turns", is zero or approximately zero, and, from here, the antenna may not work. It is proposed that such a request is far from teaching such surfaces. Also, it is proposed that such a request does not teach or suggest a multiplely connected surface structure having at least one generally flat surface which is generally perpendicular to its major or major axis, and the partially helical conducting paths which are generally perpendicular and radial with respect to the major axis, in order to improve the radiation or reception of energy, radially. A simple toroidal antenna, one with a monofilament design, responds to the electrical and magnetic field components of the signals that enter (received) or from which they exit (transmitted). On the other hand, the multiple filament (ultirrollamiento) can have the same sense of step or inclination or in different sense of step or inclination in separate windings in separate toroids, allowing the provision of directionality to the antenna and control of the polarization. A propeller shape is in the form of a ring and flange design, which shows some but not all of the qualities of a basic, opposite winding winding configuration. As is known, a linear solenoid coil creates a linear magnetic field along its central axis. The direction of the magnetic field is in accordance with the "right-hand rule", whereby if the fingers of a right hand are curved inward toward the palm and pointed in the direction of the circular current flow in the solenoid, then the The direction of the magnetic field is the same as that of the thumb when it is extended parallel to the axis around which the fingers bend. (See for example Figure 47, below). When this rule is applied to the solenoid coils wound in a right-hand direction, as in the thread of a screw to the right, the electric current and the resulting magnetic field point in the same direction, but a coil in one direction by hand Left, it has the electric current and the resulting magnetic field pointing in opposite directions. The magnetic field created by the solenoid coil is sometimes called a magnetic current. By combining a coil on the right and left hand side of the same axis, to create an opposite winding coil and feeding the individual coil elements with oppositely directed currents, the net electric current is effectively reduced to zero, while the net magnetic field is duplicated from that of single coil alone. As is also known, a balanced electric transmission line fed by a sinusoidal alternating current source, and terminated with a load impedance, propagates the current probes from the source to the load. The probes are reflected in the charge and propagate back to the source, and the net current distribution over the transmission line is found from the sum of the incident and reflected wave components, and can be characterized as standing waves on the transmission line. (See for example Figure 13, below). With a balanced transmission line, the current components in each conductor at any given point along the line are equal in magnitude but opposite in polarity, which is equivalent to the simultaneous propagation of the opposite polarized probes by equal magnitude , along separate conductors. Along a given conductor, the propagation of a positive current in one direction is equivalent to the propagation of a negative current in the opposite direction. The relative phase of the reflected incident waves depends on the impedance of the load element, ZL. For I0 = incident current signal e d = reflected current signal, with reference to Figure 13, below, then the reflection coefficient pi is defined as: "L - 1 II - 1 'Z or Pr lod ZL + 1 z 0 Since the incident and reflected currents travel in opposite directions, the equivalent reflected current, Ii' = -I? Gives the magnitude of the reflected current with respect to the direction of the incident current L0.

DESCRIPTION OF THE INVENTION An object of the present invention is to provide a vertically polarized compact antenna, especially suitable for long-range, low-frequency wave applications, but useful at any frequency where a physically low profile or non-visible antenna package is desirable. A further object of the present invention is to provide a directional antenna suitable for use in a motor vehicle or boat. Still another objective of the present invention is to provide an antenna which is approximately or nidirectional in all directions. A further objective of the present invention is to provide an antenna having a maximum radiation gain in normal directions to the direction of polarization and a minimum radiation gain in the direction of polarization.

Yet another aspect of the present invention is to provide an antenna having a simplified power configuration, which is easily coupled to a radio frequency (RF) energy source. Still another objective of the present invention is to provide an antenna that improves the radiation of radial energy. Still another objective of the present invention is to provide an antenna that improves the vertical energy radiation. According to the present invention, a toroidal antenna has a toroidal surface and first and second windings or windings comprising insulated conductors, each extending as a simple closed circuit around the surface in a segmented helical pattern. The toroid has an equal number of segments, for example, four segments, but in general greater than or equal to two segments. Each part of one of the continuous conductors within a given segment is wound opposite with respect to that part of the same conductor as in the adjacent segments. The adjacent segments of the same conductor are in nodes or junctions (reverse winding points). Each of the two continuous conductors is wound opposite each other, within each segment of the toroid. A pair of nodes (or gate) is located at the boundary between each of the adjacent pairs of segments. From segment to segment, the polarity of the current flow from a unipolar signal source is inverted through the connections in the door or access with respect to the conductors to which the nodes of the door are connected. According to the invention, the conductors in the junctions located in each other door are divided and the split ends are terminated with purely reactive, coupled impedances, which provides a 90 degree phase shift of the reflected current signals, respectively. . This provides the simultaneous cancellation of the net electric currents and the production of an almost uniform azimuthal magnetic current within the structure, creating vertically polarized electromagnetic radiation. According to the invention, a series of turns or conductive curls are "poloidally" placed on, and equally spaced around a surface of revolution, such that the major axis of each turn forms a tangent to the minor axis of the surface of revolution. In relation to the major axis of the revolution surface, the ends that are most central to all the turns are connected together in a terminal, and the remaining ends of all the turns are connected together in a second terminal. A unipolar signal source is applied through two terminals, and since the turns are electrically connected in parallel, the magnetic fields produced by all the loops or turns are in phase, thus producing an almost uniform azimuthal magnetic field, causing vertically polarized omnidirectional radiation. According to the invention, the number of loops or turns is increased, the conducting elements becoming a surface of conducting revolution, which could be either radially or continuously slotted. The frequency of operation is reduced by introducing series inductance or parallel capacitance in relation to the terminals of the composite antenna. According to the invention, the capacitance can be added with the addition of a pair of parallel conductive plates which act as a cube to a conductive surface of revolution. The surface of revolution is grooved at the junction with the plates, with a plate that is electrically connected to one side of the slot or slot, and a second plate that is connected to the other side of the slot or groove. The revolution conducting surface may also be radially slotted to emulate a series of elementary loop antennas. The bandwidth of the structure can be increased if the radius and shape of the surface of revolution are varied with the corresponding angle of revolution. According to the invention, an electromagnetic antenna includes a multiple connected surface; a first insulated conductor means extending in a first conductive path generally helical, around and at least partially on the multiplely connected surface, with at least a first direction of helical pitch or inclination; a second insulated conductor means, extending in a second helical path generally helical, around and at least partially on the surface multiplely connected, with at least a second direction of helical pitch, which is opposite the first direction of helical pitch, in order that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the multiple connected surface; the first and second signal terminals are respectively electrically connected to the first and second insulated conductor means; and the reflector means for directing the antenna signal with respect to the multiplely connected surface for receiving or transmitting the antenna signal. According to the invention, an electromagnetic antenna includes a multi-connected surface, having a major axis; a first insulated conductor means extending in a first partially helical conductive path, around and at least partially on the multiplely connected surface, with at least one first helical pitch direction; a second insulated conductive medium extending in a second partially helical conductive path, around and at least partially on the multiplely connected surface, with at least a second helical pitch direction, which is opposite to the first helical pitch direction, with the so that the first and second insulated conductor means are wound opposite each other, around and at least partially on the multiplely connected surface, with the first and second conductive paths partially helical, when they are generally perpendicular to the major axis of the surface multiplely connected, being generally radial with respect to the major axis of the multiplely connected surface, and otherwise being generally helically oriented; and first and second signal terminals respectively connected electrically to the first and second insulated conductor means. According to the invention, an electromagnetic antenna includes a generally spherical surface having a conduit along a major axis thereof; a first insulated conductor means extending in a first partially helical conductive path, around and at least partially on the generally spherical surface, with at least one first helical pitch direction; a second insulated conductive medium extending in a second partially helical conductive path, around and at least partially on the generally spherical surface, with at least a second helical pitch, which is opposite to the first helical pitch direction, with so that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the generally spherical surface, with the first and second partially helical conductive paths passing through the surface circuit generally spherical, and which are generally parallel to the major axis thereof, within the circuit, and otherwise are generally helically oriented; and first and second signal terminals respectively respectively electrically connected to the first and second insulated conductor means. According to the invention, an electromagnetic antenna includes a multiple connected surface, having a greater radius that is greater than zero, and a smaller radius that is greater than the greater radius; a first insulated conductor means extending in a first conductive path, generally helical, around and at least partially on the multiplely connected surface, with at least a first helical pitch direction; a second insulated conductor means extending in a second helical path generally helical, around and at least partially on the surface multiplely connected, with at least a second direction of helical pitch, which is opposite of the first helical passage, for the purpose that the first and second insulated conductor means be wound opposite one another relative to the other around and at least partially on the multi-connected surface; and first and second signal terminals respectively connected electrically to the first and second insulated conductor means.

According to the invention, an electromagnetic antenna includes a spherical surface; a first insulated conductor means extending in a first conducting path around and at least partially on the spherical surface, with at least a first direction of winding or winding; a second insulated conductor means extending in a second conductor path, around and at least partially on the spherical surface, with at least a second winding direction, which is opposite to the first winding direction, in order that the first winding direction and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the spherical surface; and first and second signal terminals respectively respectively electrically connected to the first and second insulated conductor means. According to the invention, an electromagnetic antenna includes a hemispherical surface; a first insulated conductor means extending in a first conducting path around and at least partially on the hemispherical surface, with at least a first winding direction; a second insulated conductor means extending in a second conducting path around and at least partially on the hemispherical surface, with at least a second winding direction, which is opposite to the first winding direction, in order that the first and second insulated conductor means are wound in opposite manner relative to one another, around and at least partially on the hemispherical surface, and first and second signal terminals respectively respectively electrically connected to the first and second insulated conductor means. The invention provides a vertically polarized, compact antenna with higher gain for a wider frequency spectrum compared to a bridge and ring configuration. Other objects, benefits and characteristics of the invention will be apparent to one of skill in the art.

BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 is a schematic view of a four-segment helical antenna, according to the invention.

Figure 2 is an enlarged view of the windings in Figure 1.

Figure 3 is an enlarged view of the windings in an alternative embodiment of the invention.

Figure 4 is a schematic view of a two-segment helical antenna (two parts) exemplifying the invention.

Figure 5 is a two-door helical antenna, with variable impedances at reverse winding points in an alternative mode, and for antenna tuning according to the invention.

Figure 6 is a field graph showing the field pattern for the antenna shown in Figure 1.

Figures 7, 8 and 9 are graphs of magnetic field current relative to the toroidal node positions for the antenna shown in Figure 1.

Figures 10, 11 and 12 are current and magnetic field plots in relation to the toroidal positions between the nodes for the antenna shown in Figure 4.

Figure 13 is an equivalent circuit for a completed transmission line.

Figure 14 is an enlarged view of poloidal windings on a toroid, according to the present invention for tuning capability, improved electric field cancellation and simplified construction.

Figure 15 is a simplified block diagram of a four quadrant version of an antenna embodying the present invention, with impedance and phase coupling elements.

Figure 16 is an enlargement of the windings of an antenna exemplifying the invention, with the primary and secondary impedance coupling coils that connect the windings.

Figure 17 is an equivalent circuit for an antenna exemplifying the invention, illustrating a tuning means.

Figures 18 and 19 are schematic diagrams of a portion of a toroidal antenna that uses the closed metal foil tuning elements around the toroid for tuning purposes as in Figure 17.

Figure 20 is a schematic view showing an antenna exemplifying the present invention, using a tuning capacitor between the opposing nodes.

Figure 21 is an equivalent circuit of an alternative tuning method of a quadrant antenna that exemplifies the present invention.

Figure 22 shows an antenna according to the present invention, with a conductive foil envelope on the toroid, for tuning purposes as in Figure 21.

Figure 23 is a section along line 23-23 in Figure 24.

Figure 24 is a perspective view of an antenna covered with a sheet according to the present invention.

Figure 25 shows an alternative embodiment of an antenna with "rotational symmetry" exemplifying the present invention.

Figure 26 is a functional block diagram of an FM transmitter using a parametric tuning device controlled by modulator, on an antenna.

Figure 27 shows a spin antenna or omnidirectional poloidal loop.

Figure 28 is a side view of a loop in the antenna shown in Figure 27.

Figure 29 is an equivalent circuit for the loop or loop antenna.

Figure 30 is a side view of a square loop antenna.

Figure 31 is a partial sectional view of the cylindrical loop antenna according to the invention.

Figure 32 is a sectional view along line 32-32 in Figure 31, and includes a diagram of the current in the windings.

Figure 33 is a partial view of a toroid with toroidal grooves for tuning and for emulation of a poloidal loop configuration according to the present invention.

Figure 34 shows a toroidal antenna with a toroidal core tuning circuit.

Figure 35 is an equivalent circuit for the antenna shown in Figure 34.

Figure 36 is a sectional view of a toroidal antenna with a central capacitance tuning arrangement, according to the present invention.

Figure 37 is a sectional view of an alternative embodiment of the antenna shown in Figure 36, with poloidal windings.

Figure 38 is an alternative modality with variable capacitance tuning.

Figure 39 is a plan view of a square toroidal antenna according to the present invention, to increase the bandwidth of the antenna and with slots for tuning or for emulation of a poloidal loop configuration.

Figure 40 is a sectional view along line 40-40 in Figure 39.

Figure 41 is a plan view of an alternative embodiment of the antenna shown in Figure 39, which has six sides with six slots for tuning or for emulation of a poloidal configuration.

Figure 42 is a sectional view along the line 42-42 in Figure 41.

Figure 43 is a conventional linear helix.

Figure 44 is an approximate linear helix.

Figure 45 is a composite equivalent of the configuration shown in Figure 45, assuming that the magnetic field is uniform or nearly uniform over the length of the helix.

Figure 46 shows a helical, toroidal antenna, wound in opposite fashion, with an external loop and a phase shift and proportional control.

Figure 47 shows the equivalent circuits in the direction to the right and in the direction to the left and the associated electric and magnetic fields.

Figure 48 is a schematic view of a series feed antenna.

Figure 49 is a schematic view of another serial feed antenna.

Figure 50 is a schematic view of another antenna having one or two power doors.

Figure 51 is a representative elevation radiation pattern for toroidal modalities of the antennas of Figures 48-51.

Figure 52 is a perspective view of a toroidal antenna with a parabolic reflector.

Figure 53 is a vertical sectional view of the toroidal antenna of Figure 52.

Figure 54 is a perspective view of a toroidal antenna with an alternative parabolic reflector.

Figure 55 is a vertical sectional view of the toroidal antenna of Figure 54.

Figure 56 is an isometric view of a cylindrical antenna having oppositely wound conductors, with partly helical and partly radial conductive paths.

Figure 57 is a radiation pattern, in elevation, representative for a toroidal antenna having helical conductive pathways.

Figure 58 is a radiation pattern, in elevation, representative for the antenna of Figure 56.

Figure 59 is a perspective view of a generally spherical toroid shape having a generally circular cross section, and a central duct.

Figure 60 is a elevation radiation pattern, representative for a toroidal antenna having helical conductive pathways.

Figure 61 is a elevation radiation pattern, representative for the antenna of Figure 59.

Figure 62 is a perspective, sectional, vertical view of a toroidal shape having a radius less than greater than a greater radius.

Figure 63 is a plan view of a conductor with a helical conductive path for the toroid shape of Figure 62.

Figure 64 is a perspective view of the conductor of Figure 63.

Fig. 65 is a perspective view of the oppositely wound conductors, with helical conductive paths for the toroid shape of Fig. 62.

Figure 66 is a perspective view of a simple spherical conductor for a spherical antenna.

Figure 67 is a perspective view of the spherical conductors wound in an opposite manner, for an antenna in spherical shape.

Figure 68 is a perspective view of oppositely wound hemispherical conductors for a spherical antenna.

Figure 69 is a perspective view of a simple, alternative, spherical conductor for a spherical antenna.

Figure 70 is a perspective view of alternate, reciprocally wound spherical conductors for a spherical antenna.

Figure 71 is a perspective view of the spherical conductors wound in opposite manner, for a spherical antenna with a series of parallel feed points.

Figure 72 is a schematic view of a four segment helical antenna for use with the toroidal shape of Figure 62.

BEST MODALITY FOR CARRYING OUT THE INVENTION With reference to Figure 1, an antenna 10 comprises two electrically isolated closed circuit conductors (windings or windings) Wl and W2 that extend around a TF of toroid shape through four equiangular segments 12 (n = 4). The windings are supplied with an electrical RF signal from two pins SI and S2. Within each segment, the "wound-up" winding, which is the source for the Wl winding can be on the right (RH), as shown by the dark solid lines, and the same for winding W2 which can be by hand left (LH) as shown by dashed lines. It is assumed that each conductor has the same number of helical turns around the shape, as determined from the equations described below. In the joint or node 14 each winding inverts the direction (as shown in the cut of each of them). The signal terminals SI and S2 are connected to the two nodes, and each of said nodes is terminated by a "gate or access". In this discussion, each pair of nodes in each of the four gates is designated a and a2, bl and b2, cl and c2, and di and d2. In Figure 1, for example, there are four doors, a, b, c and d. In relation to the minor axis of TF, in a given gate the nodes can be in any angular relation to each other and in relation to the bull, but all the doors on the structures will carry this same angular relationship if the number of turns in each segment is a whole number. For example, Figure 2 shows the diametrically opposed nodes, while Figure 3 shows the nodes that overlap. The nodes lie one above the other, but from door to door the connections of the corresponding nodes with the terminals or pins SI and S2, are inverted, as shown, producing a configuration in which the diametrically opposed segments have the same connections in parallel, with each winding that has the same sense. The result is that in each segment the currents in the windings are opposite, but the direction is inverted along with the direction of the winding, from segment to segment. It is possible to increase or decrease the segments, as long as there is an equal number of segments, but it must be understood that the nodes have a relation for the effective transmission line length for the toroid (taking into account the change in the speed of propagation due to helical winding and operating frequency). By altering the placement of the nodes, the polarization and directionality of the antenna can be controlled, especially with an external impedance 16, as shown in Figure 5. The four-segment configuration shown here has been found to produce an omnidirectional, vertically polarized field pattern that has an elevation angle? from the axis of the antenna and a plurality of electromagnetic waves El, E2 which emanate from the antenna as illustrated in Figure 6. While Figure 1 illustrates a modality with four segments and Figure 4 two segments, it should be to recognize that the invention can be carried out with any number of segments, for example, six segments. An advantage of increasing the number of segments will be to increase the radiated power and to reduce the composite impedance of the antenna feed ports, and thereby simplify the task of coupling the impedance at the signal terminal to the composite impedance of the Signal doors on the antenna. The advantage of reducing the number of segments is in the reduction of the complete size of the antenna. While the primary design goal is to produce a vertically polarized omnidirectional radiation pattern, as illustrated in Figure 6, it has therefore been recognized through the principle of equivalence of electromagnetic systems and the understanding of the electric dipole antenna elementary, that this can be achieved through the creation of a circular azimuthal ring of magnetic current or flow. Therefore, the antenna will be discussed with respect to its ability to produce such a magnetic current distribution. With reference to Figure 1, a balanced signal is applied to the signal terminals SI and S2. This signal is then communicated to the helical, toroidal feed gates, a to d via the balanced transmission lines. As is known from the theory of balanced transmission lines, at any given point along the transmission line, the currents in the two condus are 180 degrees out of phase. When reaching the nodes to which the transmission line is connected, the DC signal propagates as a traveling wave in both directions away from each node. These current distributions together with their address are shown in Figures 7 through 9, for a four-segment antenna, and Figures 10-12 for that of two segments, respectively, and are referred to in these graphs at the doors or nodes, where J refers to the electric current and M refers to the magnetic current. This analysis assumes that the signal frequency is tuned to the structure of the antenna, such that the electrical circumference of the structure is a wavelength in length, and the distribution of current on the structure is sinusoidal in magnitude, which is an approximation. The toroidal spiral turns or windings, oppositely wound of the structure of the antenna, are treated as a transmission line, however these form a transmission line with shunt, due to the radiation of the energy. The graphs of Figures 7 and 10 show the distribution of electric current with the polarity referred to the propagation direction away from the nodes from which the signals emanate. The graphs of Figures 8 and 11 show the same current distribution, when referred to a common direction counterclockwise, recognizing that the polarity of the current changes with respect to the direction to which it is referred. Figures 9 and 12 then illustrate the corresponding distribution of magnetic current using the principles illustrated in Figure 1. Figures 8 and 11 show that the distribution of net electric current on the toroidal helical structure is canceled. But as shown in Figures 9 and 12, the net magnetic current distribution is improved. In this way, those quadrature signals vanish to form an almost uniform azimuthal current distribution. The following five key elements must be satisfied to carry out the invention: 1) the antenna must be tuned to the signal frequency, for example at the signal frequency, the electrical circumferential length of each segment of the toroidal helical structure it must be of a quarter of length, 2) the signals in each node must be of uniform amplitude, e) the signals in each door must be of equal phase, 4) the signal applied to terminals SI and S2 must be be balanced and 5) the impedance of the segments of the transmission line that connect the signal terminals SI and S2 to the signal gates on the toroidal helical structure, must be coupled to the respective loads at each end of the segment of the transmission line, in order to eliminate the reflections of the signals. When the signals for the antenna are calculated, the following parameters are used in the equations that are used later. a = the main axis of a bull; b = the minor axis of the bull; D = 2 x b = smaller diameter of the bull; N = the number of turns of the helical conductor wound around the bull; n = number of turns per unit length Vg = antenna speed factor; a (normalized) = a /? = a b (normalized) = b /? = b Lw = normalized length of the conductor? g = the wavelength based on the velocity factor y? for free space m = number of antenna segments The toroidal helical antenna is at a "resonant" frequency as determined by the following three physical variables: a = major radius of the bull b = minor radius of the torus N = number of turns of the helical conductor wrapped around the torus V = wave velocity guided It has been found that the number of independent variables can be further reduced to two, Vg and N, by normalizing the variables with respect to the wavelength? of free space, and rearranging to form the functions a (Vg) and b (Vg, N). That is, this physical structure will have a corresponding resonant frequency with a wavelength of free space of?. For a four-segment antenna, resonance is defined as that frequency where the circumference of the major axis of the torus is a long wavelength. In general, the frequency of resonant operation is that frequency at which the standing wave is created on the antenna structure for which each segment of the antenna is a long-wavelength-^ (for example each node 12 in the Figure 1 is a ^ wavelength guided). In this analysis, it is assumed that the structure has a circumference greater than one wavelength, and that the feeds and windings are correspondingly configured.

The antenna speed factor is given by: V? . Y . 2pa ± L 'c X m X X (1 The physical dimensions of the bull can be normalized with respect to the free space wavelengths as follows: X X 2) The reference "Wide-Frequency-Range Tuned Helical Antennas and Circuits" by A.G. Kandoian and W. Sichak in Convention Record of the I.R.E., 1953 National Convention, Part 2 - Antennas and Communications, pp. 42-47 presents a formula that predicts the speed factor for a coaxial line with an internal, helical, linear monofilament conductor. Through the substitution of the geometric variables, this formula was transformed into a toroidal helical geometry, in US Patents Nos. 4,622.55í and 4,751,515 to give: (3) While this formula is based on a different physical embodiment of the invention described herein, it is useful with less empirical modification as an approximate description of the present invention, for design purposes, to achieve a given resonant frequency. The substitution of (1) and (2) in equation (3) and simplifying gives: 4 ) From equations (1) and (2), the velocity factor and the normalized major radius are directly proportional to each other: Va = 2p (5) In this way, equations (4) and (5) can be rearranged to solve the higher or lower torus radii normalized in terms of Vg and N: mVg 8p 6) X) subject to the fundamental property of a bull that - b ß- b = .l? to (8) Equations (2), (6), (7), (8) provide the design relationships independent of frequency, fundamental. These can be used either to find the physical size of the antenna, for a given operating frequency, for the speed factor and the number of turns, or to solve the inverse problem of determining the operating frequency given to an antenna. a specific dimension, which has a given number of helical turns. An additional constraint based on the work referred to by Kandoian and Sichak, can be expressed in terms of the normalized variables as follows: (9) Rearranging this to solve b, and substituting equation (7) we get: (10) Rearranging equation (10) to separate the variables we obtain: gave) The resulting quadratic equation can be solved to give: (12) Also, from (6) and ( 8p * 1 m 13) The restriction (13), which is derived from the restriction (8), seems to be more strict than the restriction (12).

The normalized length of the helical conductor is then given by: L = 2nj. { N 8) 2 + a2 = 2? Tß N + & V b (14) The length of the wire will be minimized when a = b and for the minimum number of turns, N. When a = b, then from (6) "8p 15) And so (16) For a four-segment antenna, m = 4 and (17) Substituting equation (15) in equation (10) we obtain 18) For a minimum length of wire, N = minimum so that for a four-segment antenna, 19) In general, the length of the wire will be the smallest for the lower speed factors, so that equation (18) can be approximated as (20) which when substituted in equation (16) gives : 2 i) Thus, for all except the two-segment antennas, the Kandoian and Sichak equations predict that the wire length per conductor will be greater than the free space wavelength. From these equations, a toroid can be constructed that effectively has the transmission characteristics of a linear half-wave antenna antenna. The experience with a number of toroidal helical antennas of opposite winding, constructed according to this invention, has shown that the resonant frequency of a given structure differs from that predicted by equations (2), (6) and (7) and in In particular, the effective frequency seems to correspond to that predicted by equations (2), (6) and (7), when the number of turns N used in the calculations is greater by a factor of two to three than the effective number of turns. for one of the two drivers. In some cases, the frequency of effective operation seems to be better correlated with the length of the wire. For a given toroidal helical conductor length Lw (a, b, N), this length will be equal to the free space length of an electromagnetic wave whose frequency is given by: fJLa.bM > Lw (atbJN) (22) In some cases, the measured resonant frequency was better predicted either by 0.75 * fw (a, b, N) or f "(a, b, 2N). For example, at a frequency of 106 Megahertz (MHz) a linear half-wave antenna could be 1,415 meters (55.7 inches) in length, assuming a speed factor of 1.0, while a toroid design encompassed by the invention could have following dimensions. a = 6.955 cm (2.738 inch) b = 1.430 cm (0.563 inch) N = 16 turns wire # 16 m = 4 segments For this modality of the toroidal design, equations (2), (6) and (7) predict a frequency resonant of 311.5 Megahertz and Vg = 0.454 for N = 16 and 166.7 Megahertz for N = 32. At the measured operating frequency, Vg = 0.154 and for equation (4) for support, the effective value of N must be 51 turns, which is a factor of 3.2 times greater than the effective value for each driver. In this case, fw (a, b, 2N) = 103.2 MHz. In a variation of the invention shown in Figure 5, the connections on the two doors to the input signal are broken, as are the conductors at the nodes corresponding. The four remaining open doors all, -al2, al2-a22, cll-c21 and c21-c22 are then terminated with a reactance Z whose impedance is adapted to the intrinsic impedance of the transmission line segments formed by the pairs of helical conductors , toroidal, oppositely wound. The signal reflections from these terminal reactances act (see Figure 13) to reflect a signal which is in quadrature phase for the incident signals, such that the current distributions on the toroidal helical conductor are similar to those of the mode of Figure 1, thus providing the same radiation pattern, but with lower power connections between the signal terminals and the signal gates, which simplifies the tuning and tuning of the antenna structure. The conductors oppositely wound, toroidal, can be accommodated in a different way to the helical, and still satisfy the spirit of this invention. Figure 14 shows an alternative arrangement of this type (a "polyloidal-peripheral winding pattern"), whereby the helix formed by each of the two insulated conductors Wl, W2, is decomposed into a series of curls or poloidal turns 14.1, interconnected. The interconnections form circular arcs in relation to the major axis. The two separate conductors are parallel anywhere, making it possible for this arrangement to provide a more accurate cancellation of the components of the colloidal electric current, and more precisely to direct the magnetic current components created by the poloidal curls. This invention is characterized by a higher interconductor capacitance, which acts to lower the resonant frequency of the structure as experimentally verified. The resonant frequency of these modes can be adjusted by adjusting the spacing between the parallel conductors W1 and W2, by adjusting the relative angle of the conductors wound in opposite directions, one with respect to the other, and with respect to the major or minor axis of the torus. . The signals in each of the signal gates SI, S2 must be balanced with respect to each other (for example, equal magnitude with uniform phase difference of 180 °) magnitude and phase in order to carry out the invention in the best way. The line segments for signal power transmission must be coupled at both ends, for example at the common terminal signal junction, and at each of the individual signal gates on the toroidal helical structure, oppositely wound. The imperfections in the coils winding oppositely, in the form on which they are wound, or in other factors, can cause variations in the impedance in the signal gates. Such variations may require compensation such as the form illustrated in Figure 15, so that the currents entering the antenna structure are of balanced magnitude and phase to enable the more complete cancellation of the toroidal electric current components as described later. In the simplest form, if the impedance at the signal terminals is Z0, typically 50 Ohms, and the signal impedance at the signal gates had a value of Z? -m * Z0, then the invention could be carried out with m power lines, each of equal length and impedance Zi, such that the parallel combination of these impedances at the signal terminal had a value of Z0. If the impedance at the signal terminals had a resistive value Zi different from the previous one, the invention could be carried out with quarter-wave transformer power lines, each one of a quarter wavelength, and having an impedance. intrinsic of Zf = Z0 Z1. In general, any impedances could be adapted with double adapter branches constructed from the elements of the transmission line. The power lines coming from the signal terminal could be inductively coupled the signal gates as shown in Figure 16. In addition to making possible the impedance of the signal gates to be coupled to the power line, this technique also acts as a symmetric-asymmetric or balun transformer, to convert an asymmetric signal in the feed terminal to a symmetrical signal in the signal gates on the oppositely wound toroidal helical structure. With this inductive coupling method, the coupling coefficient between the signal supply and the antenna structure can be adjusted to make it possible for the antenna structure to resonate freely. Other means of phase impedance and amplitude and compensation adaptation, familiar to those with experience in the art, are also possible without departing from the spirit of the present invention. The antenna structure can be tuned in a variety of ways. In the best mode, the means for tuning must be uniformly distributed around the structure, to maintain a uniform, azimuthal magnetic ring current. Figure 17 illustrates the use of the poloidal sheet structures 18.1, 19.1 (see Figures 18 and 19) that surround the two insulating conductors, which act to modify the capacitance coupling between the two helical conductors. The poloidal tuning elements may be turns or loops whether open or closed, the latter providing an additional component of inductive coupling. Figure 20 illustrates a means of balancing or compensating the signals on the antenna structure, by capacitively coupling the different nodes, and in particular diametrically opposed nodes on the same conductor. The capacitive coupling, which uses a variable capacitor Cl, can be azimuthally continuous through the use of a circular conductive sheet or mesh, either continuous or segmented, which is parallel to the surface of the toroidal shape and the toroidal extension. The embodiments in Figures 23 and 25 result from the extension of the embodiments of any of Figures 17-21, wherein the complete helical structure HS is surrounded by a shield 22.1, which is concentric anywhere. Ideally, the toroidal helical structure HS produces strictly toroidal magnetic fields, which are parallel to such a shield, so that for a sufficiently thin sheet for a given conductivity and operating frequency, the electromagnetic limit conditions are satisfied by making possible the propagation of the electromagnetic field outside the structure. A slot (poloidal) 25.1 can be added for tuning as explained herein. The oppositely wound toroidal helical antenna structure is a relatively high Q-resonator, which can serve as a combined tuning element and the radiator for an FM transmitter as shown in Figure 26, which has an oscillator amplifier 26.2 for receive a voltage from the antenna 10. Through a parametric tuning element 26.3, controlled by a modulator 26.4, modulation can be achieved. The transmission frequency Fl is controlled by the electronic adjustment of a capacitive or inductive tuning element, coupled to the antenna structure either by direct modification of the reactance or by switching a series of fixed reactive elements (discussed previously) to control the reactance, which is coupled to the structure, and thereby adjust the natural frequency of the toroidal helical structure wound in opposite manner. In still another variation of the invention, shown in Figure 27, the toroidal helical conductors of the previous embodiments are replaced by a series of N polyoidal ringlets 27.1, evenly spaced azimuthally around a toroidal shape. The portions more to the center of each turn or curl relative to the greater radius of the bull are connected together in the signal terminal SI, while the remaining outer portions of each turn or curl are connected together in the signal terminal S2 . The individual turns, while identical to one another, can be arbitrarily shaped, Figure 28, which illustrates a circular shape, and Figure 30 illustrating a rectangular shape. The electrical equivalent circuit for this configuration is shown in Figure 29. The individual loop or turn segments each act as a conventional loop or turn antenna. In the composite structure, the individual loops or turns are fed in parallel, so that the resulting components of the magnetic field, created with this in each loop or loop, are in phase and azimutially directed relative to the toroidal s, resulting in an azimuthally uniform ring of magnetic current. By comparison, in the toroidal helical antenna, the fields coming from the toroidal components of the helical conductors either counter-rolled or counter-wound, are canceled as if these components did not exist, leaving only the contributions coming from the poloidal components of the conductors . The modality of Figure 27 thus eliminates the toroidal components coming from the physical structure instead of relying on the cancellation of the correspondingly generated electromagnetic fields. By increasing the number of poloidal turns in the mode of Figure 27, the modalities of Figures 31 and 33 are given for the turns of rectangular and circular profile, respectively. The individual turns become continuous conductive surfaces, which may or may not have grooves in the radial plane, to emulate a multiple turn mode. These structures create the azimuth magnetic ring currents, which are parallel anywhere to the conductive toroidal surface, and whose corresponding electric fields are perpendicular anywhere to the conductive toroidal surface. In this way, the electromagnetic waves created by this structure can propagate through the conductive surface, since the surface is sufficiently thin for the case of a continuous conductor. This device will have the effect of a ring of electric dipoles in the moving load, between the upper or lower sides of the structure, for example, parallel to the direction of the major axis of the toroidal s. The embodiments of Figures 27 and 31 share the disadvantage of relatively large size, due to the need for the circumference of the turn to be of the order of half a wavelength for the resonant operation. However, the size of the loop or turn can be reduced by the addition of any inductance in series or reactance in parallel to the structures of Figures 27 and 31. Figure 34 illustrates the addition of the series inductance by the formation of the conductor central of the embodiment of Figure 31, in a solenoid inductor 35.1. Figure 36 illustrates the addition of parallel capacitance 36.1 to the embodiment of Figure 31. The parallel capacitor is in the form of a cube 36.2 for the toroidal structure TS, which also serves to provide mechanical support for the toroidal s and for the central electrical connector 36.3, by means of which the signal at terminals SI and S2 is fed to the antenna structure. The parallel capacitor and the structural cube are formed from two conductive plates Pl and P2, made of copper, aluminum and some other non-ferrous conductor, and separated by a medium such as air, Teflon, polyethylene or other low dielectric material. loss 36.4. The connector 36.3 with terminals SI and S2 is conductively coupled in the center of the parallel plates Pl and P2, respectively, which are in turn conductively coupled to the respective sides of a toroidal groove on the inside of the conductive toroidal surface TS. The signal current flows radially outward from the connector 36.3 through the plates Pl and P2, and around the conducting toroidal surface TS. The addition of the capacitance provided by the conductive plates Pl and P2 makes it possible for the polyloidal circumference of the toroidal surface TS to be significantly smaller than what might otherwise be required for a similar state of resonance by a loop or loop antenna. that operates at the same frequency. The capacitive tuning element of Figure 36 can be combined with the inductive turns of Figure 27 to form the modality of Figure 37, the design of which can be illustrated by assuming for the equivalent circuit of Figure 38, that all capacitance is provided by the parallel plate capacitor, and all inductance is provided by the wire turns. The formulas for the capacitance of a parallel plate capacitor and for a wire or cable inductor are given in Reference Reference Da ta for Radi or Engineers 7a ed., E.C. Jordan ed., 1986, Howard W. Sams, p. 6-13 as: ;2. 3) : 24 where C = capacitance pfd LW? re = inductance μH A = plate area cm2 (square inch) t = plate spacing cm (inch) N = number of plates a = average radius of the wire turn cm (inch) d = wire diameter cm (inch) Gr = relative dielectric constant The resonant frequency of the equivalent parallel circuit, assuming a total of N wires, is then given by: ! 25) 2p: 2 6) For a toroidal shape with a smaller diameter = 7.00 cm (2.755 inches) and a larger internal diameter (diameter of the capacitor plates) of 10.28 cm (4.046 inches) for N = 24 turns of 16 gauge wire (d = 0.16 cm (0.063) inches)) with a separation of t = 0.358 cm (0.141 inch) gives a calculated resonant frequency of 156.5 MHz. For the modality of Figure 38, the inductance of a single turn in the toroidal ripples is approximated by: 27 where μ0 is the permeability of the free space = 400p nH / m, and a and b are the major and minor radius of the toroidal shape, respectively. The capacitance of the parallel plate capacitor formed as the bull's cube is given by: (28 here e0 is the permittivity or specific inductivity of the free space = 8.854 pfd./m. Substituting equations (27) and (28) in given equations (25) and (26): (2 9; Equation (29) predicts that the toroidal configuration illustrated above, except for a continuous conductive surface, will have the same resonant frequency of 156.5 MHz if the separation of plates is increased to 1.01 cm (0.397 inch). The modalities of Figures 36, 37 and 38 can be tuned by adjusting either the full plate separations, or the separation of a relatively narrow annular groove, from the plate as shown in Figure 38, where this Fine tuning means is azimuthally symmetric to preserve the symmetry in the signals, which propagate radially outwards from the center of the structure. Figures 39 and 41 illustrate the means for increasing the bandwidth of this antenna structure. Since signals propagate outward in a radial direction, the bandwidth is increased by providing different differential resonant circuits in different radial directions. The variation in geometry is made azimuthally symmetric to minimize the geometric perturbation to the azimuthal magnetic field. Figures 39 and 41 illustrate geometries that are easily formed from commercially available pipe fittings, while Figure 25 (or Figure 24) illustrates a geometry with a sinusoidal variant radius which could reduce geometric perturbations to the magnetic field . The prior art of helical antennas shows their application in the remote detection of geotechnical characteristics and for navigation from them. For this application, relatively low frequencies are used, requiring large structures for proper operation. The linear helical antenna is illustrated in Figure 43. This can be approximated by Figure 44, where the true helix is decomposed into a series of simple turns or curls separated by linear interconnections. If the magnetic field were uniform or almost uniform over the length of this structure, then the spinning elements could be separated from the linear composite element, to form the structure of Figure 45. This structure can also be compressed in size by replacing then by the linear element, either of the toroidal helical or toroidal poloidal antenna structures described herein, as illustrated in Figure 46. The primary advantage of this configuration is that the entire structure is more compact than the corresponding linear helix, which is advantageous for portable applications such as air, land or marine vehicles, or for non-visible applications. A second advantage of this configuration, and that of Figure 45, is that the signal components of the magnetic field of the electric field are decomposed, making it possible that these are subsequently processed and recombined in a manner different from that inherent for the linear helix, but which can provide additional information.

With reference to Figure 48, a schematic of an electromagnetic antenna 48 is illustrated. The antenna 48 includes a surface 49, such as the toroidal shape TF of Figure 1; an insulated conductor circuit 50; and two signal terminals 52, 54, although the invention is applicable to a wide variety of surfaces such as, for example, a multi-connected surface, a generally spherical surface (as shown with Figure 59), a spherical surface ( as shown with Figure 66), or a hemispherical surface (as shown in Figure 68). As used herein the term "multi-connected surface" will expressly include, but not be limited to: (a) any toroidal surface such as the toroidal form TF of Figure 1, which has its greater radius greater than or equal to its smaller radius; (b) other surfaces formed by the rotation of a circle, or a closed curve in the plane or polygon that has a plurality of different radii around an axis that lies on its plane, with the greater radius of other surfaces, which is greater of zero, and with the smaller radius of other surfaces that is less than or equal to or greater than the greater radius; and (c) other surfaces such as surfaces similar to those of a washer or nut, such as a hexagonal nut formed from a generally flat material, in order to define, with respect to its plane, a larger internal circumference of zero, and an outer circumference greater than the inner circumference, with the outer and lower circumferences that are either a flat closed curve and / or a polygon. The exemplary isolated conductor circuit 50 extends in a conductive path 56 around and on the surface 49 from a node 60 (+) to another node 62 (-). The insulated conductor circuit 50 also extends in another conductive path 58 around and on the surface 49, from the node 62 (-) to the node 60 (+), whereby an endless, simple conductive path is formed around and over the surface 49. As discussed above in connection with Figure 1, the conductive tracks 56, 58 can be oppositely wound helical conductive paths, having the same number of turns, with the direction of helical pitch or inclination for the conductive track 56 which is on the right hand (RH), as shown by the solid line, and the direction of helical pitch or inclination for the driving path 58 that is on the left (LH) which is opposite to the direction of RH, as It is shown by dashed lines.

The conductive tracks 56, 58 may be accommodated in a shape different from the helical, such as an overall helical shape, a partially helical shape, a pole-peripheral pattern, or a spiral pattern, and still satisfy the spirit of this invention . The conductive tracks 56, 58 can be "winding or polyloidal-peripheral winding patterns" wound in opposite directions having opposite winding directions, as discussed above, in relation to Figure 14, whereby the helix formed by each of the two insulated conductors Wl, W2, is decomposed into a series of interconnected 14.1 polyloidal loops or loops. Continuing with reference to Figure 48, the conductive tracks 56, 58 reverse the direction in the nodes 60, 62. The signal terminals 52, 54 are respectively electrically connected to the nodes 60, 62. The signal terminals 52, 54 supply or receive from the insulated conductor circuit 50 an electrical signal 64 RF, which leaves (transmitted) or enters (received). For example, in the case of a transmitted signal, the simple worm path of the insulated conductor circuit 50 is fed in series from the signal terminals 52, 54.

It will be appreciated by those skilled in the art that the conductor tracks 56, 58 may be formed by a single insulated conductor, such as, for example, a wired or printed circuit conductor., which forms the simple worm path, including the conductive path 56 from the node 60 to the node 62, and the conducting path 58 from the node 62 again to the node 60. It can also be appreciated by those of experience in the art. , that the conductive tracks 56, 58 can be formed by plural insulated conductors such as an insulated conductor forming the conductive path 56 from the node 60 to the node 62, and another insulated conductor which forms the conductive path 58 from the node 62 again to the node 60. The nominal operating frequency of the signal 64 is tuned to the front structure 48, so that the electrical circumference of the same is of a length of half a wavelength, and that the current distribution on the structure is sinusoidal in magnitude, which is an approximation. The oppositely wound conductive tracks 56, 58, each having a length of about one half of a guided wavelength of the nominal operating frequency, can be observed as elements of a non-uniform transmission line, with a power supply compensated. The tracks 56, 58 form a closed turn which, for example, in the case of a toroidal surface such as the toroid shape TF of Figure 1, has been twisted to form "Figure 8" and then folded back on itself to form two concentric windings. With reference to Figure 49, a schematic of another electromagnetic antenna 48 'is illustrated. The antenna 48 'includes a surface such as the surface 49 of Figure 48, an insulated conductor circuit 50', and two signal terminals 52 ', 54'. Except as discussed herein, the electromagnetic antenna 48 ', the insulated conductor circuit 50', and the signal terminals 52 ', 54', are in general the same as the respective electromagnetic antenna 48, the insulated conductor circuit 50, and the signal terminals 52, 54 of Figure 48. The exemplary insulated conductor circuit 50 'extends in a conductive path 56' around and on the surface 49 from a node 60 '(+) to an intermediate node A and from the intermediate node A to another node 62 '(-). The insulated conductor circuit 50 'also extends in another conductive path 58' around and on the surface 49 from the node 62 '(-) to another intermediate node B, and from the intermediate node B to the node 60' (+), whereby a conductive, sinuous, simple path is formed around and on the surface 49. As discussed above in connection with Figures 14 and 48, the conductive tracks 56 ', 58' may be helical conductive paths of opposite winding that have the same number of turns or may be accommodated in a different way to the purely helical, such as a generally helical shape, a partially helical shape, a spiral shape or "polyloidal-peripheral" winding patterns of opposite winding which have directions of opposite winding. The signal terminals 52 ', 54' supply to or receive from the isolated conductor circuit 50 'an electrical signal RF 64 of output (transmitted) or input (received). The conductive paths 56 ', 58', each having a length of about one half of a guided wavelength of the nominal operating frequency of the signal 64, reverse the direction at the nodes 60 ', 62'. The signal terminals 52 ', 54' are respectively electrically connected to the intermediate nodes A, B. Preferably, the nodes 60 ', 62' are diametrically opposed to the intermediate nodes A, B so that the length of the tracks conductors 56 ', 58' from the respective nodes 60 ', 62' to the respective intermediate nodes A, B is the same as the length of the conductor tracks 56 ', 58' from the respective intermediate nodes A, B to the respective nodes 62 ', 60'. It will be appreciated by those skilled in the art that the conductive tracks 56 ', 58' may be formed by a single insulated conductor which forms the simple, worm-type conductive path that includes the conductive path 56 'from the node 60' to the intermediate node A and then to node 62 ', and conductive path 58' from node 62 'to intermediate node B and then to node 60'. It may further be appreciated by those skilled in the art, that each of the conductive paths 56 ', 58' may be formed by one or more insulated conductors such as, for example, an insulated conductor from the node 60 'to the intermediate node. A, and from the intermediate node A to the node 62 '; or an isolated conductor from node 60 'to intermediate node A, and another isolated conductor from intermediate node A to node 62'. With respect to Figure 50, a schematic of another electromagnetic antenna 66 is illustrated. The antenna 66 includes a surface such as the surface 49 of Figure 48, a first insulated conductor circuit 68, a second insulated conductor circuit 70, and two terminals of signals 72, 74. The insulated conductor circuit 68 includes a pair of helical conductor paths 76, 78, and the insulated conductor circuit 70 similarly includes a pair of helical conductor paths 80, 82. The insulated conductor circuit 68 extends in the track conductive 76 around and partially on the surface 49 from a node 84 to a node 86, and also extends on the conductive path 78 around and partially on the surface 49 from the node 86 to the node 84, so that the tracks conductors 76, 78 form an endless conductive path around and on the surface 49. The insulated conductor circuit 70 extends in the conductive path 80 around and partially on the surface 49, from a node 88 to a node 90, and also extends in the conductive path 82 about and partially on the surface 49, from the node 90 to the node 88, so that the conductive tracks 80, 82 form another worm conduit around and on the surface 49. As discussed above in connection with Figures 14 and 48, the conductive tracks 76, 78 and 80, 82 may be helical conductive paths of opposite winding, having the same number of turns, or they may be otherwise accommodated to the purely helical, such as a generally helical shape, a partially helical shape, a spiral shape, or "poloidal-peripheral" winding patterns against windings, which have opposite winding directions. For example, the direction of passage of the driving track 76 may be on the right (RH) as shown by the solid line, the direction of passage for the driving path 78 which is on the left (RH) which is opposite to the RH direction of passage, as shown by dashed lines, and the direction of passage for conductor tracks 80 and 82 which is LH and RH, respectively. The conductive tracks 76, 78 reverse the direction in the nodes 84 and 86. The conductive tracks 80, 82 reverse the direction in the nodes 88 and 90. The signal terminals 72, 74 supply to or receive the insulated conductor circuits 68, 70 an RF electrical signal 92 that exits (transmitted) or enters (received). For example, in the case of a transmitted signal, the pair of worm conductors of the insulated conductor circuits 68, 70 are fed in series from the signal terminals 72, 74, although the invention is applicable to the parallel feeds in the nodes 84. , 88 and at nodes 90, 86. Each of the conductive paths 76, 78, 80, 82 have a length of about one quarter of the guided wavelength of the nominal operating frequency of the signal 92. As shown in Figure 50, the signal terminal 72 is electrically connected to the node 84, and the signal terminal 74 is electrically connected to the node 88. It may be appreciated by those skilled in the art, that the isolated conductor circuits 68, 70 may be be each formed by one or more isolated drivers. For example, the insulated conductor circuit 68 may have a single conductor for the two conductor tracks 76, 78; a simple conductor for each of the conductive tracks 76, 78; or electrically interconnected, multiple conductors, for each of the conductive pathways 76, 78. Referring to FIG. 51, a representative pattern of elevation radiation is illustrated for the electromagnetic antennas 48, 48 ', 66 of FIGS. 48, 49 , 50, respectively. These antennas are linear (for example, vertically) polarized, and have a physically low profile associated with the smaller diameter of the surface 49 of Figures 48, 49, 50, along the polarization direction. In addition, such antennas are generally omnidirectional in directions that are normal to the polarization direction, with a maximum radiation gain in the normal directions to the polarization direction, and a minimum radiation gain in the polarization direction. The opposite winding conductive pathways, such as the conductive tracks 56, 58 of Figure 48, provide destructive interference which cancels the resulting electric fields and constructive interference that reinforces the resulting magnetic fields. With reference to Figures 52 and 53, an electromagnetic antenna 94 includes a toroidal antenna 96, such as antennas 10, 48, 48 ', 66 of the respective Figures 1, 48, 49, 50; and a parabolic reflector 98, such as a satellite disk reflector, which directs the signals of the antenna 100 102 with respect to the toroidal surface 103 of the antenna 96, for the reception or transmission of antenna signals 100, 102 , although the invention is more generally applicable to multiple-connected surfaces and to various types of reflectors. The parabolic reflector 98 has a generally parabolic shape with a vertex 104, an aperture 106 and a central axis 108 between the apex 104 and the aperture 106. The parabolic reflector 98 further has a focal point 110 on the central axis 108. The surface toroidal 103 is generally located between the apex 104 and the aperture 106 of the parabolic reflector. Preferably, the major axis of the toroidal surface 103 is located along the central axis 108 of the parabolic reflector 98, with the center of the toroidal surface 103 which is located at the focal point 110 of the parabolic reflector 98. The electromagnetic antenna 94 provides the directionality for the exemplary toroidal antenna 96. The parabolic reflector 98 directs the electromagnetic signals 100, 102 to the gain portions 111 of the field pattern 112 of the antenna 96. Other unwanted signals 114, 116 respectively, find the gain portions. lowers 118, 119 of the field pattern 112 of the antenna 96, or are even deflected by the parabolic reflector 98, such as at a point 120. With reference to Figures 54 and 55, an electromagnetic antenna 94 'includes the toroidal antenna 96 of Figures 52-53, and a parabolic reflector 98 'which directs antenna signals 100, 102 in a manner similar to that discussed earlier in connection to Figure 53. The parabolic reflector 98 'has an opening 122 and a shape 124 in general parabolic (shown in dashed lines in the drawing) which defines a vertex 104 approximately in the center of the opening 122. The other opening 106 of the parabolic reflector 98 'is larger than the opening 122. The toroidal surface 103 is generally located between the openings 106, 122 of the parabolic reflector 98'. Except for the opening 122, the parabolic reflector 98 'is generally similar to the parabolic reflector 98 of Figures 52-53. The exemplary parabolic reflector 98 'in general, and the aperture 122 thereof in particular, take advantage of the field pattern 112 of the antenna 96. The low gain portion 119 in the background (with respect to Figure 55) of the antenna 96 does not contribute significantly to the transmission or reception of the antenna signals 100, 102. Consequently the absence of the surface of the parabolic reflector 98 'in the opening 122 thereof, does not significantly affect the transmission or reception of the signals. antenna signals 100, 102. An unwanted signal 126 (coming from the bottom of Figure 55) towards the aperture 122, merely encounters the low gain portion 119 of the antenna 96. The absence of the surface of the parabolic reflector 98 'in opening 122, greatly increases the aerodynamic properties of the electromagnetic antenna 94 'for installations with strong wind, such as a motor vehicle or boat, thereby reducing wind drag and, hence, the required weight and structural strength of the parabolic reflector 98 'necessary to resist such wind. With reference to Figure 56, an electromagnetic antenna 128 includes a surface, such as the surface 130 generally cylindrical, having an internal diameter or hole 132, an upper surface 134 and a lower surface 136, although the invention is applicable to other multiply connected surfaces such as a generally toroidal surface having an upper surface 134 generally flat, and / or a lower surface 136. The antenna 128 includes a first insulated conductor circuit 138, which extends in a partially helical conductive path, around and at least partially on the surface 130, with at least one first direction of helical pitch (for example, on the right (RH)). Antenna 128 also includes a second isolated conductor circuit 140, which extends in another conductive partially helical path, around and at least partially on the surface 130, with at least a second direction of helical passage (for example, on the left (LH)), in order that the insulated conductor circuits 138, 140 are oppositely wound one with respect to the other, around and at least partially on the surface 130. The major axis 142 of the electromagnetic antenna 128 is generally perpendicular with respect to the upper surface 134 and the lower surface 136 The insulated conductor circuits 138, 140 are generally radial with respect to the major axis 142, as shown with the radial portions 146, 146, respectively, on the upper surface 134. The insulated conductor circuits 138, 140 are also in general radially with respect to the major axis 142, as shown with the radial portions 148, 150 (shown in the dashed line drawing), respectively, on Surface 136. Otherwise, the insulated conductor circuits 138, 140 are generally helically oriented as shown with the generally helical portions 152, 154, respectively, on the outer surface 156 of the generally cylindrical surface 130, as well as with the portions 156, 158 in general helical, respectively, within the internal diameter 132 of the surface 130 generally cylindrical. Those skilled in the art will appreciate that the generally cylindrical surface 130, exemplary, and insulated conductor circuits 138, 140 with the radial portions 144, 146, 148, 150 and the generally helical portions 152, 154, 156, 158 may be used with the antennas 10, 48, 48 ', 66 of the respective Figures 1, 48, 49, 50. Figure 57 illustrates a radiation pattern in elevation, representative for the antennas 10, 48, 48', 66 of the Figures respective 1, 48, 49, 50 employing a toroidal surface with helical conducting paths. Also with reference to Figure 58, the exemplary electromagnetic antenna 128 of Figure 56 radiates or receives more energy radially and, therefore, less energy is radiated or received vertically. Accordingly, in this embodiment, the pattern of radiation on the top and bottom of the antenna 128 is further reduced, compared to antennas having helical conductive paths, and the radial radiation pattern is improved. In addition, the insulated conductor circuits 138, 140, which use some linear conductor portions 144, 146, 148, 150, reduce the relative size of the largest radius of the antenna 128.

With reference to Figure 59, an electromagnetic antenna 160 includes a toroid-shaped surface 162, generally spherical, with a cross-section 164 generally circular (as shown by the various latitude lines) and a conduit 166 (shown in the lines hidden in the drawing) along the major axis 168 of the surface 162. The antenna 160 includes a first insulated conductor circuit 170, which extends in a first conductor path 172, partially helical, around and at least partially on the surface generally spherical 162, with at least one first direction of helical pitch (for example, RH). The antenna 160 also includes a second insulated conductor circuit 174, which extends on a second conductor path 176, partially helical and at least partially on the generally spherical surface 162, with at least a second helical pitch (e.g. LH), so that the first and second insulated conductor circuits 170, 174 are wound opposite one another relative to the other around and at least partially on the generally spherical surface 162. The conductive, partially helical, tracks 172, 176 pass through the conduit 166 and are generally parallel to the major axis 168 within the conduit 166 as shown with the generally linear portions 178., 180 of the respective tracks 172, 176. Otherwise, the tracks 172, 176 have respective portions 182, 184 in general helical. Those skilled in the art will appreciate that the generally spherical, exemplary surface 162 and insulated conductor circuits 170, 174 with the generally linear portions 178, 180, and the generally helical portions 182, 184, may be employed with the antennas. , 48, 48 ', 66 of the respective Figures 1, 48, 49, 50. Figure 60 illustrates a representative pattern of elevation radiation for the antennas 10, 48, 48', 66 of the respective Figures 1, 48, 49 , 50 using a toroidal surface with helical conductive pathways. Also with reference to Figure 61, the exemplary electromagnetic antenna 160 of Figure 59 radiates or receives more energy vertically. Therefore, in this embodiment, the pattern of radiation on the top and bottom of the antenna 160 is improved, as compared to antennas having conductive helical paths. In this way, this modality produces a slightly more symmetrical radiation pattern. Figure 62 illustrates a perspective, sectional, vertical view of a toroid shape 186 in which the smaller radius is larger than the greater radius thereof, although the invention is applicable to any multiple connected surface, having a larger radius that is greater than zero and a smaller radius that is larger than the greater radius. Also with reference to Figures 63 and 64, the perspective and perspective views in plan illustrate the path of an insulated conductor circuit 188 having four turns 190, 192, 194, 196, although the invention is applicable to insulated conductor circuits. that have any number of turns. Employed with the exemplary toroidal shape 186, the insulated conductor circuit 188 extends in a generally helical conductive path, around and at least partially on the surface 197 of the exemplary toroid shape 186, in a manner described below, with at least one first helical pitch direction (eg, RH). Also with reference to Figure 65, another insulated conductor circuit 198 having four turns 200, 202, 204, 206 may also be employed with the exemplary toroidal form 186. The second insulated conductor circuit 198 extends in a generally helicoidal conducting path. , around and at least partially on the surface 197 of the toroid shape 186, with at least a second helical pitch (eg, LH), so that the insulated conductor circuits 188, 198 are wound opposite one with respect to the other. the other, around and at least partially on the surface 197 of the toroid shape 186. The surface 197 of the toroid shape 186 can be implemented, for example, as a mesh screen surface having a plurality of openings 208 in it, for routing the insulated conductor circuits 188, 198 through it. In this exemplary form, the central portion 210 of the toroid form 186 is accessible for the routing of the portions 211 (best seen in Figure 63) of the circuits 188, 198 therein, although other implementations are possible such as, for example , mounting the toroid shape 186 with a plurality of pie slices forming the central portion 210 and which provide routing channels for the circuits 188, 198; or the drilling of suitable routing holes within a solid toroidal shape. Those skilled in the art will appreciate that the exemplary toroidal shape 186 and exemplary isolated conductor circuits 188, 198 may be employed with the antennas 10, 48, 48 ', 66 of the respective Figures 1, 48, 49, 50. circuits 188, 198 pass through two common points 212, 214 in the toroid form 186 in respective portions 216, 218 (shown in Figure 65) of the circuits 188, 198. As shown schematically in Figure 72, the antenna 219, which is similar to the antenna 10 of Figure 1, includes the nodes al, b2, cl, d2 which converge (with the smaller values of the greater radius) in a terminal 220, and the nodes a2, bl, c2, di converge similarly in a terminal 222, where the lines between the nodes al, b2, cl, d2 and a2, bl, c2, di are shown for illustration convenience. In this way, the antenna 219 has a simple door on the terminals 220, 222, or alternatively, they can be powered independently on each of the segments 12. In turn, the terminals 220 and 222 are electrically connected to the respective nodes at , b2, cl, d2 and a2, bl, c2, where they converge (with the smaller values of the greater radius) at substantially common points 212, 214, along the major axis 224 of the toroid form 186. The points 212, 214 are associated with the respective portions 216, 218 (shown in Figure 65) of the circuits 188", 198. A three-dimensional toroidal surface such as the toroid shape TF of Figure 1, can be represented by the following equations: x = acos { Q) + eos (f) eos (?) (30) y = asen (?) + bcos (f) sin (?): 31) z = bsen. { f) (32) where a: major radius b: minor radius f: poloidal angle (0 to 2p)?: azimuth angle (0 to 2p) An existing helix on the toroid form TF of Figure 1 is defined by adjusting: f = N? (33; where N: number of turns in the propeller N > 0: windings on the right (RH) N < 0: left hand winding (LH) The equations that define a helix are: x = acos (Q) + bcos (N?) eos (?) (34) y = asen (?) + bcos (N?) sin (?) (35) z = J sin (N? J (36) By taking N positive and negative values, Equations 34-36 adequately describe the windings or windings oppositely.

With reference to Figures 66 and 67, the spherical conductors 226, 228 of opposite winding for a spherical-shaped antenna 230, having a spherical surface 232 are illustrated. Although a spherical surface is preferred, the invention is applicable to the surfaces in general spherical. The conductor 226 extends in a first conductive path around and at least partially on the spherical surface 232, with at least a first winding direction (eg, RH). The conductor 228 extends in a second conducting path around and at least partially on the spherical surface 232, with at least a second winding direction (eg, LH), so that the conductors 226, 228 are wound opposite one another. in relation to the other, around and at least partially on the spherical surface 232.

For the spherical mode, the equations that describe the windings of the opposite winding are developed by adjusting the radius greater than zero, as shown in the following equations: Cos (N?) Eos (?; (37) Cos (N?) Sin (?) (38) z = ¿sin (N?) (39) A sphere provides the benefit of a more spherical radiation pattern, although the invention is applicable to generally spherical embodiments, where the major radius is greater than zero. This approximates the radiation pattern of an ideal isotropic radiator or point source, which projects energy equally in all directions. By using the windings or winding-wound windings 226, 228, the electric fields cancel and leave a magnetic loop or loopback of approximately zero radius.

Those skilled in the art will appreciate that the exemplary spherical surface 232 and the opposite windings 226, 228 exemplary, may be employed with the antennas 10, 48, 48 ', 66 of the respective Figures 1, 48, 49, 50 where, for example, the polar nodes 233A, 233B of Figure 67 facilitate the changes between the winding directions (eg, LH and RH) where the winding paths 226, 228 counter-winding, generally intersect repeatedly around them. .

With reference to Figure 68, the oppositely wound hemispherical conductors 234, 236 are illustrated for a hemispherical antenna 238, having a hemispherical surface 240 on a plane 242. For the hemispherical mode, the equations describing the windings oppositely wound, they are developed by equations 37-39 above, where z is greater than or equal to zero. The conductor 234 extends in a first conducting path around and at least partially on the hemispherical surface 240, with at least one first winding direction (eg, RH) and the conductor 236 extends in a second conducting path, around and at the less partially on the hemispherical surface 240, with at least one second winding direction (e.g., LH) so that the conductors 234, 236 are wound opposite each other at least partially and partly over the hemispherical surface 240 .

For clarity of description of the opposedly wound conductors, and connections thereto, the plane 242 includes a left portion 244 and a right portion 246. Approximately in the center of the plane 242, there are a pair of terminals A, B of which the terminal A is shifted for illustration convenience. A plurality of feeds 248 are connected to the terminal A and the plurality of feeds 250 are connected to the terminal B. The feeds 248, 250 are preferably shielded, and have the same electrical impedance.

Preferably, the plane 242 is a ground plane which reflects each winding or coil electrically, and creates an image in the mirror thereof. In this way, if the hemispherical antenna 238 is on the bottom of an airplane or on the upper wall of a car, then, from a distance, the radiation pattern thereof approaches that of a spherical antenna.

On the right portion 246 of the plane 242, the feeds 248, 250 are connected to the conductors 236, 234, respectively. On the left portion 244 of the plane 242, the feeds 248, 250 are connected to the conductors 234, 236, respectively. The exemplary hemispherical antenna 238 is useful for stimulating or detecting ground currents, such as those employed in geophysical exploration, and in general projects or receives energy equally in all directions above plane 242 of Figure 68.

With reference to Figures 69 and 70 the alternative spherical conductors oppositely wound 226 ', 228' are illustrated for the spherical surface 232 of Figure 67. In this spherical embodiment, the spherical conductors 226 ', 228' do not cross repeatedly in the poles as discussed in connection with Figure 67. The antenna 230 'is created, for example, by rotation of the spherical surface 232 as the conductors 226', 228 'are applied.

Mathematically, a transformation matrix is introduced to operate on the position vector (x, y, z) defined by Equations 37-39. By applying the same transformation operator to both oppositely wound conductors 226 ', 228', the transformation retains the counter-balanced symmetry originally contained in the toroidal mode of Equations 34-36.

Equation 40 illustrates the general form of the transformed equations. The transformation matrix is, in general, a function of f y?. (40) where : (X, Y, Z): transformed coordinates (X, Yr Z) untransformed coordinates You? . general function of y? The transformation matrix of Equation 40 is defined as any matrix that retains the symmetry of the opposite winding of the windings.

For example, the geometry of the opposingly wound conductors 226 ', 228' may be distorted by stretching or rotation, although the invention is applicable to any windings or windings that provide destructive interference in order to cancel the resulting electric fields, and constructive interference in order to reinforce the resulting magnetic fields. In order to illustrate this transformation, an example will be provided.

Example 41 In this example, the spherical surface 232 is rotated in the XZ plane as a function of,, although the invention is applicable to a wide range of transformations associated with the toroidal surfaces, the multiplely connected surfaces, the generally spherical surfaces and the surfaces spherical With reference to Figure 71, an antenna 254 having one or two power doors is illustrated. The insulated conductor circuit 256 extends in the conductive path 258, around and partially on the surface 232 from a node 260 (+) to a node 262 (-). After changing the winding direction at node 262 (-), the insulated conductor circuit 256 extends in the conductive path 274, around and partially on the surface 232 from node 262 (-) to node 260 (+) in the order in which the conductor tracks 258, 274 form an endless conductor path around and on the surface 232. The insulated conductor circuit 266 (shown in dashed lines) extends in the conductor path 268 around and partially on the surface 232, from a node 270 (-) to a node 272 (+). After changing the winding direction of the node 272 (+), the insulated conductor circuit 266 extends on the conductive path 264, around and partially on the surface 232 from the node 272 (+) to the node 270 (-), with so that the conductive tracks 268, 264 form another endless conducting path around and on the surface 232.

The exemplary antenna 254 provides for the transmission and reception of the antenna signals. For example, in the case of a transmitted signal, the pair of worm conductors of the insulated conductor circuits 256, 266 are fed in series from the nodes 272, 262, although the invention is applicable to the parallel feeds in the nodes 272, 262 and nodes 260, 270.

In addition to the modifications and variations discussed or suggested previously, one of ordinary skill in the art may be able to make other modifications and variations without departing from the true scope and spirit of the invention.

Claims (41)

1. An electromagnetic antenna for use with an antenna signal, the electromagnetic antenna comprises: a multiplely connected surface; the first insulated conductor means extending in a first helical path generally helical, around and at least partially on the surface multiplely connected with at least a first direction of helical pitch or inclination; the second insulated conductor means extending in a second generally helicoidal conductive path, around and at least partially on the multiplely connected surface, with at least one second helical pitch direction, which is opposite to the first helical pitch direction, with so that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the multiple connected surface; the first and second signal terminals respectively electrically connected to the first and second insulated conductor means; Y the reflector means for directing the signal of the antenna with respect to the multiplely connected surface, for the reception or transmission of the antenna signal.

2. The electromagnetic antenna according to claim 1, wherein the reflector means includes a parabolic reflector.

3. The electromagnetic antenna according to claim 2, wherein the parabolic reflector has a generally parabolic shape with a vertex and an opening; and wherein the multiple connected surface is generally located between the apex and the parabolic reflector aperture.

4. The electromagnetic antenna according to claim 3, wherein the parabolic reflector further has an axis between the vertex and the aperture; and wherein the multiple connected surface has a major axis which is generally located along the axis of the parabolic reflector.

5. The electromagnetic antenna according to claim 4, wherein the additional parabolic reflector has a focal point on the axis thereof; and wherein the multiplely connected surface is a toroidal surface having a major axis and a center thereon, with the center of the toroidal surface being generally located at the focal point of the parabolic reflector.

6. The electromagnetic antenna according to claim 2, wherein the parabolic reflector has a first aperture, a generally parabolic shape defining a vertex approximately in the first aperture, and a second aperture which is larger than the first aperture; and wherein the multiple connected surface is generally located between the first and second apertures of the parabolic reflector.

7. The electromagnetic antenna according to claim 6, wherein the parabolic reflector further has a central axis between the first and second openings; and wherein the multiple connected surface has a major axis which is generally located along the central axis of the parabolic reflector.

8. The electromagnetic antenna according to claim 7, wherein the parabolic reflector further has a focal point on the central axis thereof; and wherein the multiplely connected surface is a toroidal surface having a major axis and a center thereon, with the center of the toroidal surface being generally located at the focal point of the parabolic reflector.

9. The electromagnetic antenna according to claim 2, wherein the multiple connected surface is a toroidal surface; and wherein the parabolic reflector has a generally parabolic shape with a vertex and an aperture; and wherein the toroidal surface is generally located between the vertex and the opening of the parabolic reflector.

10. The electromagnetic antenna according to claim 2, wherein the multiple connected surface is a toroidal surface; wherein the parabolic reflector has a first aperture, a generally parabolic shape which defines a vertex approximately in the first aperture, and a second aperture which is larger than the first aperture; and wherein the toroidal surface is generally located between the first and second apertures of the parabolic reflector.

11. The electromagnetic antenna according to claim 1, wherein the first insulated conductor means extends in the first generally helical conductive path, around and on the multiple connected surface, with the first direction of helical passage from a first node to a second direction. node; and wherein the second insulated conductor means extends in a second helical path generally helical, around and on the surface multiplely connected, with the second direction of helical passage from the second node to the first node, in order that the first and second generally helical conductive paths, are wound opposite one another relative to each other, and form a simple, endless conductive path around and on the multiply connected surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

12. The electromagnetic antenna according to claim 1, wherein the first insulated conductor means extends in a first helical path generally helical, around and on the multiple connected surface, with the first direction of helical passage coming from a first node towards a second node, and from the second node to a third node; wherein the second insulated conductor means extends in the second conductive path generally helical, around and on the surface multiplely connected, with the second direction of helical passage from the third node to a fourth node, and from the fourth node to the first node node, so that the first and second conductors in general helical, are wound opposite one another in relation to each other, and form a simple worm, around, and on the surface multiple connected; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

13. The electromagnetic antenna according to claim 1, wherein the first insulated conductor means extends in a first helical path generally helical, around and partially on the surface multiplely connected, with the first direction of helical passage coming from a first node towards a second node, and also extends in a third helical path generally helicoidal, around and partially on the surface multiplely connected, with the second direction of helical passage from the second node to the first node, in order that the first and third generally helical conductive pathways, forming a first endless conducting path, around and on the multiply connected surface; and wherein the second insulated conductor means extends in the second generally helical conductive path, around and partially on the surface multiplely connected, with the second direction of helical passage coming from a third node, towards a fourth node, and also extends in a fourth generally helical conductive path, around and partially on the surface multiplely connected, with the first direction of helical passage coming from the fourth node towards the third node, so that the third and fourth conductor paths in general helical form a second endless conducting path, around and on the multiplely connected surface, with the first and third generally helical conductive paths that are wound opposite each other relative to the second fourth generally helical conductive pathways, respectively; wherein the first signal terminal is electrically connected to the first node; and wherein the second signal terminal is electrically connected to the second node.

14. An electromagnetic antenna for use with an antenna signal, the electromagnetic antenna comprises: a multi-connected surface having a major axis and at least one generally flat surface, which is generally perpendicular to the major axis; the first insulated conductor means extending in a first partially helical conductive path, around and at least partially on the multiplely connected surface, with at least one first direction of helical pitch; the second insulated conductor means extends in a second partially helical conducting path, around and at least partially on the multiplely connected surface, with at least a second helical pitch, which is opposite to the first helical pitch direction, for the purpose that the first and second insulated conductive means be wound opposite one another relative to each other, around and at least partially on the multiplely connected surface, with the first and second conductive paths partially helical, when they are generally perpendicular to the major axis of the multiply connected surface, which is generally radial with respect to the major axis of the multiplely connected surface, and which is otherwise generally helical oriented; Y the first and second signal terminals respectively electrically connected to the first and second insulated conductor means.

15. The electromagnetic antenna according to claim 14, wherein the multiple connected surface is a generally cylindrical surface.

16. The electromagnetic antenna according to claim 14, wherein the multiple connected surface is a generally toroidal surface.

17. The electromagnetic antenna according to claim 14, wherein the first insulated conductor means extends in the first partially helical conductive path, around and on the multiple connected surface, with the first direction of helical passage from a first node to a second node; and wherein the second insulated conductor means extends in the second partially helical conductive path, around and on the surface multiplely connected, with the second direction of helical passage coming from the second node towards the first node, in order that the first and second partially helical conductive paths are wound opposite one another relative to each other, and form a simple, endless conducting path around and on the multiply connected surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

18. The electromagnetic antenna according to claim 14, wherein the first insulated conductor means extends in the first partially helical conductive path, around and on the multiple connected surface, with the first direction of helical passage from a first node to a second node , and from the second node to a third node; wherein the second insulated conductor means extends in the second partially helical conductive path, around and on the surface multiplely connected, with the second direction of helical passage from the third node to a fourth node, and from the fourth node to the first node , so that the first and second partially helical conductive pathways are wound in opposite fashion relative to each other, and form a simple worm track around and on the multiply connected surface; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

19. The electromagnetic antenna according to claim 14, wherein the first insulated conductor means extends in the first partly helical conductive path, around and partially on the multiplely connected surface, with the first helical passage direction coming from a first node towards a second node, and also extends in a third partially helical conductive path, around and partially on the surface multiplely connected, with the second direction of helical passage from the second node to the first node, so that the first and third ways partially helical conductors form a first continuous conductor path, around and on the surface multiple connected; and wherein the second insulated conductor means extends in the second partially helical conducting path, around and partially over the multiplely connected surface, with the second direction of helical passage from a third node to a fourth node, and also extends in a fourth direction. partially helical conductive path, around and partially on the multiple connected surface, with the first direction of helical passage from the fourth node towards the third node, so that the third and fourth partially helical conductive pathways form a second endless conducting path, around and on the multi-connected surface, with the first and second partially helical conductive paths being wound opposite each other relative to the second and fourth partially helical conductive paths, respectively; wherein the first signal terminal is electrically connected to the third node; and wherein the second signal terminal is electrically connected to the second node.

20. An electromagnetic antenna for use with an antenna signal, the electromagnetic antenna comprises: a surface, the surface is (a) spherical or generally spherical, or (b) multiply connected with a greater radius that is greater than zero and a smaller radius that is larger than the greater radius; the first insulated conductor means extending in a first conducting path around and at least partially on the surface, with at least a first winding direction; the second insulated conductor means extending in a second conducting path, around and at least partially on the surface, with at least a second winding direction, which is opposite to the first winding direction, in order that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the surface; Y the first and second signal terminals respectively electrically connected to the first and second insulated conductor means.

21. The electromagnetic antenna according to claim 20, wherein the surface is a multi-connected surface; wherein the first insulated conductor means extends in the first conductor path around and on the surface with the first winding direction from a first node, to a second node; and wherein the second insulated conductor means extends in the second conductor path around and on the surface with the second winding direction, from the second node to the first node, so that the first and second conductor paths form a path simple worm conductor, around and on the surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

22. The electromagnetic antenna according to claim 20, wherein the surface is a multi-connected surface; wherein the first insulated conductor means extends in the first conductor path around and on the surface with the first winding direction from a first node to a second node and from the second node to a third node; wherein the second insulated conductor means extends in the second conductor path, around and on the surface with the second winding direction, from the third node to a fourth node, and from the fourth node to the first node, in order to that the first and second conductive pathways form a simple worm track around and on said surface; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

23. The electromagnetic antenna according to claim 20, wherein the surface is a multi-connected surface; wherein the first insulated conductor means extends in the first conductor path around and partially on the surface, with the first winding direction from a first node towards a second node, and also extends in a second conductor path around and partially on the surface, with the second winding direction from the second node towards the first node, in order that the first and third conductive pathways form a first endless conducting path, around and on the surface; and wherein the second insulated conductor means extends in the second conductor path, around and partially on the surface, with a second direction of winding from a third node to a fourth node, and also extends in a fourth conductor path around and partially on said surface, with the first winding direction from the fourth node towards the third node, in order that the third and fourth conductive pathways form a second endless conducting path, around and on said surface, with the first and third conductive pathways which are wound in relation to the second and fourth conductive pathways, respectively; wherein the first signal terminal is electrically connected to the first node; and wherein the second signal terminal is electrically connected to the second node.

The electromagnetic antenna according to claim 20, wherein the surface is a multi-connected surface; wherein the first insulated conductor means extends in the first conductor path, around and on the surface, and forms a first endless conductor path around and on said surface, with the first conductor path having the first direction of winding (RH) and the second direction of winding (LH), which is opposite to the first direction of winding; wherein the second insulated conductor means extends in the second conductor path, around and on the surface, and forms a second endless conductor path around and on said surface, with the second conductor path having the first and second winding directions; wherein the first and second insulated conductor means are wound opposite one another relative to each other in a plurality of adjacent surface segments extending around the surface, with each of the segments being defined by a first node (ai) , b2) in which one of the first and second insulated conductor means changes from the first to the second winding direction, and a second node (bi, a2) in which the other of the first and second insulated conductor changes from the second towards the first direction of winding; wherein the first signal terminal is electrically connected to the first node at a substantially common first point; and wherein the second signal terminal is electrically connected to the second nodes at a substantially common second point.

25. The electromagnetic antenna according to claim 24, wherein the surface is a surface of a toroidal shape having a major axis; and wherein the first and second substantially common points are generally located along the major axis of the toroidal shape.

26. The electromagnetic antenna according to claim 20, wherein the surface is a spherical surface having a radius, b; where ? it is an azimuthal angle; wherein N is a number of turns in a conductive path, with N being positive for one of the first and second winding directions, and which is negative for the bull of the first and second winding directions; where x, y and z are positions that define a position vector; and wherein the first and second conductive pathways are defined by: x = bcos (N?) eos (?) y = bcos (N?) sin (?) z = bsen. { N? )

27. The electromagnetic antenna according to claim 26, wherein the first insulated conductor means extends in the first conductive path around and on the spherical surface, with the first direction of winding from a first node towards a second node; and wherein the second insulated conductor means extends in the second conductor path, around and on the spherical surface, with the second direction of winding from the second node towards the first node, so that the first and second conductor paths are co-opted one in relation to the other, and form a simple, endless conducting path around and on the spherical surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

28. The electromagnetic antenna according to claim 26, wherein the first insulated conductor means extends in the first conductive path, around and on the spherical surface, with the first direction of winding from a first node to a second node, and from the first node. second node towards a third node; wherein the second insulated conductor means extends in the second conductor path, around and on the spherical surface, with the second winding direction from the third node to a fourth node, and from the fourth node to the first node, in order that the first and second conductive pathways are wound counter to one another in relation to each other and form a simple worm path, around and on the spherical surface; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

29. The electromagnetic antenna according to claim 26, wherein the first insulated conductor means extends in the first conductive path around and partially on the spherical surface, with the first direction of winding from a first node to a second node, and is also extends in a third conducting path, around and partially on the spherical surface, with the second winding direction from the second node towards the first node, so that the first and third conductive pathways form a first endless conducting path around and over the spherical surface; and wherein the second insulated conductor means extends in the second conductor path around and partially on the spherical surface, with the second winding direction from a third node to a fourth node, and also extends in a fourth conductor path around and partially on the spherical surface, with the first winding direction from the fourth node towards the third node, in order that the third and fourth conductor paths form a second endless conducting path, around and on the spherical surface, with the first and third conductive paths that are wound opposite each other relative to the second and fourth conductive paths, respectively; wherein the first signal terminal is electrically connected to the first node; and wherein the second signal terminal is electrically connected to the second node.

30. The electromagnetic antenna according to claim 26, wherein the spherical surface has a pair of poles; and wherein the first and second conductive paths intersect in general at each of the poles.

31. The electromagnetic antenna according to claim 26, wherein the spherical surface has a pair of poles; and wherein the first and second conductive pathways intersect in general away from each of the poles.

32. The electromagnetic antenna according to claim 20, wherein the surface is a generally spherical surface having a conduit along a major axis thereof, with the first and second conductive passages passing through the conduit of the generally spherical surface, and which are generally parallel to the major axis thereof, inside the duct.

33. The electromagnetic antenna according to claim 32, wherein the first insulated conductor means extends in the first conductive path, around and on the generally spherical surface, with the first direction of winding from the first node towards the second node; and wherein the second insulated conductor means extends in the second conductor path around and on the generally spherical surface, with the second direction of winding from the second node to the first node, so that the first and second conductor paths they are oppositely wound one with respect to the other, and form a simple worm track around and on the generally spherical surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

34. The electromagnetic antenna according to claim 32, wherein the first insulated conductor means extends in the first conductive path, around and on the generally spherical surface with the first direction of winding from a first node to a second node, and from the second node towards a third node; wherein the second insulated conductor means extends in the second partially conducting path, around and on the generally spherical surface with the second winding direction, from the third node to a fourth node, and from the fourth node to the first node, so that the first and second conductive pathways are wound opposite one another relative to the other, and form a simple, endless conducting path around and on the generally spherical surface; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

35. The electromagnetic antenna according to claim 32, wherein the first insulated conductor means extends in the first conductive path around and partially on the generally spherical surface, with the first direction of winding from a first node to a second node, and it also extends in a third conducting path around and partially on the generally spherical surface, with the second winding direction from the second node, towards the first node, so that the first and second conductive pathways form a first conducting path endless, around and on the generally spherical surface; and wherein the second insulated conductor means extends in the second conductor path, around and partially on the generally spherical surface, with the second winding direction from the third node towards a fourth node, and also extends in a fourth conducting pathway. around and partially on the generally spherical surface, with the first winding direction from the fourth node towards the third node, in order that the third and fourth conductor paths form a second endless conductor path, around and on the surface in general spherical, with the first and third conductive paths that are wound opposite each other relative to the second and fourth conductive paths, respectively; wherein the first signal terminal is electrically connected to the first node; and wherein the second signal terminal is electrically connected to the second node.

36. An electromagnetic antenna for use with an antenna signal, the electromagnetic antenna comprises: a hemispherical surface; the first insulated conductor means extending in a first conductive path, around and at least partially on the hemispherical surface, with at least a first winding direction; the second insulated conductor means extending in a second conducting path around and at least partially on the hemispherical surface, with at least one second winding direction, which is opposite to the first winding direction, in order that the first and second insulated conductor means are wound opposite one another relative to the other, around and at least partially on the hemispherical surface; Y the first and second signal terminals respectively electrically connected to the first and second insulated conductor means.

37. The electromagnetic antenna according to claim 36, wherein the first insulated conductor means extends in the first conductor path around and on the hemispherical surface, with the first winding direction from a first node to a second node; and wherein the second insulated conductor means extends in the second conductor path, around and on the hemispherical surface with the second winding direction, from the second to the first node, so that the first and second conductor paths are wound oppositely one in relation to the other, and form a simple endless conducting path, around and on the hemispheric surface; and wherein the first and second signal terminals are respectively electrically connected to the first and second nodes.

38. The electromagnetic antenna according to claim 36, wherein the first insulated conductor means extends in the first conductive path around and on the hemispherical surface, with the first direction of winding from a first node to a second node, and from the second node. node to a third node; wherein the second insulated conductor means extends in the second conductor path around and on the hemispherical surface, with the second winding direction from the third node to a fourth node, and from the fourth node to the first node, in order to that the first and second conductive pathways are wound counter to one another in relation to each other and form a simple, endless conducting path around and on the hemispherical surface; and wherein the first and second signal terminals are respectively electrically connected to the second and fourth nodes.

39. The electromagnetic antenna according to claim 36, wherein the first insulated conductor means extends in the first conductive path, around and partially on the hemispherical surface, with the first direction of winding from a first node to a second node, and also it extends in a third conductive path around and partially on the hemispherical surface, with the second winding direction from the second node towards the first node, so that the first and third conductive pathways form a first, endless conductive path, around and on the hemispheric surface; and wherein the second insulated conductor means extends in the second conductor path, around and partially on the hemispherical surface, with the second winding direction from a third node to a fourth node, and also extends in a fourth conductor path around and partially on the hemispherical surface, with the first winding direction from the fourth node towards the third node, in order that the third and fourth conductive pathways form a second endless conducting path, around and on the hemispherical surface, with the first and the third conductive paths that are wound opposite each other relative to the second and fourth conductive paths, respectively, wherein the first signal terminal is electrically connected to the first node; and wherein the second signal terminal is electrically connected to the second node.

40. The electromagnetic antenna according to claim 36, wherein the hemispherical surface includes a flat surface, associated with the first and second signal terminals.

41. The electromagnetic antenna according to claim 40, wherein the flat surface is a terrestrial plane.