KR970008671B1 - Data transceiver - Google Patents

Abstract

A data transceiver of a broad band diffusion communication system by using pilot channel is provided, which includes a Walsh code generating part for generating first and second walsh codes, a walsh modulating part for multiplexing a predetermined pilot signal and data with the first and the second walsh codes to output the walsh-modulated pilot signal and data, a PN code generating part for generating a predetermined PN code, a band diffusion part for band-diffusing the input walsh-modulated input pilot signal and the data with the PN code, a response filtering part for filtering finite impulse response of the band diffused pilot signal and data, digital-to-analogue converting part for converting the filtered pilot signal and data into analogue signals, a low band fliter for filtering respective low bands of the analogue-converted pilot signal and data, an intermediate frequency mixing part for producing the pilot signal and data which are mixed with respective intermediate frequencies, a coupler for coupling the pilot signal and data which are mixed with respective intermediate frequencies to output, a broad band filter for fiitering broad bands of the output from the coupler, and an amplifier for amplifying the broad band filtered signals with a predetermined amplification rate to transmit, wherein the construction of the receiver may be simplified by forming I and Q channels respectively by using the pilot signal and data which are commonly multipled with the same PN code generater, and the pilot signal component and the data signal component are not coupled together so that the pure pilot signal component are utilized for synchronization.

Description

Data Transceiver of Spread Spectrum Communication System using Pilot Channel

1 is a block diagram of a data transmitter of a spread spectrum communication system using a conventional DPSK modulation scheme.

2 is a block diagram of a data transmitter of a spread spectrum communication system using a conventional pilot channel.

3 is a block diagram of a data transmitter of a spread spectrum communication system according to the present invention.

4 is a block diagram of a data receiver of a spread spectrum communication system according to the present invention.

5 is a detailed configuration diagram of a synchronous demodulator in the data receiver configuration of FIG.

The present invention relates to a spread spectrum communication system, and more particularly, to a data transceiver of a spread spectrum communication system using a pilot channel.

1 is a block diagram of a transmitter of a spread spectrum communication system using a conventional differential phase-shift keying (DPSK) modulation scheme. First, the DPSK encoder 102 receives input baseband data and generates a PN (Pseudo Noise) code generator 103. Multiply by the PN code outputted from the The output of the spreader 104 then passes through a finite impulse response (FIR) filter 105 and passes through a D / A converter 106 and an LPF 107. The output of the LPF 107 is multiplied and modulated by the carrier signal cosωct and the mixer 109 and propagated to free space through the antenna 112 via the BPF 110 and the amplifier 111.

The above-mentioned spread spectrum communication system of DPSK modulation method enables asynchronous detection when demodulating data at the receiving end by performing differential modulation.

However, DPSK modulation and demodulation cause a 1-bit error when demodulating, resulting in a 2-bit error. In addition, since the PN code signal component modulated by the data is transmitted instead of the pure PN code, there is a difficulty when the receiving end tries to synchronize the PN code.

Therefore, in order to solve the above problems, a spread spectrum communication system using a pilot channel is used.

2 is a block diagram of a transmitter in a spread spectrum communication system using a conventional pilot channel. The transmitted signal includes a pilot signal and data. The data is actually the information signal to be transmitted, and the pilot signal is always a signal of "1", and is an additional information signal transmitted in order to more easily match the PN code synchronization at the receiving end. The pilot signals and data are multiplied by the outputs of the first and second Walsh code generators 203 and 204 and the first and second Walsh modulators 205 and 206, respectively. The outputs of the modulators 205 and 206 are simultaneously separated into I and Q channels, respectively. The outputs of the first Walsh modulator 205, which is a pilot component, are the outputs of the I channel-PN code generator 207 and the first channel in the I channel. The multiplier multiplies and spreads in the spreader 208. In the Q channel, the multiplier multiplies and multiplies the output of the Q channel-PN code generator 210 by the third spreader 211. The output of the second Walsh modulator 206, which is a data component, is multiplied by the output of the Q channel-PN code generator 210 and the fourth spreader 212 in the Q channel, and is spread by the I channel-PN code generator in the I channel. The output of 207 is multiplied by the second diffuser 211 to spread.

The outputs of the first to fourth spreaders 208, 209, 211, and 212 pass through the first to fourth FIR filters 213 to 216, respectively, and are converted into analog signals by the first to 4D / A converters 217 to 220, respectively.

The output of the first D / A converter 217, which is the I channel signal component of the pilot channel, and the output of the second D / A converter 218, which is the I channel signal component of the data channel, are added by the I channel signal component combiner 221. An I-channel signal is formed, and the output of the 3D / A converter 219 which is the Q channel signal component of the pilot channel and the output of the 4D / A converter 220 which is the Q channel signal component of the data channel are Q channel signal components. Added at combiner 222 to form a Q channel signal.

The output of the I-channel combiner 221 and the Q-channel combiner 222 combined with the pilot and data signal components pass through the first and second LPFs 223 and 224, respectively. The output of the first LPF 223 is multiplied by the cosω _IF t which is the I-phase component of the intermediate frequency in the first mixer 227, and the output of the second LPF 224 is the sinω _IF t which is the Q-phase component and the second mixer ( 228). The outputs of the first and second mixers 227 and 228 are combined at the combiner 229, and the combined signal is multiplied by the cosω _RF t at the third mixer 231.

If ω c is the carrier frequency, ω c = ω _IF + ω _RF . The output of the third mixer 231 passes through the BPF 232, is amplified by the amplifier 233, and propagates to free space through the antenna.

By additionally transmitting a pilot signal in addition to data which is an information signal to be transmitted, it is possible to perform synchronous demodulation of data by a pilot signal when demodulating data at a receiving end. In addition, since the pilot signal component is always transmitted with "1", the pure PN code component of the pilot channel I and Q channel PN codes is not modulated. Therefore, when the receiver tries to synchronize the PN code, it can synchronize the code with an unmodulated pure PN code. The pilot channel and the data channel are separated by Walsh codes which are outputs of the first and second Walsh code generators 203 and 204.

However, a transmitter of a spread spectrum communication system using a pilot channel having the configuration of FIG. 2 adopts a quadrature phase shift keying (QPSK) spreading scheme that spreads pilot and data signals to both I and Q channels. The system becomes very complicated. In addition, the first and second combiners 221 and 222 make it difficult to acquire codes at the receiving end due to deterioration of cross correlation characteristics due to the combination of pilot and data signal components.

Accordingly, an object of the present invention is to provide a data transmitter of a pilot channel type spread spectrum communication system that spreads and transmits a pilot and data signal using one PN code generator.

Another object of the present invention is to provide a data receiver of a pilot channel type spread spectrum communication system that demodulates data by spreading the spectrum and despreading the pilot and data signals using a single PN code generator.

Another object of the present invention is to provide a data transceiver of a pilot channel spread spectrum communication system using a single PN code generator.

In the present invention for achieving the above object, in a spread spectrum communication system, a data transmitter includes Walsh code generating means for generating and outputting first and second Walsh codes having respective code systems, predetermined pilot signals, and desired transmission. A Walsh modulator for receiving the first and second Walsh codes, multiplying the pilot signal and the data, and outputting a Walsh-modulated pilot signal and data; and a PN code for generating and outputting a predetermined PN code. Band spreading means for receiving the Walsh-modulated pilot signal and data as a generation means, and spreading the two Walsh-modulated input signals as the PN codes, respectively, and outputting the finite-spread pilot signal and data. Finite impulse response filtering means for filtering and outputting impulse response, respectively, and filtering output from the finite impulse response filtering means. A digital-analog converting means for converting the spread spectrum signal and data into an analog signal and outputting the low-pass filtering means for receiving the analog-converted pilot signal and data and performing low-pass filtering; The low-pass filtered pilot signal and data and a predetermined intermediate frequency signal are input, and the pilot input signal is multiplied by cosω _IF t, which is an I-phase component of the intermediate frequency, and is a Q-phase component of the data input signal and the intermediate frequency. an intermediate frequency mixing means for outputting a pilot signal and data mixed with the intermediate frequency signal by multiplying sinω _IF t, combining means for receiving and combining the intermediate frequency mixed pilot signal and data, and the combining means; receives the input of the output signal with a predetermined _RF carrier signal cosω t, the two mixing outputs multiplied by the input signal End, and filtering means for band-pass filtering the output receives the output signal of the mixing means and receiving the band filtered signal amplification according to a predetermined amplification ratio is composed of the amplification means for transmitting via the antenna.

The data receiver for achieving the above-mentioned other objects includes: amplifying means for amplifying and outputting a received signal received through an antenna, second band filtering means for receiving an output signal of the low noise amplifying means and band-filtering the output signal; A first mixing means for receiving a band-filtered signal and a radio frequency signal cosω _RF t, multiplying the two input signals, and converting the signal into a signal having an intermediate frequency component; and an output signal of the second mixing means and an I of an intermediate frequency. - a second for outputting a phase component of cosω _IF t with two mixed signals, each input receives the mixed sinω _IF t of Q- phase component of the intermediate frequency, the input signal from the second mixing means for multiplying said two intermediate frequency signals A mixing means, a second low pass filtering means for receiving the two mixed signals and low-pass filtering them respectively, and receiving the two low-pass filtered signals digitally An analog-digital converting means for converting the signal into a signal, and outputting the PN code, the PN code generating means for generating a PN code in synchronization with the predetermined PN clock, and receiving the two digitally converted signals and the PN code, Despreading means for multiplying the two digitally converted signals by the PN code and converting the demultiplexed signals into I (t) which is an despread I channel signal and Q (t) which is a Q channel signal, respectively; And initial synchronization and synchronization tracking means for receiving Q (t) and synchronizing and tracking the PN codes of the two input signals and outputting a synchronization tracking result signal corresponding to the result, and receiving the synchronization tracking result signal. PN clock control means for outputting a clock control signal corresponding to an input signal, and PN clock generation for receiving and outputting the clock control signal and generating and outputting a PN clock controlled by the input signal to control generation of a PN code. However, when the I (t) and the Q (t) are received and the PN code synchronization of the two input signals is confirmed and the PN code synchronization is confirmed, the synchronous demodulation outputs the two input signals as synchronous demodulated data. Means.

Hereinafter, exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings.

3 is a block diagram of a transmitter in a spread spectrum communication system according to the present invention.

The first Walsh code generator 303 and the second Walsh code generator 304 generate and output first and second Walsh codes, respectively.

The first multiplier 305 receives the pilot signal and multiplies the first Walsh code input from the first Walsh code generator 303 to output a Walsh-modulated pilot signal.

The second multiplier 306 receives data desired to be transmitted and multiplies the first Walsh code input from the second Walsh code generator 304 to output Walsh-modulated data.

The first PN code generator 307 generates and outputs a predetermined PN code.

The third multiplier 308 multiplies the Walsh-modulated pilot signal by the PN code and outputs the spread spectrum signal.

The fourth multiplier 309 multiplies the Walsh-modulated data by the PN code and outputs the spread spectrum data.

The first FIR filter 310 filters the output of the third multiplier 308 and outputs it by finite impulse response filtering.

The second FIR filter 311 filters the output of the fourth multiplier 309 and outputs it by finite impulse response filtering.

The first D / A converter 312 converts the output of the first FIR filter 310 into an analog signal.

The second D / A converter 313 converts the output of the second FIR filter 311 into an analog signal.

The first and second LPFs 314 and 315 may low pass filter the outputs of the first and second D / A converters 311 and 312, respectively.

The fifth multiplier 318 receives the I-channel output of the first LPF 314, which is a pilot signal component, and cosω _IF t, which is an I-phase component of an intermediate frequency, and multiplies the two input signals.

The sixth multiplier 319 receives the Q channel output of the second LPF 315, which is a data signal component, and sinω _IF t, which is a Q-phase component of an intermediate frequency, and multiplies the two input signals.

The combiner 320 receives the outputs of the fifth and sixth multipliers 318 and 319 and combines and outputs the two input signals.

The seventh multiplier 322 receives the output of the combiner 320 and the intermediate frequency cosω _RF t, and multiplies the two input signals to output a mixed signal.

The first BPF 323 receives the output of the seventh multiplier 322 and outputs the result of band filtering.

The amplifier 324 receives the band-filtered signal and amplifies it according to a predetermined amplification ratio and outputs it through an antenna.

4 is a block diagram of a receiver of a spread spectrum communication system according to the present invention.

The low noise amplifier (LNA) 402 amplifies and outputs a received signal received from an antenna as a high frequency amplifier.

The second BPF 403 band filters the received signal output from the LNA 402.

The eighth multiplier 405 receives the band-filtered signal and cosω _RF t, multiplies the two input signals, and converts the signal into an intermediate frequency signal.

The ninth multiplier 408 receives the output signal of the eighth multiplier 405 and cosω _IF t, which is an I-phase component of the intermediate frequency, and multiplies the two input signals and outputs the multiplied signals.

The tenth multiplier 409 receives the output signal of the eighth multiplier 405 and sinω _IF t, which is a Q-phase component of an intermediate frequency, and multiplies the two input signals and outputs the multiplied signals.

The third and fourth LPFs 410 and 411 receive the output signals of the ninth and tenth multipliers 408 and 409, respectively, and perform low pass filtering to output the spread signal components.

The first and second A / D converters 412 and 413 receive the filtering outputs of the first and second LPFs 410 and 411, respectively, and convert the digital outputs into digital signals.

The second PN code generator 414 receives a predetermined PN clock and generates and outputs a PN code in synchronization with this.

The eleventh and twelfth multipliers 415 and 416 are despreaders that receive the output signals of the digitally converted first and second A / D converters 412 and 413 and the PN codes, respectively, and multiply the two input signals to spread the band despread. Outputs the I channel signal I (t) and the Q channel signal Q (t).

The initial sync and sync tracker 417 receives I (t) and Q (t) from the eleventh and twelfth multipliers 415 and 416, and synchronizes and tracks the PN codes of the two input signals to correspond to the results. Output the result signal.

The PN clock controller 418 receives the synchronization tracking result signal and outputs a clock control signal corresponding to the input signal.

The PN clock generator 419 receives the clock control signal and generates and outputs a PN clock controlled by the input signal to control the generation of the PN code.

When the synchronous demodulator 422 receives I (t) and Q (t) from the eleventh and twelfth multipliers 415 and 416, confirms that the PN code is synchronized with the two input signals and confirms that the PN code is synchronized. Auxiliary data is output from the two input signals.

5 is a detailed configuration diagram of the synchronous demodulator 422 in the configuration of FIG. 4 described above, and is configured as follows.

The third and fourth Walsh code generators 503 and 506 generate and output the third and fourth Walsh codes, respectively. Here, the third Walsh code generator 503 generates the same Walsh code as the first Walsh code generator 303 in the transmitter shown in FIG. 3, and the fourth Walsh code generator 506 is shown in FIG. Generate the same Walsh code as the second Walsh code generator 304 at the transmitter.

The thirteenth multiplier 504 receives I (t), which is an I channel signal output from the eleventh multiplier 415, and a third Walsh code from the third Walsh code generator 503, and multiplies the two input signals. Output

The fourteenth multiplier 505 receives Q (t), which is a Q channel signal output from the twelfth multiplier 416, and a third Walsh code from the third Walsh code generator 503, and multiplies the two input signals. Output

The fifteenth multiplier 507 receives I (t) which is an I-channel signal output from the eleventh multiplier 415 and a fourth Walsh code from the fourth Walsh code generator 506, and multiplies the two input signals. Output

The sixteenth multiplier 508 receives Q (t) which is a Q channel signal output from the twelfth multiplier 416 and a fourth Walsh code from the fourth Walsh code generator 506, and multiplies the two input signals. Output

The first and second accumulators 509 and 510 receive the output signals of the thirteenth and fourteenth multipliers 504 and 505, respectively, and accumulate and output the input signals.

The third and fourth accumulators 511 and 512 receive the output signals of the fifteenth and sixteenth multipliers 507 and 508, respectively, and accumulate and output the input signals.

The seventeenth multiplier 513 receives the output signals of the first and fourth accumulators 509 and 512 and multiplies the two input signals and outputs the multiplied output signals.

The eighteenth multiplier 514 receives the output signals of the second and second accumulators 510 and 511 and multiplies the two input signals and outputs the multiplied output signals.

The subtractor 515 receives the output signals of the seventeenth and eighteenth multipliers 513 and 514 and outputs a difference between the two input signals.

The determiner 516 receives an output signal of the subtractor 515, detects a phase of the data from the input signal, and finally outputs demodulated data.

Hereinafter, an operation of a data transceiver of a spread spectrum communication system using a pilot channel according to the present invention will be described in detail with reference to FIGS. 3 to 5.

The transmitted signal is largely composed of pilot and data as described above. The data is actually an information signal to be transmitted, and the pilot always transmits a signal of " 1 " and the phase of the pilot channel can be changed for the purpose of facilitating PN code synchronization at the receiving end or when demodulating the data at the receiving end. Used for reporting synchronous demodulation. The above-described pilot signal component forms an I channel signal, and the data signal component forms a Q channel signal component.

First, the pilot signal is multiplied by the first Walsh code and the first multiplier 305, and the data signal is multiplied by the second Walsh code and the second multiplier 306.

The Walsh-modulated pilot signal component and the Walsh-modulated data signal component are multiplied by the PN code of the first PN code generator 307 and the third and fourth multipliers 308 and 309 used as the band spreaders, respectively, to spread and spread. The signal is converted into a signal component. The outputs of the third and fourth multipliers 308 and 309 pass through the first and second FIR filters 310 and 311, and are converted into analog signals through the first and second D / A converters 312 and 313, respectively.

The analog signals are then low-pass filtered through the first and second LPFs 314 and 315, respectively. The output of the first LPF 314 of the I channel, which is the pilot signal component, is multiplied by the fifth multiplier 318 with cosω _IF t, which is the I-phase component of the intermediate frequency, and the second LPF 315 of the Q channel, which is a data signal component. The output of is multiplied by sinω _IF t, which is the Q-phase component of the intermediate frequency, by the sixth multiplier 319. That is, the pilot channel and the data channel are separated by the first and second Walsh codes, which are the outputs of the first and second Walsh code generators 303 and 304, respectively, and by the orthogonal functions cosω _IF t and sinω _IF t.

In addition, the outputs of the fifth and sixth multipliers 318 and 319 are combined at the combiner 320. That is, the combiner 320 combines the I-channel signal, which is a pilot component, and the Q-channel signal, which is a data component. The output of the combiner 320 is multiplied by the carrier signal cosω _IF t in the third mixer 322.

The output of the seventh multiplier 322 is band filtered through the first BPF 323, amplified by the amplifier 324, and propagated to free space through the antenna.

Then, the signal received from the antenna at the receiver is multiplied by the radio frequency signal cosω _RF t and the eighth multiplier 405 through the low noise amplifier 402 and the second BPF 403 and converted into a signal of the intermediate frequency component. The output of the eighth multiplier 405, which is the intermediate frequency signal component, is multiplied by cosω _IF t which is the I-phase component of the intermediate frequency in the ninth multiplier 408, and the Q-phase component of the intermediate frequency in the tenth multiplier 409. Is multiplied by sinω _IF t and converted into spread signal components through the third and fourth LPFs 410 and 411, respectively. The outputs of the third and fourth LPFs 410 and 411 are converted into digital signals through the first and second A / D converters 412 and 413, respectively. The output signals of the A / D-converted first and second A / D converters 412 and 413 are multiplied and despread by the PN codes in the eleventh and twelfth multipliers 415 and 416, which are despreaders, respectively.

The outputs of the eleventh and twelfth multipliers 415 and 416 are input to the initial sync and sync tracker 417 to perform the process of synchronizing the PN code and the sync trace process, and correspond to the initial sync and sync tracker ( The output of 417 is input to the PN clock controller 418. Thereafter, the PN clock generator 419 adjusts the code generation speed of the second PN code generator 414 in response to the control of the PN clock controller 418.

In addition, when it is confirmed that the PN code synchronization is correct by the initial synchronization and the synchronization tracker 417, the synchronous demodulator 422 performs demodulation by performing synchronous demodulation using the I channel signal I (t) and the Q channel signal Q (t). Get the data.

At this time, the operation of the synchronous demodulator 422 will be described in detail according to the configuration of the synchronous demodulator 422 shown in FIG. 5. First, the I channel signal I (t) and the Q channel signal Q (t) The thirteenth and fourteenth multipliers 504 and 505 are input to multiply the third Walsh code. The I channel signal I (t) and the Q channel signal Q (t) are input to the fifteenth and sixteenth multipliers 507 and 508 and multiplied by the fourth Walsh code. Here, the third Walsh code generator 503 generates the same Walsh code as the first Walsh code generator 303 in the transmitter shown in FIG. 3, and the fourth Walsh code generator 506 is shown in FIG. Generate the same Walsh code as the second Walsh code generator 304 at the transmitter.

That is, the outputs of the thirteenth and fourteenth multipliers 504 and 505 are pilot signal components, and the outputs of the fifteenth and sixteenth multipliers 507 and 508 are data signal components. The outputs of the thirteenth and fourteenth multipliers 504 and 505 are accumulated in the first and second accumulators 509 and 510, respectively. The outputs of the fifteenth and sixteenth multipliers 507 and 508 are respectively accumulated in the third and fourth accumulators 511 and 512. Accumulate. Thereafter, the outputs of the first and fourth accumulators 509 and 512 are multiplied by the seventeenth multiplier 513, and the outputs of the second and second accumulators 510 and 511 are multiplied by the eighteenth multiplier 514.

The output of the seventeenth multiplier 513 and the output of the eighteenth multiplier 514 are subtracted by the subtractor 515, and the subtractor 515 outputs the subtracted value. The decision unit 516 detects the phase of the data from the subtractor 515 and demodulates the data to output the demodulated data.

Therefore, as described above, in the present invention, only the I-channel signal component is formed by using the pilot signal, and only the Q-channel signal component is formed by using the data, and the I-channel and Q-channel signal components are both the same as the PN code generator. Since it is multiplied by the output, the configuration of the receiver is simplified.

In addition, the present invention does not have a coupler configuration and process for combining the spread spectrum and analog converted signal, so that the pilot signal component is not disturbed by the data signal component, thereby causing a problem of degradation of code acquisition characteristics due to cross correlation. There is no effect. That is, since the pilot signal component and the data signal component are not combined, the receiver is able to synchronize the code using only the pure pilot component and thus code acquisition is easier.

Claims (8)

In a spread spectrum communication system, a Walsh code generation unit generating and outputting first and second Walsh codes, and a pilot signal that is Walsh-modulated by multiplying a predetermined pilot signal and desired data by the first and second Walsh codes, respectively. Walsh modulator for outputting signal and data, PN code generator for generating and outputting predetermined PN code, and spreading the two Walsh modulated input signals as the PN code by receiving Walsh modulated pilot signal and data. And a finite impulse response filter for filtering and outputting the band spread pilot signal and data by finite impulse response filtering, respectively, and the filtered and spread band spread pilot signal and data as analog signals. A digital-to-analog converter for converting and outputting the low-pass filter for the analog-converted pilot signal and data Inverse filter unit, multiplies the _IF t cosω the I- phase component of the low-bit pilot signal and the intermediate frequency filter is multiplied by sinω _IF t of Q- phase component of the low-pass-filtered data and the medium frequency of intermediate frequency mixing pilot An intermediate frequency mixer for outputting a signal and data, a combiner for combining the intermediate frequency mixed pilot signal and data, and a mixer for multiplying the output signal of the combiner and a predetermined radio frequency signal cosω _RF t And a band pass filter for band-filtering and outputting the output signal of the mixer, and an amplifier for receiving the band-filtered signal and amplifying and transmitting the band-filtered signal according to a predetermined amplification ratio. Data transmitter of the system. The spreader of claim 1, wherein the spreader multiplies the first multiplier by multiplying the Walsh-modulated pilot signal by the PN code and outputs the spread-band spread signal by multiplying the Walsh-modulated data by the PN code. A data transmitter of a spread spectrum communication system using a pilot channel, characterized by comprising a second multiplier for outputting the data. 3. The apparatus of claim 2, wherein the finite impulse response filter unit comprises: a first finite impulse response filter for outputting the output signal of the first multiplier by finite impulse response filtering; and a finite impulse response filtering and outputting the output signal of the second multiplier; A data transmitter of a spread spectrum communication system using a pilot channel, comprising a second finite impulse response filter. In a spread spectrum communication system, a first Walsh code generator generating and outputting a first Walsh code, a second Walsh code generator generating and outputting a second Walsh code, a pilot signal and a first Walsh code are multiplied by a Walsh modulation. A first multiplier for outputting a pilot signal, a second multiplier for outputting Walsh-modulated data by multiplying the desired data with the second Walsh code, a PN code generator for generating and outputting a predetermined PN code, and the Walsh A third multiplier for multiplying the modulated pilot signal by the PN code and outputting the spread spectrum signal, a fourth multiplier for multiplying the Walsh-modulated data and the PN code and outputting the spread spectrum data; A first finite impulse response filter that receives an output signal of a three multiplier and filters and outputs a finite impulse response filter, and a finite impulse response filtering that receives an output signal of the fourth multiplier A second finite impulse response filter to be output, a first digital to analog converter for converting and outputting the output of the first finite impulse response filter, and an analog signal to the output of the second finite impulse response filter. A second digital-analog converter for converting and outputting the first output signal, first and second LPFs for low-pass filtering the outputs of the first and second digital-analog conversion means, and cosω, which is an I-phase component of an intermediate frequency. A fifth multiplier for multiplying the _IF t by the lowpass filtered pilot signal from the first LPF and outputting the intermediate frequency mixed pilot signal, and the lowpass filtered data from sinω _IF t which is the Q-phase component of the intermediate frequency and the second LPF And a sixth multiplier for outputting the intermediate frequency mixed data by multiplying, a combiner for combining and outputting the intermediate frequency mixed pilot signal and data, and an output signal of the combiner; Defined as a wireless frequency signal mixer output multiplied by cosω _RF t, also composed of a band pass filter and an amplifier and transmitting the amplified along the band-filtered signal to a predetermined amplification ratio, which receives the output signal from the mixer output to the band filter A data transmitter of a spread spectrum communication system using a pilot channel, characterized in that. In a spread spectrum communication system, a first Walsh code generator generating and outputting a first Walsh code, a second Walsh code generator generating and outputting a second Walsh code, a pilot signal and a first Walsh code are multiplied by a Walsh modulation. A first multiplier for outputting a pilot signal, a second multiplier for outputting Walsh-modulated data by multiplying the data desired to be transmitted with the second Walsh code, and receiving a predetermined PN clock to generate a PN code in synchronization with the input A PN code generator configured to multiply the Walsh-modulated pilot signal by the PN code and output a band-spread pilot signal, and multiply the Walsh-modulated data by the PN code and output the band-spread data. A fourth multiplier, a first finite impulse response filter that receives the output signal of the third multiplier and filters and outputs a finite impulse response filter, and an output signal of the fourth multiplier A second finite impulse response filter that receives and outputs a finite impulse response filter, a first digital-analog converter that converts and outputs an output of the first finite impulse response filter into an analog signal, and a second finite impulse response filter A second digital-analog converter for converting and outputting an output into an analog signal, first and second low pass filters for low-pass filtering the outputs of the first and second digital-analog converting means, respectively, and an intermediate A fifth multiplier for multiplying the cosω _IF t which is the I-phase component of the frequency by the low-pass filtered pilot signal from the first LPF and outputting the intermediate frequency mixed pilot signal, and the sinω _IF t which is the Q-phase component of the intermediate frequency; A sixth multiplier for multiplying the low pass filtered data from the second LPF to output the intermediate frequency mixed data, and combining the intermediate frequency mixed pilot signal and the data A combiner, and an output signal with a predetermined radio frequency signal cosω _RF t the mixer output is multiplied and a band pass filter and the band-filtered signal, which receives the output signal from the mixer output to the band filter of the combiner predetermined amplification ratio that An amplifier for amplifying and transmitting the signal, a low noise amplifier for amplifying and outputting a received signal received through an antenna, a band pass filter for receiving an output signal of the low noise amplifying means and band filtering the output signal, and the band filtered signal. And a seventh multiplier that multiplies and cosω _RF t which is a radio frequency signal and converts the signal into an intermediate frequency signal, and an eighth multiplier multiplies and outputs the output signal of the seventh multiplier by cosω _IF t which is an I-phase component of the intermediate frequency. And a ninth multiplier for multiplying the output signal of the seventh multiplier by sinω _IF t, which is an intermediate frequency Q-phase component, and the eighth and ninth products. Third and fourth low pass filters that receive the output signals of the multiplier, respectively, and perform low-pass filtering, and first and second analog-to-digital converters that receive the low-pass filtered signals and convert the two signals into digital signals. And a tenth multiplier outputting I (t), which is an I-channel signal despread by multiplying the output signal of the first analog-digital conversion means by the PN code, and the output of the second analog-digital conversion means. An eleventh multiplier that outputs Q (t), which is a Q channel signal despread by multiplying the signal by the PN code, and receives I (t) and Q (t) from the tenth and eleventh multipliers, An initial synchronization and synchronization tracker for synchronizing and synchronizing PN codes and outputting a synchronization tracking result signal corresponding to the result; a PN clock controller for outputting a clock control signal corresponding to the synchronization tracking result signal; and the clock control signal. Controlled PN nose A PN clock generator generating and outputting a PN clock for controlling the generation of the node; and when the PN code synchronization of the I (t) and Q (t) is confirmed and the PN code synchronization is confirmed, the two input signals are synchronously demodulated. A data transceiver of a spread spectrum communication system using a pilot channel, characterized by comprising a synchronous demodulator for outputting data. 6. The apparatus according to claim 5, wherein the synchronous demodulation means comprises: first and second Walsh code generators for generating and outputting third and fourth Walsh codes corresponding to the first and second Walsh codes, respectively, and the I (t). And a first multiplier for receiving the first Walsh code and multiplying the two input signals and outputting the multiplier and a second multiplier for receiving the Q (t) and the first Walsh code and multiplying the two input signals and outputting the multiplier. A third multiplier that receives the I (t) and the second Walsh code, multiplies and outputs the two input signals, receives the Q (t) and the second Walsh code, and multiplies the two input signals A first accumulator and a second accumulator for receiving an output fourth multiplier, output signals of the first and second multipliers, respectively, accumulating the input signals, and outputting the output signals of the third and fourth multipliers; Are respectively inputted, and accumulate and output the input signals, respectively. Is a second accumulator and a fourth accumulator, the output signals of the first and fourth accumulators are input, a fifth multiplier that multiplies the two input signals and outputs the output signals of the second and third accumulators, A sixth multiplier that multiplies the two input signals and outputs the output signal of the fifth and sixth multipliers, a subtractor that calculates and outputs a difference between the two input signals, and an output signal of the subtractor And a determiner configured to detect a phase of the data from the input signal and finally demodulate and output the data. A spread spectrum communication system comprising: a low noise amplifier for amplifying and outputting a received signal received through an antenna, a band pass filter for band filtering and outputting an output signal of the low noise amplifier, and the band filtered signal and a radio frequency signal; a first multiplier multiplying the cosω _RF t into a signal of an intermediate frequency component, a second multiplier multiplying the output signal of the first multiplier by cosω _IF t which is an I-phase component of the intermediate frequency, and outputting the first multiplier; A third multiplier for multiplying the multiplier output signal by sinω _IF t, the Q-phase component of the intermediate frequency, and first and second low pass filters for low-pass filtering the output signals of the second and third multipliers, respectively; And first and second analog-to-digital converters which receive the low-pass filtered signals, respectively, convert them into digital signals, and output the same; A PN code generator for generating and outputting a PN code, a fourth multiplier for outputting I (t) which is an I channel signal despread by multiplying the output signal of the first analog-to-digital converter and the PN code, and the fourth A multiplier and a fifth multiplier for outputting Q (t), which is a Q channel signal despread by multiplying the PN code by the output signal of the second analog-to-digital converting means, and input from the fourth and fifth multipliers PN codes of I (t) and Q (t) for synchronization and synchronous tracking, and initial and synchronous trackers for outputting synchronous tracking result signals corresponding to the results, and PN for outputting clock control signals corresponding to the synchronous tracking result signals. A PN clock generator for generating and outputting a PN clock that is controlled by the clock control signal and controls the generation of the PN code, and confirms the PN code synchronization of the I (t) and Q (t) and synchronizes the PN code. If it is confirmed that the data is corrected, I (t) and Q (t) Band data receiver in a spread communication system using a pilot channel, characterized in that the synchronous demodulator that consists of force. 8. The apparatus of claim 7, wherein the demodulation demodulator comprises: first and second Walsh code generators for generating and outputting first and second Walsh codes, the I (t) and the first Walsh code; A first multiplier that multiplies and outputs a signal, a second multiplier that receives the Q (t) and the first Walsh code, multiplies and outputs the two input signals, and outputs the I (t) and the second Walsh code A third multiplier for receiving and multiplying and outputting the two input signals, a fourth multiplier for receiving the Q (t) and the second Walsh code and multiplying and outputting the two input signals, and the first and second Receives an output signal of a multiplier, respectively, and receives the first and second accumulators for accumulating and outputting the input signals, respectively, and outputs the output signals of the third and fourth multipliers, respectively, and accumulates the input signals. A third accumulator and a fourth accumulator, and the first and the second accumulators A fifth multiplier that receives an output signal of a four accumulator and receives the output signals of the second and third accumulators by multiplying the two input signals and outputs the multiplier and a sixth multiplier that multiplies and outputs the two input signals; A subtractor that receives the output signals of the fifth and sixth multipliers, calculates and outputs a difference between the two input signals, receives an output signal of the subtractor, detects a phase of the data from the input signal, and finally demodulates the data A data receiver of a spread spectrum communication system using a pilot channel, characterized in that it is configured as an output determinant.