KR20240024126A - Active compensation device for using parallel aplifier - Google Patents

Abstract

The present invention relates to an active compensation device that actively compensates for noise occurring in a common mode in each of at least two large current paths connected to a first device, and transmits a large current supplied by a second device to the first device. At least two high current paths, a sensing unit that senses a common mode noise current on the high current path and generates a plurality of output signals in parallel based on the noise current, and amplifies each of the plurality of output signals to generate a plurality of output signals. A plurality of amplification units respectively corresponding to the plurality of output signals, which generate amplification signals in parallel, and drawing a compensation current from the high current path based on the plurality of amplification signals, or providing compensation on the high current path An active compensation device including a compensation unit that generates voltage is provided.

Description

Active compensation device using a parallel amplifier {ACTIVE COMPENSATION DEVICE FOR USING PARALLEL APLIFIER}

Embodiments of the present invention relate to an active compensation device that compensates for noise current and/or noise voltage occurring in a common mode on two or more high current paths connecting two devices.

In general, electrical devices such as home appliances, industrial electrical products, or electric vehicles emit noise while operating. For example, noise may be emitted through power lines due to the switching operation of power conversion devices within electronic devices. If this noise is left unattended, it is not only harmful to the human body but also causes malfunctions or failures in surrounding parts and other electronic devices. In this way, the electromagnetic interference that electronic devices cause to other devices is called EMI (Electromagnetic Interference), and among them, noise transmitted through wires and board wiring is called conducted emission (CE) noise.

In order to ensure that electronic devices operate without causing malfunctions in surrounding components and other devices, the amount of EMI noise emissions from all electronic products is strictly regulated. Therefore, most electronic products necessarily include a noise reduction device (e.g., EMI filter) that reduces EMI noise current in order to satisfy regulations on noise emissions. For example, in white appliances such as air conditioners, electric vehicles, aviation, and energy storage systems (ESS), EMI filters are essential. Conventional EMI filters use a common mode choke (CM choke) to reduce common mode (CM) noise among conducted emission (CE) noise. A common mode (CM) choke is a passive filter that suppresses common mode noise current.

Meanwhile, in order to prevent magnetic saturation of the common mode choke and maintain noise reduction performance in a high power/high current system, the size or number of common mode chokes must be increased. This caused the problem that the size and price of EMI filters for high-power products increased significantly.

Recently, in order to overcome the disadvantages of passive EMI filters as described above, interest in the development of active EMI filters including amplifiers is increasing.

However, there is a limit to the maximum noise that a single amplifier can handle (or process). Since the DC voltage that can be used in an amplifier is generally limited, there are limits to increasing the noise limit that the amplifier can handle. Therefore, if the noise current increases, the amplifier may not function properly.

The present invention was devised to improve the above problems, and its purpose is to provide an active compensation device using a parallel amplifier that can accommodate and compensate for larger noise.

However, these tasks are illustrative and do not limit the scope of the present invention.

According to an embodiment of the present invention, an active compensation device that actively compensates for noise occurring in a common mode in each of at least two high current paths connected to a first device is to compensate for the high current supplied by the second device to the first device. At least two high current paths to the device; a sensing unit that senses a common mode noise current in the high current path and generates a plurality of output signals in parallel based on the noise current; a plurality of amplifier units respectively corresponding to the plurality of output signals, which amplify each of the plurality of output signals to generate a plurality of amplified signals in parallel; It may include a compensator that draws a compensation current from the high current path based on the plurality of amplified signals or generates a compensation voltage on the high current path.

According to one embodiment, the sensing unit includes a transformer including a primary side disposed on the high current path and a secondary side where the plurality of output signals are generated in parallel, and on the secondary side of the sensing unit, A first wire connected to the input terminal of the first amplifier among the plurality of amplifiers and a second wire connected to the input terminal of the second amplifier among the plurality of amplifiers may each be wound.

According to one embodiment, the compensation unit includes a transformer including a primary side connected to the output terminal of each of the plurality of amplifiers and a secondary side connected to the high current path, and the primary side of the compensation unit includes, A third wire through which the current output from the first amplification unit among the plurality of amplification units flows and a fourth wire through which the current output from the second amplification unit among the plurality of amplification units flows may be each wound.

According to one embodiment, the plurality of amplifying units are composed of a first amplifying unit and a second amplifying unit, and the compensating unit is configured such that a wire connecting the output terminal of the first amplifying unit and the output terminal of the second amplifying unit is a primary side wire and is connected to the core. The high current path may pass through or be wound around the core as a secondary side wire.

According to one embodiment, the amplification unit is composed of a first amplification unit, a second amplification unit, a third amplification unit, and a fourth amplification unit, and the sensing unit generates a first output voltage and a second output voltage based on the noise current. Generating an output voltage, the first output voltage is differentially input to the first amplifier and the third amplifier, respectively, and the second output voltage is differentially input to the second amplifier and the fourth amplifier, respectively. is input, and the compensation unit generates a compensation voltage on the high current path based on the first amplification voltage output from the first amplification unit and the second amplification voltage output from the second amplification unit, and the active compensation The device may further include another compensation unit that draws compensation current from the high current path based on the third amplification voltage output from the third amplification unit and the fourth amplification voltage output from the fourth amplification unit. .

Other aspects, features and advantages in addition to those described above will become apparent from the following drawings, claims and detailed description of the invention.

According to various embodiments of the present invention as described above, the noise that can be accommodated and compensated for in the active compensation device can be increased. For example, even for the same DC voltage supply, the noise current that the active compensation device can accept and compensate for can become larger by using a parallel amplifier.

According to various embodiments of the present invention, it is possible to reduce stress on an amplifier in an active compensation device for sensing and compensating for the same noise.

Additionally, it is possible to provide a compensation device that does not significantly increase price, area, volume, or weight even in high-power systems.

Of course, the scope of the present invention is not limited by this effect.

Figure 1 schematically shows the configuration of a system including an active compensation device 100 according to an embodiment of the present invention.
FIG. 2 is a specific example of the active compensation device shown in FIG. 1 and schematically shows a system including an active compensation device 100A according to an embodiment.
FIG. 3 schematically shows a specific example of the active compensation device 100A shown in FIG. 2.
FIG. 4 is a specific example of the active compensation device shown in FIG. 1 and schematically shows a system including an active compensation device 100A-1 according to an embodiment.
FIG. 5 is a specific example of the active compensation device shown in FIG. 1 and schematically shows a system including an active compensation device 100B according to an embodiment.
FIG. 6 schematically shows an active compensation device 100B-1 as an example of the active compensation device 100B shown in FIG. 5.
FIG. 7 schematically shows an active compensation device 100B-2 as another example of the active compensation device 100B shown in FIG. 5.
Figure 8 schematically shows the functional configuration of an active compensation device 100C according to another embodiment of the present invention.
FIG. 9 schematically shows an active compensation device 100C-1 as an example of the active compensation device 100C shown in FIG. 8.
FIG. 10 schematically shows an active compensation device 100C-2 as another example of the active compensation device 100C shown in FIG. 8.
Figure 11 schematically shows the configuration of a system including an active compensation device 100D according to another embodiment of the present invention.
Figure 12 schematically shows the configuration of a system including an active compensation device 100E according to another embodiment of the present invention.
Figure 13 schematically shows the configuration of a system including an active compensation device 100F according to an embodiment of the present invention.
FIG. 14 schematically shows an active compensation device 100F-1 as an example of the active compensation device 100F shown in FIG. 13.
FIG. 15 schematically shows an active compensation device 100F-2 as another example of the active compensation device 100F shown in FIG. 13.

Since the present invention can be modified in various ways and can have various embodiments, specific embodiments will be illustrated in the drawings and described in detail in the detailed description. The effects and features of the present invention and methods for achieving them will become clear by referring to the embodiments described in detail below along with the drawings. However, the present invention is not limited to the embodiments disclosed below and may be implemented in various forms.

Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings. When describing with reference to the drawings, identical or corresponding components will be assigned the same reference numerals and redundant description thereof will be omitted. .

In the following embodiments, terms such as first and second are used not in a limiting sense but for the purpose of distinguishing one component from another component. In the following examples, singular terms include plural terms unless the context clearly dictates otherwise. In the following embodiments, terms such as include or have mean that the features or components described in the specification exist, and do not exclude in advance the possibility of adding one or more other features or components. In the drawings, the sizes of components may be exaggerated or reduced for convenience of explanation. In cases where an embodiment can be implemented differently, a specific process sequence may be performed differently from the described sequence. In the following embodiments, when areas, components, parts, units, modules, etc. are connected, not only are the areas, components, parts, units, and modules directly connected, but also the areas, components, parts, units, and modules are connected. This also includes cases where other areas, components, parts, units, and modules are interposed and indirectly connected.

Figure 1 schematically shows the configuration of a system including an active compensation device 100 according to an embodiment of the present invention. The active compensation device 100 is a noise current I _n (e.g., EMI noise current) and/ Alternatively, noise voltages (e.g. EMI noise voltage) can be actively compensated.

Referring to FIG. 1, the active compensation device 100 includes a sensing unit 120, a first amplification unit 131, a second amplification unit 132, an N-th amplification unit 133, and a compensation unit 160. may include. N is a natural number of 2 or more. That is, the active compensation device 100 according to various embodiments of the present invention may include two or more parallel amplifiers.

In this specification, the first device 300 may be various types of devices that use power supplied by the second device 200. For example, the first device 300 may be a load driven using power supplied by the second device 200. Additionally, the first device 300 stores energy using power supplied by the second device 200, and may be a load (eg, an electric vehicle) driven using the stored energy. However, it is not limited to this.

In this specification, the second device 200 may be a device of various types for supplying power to the first device 300 in the form of current and/or voltage. For example, the second device 200 may be a device that produces and supplies power, or it may be a device that supplies power produced by another device (for example, an electric vehicle charging device). Of course, the second device 200 may be a device that supplies stored energy. However, it is not limited to this. A power conversion device may be located on the first device 300 side. For example, by the switching operation of the power conversion device, common mode noise current I _n may be input onto the high current paths 111 and 112. Or, for example, the noise current leaked from the first device 300 flows into the large current paths 111 and 112 through the second device 200 via the ground (e.g., reference potential 1), thereby causing the noise current I _n may occur.

The noise current I _n occurring in the same direction on the large current paths 111 and 112 may be referred to as a common mode noise current. In addition, the common mode noise voltage (not shown) may be a voltage generated between the ground (e.g., reference potential 1) and the large current paths 111 and 112, rather than a voltage generated between the large current paths 111 and 112. .

For example, the first device 300 may correspond to a noise source, and the second device 200 may correspond to a noise receiver.

The two or more large current paths 111 and 112 may be paths for transmitting power supplied by the second device 200, that is, large currents I21 and I22, to the first device 300. For example, they may be power lines. For example, each of the two or more high current paths 111 and 112 may be a live line and a neutral line. At least a portion of the large current paths 111 and 112 may pass through the compensation device 100. The large currents I21 and I22 may be alternating currents having a frequency in the second frequency band. The second frequency band may be, for example, a 50Hz to 60Hz band.

Additionally, the two or more large current paths 111 and 112 may be paths through which the noise current I _n is transmitted from the first device 300 to the second device 200. Alternatively, it may be a path in which noise voltage is generated based on the ground (e.g., reference potential 1).

The noise current I _n (or noise voltage) may be input in common mode to each of the two or more large current paths 111 and 112. The noise current I _n may be a current unintentionally generated in the first device 300 due to various causes. For example, the noise current I _n may be a noise current due to parasitic capacitance between the first device 300 and the surrounding environment. Alternatively, the noise current I _n may be a noise current generated by a switching operation of the power conversion device of the first device 300. The noise current I _n and the noise voltage (not shown) may have a frequency in the first frequency band. The first frequency band may be a higher frequency band than the above-described second frequency band. The first frequency band may be, for example, a 150KHz to 30MHz band.

Meanwhile, the two or more large current paths 111 and 112 may include two paths as shown in FIG. 1, three paths (e.g., a three-phase, three-wire power system), or four paths (e.g., a three-phase, four-wire power system). line power system). The number of high current paths 111 and 112 may vary depending on the type and/or type of power source used by the first device 300 and/or the second device 200.

The sensing unit 120 detects the noise current I _n on two or more large current paths 111 and 112, and sends an output signal corresponding to the noise current I _n to the first, second and N amplifier units 131, 132 and 133. can be created. In other words, the sensing unit 120 may mean a means for detecting the noise current I _n on the large current paths 111 and 112. At least a portion of the large current paths 111 and 112 may pass through the sensing unit 120 for sensing the noise current I _n , but the portion where the output signal by sensing is generated within the sensing unit 120 is a large current. It may be insulated from the paths 111 and 112. For example, the sensing unit 120 may be implemented as a transformer. For example, the sensing unit 120 may be a CM choke on which power lines corresponding to the high current paths 111 and 112 are wound, and the wires on the amplification units 131 and 132 are wound over the CM choke. The sensing unit 120 is insulated from the large current paths 111 and 112 and sends an output signal (e.g., induced voltage or induced current) based on the noise current I _n on the large current paths 111 and 112 to the first and second , can be induced to the wires on the N-th amplification unit (131, 132, 133), respectively. That is, the sensing unit 120 can generate a plurality of output signals. The output signal (eg, induced voltage or induced current) may be an input signal of the first, second, and Nth amplification units 131, 132, and 133.

According to various embodiments of the present invention, an active compensation device may include a plurality of amplifier units. For example, the sensing unit 120 may generate an output signal corresponding to each of the plurality of amplifying units based on the noise current I _n on the large current paths 111 and 112. The output signal from the sensing unit 120 may be input to each of the plurality of amplifier units.

Although FIG. 1 shows the first, second, and Nth amplification units 131, 132, and 133, N is a natural number of 2 or more, so the amplification unit of the active compensation device according to various embodiments includes two first and second amplification units. Of course, it may be composed of only parts 131 and 132. Hereinafter, the first, second, and Nth amplification units 131, 132, and 133 will be described as examples.

According to one embodiment, the sensing unit 120 may be differentially connected to the input terminals of the first, second, and N-th amplifier units 131 and 132, respectively.

The first, second, and N-th amplifier units 131, 132, and 133 are electrically connected to the sensing unit 120 to amplify the output signal output by the sensing unit 120 and generate an amplified output signal. You can. In the present invention, 'amplification' by the amplification units 131, 132, and 133 may mean adjusting the size and/or phase of the amplification target. The amplification units 131, 132, and 133 may be implemented using various means and may include active elements. In one embodiment, each of the amplification units 131, 132, and 133 may include OP-AMP. For example, each of the amplifier units 131, 132, and 133 may include a plurality of passive elements such as resistors and capacitors in addition to the OP-AMP. In another embodiment, the amplification units 131, 132, and 133 may include a Bipolar Junction Transistor (BJT). For example, the amplification units 131, 132, and 133 may include a plurality of passive elements such as resistors and capacitors in addition to the BJT. However, it is not limited to this, and the means for 'amplification' described in the present invention can be used without limitation as the amplification units 131, 132, and 133 of the present invention. The reference potential of the amplification units 131, 132, and 133 (reference potential 2) and the reference potential of the compensation device 100 (reference potential 1) may be distinct potentials.

The amplifying units 131, 132, and 133 receive power from the third device 400, which is distinct from the first device 300 and/or the second device 200, and output the output signal from the sensing unit 120. can be amplified to generate an amplification current or an amplification voltage. At this time, the third device 400 may be a device that receives power from a power source unrelated to the first device 300 and the second device 200 and generates input power for the amplifiers 131, 132, and 133. Optionally, the third device 400 may be a device that receives power from any one of the first device 300 and the second device 200 to generate input power for the amplifiers 131, 132, and 133. there is.

The output signal (eg, current or voltage) amplified by the amplification units 131, 132, and 133 may be input to the compensation unit 160. For example, the first amplification unit 131 outputs a first amplification current (or a first amplification voltage) toward the compensator 160, and the second amplification unit 132 outputs a first amplification current (or first amplification voltage) toward the compensator 160. The second amplification current (or the second amplification voltage) is output, and the N-th amplification unit 133 may output the N-th amplification current (or the N-th amplification voltage) to the compensation unit 160.

The compensation unit 160 may generate a compensation current or compensation voltage based on the amplified signals output from the first, second, and N-th amplification units 131, 132, and 133, respectively.

According to one embodiment, the compensation unit 160 includes the first amplification current output from the first amplification unit 131, the second amplification current output from the second amplification unit 132, and the N-th amplification unit 133. ), a compensation current can be generated based on the Nth amplified current output from. The compensation current can offset or reduce the noise current I _n on the large current paths 111 and 112 by being injected into or drawn from the large current paths 111 and 112. The output side of the compensation unit 160 may be connected to the high current paths 111 and 112 to flow the compensation current to the high current paths 111 and 112, but may be insulated from the amplification unit 130. For example, the compensation unit 160 may include a compensation transformer for the insulation. The compensation current is injected into the large current paths 111 and 112 to cancel out the noise current I _n , or by allowing at least a portion of the noise current I _n to flow to the ground (e.g., reference potential 1), thereby generating the noise current I _n. can be reduced. In this case, the compensation unit 160 may correspond to current compensation. A detailed description of current compensation is described later in FIGS. 2 to 4 and FIGS. 14 to 15.

According to another embodiment, the compensation unit 160 operates the high current path 111 based on the first amplification voltage output from the first amplification unit 131 and the second amplification voltage output from the second amplification unit 132. , 112), a compensation voltage can be generated in series. The output side of the compensator 160 may generate a compensation voltage in series to the large current paths 111 and 112, but may be insulated from the amplification units 131 and 132. For example, the compensation unit 160 may be made of a compensation transformer for the insulation. The compensation voltage can have the effect of suppressing the noise current I _n flowing on the large current paths 111 and 112. In this case, the compensation unit 160 may correspond to voltage compensation. A detailed description of voltage compensation is described later in FIGS. 5 to 7.

The compensator 160 may be a feedforward type that compensates for noise input from the first device 300 at the front end, which is the power source. However, the present invention is not limited to this, and the active compensation device 100 may include a feedback type compensation unit that compensates for noise by returning to the rear end.

FIG. 2 shows a more specific example of the embodiment using two amplification units among the contents shown in FIG. 1, and schematically shows a system including an active compensation device 100A according to an embodiment of the present invention. 3 schematically shows a specific example of the active compensation device 100A.

2 and 3, the active compensation device 100A according to an embodiment of the present invention includes a sensing transformer 120A, a first amplifier 131A, a second amplifier 132A, and a compensation transformer ( 140A), and a compensation capacitor unit 150A.

According to one embodiment, the sensing transformer 120A is an example of the above-described sensing unit 120, and the first and second amplification units 131A and 132A are the above-described first and second amplification units 131 and 132. ) is an example. Therefore, the description of the above-described sensing unit 120 and the first and second amplifiers 131 and 132 may correspond to the description of the sensing transformer 120A and the first and second amplifiers 131A and 132A. there is.

Additionally, according to one embodiment, the above-described compensation unit 160 may be implemented with a compensation transformer 140A and a compensation capacitor unit 150A.

The active compensation device 100A can actively compensate for the noise current I _n input in common mode to each of the two large current paths 111 and 112 connected to the first device 300.

In one embodiment, as an example of the above-described sensing unit 120, the sensing transformer 120A is insulated from the high current paths 111 and 112 and generates noise current I _n or noise current I on the high current paths 111 and 112. It may be a means for detecting the voltage induced at both ends of the sensing transformer (120A) due to _n . The sensing transformer 120A may sense the voltage induced at both ends of the sensing transformer 120A due to noise current input from the first device 300 to the high current paths 111 and 112 (e.g., power lines).

The sensing transformer 120A is connected to the core C1, the primary side (e.g. primary winding) corresponding to the high current path 111 and 112 (e.g. power line), and the input terminal of the amplifier units 131A and 132A. May include a secondary side (e.g. secondary winding). For example, the high current path 111, 112 corresponding to the primary side passes through the core C1, and the wire on the amplifier side corresponding to the secondary side may be wound around the core C1. there is. However, it is not limited to this.

According to one embodiment, on the primary side of the sensing transformer 120A, the first high current path 111 and the second high current path 112 may pass through or be wound around the core C1, respectively.

According to one embodiment, the secondary side of the sensing transformer 120A is differentially connected to the first wire L1 and the input terminal of the second amplifier 132A, which are differentially connected to the input terminal of the first amplifier 131A. The second wire L2 may be wound around the core C1.

The sensing transformer 120A generates an induced current or induced voltage on the secondary side based on the magnetic flux density induced by the noise current I _n on the primary side where the large current paths 111 and 112 pass through the core C1. can do.

Specifically, the sensing transformer 120A has a magnetic flux density induced by the noise current I _n on the first large current path 111 (e.g., a live line) and a noise current on the second large current path 112 (e.g., a neutral line). The magnetic flux densities induced by I _n may be configured to overlap (or reinforce) each other. At this time, large currents (I21, I22) also flow on the large current paths (111, 112), and the magnetic flux density induced by the large current (I21) on the first large current path (111) and the large current (I22) on the second large current path (112) The magnetic flux densities induced by I22) can be configured to cancel each other. Also, as an example, the sensing transformer 120A may determine that the magnitude of the magnetic flux density induced by the noise current I _n in the first frequency band (e.g., a band ranging from 150 KHz to 30 MHz) is the size of the magnetic flux density in the second frequency band (e.g., a band ranging from 150 KHz to 30 MHz). For example, it may be configured to be larger than the size of the magnetic flux density induced by the large current (I21, I22) in the range of 50Hz to 60Hz.

In this way, the sensing transformer 120A is configured so that the magnetic flux densities induced by the large currents I21 and I22 cancel each other, so that only the noise current I _n can be sensed.

Meanwhile, according to an embodiment of the present invention, the sensing transformer 120A outputs a signal input to the first amplifier 131A and a signal input to the second amplifier 132A, respectively, based on the noise current I _n . can do. That is, the sensing transformer 120A can output a plurality of output signals in parallel from the secondary side.

For example, in the case of using two parallel amplifiers, the first induced current generated in the first wire (L1) of the secondary side of the sensing transformer (120A) may be differentially input to the first amplifier (131A), , The second induced current generated in the second wire (L2) on the secondary side of the sensing transformer (120A) may be differentially input to the second amplifier (132A).

Or, for example, depending on the configuration of the amplification units 131A and 132A, the first wire L1 on the secondary side of the sensing transformer 120A is connected to the input terminal of the first amplification unit 131A and the first amplification unit ( It may be placed on a path connecting the reference potential (reference potential 2) of 131A). That is, one end of the first wire (L1) on the secondary side is connected to the input terminal of the first amplification unit (131A), and the other end of the first wire (L1) on the secondary side is connected to the first amplification unit (131A). It can be connected to the reference potential (reference potential 2). Likewise, the second wire (L2) on the secondary side of the sensing transformer (120A) is on a path connecting the input terminal of the second amplifier (132A) and the reference potential (reference potential 2) of the second amplifier (132A). can be placed.

For example, in the sensing transformer 120A, if the turns ratio of the first wire L1 on the primary side and the secondary side is 1:N _sen1 , the current induced in the first wire L1, that is, the first amplification The current input to the unit 131A is I _n /2N _sen1 . In addition, in the sensing transformer 120A, if the turns ratio of the second wire L2 on the primary side and the secondary side is 1:N _sen2 , the current induced in the second wire L2, that is, the second amplifier 132A ) The current input is I _n /2N _sen2 . That is, the first and second amplifiers 131A and 132A can sense the noise current I _n in parallel by dividing it into two amplifiers.

Therefore, according to one embodiment, if the number of turns of the first wire (L1) and the second wire (L2) is the same, the input currents of the first amplification unit (131A) and the second amplification unit (132A) may be the same or correspond to each other. there is. That is, if the number of turns of the first wire (L1) and the second wire (L2) is the same, the output current by sensing the noise current I _n is divided by 1/2 and divided into 1/2 by the first amplification unit (131A) and the second amplification unit (131A). Each can be input as (132A). However, the present invention is not limited to this, and according to another embodiment, the number of turns of the first wire (L1) and the second wire (L2) may be different. In this case, the input current of the first amplifier 131A and the input current of the second amplifier 132A may also be different from each other.

The first amplifier 131A may amplify the first induced current induced in the first wire L1 on the secondary side according to the gain (eg, F1) of the first amplifier 131A. Likewise, the second amplifier 132A may amplify the second induced current induced in the second wire L2 on the secondary side according to the gain (e.g., F2) of the second amplifier 132A. there is.

According to one embodiment, the gain (F1) of the first amplifier (131A) and the gain (F2) of the second amplifier (132A) may be designed to have the same size. For example, it can be designed to satisfy F1 = -F2. In this case, the first amplification unit 131A and the second amplification unit 132A may operate complementary to each other. For example, the first amplifier 131A and the second amplifier 132A may operate in a full-bridge form.

However, the present invention is not limited to this, and according to one embodiment, the gain (F1) of the first amplifier (131A) and the gain (F2) of the second amplifier (132A) may be different from each other.

The compensation transformer 140A and the compensation capacitor unit 150A may correspond to the compensation unit 160 described above. The current amplified by the first amplifier 131A and the current amplified by the second amplifier 132A each flow to the primary side of the compensation transformer 140A.

The compensation transformer 140A may be a means for insulating the amplification units 131A and 132A including active elements from the high current paths 111 and 112. That is, the compensation transformer 140A is insulated from the high current paths 111 and 112 and generates a compensation current for injection into the high current paths 111 and 112 on the secondary side based on the amplified current flowing through the primary side. It may be a means for

The compensation transformer 140A has a core C2, a primary side (e.g. primary winding) connected to the output terminal of the amplification units 131A and 132A, and a secondary side connected to the high current paths 111 and 112 ( e.g. secondary winding). The compensation transformer 140A may have the primary side wires (L3, L4) and the secondary side wire wound around one core (C2). On the primary side of the compensation transformer 140A, the wire L3 through which the output current of the first amplifier 131A flows and the wire L4 through which the output current of the second amplifier 132A flows are connected to the core C2. Each may be in a coiled form.

The compensation transformer 140A may generate an induced current in the secondary side wire based on the magnetic flux density induced by the current flowing in the primary side.

At this time, the secondary side of the compensation transformer 140A may be placed on a path connecting the compensation capacitor unit 150A, which will be described later, and the reference potential (reference potential 1) of the active compensation device 100A. That is, one end of the secondary side is connected to the high current path (111, 112) through the compensation capacitor unit (150A), and the other end of the secondary side is connected to the reference potential (reference potential 1) of the active compensation device (100A). can be connected Meanwhile, the primary side of the compensation transformer (140A), the amplifier units (131A, 132A), and the secondary side of the sensing transformer (120A) have a reference potential (reference potential 2) that is distinct from the remaining components of the active compensation device (100A). ) can be connected to. The reference potential (reference potential 1) of the active compensation device (100A) and the reference potential (reference potential 2) of the amplification units (131A, 132A) can be distinguished.

In this way, the present invention uses a different reference potential from the remaining components for the component that generates the compensation current (or compensation voltage in the embodiment described later), and uses a separate power source, so that the component that generates the compensation current is insulated. It can be operated in an activated state, thereby improving the reliability of the active compensation device (100A).

Meanwhile, the primary side of the compensation transformer (140A) has a third wire (L3) through which the current output from the first amplification unit (131A) flows and a fourth wire (L4) through which the current output from the second amplification unit (132A) flows. Each of these can be wound.

According to one embodiment, F1* I _n /2N _sen1 , which is the output current of the first amplifier 131A, may flow through the third wire L3. Additionally, F2*I _n /2N _sen2 , which is the output current of the second amplifier 132A, may flow through the fourth wire L4.

For example, in the compensation transformer (140A), the turns ratio between the third wire (L3) on the primary side and the secondary side is 1:N _inj1 , and the turns ratio between the fourth wire (L4) on the primary side and the secondary side is 1:N inj1. :N _inj2 , the current induced in the secondary side of the compensation transformer (140A) is 'F1*I _n /2(N _sen1 *N _inj1 )+F2* I _n /2(N _sen2 *N _inj2 )' It can be the same.

According to one embodiment, the first amplifier 131A and its input and output terminals and the second amplifier 132A and its input and output terminals may be symmetrical to each other (F1 = F2, N _sen1 =N _sen2 , N _inj1 =N _inj2 ). However, the present invention is not limited to this.

The current (i.e., secondary side current) converted through the compensation transformer (140A) is injected as a compensation current (I _c ) into the high current paths (111, 112) (e.g., power line) through the compensation capacitor unit (150A), or can be withdrawn In one embodiment, when the compensation current (I _c ) is injected into the large current path (111, 112), in order to cancel the noise current I _n , the compensation current (I _c ) may be out of phase with the noise current I _n . . In another embodiment, when the compensation current (I _c ) is drawn from the large current paths 111 and 112, the compensation current (I _c ) may be proportional to the noise current I _n . At least a portion of the noise current I _n may be drawn as a compensation current (I _c ) and flow to the ground (i.e., reference potential 1). Therefore, the noise current I _n can be reduced.

As described above, the compensation capacitor unit 150A may provide a path through which the current generated on the secondary side of the compensation transformer 140A flows to each of the high current paths 111 and 112.

The compensation capacitor unit 150A includes two Y-capacitors (Y-capacitor, Y-cap), one end of which is connected to the secondary side of the compensation transformer 140A, and the other end of which is connected to the high current paths 111 and 112. ) may include. One end of each of the two Y-caps shares a node connected to the secondary side of the compensation transformer (140A), and the opposite ends of each of the two Y-caps are connected to the first high current path 111 and the second high current path, respectively. It may have a node connected to (112).

The compensation capacitor unit 150A may flow the compensation current Ic induced by the compensation transformer 140A to or draw the compensation current Ic from the power line. Through this, the active compensation device 100A can reduce noise. .

The first and second amplifiers 131A and 132A of the active compensation device 100A according to an embodiment of the present invention supply the same DC voltage (e.g., the third device 400) using a full-bridge circuit. It can also accept and generate a current swing that is twice that of the voltage supply.

Meanwhile, referring to FIG. 3, the active compensation device 100A according to an embodiment of the present invention may further include a decoupling capacitor unit 170A.

The decoupling capacitor unit 170A is disposed between the above-described compensation unit 160 and the second device 200, with one end connected to the reference potential 1 and the other end connected to the high current paths 111 and 112, respectively. It may consist of two Y-capacitors connected.

The decoupling capacitor unit 170A may be a means for ensuring that the output impedance from the above-described compensation unit 160 to the second device 200 satisfies a predetermined condition. In other words, the decoupling capacitor unit 170A is a means for outputting the compensation current to the second device 200 along at least two large current paths 111 and 112 and preventing it from returning to the active compensation device 100A. It can be.

For example, the impedance of the second device 200 may vary arbitrarily depending on the surrounding conditions of the power system and filter. For example, home appliances may have various impedance values depending on their components (eg, motor, heater, light emitting device, etc.). The decoupling capacitor unit 170A prevents the output performance of the compensation current of the active compensation device 100 from significantly changing depending on changes in the impedance value of the second device 200, allowing it to be applied in various systems.

Meanwhile, the active compensation device 100A according to this embodiment may be a feedforward type compensation filter that compensates for noise input from the first device 300 at the front end, which is the power source. Additionally, the active compensation device (100A) may correspond to current compensation.

Meanwhile, the amplification unit according to the present invention is not limited to consisting of a first amplification unit 131A and a second amplification unit 132A, and as shown in FIG. 4, the active compensation device 100A-1 according to an embodiment may include a plurality of amplification units including a first amplification unit 131A, a second amplification unit 132A, and an N-th amplification unit 133A. The plurality of amplifiers 131A, 132A, and 133A may operate in parallel with each other. For example, the plurality of amplifier units 131A, 132A, and 133A may be connected in parallel to the sensing transformer 120A and the compensation transformer 140A, respectively. The method in which the N-th amplifier 133A is connected to the sensing transformer 120A and the compensation transformer 140A is that the first and second amplifiers 131A and 132A are connected to the sensing transformer 120A and the compensation transformer 140A. It may correspond to the way it is connected.

For example, referring to FIG. 4, the core C1 of the sensing transformer 120A has an N-th wire (not shown) that corresponds to the secondary side and is differentially connected to the input terminal of the N-th amplifier 133A. This can be further wound. For example, the N-th induced current generated from the N-th wire (not shown) on the secondary side of the sensing transformer 120A may be differentially input to the N-th amplifier 133A.

Additionally, the N-th amplification unit 133A may output the output current of the N-th amplification unit 133A based on the input N-th induced current and the current gain of the N-th amplification unit 133A. The wire through which the output current of the N-th amplifier 133A flows may be additionally wound around the core C2 of the compensation transformer 140A. In this case, the compensation transformer 140A may generate a compensation current at the output current of each of the first, second, and N-th amplifier units 131A, 132A, and 133A and a turns ratio corresponding to each output terminal.

FIG. 5 shows a more specific example of the embodiment shown in FIG. 1 and schematically shows a system including an active compensation device 100B according to an embodiment of the present invention.

FIG. 6 schematically shows an active compensation device 100B-1 as an example of the active compensation device 100B shown in FIG. 5, and FIG. 7 is another example of the active compensation device 100B shown in FIG. 5. By way of example, an active compensation device 100B-2 is schematically shown.

Referring to FIG. 5, the active compensation device 100B may include a sensing unit 120B, a first amplification unit 131B, a second amplification unit 132B, and a compensation transformer 160B. The sensing unit 120B, the first and second amplification units 131B and 132B, and the compensation transformer 160B are respectively the above-described sensing unit 120, the first and second amplification units 131 and 132, and the compensation unit ( 160) is an example.

The active compensation device 100B can actively compensate for the noise current I _n input in common mode to each of the two large current paths 111 and 112 connected to the first device 300.

The sensing unit 120B may sense the noise current I _n on the large current path 111 and 112, and output an output signal based on the noise current I _n to the first and second amplifier units 131B and 132B, respectively. . The sensing unit 120B may output a first output signal and a second output signal based on the noise current I _n , and the first output signal is input to the first amplifier 131B and the second output signal is It may be input to the second amplifier 132B. For example, the first output signal may be input as a differential voltage to the input terminal of the first amplifier 131B, and the second output signal may be input as a differential voltage to the input terminal of the second amplifier 132B. Depending on the configuration of the sensing unit 120B, the first output signal and the second output signal may be the same or different from each other.

The first amplification unit 131B may output a first output voltage V1 corresponding to the product of the voltage input to the first amplification unit 131B and the voltage gain of the first amplification unit 131B. The second amplification unit 132B may output a second output voltage V2 corresponding to the product of the voltage input to the second amplification unit 132B and the voltage gain of the second amplification unit 132B. The first and second output voltages V1 and V2 may represent potentials for reference potential 2 of the amplification units 131B and 132B, respectively.

In the active compensation device 100B according to an embodiment of the present invention, the difference between the first output voltage V1 and the second output voltage V2 may be input to the compensation transformer 160B. That is, the difference between the first output voltage (V1) and the second output voltage (V2) may correspond to the input voltage of the compensation transformer (160B).

The compensation transformer 160B may be an example of the compensation unit 160 described above. In other words, the above-described compensation unit 160 can be implemented as a compensation transformer 160B in the active compensation device 100B according to an embodiment.

The voltage applied to the primary side of the compensation transformer 160B may correspond to the difference between the output voltage V1 of the above-described first amplifier 131B and the output voltage of the second amplifier 131B.

The compensation transformer 160B may induce a compensation voltage in series on the high current paths 111 and 112 on the secondary side, based on the voltage applied to the primary side. The compensation voltage generated in series on the large current paths 111 and 112 may have the effect of suppressing the noise current I _n flowing on the large current paths 111 and 112.

In FIG. 5, the compensation transformer 160B is shown as generating a compensation voltage at the front end of the power source (that is, between the sensing unit 120B and the second device 200), but the present invention is not limited thereto. For example, the compensation transformer 160B may generate a compensation voltage on the high current paths 111 and 112 between the sensing unit 120B and the first device 300.

Hereinafter, with reference to FIGS. 6 and 7, active compensation devices 100B-1 and 100B-2, which are examples of the active compensation device 100B, will be described.

The amplification units 131B and 132B and the compensation transformer 160B of the compensation device 100B-1 and 100B-2 may correspond to each other. According to one embodiment, the sensing unit 120B-1 of the compensation device 100B-1 and the sensing unit 120B-2 of the compensation device 100B-2 may be different from each other.

The sensing units 120B-1 and 120B-2 of the compensation devices 100B-1 and 100B-2 according to an embodiment include a CM choke around which the first high current path 111 and the second high current path 112 are wound. Yes, the secondary side wire may be overwrapped. In this way, when the sensing units (120B-1, 120B-2) are formed using the CM choke, the sensing units (120B-1, 120B-2) not only perform the sensing and voltage transformation functions, but also act as a passive filter as the CM choke. can play a role.

That is, when the sensing units (120B-1, 120B-2) are formed by wrapping the secondary wire around the CM choke, the sensing units (120B-1, 120B-2) sense and transform the noise current I _n . Together, they can simultaneously play a role in suppressing or blocking the noise current I _n .

The primary side of the sensing units 120B-1 and 120B-2 may be a winding in which the first high current path 111 and the second high current path 112 are wound around the CM choke, respectively.

Meanwhile, in one embodiment (see FIG. 6), one wire may be wrapped around the CM choke on the secondary side of the sensing unit 120B-1. The single wire may be connected in parallel to the input terminal of the first amplifier 131B and simultaneously connected in parallel to the input terminal of the second amplifier 132B. For example, the voltage (V _sen ) induced on the secondary side of the sensing unit (120B-1) is differentially input to the input terminal of the first amplifying unit (131B), and at the same time is input to the input terminal of the second amplifying unit (132B). Can be entered differentially.

For example, in the embodiment of FIG. 6, the voltage (V _sen ) induced on the secondary side of the sensing unit 120B-1 is the same in the first amplification unit 131B and the second amplification unit 132B. can be entered.

The first amplification unit 131B produces a first output voltage (V1) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the first amplification unit (131B) by the voltage gain (G1) of the first amplification unit (131B). can be output. The second amplification unit 132B generates a second output voltage (V2) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the second amplification unit (132B) by the voltage gain (G2) of the second amplification unit (132B). can be output. The first output voltage V1 and the second output voltage V2 may be potentials based on reference potential 2 of the amplification units 131B and 132B. The difference between the first output voltage (V1) and the second output voltage (V2) may be the input voltage of the compensation transformer (160B). According to one embodiment of FIG. 6, G1=-G2 may be satisfied.

Meanwhile, in another embodiment (see FIG. 7), on the secondary side of the sensing unit 120B-2, wires corresponding to the first amplification unit 131B and the second amplification unit 132B are respectively connected to the CM choke. It can be added. For example, the secondary side of the sensing unit 120B-2 is differentially connected to the first wire L11 and the input terminal of the second amplifying unit 132A, which are differentially connected to the input terminal of the first amplifying unit 131B. The second wire L12 may be wound around each of the CM chokes.

For example, the voltage V _sen1 induced in the first wire (L11) of the secondary side of the sensing unit (120B-2) is differentially input to the first amplifying unit (131B), and the secondary side of the sensing unit (120B-2) The voltage V _sen2 induced in the second wire L12 may be differentially input to the second amplifier 132B.

In the embodiment of FIG. 7, the differential input voltage V _sen1 of the first amplifier 131B and the differential input voltage V _sen2 of the second amplifier 132B are the number of turns of the first wire L11 on the secondary side and It can be generated based on the number of turns of the second wire (L12) on the secondary side. According to one embodiment, the first wire L11 and the second wire L12 may be wound to generate input voltages of opposite phases to each amplification unit 131B and 132B. For example, if the number of turns of the first wire (L11) and the second wire (L12) on the secondary side are the same, the differential input voltages V _sen1 and V _sen2 of each amplification unit (131B, 132B) are the same and opposite in size. It could be a phase. That is, V _sen1 =-V _sen2 . For example, the input voltage V _sen1 of the first amplification unit 131B is the voltage induced on the primary side of the sensing unit 120B-2 (i.e., across the CM choke) and the voltage between the primary and secondary sides. It may correspond to a value multiplied by the turns ratio of the first wire (L11). The input voltage V _sen2 of the second amplifying unit 132B is the voltage induced in the primary side of the sensing unit 120B-2 multiplied by the turns ratio of the second wire L12 on the primary side and the secondary side. It can correspond to . According to one embodiment of FIG. 7, G1=+G2 can be satisfied.

The first amplification unit 131B generates a first output voltage V1 corresponding to the input voltage V _sen1 of the first amplification unit 131B multiplied by the voltage gain G1 of the first amplification unit 131B. Can be printed. The second amplification unit 132B produces a second output voltage (V2) corresponding to the value obtained by multiplying the differential input voltage (V _sen2 ) of the second amplification unit (132B) by the voltage gain (G2) of the second amplification unit (132B). can be output. The first output voltage (V1) and the second output voltage (V2) are potentials based on reference potential 2 of the amplification units (131B, 132B). The difference between the first output voltage (V1) and the second output voltage (V2) may be the input voltage of the compensation transformer (160B).

Meanwhile, referring again to FIGS. 6 and 7 together, the compensation transformer 160B may have a structure in which the primary side wire and the secondary side wire pass through one core or are wound at least once. The primary side wire may be a wire connecting the output terminal of the first amplification unit (131B) and the output terminal of the second amplification unit (132B). The secondary side wires may correspond to high current paths 111 and 112.

The potential difference between the output of the first amplifier 131B and the output of the second amplifier 132B becomes the primary side voltage of the compensation transformer 160B, and the compensation transformer 160B is the secondary side voltage based on the potential difference. A compensation voltage V _inj1 can be generated in series on the high current paths 111 and 112.

The compensation voltage V _inj1 induced in the secondary side of the compensation transformer 160B is the potential difference between the output of the first amplifier 131B and the output of the second amplifier 132B, and the primary side and the secondary It can correspond to the value multiplied by the turns ratio of each side.

The active compensation devices (100B-1, 100B-2) according to one embodiment are capable of performing voltage compensation (V _inj1 ) on the high current paths (111, 112), which are applied to the sensing units (120B-1, 120B-2). It can provide an effect corresponding to the effect of increasing the inductance of the CM choke, thereby suppressing the noise current I _n (L boost type).

Meanwhile, the compensation devices 100B-1 and 100B-2 according to one embodiment may further include a decoupling capacitor unit 170B.

According to one embodiment, the decoupling capacitor unit 170B may be disposed between the sensing units 120B-1 and 120B-2 and the first device 300. The decoupling capacitor unit 170B may be composed of two Y-capacitors, one end of which is connected to the reference potential 1 and the other end of which are connected to the high current paths 111 and 112, respectively.

Figure 8 schematically shows the functional configuration of an active compensation device 100C according to another embodiment of the present invention.

FIG. 9 schematically shows an active compensation device 100C-1 as an example of the active compensation device 100C shown in FIG. 8, and FIG. 10 is another example of the active compensation device 100C shown in FIG. 8. By way of example, an active compensation device 100C-2 is schematically shown. 8 to 10, the first device 300, the second device 200, the third device 400, reference potential 1, and reference potential 2 are omitted.

Referring to FIG. 8, the active compensation device 100C includes a sensing unit 120C, first, second, third, and fourth amplification units 131C, 132C, 133C, and 134C, a first compensation unit 160C, and a first compensation unit 160C. 2 May include a compensation unit 190C.

The active compensation device 100C can actively compensate for the noise current I _n generated in common mode on the large current paths 111 and 112.

The sensing unit 120C is an example of the above-described sensing unit 120 and may correspond to the description of the sensing unit 120. The sensing unit 120C senses the noise current I _n input from the large current paths 111 and 112, which are the primary side of the sensing unit 120C, and outputs an output signal based on the noise current I _n to the first, second and third signals. , 4 can be output to the amplification units (131C, 132C, 133C, and 134C), respectively. For example, the sensing unit 120C may output four output signals corresponding to each amplifying unit 131C, 132C, 133C, and 134C based on the noise current I _n . Each of the four output signals may be input to the first, second, third, and fourth amplifier units (131C, 132C, 133C, and 134C), respectively.

For example, the first and second amplifiers 131C and 132C are configured to generate the input signal of the first compensation unit 160C, and the third and fourth amplifiers 133C and 134C are configured to generate the input signal of the second compensation unit 190C. ) is a configuration for generating an input signal.

According to one embodiment, the input terminal of the first amplifier 131C and the input terminal of the third amplifier 133C may be connected in parallel. For example, the differential input voltage of the first amplifier 131C and the differential input voltage of the third amplifier 133C may be the same. Meanwhile, the output signal (e.g., current or voltage) of the first amplification unit 131C and the output signal (e.g., current or voltage) of the third amplification unit 133C are It may vary depending on the gain of each unit 133C. Meanwhile, the output signal of the first amplification unit 131C may be connected to the input side of the first compensator 160C, and the output signal of the third amplification unit 133C may be connected to the input side of the second compensator 190C. You can.

According to one embodiment, the input terminal of the second amplifier 132C and the input terminal of the fourth amplifier 134C may be connected in parallel. For example, the differential input voltage of the second amplifier 132C and the differential input voltage of the fourth amplifier 134C may be the same. Meanwhile, the output signal (e.g., current or voltage) of the second amplification unit 132C and the output signal (e.g., current or voltage) of the fourth amplification unit 134C are It may vary depending on the gain of each unit 134C. Meanwhile, the output signal of the second amplification unit 132C may be connected to the input side of the first compensator 160C, and the output signal of the fourth amplification unit 134C may be connected to the input side of the second compensator 190C. You can.

According to one embodiment, the difference between the output voltage V11 of the first amplification unit 131C and the output voltage V12 of the second amplification unit 132C may correspond to the input voltage of the first compensator 160C. there is. According to one embodiment, the difference between the output voltage (V13) of the second amplification unit (133C) and the output voltage (V14) of the fourth amplification unit (134C) may correspond to the input voltage of the second compensator (190C). there is.

Meanwhile, the output voltages (V11, V12, V13, V14) of the amplification units (131C, 132C, 133C, 134C) may represent the voltage based on the reference potential 2 of the amplification units (131C, 132C, 133C, 134C). there is.

According to one embodiment, the first compensation unit 160C determines the high current path based on the difference between the output voltage V11 of the first amplification unit 131C and the output voltage V12 of the second amplification unit 132C. A compensation voltage can be induced in series on (111, 112). The compensation voltage generated in series on the large current paths 111 and 112 may have the effect of suppressing the noise current I _n flowing on the large current paths 111 and 112.

According to one embodiment, the second compensating unit 190C operates a high current path ( Compensation current can be drawn from 111, 112) to the ground (e.g., reference potential 1). The compensation current may have the effect of reducing the size of the noise current I _n flowing on the large current paths 111 and 112. A detailed description of the second compensation unit 190C will be described later with reference to FIGS. 9 and 10.

Hereinafter, with reference to FIGS. 9 and 10, active compensation devices 100C-1 and 100C-2, which are examples of the active compensation device 100C, will be described.

Amplification units (131C, 132C, 133C, 134C), first compensation transformer (161C), second compensation transformer (191C), and compensation capacitor unit (192C) of compensation device (100C-1) and compensation device (100C-2) ) can correspond to each other. Meanwhile, the above-described first compensation unit 160C includes a first compensation transformer 161C, and the second compensation unit 190C includes a second compensation transformer 191C and a compensation capacitor unit 192C.

According to one embodiment, the sensing unit 120C-1 of the compensation device 100C-1 and the sensing unit 120C-2 of the compensation device 100C-2 may be different from each other.

The sensing units 120C-1 and 120C-2 of the compensation devices 100C-1 and 100C-2 according to an embodiment are CM chokes around which the first high current path 111 and the second high current path 112 are wound. Yes, the secondary side wire may be overwrapped. In this way, when the sensing units (120C-1, 120C-2) are formed using the CM choke, the sensing units (120C-1, 120C-2) not only perform the sensing and transforming functions, but also function as a passive filter as the CM choke. can play a role.

That is, when the sensing units (120C-1, 120C-2) are formed by wrapping the secondary wire around the CM choke, the sensing units (120C-1, 120C-2) sense and transform the noise current I _n . Together, they can simultaneously play a role in suppressing or blocking the noise current I _n .

The primary side of the sensing units 120C-1 and 120C-2 may be a winding in which the first high current path 111 and the second high current path 112 are wound around the CM choke, respectively.

Meanwhile, in one embodiment (see FIG. 9), one wire may be wrapped around the CM choke on the secondary side of the sensing unit 120C-1. The single wire may be connected in parallel to the input terminals of the first, second, third, and fourth amplifier units (131C, 132C, 133C, and 134C). For example, the voltage (V _sen ) induced on the secondary side of the sensing unit (120C-1) is differentially applied to the input terminals of all the first, second, third, and fourth amplifier units (131C, 132C, 133C, and 134C). can be entered.

For example, in the embodiment of Figure 9, the voltage (V _sen ) induced on the secondary side of the sensing unit (120C-1) is the first and third amplification units (131C and 133C) and the second and fourth amplification units. The same can be entered in (132C, 134C).

The first amplifier (131C) produces a first output voltage (V11) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the first amplifier (131C) by the voltage gain (G1) of the first amplifier (131C). can be output. The second amplification unit 132C produces a second output voltage (V12) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the second amplification unit 132C by the voltage gain (G2) of the second amplification unit 132C. can be output. The first output voltage V11 and the second output voltage V12 may be potentials based on the reference potential (reference potential 2) of the amplification units 131C and 132C. The difference between the first output voltage (V11) and the second output voltage (V12) may be the input voltage of the first compensation transformer (161C). According to one embodiment of FIG. 9, G1=-G2 may be satisfied.

The third amplification unit 133C produces a third output voltage (V13) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the third amplification unit (133C) by the voltage gain (G3) of the third amplification unit (133C). can be output. The fourth amplification unit 134C produces a fourth output voltage (V14) corresponding to the value obtained by multiplying the differential input voltage (V _sen ) of the fourth amplification unit 134C by the voltage gain (G4) of the fourth amplification unit 134C. can be output. The third output voltage V13 and the fourth output voltage V14 may be potentials based on the reference potential (reference potential 2) of the amplification units 133C and 134C. The difference between the third output voltage (V13) and the fourth output voltage (V14) may be the input voltage of the second compensation transformer (191C). According to one embodiment of FIG. 9, G3=-G4 may be satisfied.

Meanwhile, in another embodiment (see FIG. 10), the secondary side of the sensing unit 120C-2 includes a first wire L21 and a second wire connected in parallel to the input terminals of the first and third amplification units 131C and 133C. , 4 A second wire (L22) connected in parallel to the input terminals of the amplification units (132C, 134C) may be each wrapped around the CM choke.

For example, the voltage V _sen1 induced in the first wire (L21) of the secondary side of the sensing unit (120C-2) may be differentially input to the first amplification unit (131C) and the third amplification unit (133C), respectively. . The voltage V _sen2 induced in the second wire L22 on the secondary side of the sensing unit 120C-2 may be differentially input to the second amplification unit 132C and the fourth amplification unit 134C.

In the embodiment of FIG. 10, the input voltages V _sen1 and V _sen2 are the number of turns of the first wire (L21) on the secondary side of the sensing unit (120C-2) and the number of turns of the second wire (L22) on the secondary side. It can occur based on the player. According to one embodiment, the first wire (L21) and the second wire (L22) are input voltages of opposite phases to the first and third amplification units (131C and 133C) and the second and fourth amplification units (132C and 134C). It can be wound to generate .

For example, if the number of turns of the first wire (L21) and the second wire (L22) on the secondary side are the same, the differential input voltages V _sen1 and V _sen2 of each amplification unit (131C, 132C, 133C, 134C) are different from each other. They can be of equal size and opposite phase. That is, V _sen1 =-V _sen2 . For example, the input voltage V _sen1 of the first and third amplification units 131C and 133C is the voltage induced on the primary side of the sensing unit 120C-2 (i.e., across the CM choke). It may correspond to a value multiplied by the turns ratio of the first wire (L21). The input voltage V _sen2 of the second and fourth amplifier units 132C and 134C is the voltage induced in the primary side of the sensing unit 120C-2 multiplied by the turns ratio of the primary side to the second wire L12. It can correspond to .

The first amplification unit 131C generates a first output voltage V11 corresponding to the value obtained by multiplying the input voltage V _sen1 of the first amplification unit 131C by the voltage gain G1 of the first amplification unit 131C. Can be printed. The second amplification unit 132C produces a second output voltage (V12) corresponding to the value obtained by multiplying the differential input voltage (V _sen2 ) of the second amplification unit 132C by the voltage gain (G2) of the second amplification unit 132C. can be output. The third amplification unit 133C generates a third output voltage V13 corresponding to the input voltage V _sen1 of the third amplification unit 133C multiplied by the voltage gain G3 of the third amplification unit 133C. Can be printed. The fourth amplification unit 134C produces a fourth output voltage (V14) corresponding to the value obtained by multiplying the differential input voltage (V _sen2 ) of the fourth amplification unit 134C by the voltage gain (G4) of the fourth amplification unit 134C. can be output. According to one embodiment of FIG. 10, G1=+G2 and G3=+G4 can be satisfied.

The output voltages V11, V12, V13, and V14 are potentials based on reference potential 2 of the amplification units (131C, 132C, 133C, and 134C). The difference between the first output voltage (V11) and the second output voltage (V12) may be the input voltage of the first compensation transformer (161C). The difference between the third output voltage (V13) and the fourth output voltage (V14) may be the input voltage of the second compensation transformer (191C).

Meanwhile, referring again to FIGS. 9 and 10 together, the first compensation transformer 161C may have a structure in which the primary side wire and the secondary side wire pass through one core or are wound at least once. The primary side wire may be a wire connecting the output terminal of the first amplifier 131C and the output terminal of the second amplifier 132C. The secondary side wires may correspond to high current paths 111 and 112.

The potential difference (e.g., V11-V12) between the output of the first amplifier 131C and the output of the second amplifier 132C becomes the primary side voltage of the first compensation transformer 161C, and the first compensation transformer 161C ) can generate a compensation voltage V _inj1 in series on the high current paths 111 and 112 on the secondary side based on the potential difference. The compensation voltage V _inj1 may correspond to a value obtained by multiplying the voltage on the primary side of the first compensation transformer 161C by the turns ratio of the primary side and the secondary side.

The active compensation devices (100C-1, 100C-2) according to one embodiment are capable of performing voltage compensation (V _inj1 ) on the large current paths (111, 112), which is applied to the sensing units (120C-1, 120C-2). It can provide an effect corresponding to the effect of increasing the inductance of the CM choke, thereby suppressing the noise current I _n (L boost type).

Meanwhile, the second compensation transformer 191C and the compensation capacitor unit 192C may correspond to the above-described second compensation unit 190C. The second compensation transformer (191C) is insulated from the large current paths (111, 112) and generates a compensation current on the secondary side for injection into the large current paths (111, 112) based on the voltage generated on the primary side. It may be a means to do so.

According to one embodiment, the second compensation transformer (191C) has a primary side (e.g., primary winding) connected to the output terminals of the second and fourth amplifiers (132C, 134C), and a high current path (111, 112) It may include a connected secondary side (e.g. secondary winding). For example, a wire connecting the output terminal of the second amplifier 132C and the output terminal of the fourth amplifier 134C may be wound on the primary side of the second compensation transformer 191C.

The second compensation transformer 191C may have a structure in which the primary side wire and the secondary side wire pass through one core or are wound at least once.

The secondary side of the second compensation transformer 191C may be placed on a path connecting the compensation capacitor unit 192C and the reference potential (reference potential 1) of the compensation devices 100C-1 and 100C-2. That is, one end of the secondary side is connected to the high current path (111, 112) through the compensation capacitor unit (192C), and the other end of the secondary side is connected to the reference potential ( It can be connected to the reference potential 1).

The primary side voltage of the second compensation transformer 191C may be the potential difference (eg, V13-V14) between the output of the third amplifier 133C and the output of the fourth amplifier 134C. The second compensation transformer 191C may generate an induced voltage V _inj2 on the secondary side based on the primary side voltage (eg, V13-V14) and the turns ratio. The induced voltage V _inj2 may correspond to the product of the primary side voltage (eg, V13-V14) and the turns ratio.

The voltage V _inj2 converted through the second compensation transformer 191C may draw a compensation current I _c from the high current paths 111 and 112 (eg, power line) through the compensation capacitor unit 192C.

The compensation capacitor unit 192C may provide a path through which at least a portion of the noise current on the large current paths 111 and 112 is drawn to the secondary side of the second compensation transformer 191C.

The compensation capacitor unit 192C includes two Y-capacitors (Y-capacitors), one end of which is connected to the secondary side of the second compensation transformer 191C, and the other end of which are connected to the high current paths 111 and 112, respectively. Y-cap) may be included.

The compensation capacitor unit 192C may draw compensation current I _c from the power line based on the voltage V _inj2 induced by the second compensation transformer 191C. Since the compensation current I _c compensates (or cancels out) the noise current on the high current paths 111 and 112, the compensation devices 100C-1 and 100C-2 can reduce noise.

Figure 11 schematically shows the configuration of a system including an active compensation device 100D according to another embodiment of the present invention. Hereinafter, description of content that overlaps with the content described with reference to FIGS. 1 to 10 will be omitted.

Referring to FIG. 11, the active compensation device 100D can actively compensate for the noise current I _n input in common mode to each of the high current paths 111D, 112D, and 113D connected to the first device 300D.

For this purpose, the active compensation device (100D) includes three large current paths (111D, 112D, 113D), a sensing unit (120D), and a first, second, and N amplification unit arranged in parallel on the output side of the sensing unit (120D). (131D, 132D, 133D), and a compensation unit (160D) disposed on the output side of the first, second, and N amplification units (131D, 132D, 133D) (N is a natural number of 2 or more). .

In contrast to the active compensation device 100 according to the embodiment described in FIG. 1, the active compensation device 100D according to the embodiment shown in FIG. 11 includes three large current paths 111D, 112D, and 113D, Accordingly, there is a difference between the primary side of the sensing unit 120D and the secondary side of the compensation unit 160D.

The active compensation device 100D may include a first large current path 111D, a second large current path 112D, and a third large current path 113D that are distinct from each other. According to one embodiment, the first high-current path 111D may be an R-phase power line, the second high-current path 112D may be an S-phase power line, and the third high-current path 113D may be a T-phase power line. The noise current I _n may be input in common mode to each of the first large current path 111D, the second large current path 112D, and the third large current path 113D.

The sensing unit 120D may correspond to the above-described sensing transformer 120A and the sensing unit 120B (eg, 120B-1, 120B-2). However, the primary side of the sensing unit 120D may be disposed on the first large current path 111D, the second large current path 112D, and the third large current path 113D.

The secondary side of the sensing unit 120D has a first output corresponding to the input of the first amplifying unit 131D, a second output corresponding to the input of the second amplifying unit 132D, and a second output corresponding to the input of the N-th amplifying unit 133D. The third output corresponding to the input can be output in parallel.

The input signal of the primary side of the compensator 160D may be based on the output signal output from each of the first, second, and N amplification units 131D, 132D, and 133D.

The compensation unit 160D may correspond to the compensation transformer 140A and the compensation capacitor unit 150A, which perform current compensation as described above. Alternatively, the compensation unit 160D may correspond to the compensation transformer 160B, which performs voltage compensation as described above.

In addition, the sensing unit 120D corresponds to the above-described sensing unit 120C, the compensating unit 160D corresponds to the above-described first compensating unit 160C, and the active compensation device 100D corresponds to the second compensating unit 100D. It may further include a compensation unit that performs voltage compensation corresponding to (190C).

Meanwhile, the secondary side of the compensator 160D may be disposed in each of the first large current path 111D, the second large current path 112D, and the third large current path 113D.

According to one embodiment, the compensator 160D operates three high current paths 111D, 112D, and 113D based on the voltages (i.e., primary side voltages) output from the first and second amplification units 131D and 132D, respectively. ) A compensation voltage (i.e., secondary side voltage) can be generated in series for each. In this case, for example, the compensation unit 160D may include a compensation transformer.

According to another embodiment, the compensation unit 160D is based on the induced current generated based on the current output from the first, second, and N amplification units 131D, 132D, and 133D, respectively, to the first high current path 111D, A compensation current may be injected into each of the second large current path 112D and the third large current path 113D, or the compensation current may be drawn at a reference potential of 1. In this case, for example, the compensation unit 160D may include a compensation transformer and a compensation capacitor unit.

The active compensation device 100D according to this embodiment can compensate for common mode noise on the power line of a three-phase, three-wire power system.

Figure 12 schematically shows the configuration of a system including an active compensation device 100E according to another embodiment of the present invention. Hereinafter, description of content that overlaps with the content described with reference to FIGS. 1 to 10 will be omitted.

Referring to FIG. 12, the active compensation device 100E can actively compensate for the noise current I _n input in common mode to each of the high current paths 111E, 112E, 113E, and 114E connected to the first device 300E. .

For this purpose, the active compensation device (100E) includes four large current paths (111E, 112E, 113E, 114E), a sensing unit (120E), and a first, second, and Nth circuit arranged in parallel on the output side of the sensing unit (120E). It may include amplifying units 131E, 132E, and 133E, and a compensating unit 160E disposed on the output side of the first, second, and N amplifying units 131E, 132E, and 133E (N is 2 or more. natural number).

In contrast to the active compensation device 100 according to the embodiment described in FIG. 1, the active compensation device 100E according to the embodiment shown in FIG. 12 includes four large current paths 111E, 112E, 113E, and 114E. And, accordingly, there is a difference between the primary side of the sensing unit 120E and the secondary side of the compensation unit 160E.

The active compensation device 100E may include a first large current path 111E, a second large current path 112E, a third large current path 113E, and a fourth large current path 114E that are distinct from each other. According to one embodiment, the first large current path 111E is the R phase, the second large current path 112E is the S phase, the third large current path 113E is the T phase, and the fourth large current path 114E is the T phase. may be an N-phase power line. The noise current I _n may be input in common mode to each of the first large current path 111E, the second large current path 112E, the third large current path 113E, and the fourth large current path 114E.

The sensing unit 120E may correspond to the above-described sensing transformer 120A and the sensing unit 120B (eg, 120B-1, 120B-2). However, the primary side of the sensing unit 120E may be disposed on the first large current path 111E, the second large current path 112E, the third large current path 113E, and the fourth large current path 114E. there is.

The secondary side of the sensing unit 120E has a first output corresponding to the input of the first amplifying unit 131E, a second output corresponding to the input of the second amplifying unit 132E, and a second output corresponding to the input of the N-th amplifying unit 133E. The third output corresponding to the input can be output in parallel.

The input signal of the primary side of the compensator 160E may be based on the output signal output from each of the first, second, and N amplification units 131E, 132E, and 133E.

The compensation unit 160E may correspond to the compensation transformer 140A and the compensation capacitor unit 150A, which perform current compensation as described above. Alternatively, the compensation unit 160E may correspond to the compensation transformer 160B, which performs voltage compensation as described above.

In addition, the sensing unit 120E corresponds to the above-described sensing unit 120C, the compensating unit 160E corresponds to the above-described first compensating unit 160C, and the active compensation device 100E corresponds to the second compensating unit 100E. It may further include a compensation unit that performs voltage compensation corresponding to (190C).

Meanwhile, the secondary side of the compensator 160E may be disposed in each of the first large current path 111E, the second large current path 112E, the third large current path 113E, and the fourth large current path 114E.

According to one embodiment, the compensation unit 160E is based on the voltage (i.e., primary side voltage) output from the first and second amplification units 131E and 132E, respectively, through four high current paths 111E, 112E, and 113E. , 114E), a compensation voltage (i.e., secondary side voltage) can be generated in series. In this case, for example, the compensation unit 160E may include a compensation transformer.

According to another embodiment, the compensation unit 160E is based on the induced current generated based on the current output from the first, second, and N amplification units 131E, 132E, and 133E, respectively, to the first large current path 111E, A compensation current may be injected into each of the second large current path 112E, the third large current path 113E, and the fourth large current path 114E, or the compensation current may be drawn at the reference potential of 1. In this case, for example, the compensation unit 160E may include a compensation transformer and a compensation capacitor unit.

The active compensation device 100E according to this embodiment can compensate for common mode noise on the power line of a three-phase, four-wire power system.

Figure 13 schematically shows the configuration of a system including an active compensation device 100F according to an embodiment of the present invention. As described above as another example in the description of FIG. 1, the active compensation device 100F is an example of a type that senses noise at the front end, which is the power source, and returns to the rear end to compensate.

FIG. 14 schematically shows an active compensation device 100F-1 as an example of the active compensation device 100F shown in FIG. 13, and FIG. 15 shows another example of the active compensation device 100F shown in FIG. 13. This schematically shows the active compensation device (100F-2).

Referring to FIG. 13, the active compensation device 100F may include a sensing unit 120F, a first amplification unit 135F, a second amplification unit 136F, and a compensation unit 190F. Referring to FIGS. 14 and 15 , the compensation unit 190F may include a compensation transformer 191F and a compensation capacitor unit 192F.

The sensing unit 120F, the first amplifying unit 135F, the second amplifying unit 136F, and the compensating unit 190F are the sensing unit 120C and the third amplifying unit 133C described above in FIGS. 8 to 10, respectively. ), the fourth amplification unit 134C, and the second compensation unit 190C.

The active compensation device 100F can actively compensate for the noise current I _n input in common mode to each of the two large current paths 111 and 112 connected to the first device 300.

The sensing unit 120F may sense the noise current I _n on the large current paths 111 and 112, and output an output signal based on the noise current I _n to the first and second amplifying units 135F and 136F, respectively. . The sensing unit 120F may output a first output signal and a second output signal, respectively, based on the noise current I _n , and the first output signal is input to the first amplifier 135F and the second output signal is It may be input to the second amplifier 136F.

Referring to FIGS. 14 and 15 , the sensing unit 120F may have a secondary side wire wrapped around a CM choke around which the first high current path 111 and the second high current path 112 are wound. The primary side of the sensing units 120F-1 and 120F-2 may be a winding in which the first high current path 111 and the second high current path 112 are wound around the CM choke, respectively.

Meanwhile, in one embodiment (see FIG. 14), one wire may be wrapped around the CM choke on the secondary side of the sensing unit 120F-1. The single wire may be connected in parallel to the input terminal of the first amplifier 135F and the input terminal of the second amplifier 136F.

In this case, for example, the voltage (V _sen ) induced on the secondary side of the sensing unit (120F-1) may be equally input to the first amplification unit (135F) and the second amplification unit (136F). . According to one embodiment, when the voltage gain of the first amplification unit 135F is G5 and the voltage gain of the second amplification unit 136F is G6, G5 = -G6 may be satisfied. The difference between the output voltage of the first amplification unit 135F and the output voltage of the second amplification unit 136F may be the input voltage of the compensator 190F. That is, it may be the input voltage of the compensation transformer 191F.

Meanwhile, in another embodiment (see FIG. 15), on the secondary side of the sensing unit 120F-2, a first wire L31 and a second amplifying unit (L31) connected in parallel to the input terminal of the first amplifying unit 135F The second wire (L32) connected in parallel to the input terminal of 136F) can be each wrapped around the CM choke.

For example, the voltage V _sen1 induced in the first wire (L31) of the secondary side of the sensing unit (120F-2) may be differentially input to the first amplifying unit (135F). The voltage V _sen2 induced in the second wire L32 on the secondary side of the sensing unit 120F-2 may be differentially input to the second amplifying unit 136F.

According to one embodiment, the first wire (L31) and the second wire (L32) are wound to generate input voltages of the same size and opposite phase to the first amplification unit (135F) and the second amplification unit (136F). It can be. For example, if the number of turns of the first wire (L21) and the second wire (L22) on the secondary side is the same, V _sen1 = -V _sen2 . Additionally, when the voltage gain of the first amplification unit 135F is G5 and the voltage gain of the second amplification unit 136F is G6, G5 = +G6 can be satisfied. The difference between the output voltage of the first amplification unit 135F and the output voltage of the second amplification unit 136F may be the input voltage of the compensator 190F. That is, it may be the input voltage of the compensation transformer 191F.

Meanwhile, referring again to FIGS. 14 and 15 together, the compensation transformer 191F and the compensation capacitor unit 192F may correspond to the above-described second compensation transformer 191C and the compensation capacitor unit 192C.

The compensation transformer 191F may generate an induced voltage V _inj2 on the secondary side depending on the input voltage and turns ratio. The voltage V _inj2 converted through the compensation transformer 191F can draw a compensation current I _c from the high current paths 111 and 112 (eg, power line) through the compensation capacitor unit 192F.

Meanwhile, the active compensation devices (100F, 100F-1, 100F-2) shown in Figures 13, 14, and 15 are also applicable to the 3-phase 3-wire system and 3-phase 4-wire system as shown in Figures 11 and 12. am.

According to various embodiments of the present invention, noise that can be accommodated and compensated for in an active compensation device can increase. For example, even for the same DC voltage supply (e.g., voltage supply of the third device 400), the noise current that the active compensation device can accept and compensate for can become larger by using a parallel amplifier.

According to various embodiments of the present invention, the stress on the amplifier can be reduced even when sensing and compensating for the same noise. Specifically, by using a plurality of parallel amplifiers, the maximum noise tolerance can be increased within a limited DC voltage (eg, the supply voltage of the third device 400).

In addition, unlike the case where only the CM choke is used, the active compensation device according to various embodiments may have only a small increase in size or price even if it is used for high power.

In addition, since the active compensation device according to various embodiments of the present invention has a structure that is electrically insulated from a high current path (e.g., a power line), the elements included in the amplification unit 130 can be protected from electrical overstress (EOS). . For example, since the amplifier 130 according to various embodiments of the present invention is insulated from the power line, it can use DC low voltage (e.g., third device 400, within 48V) used in the control board. Therefore, the amplifier 130 does not require a separate power conversion circuit.

The specific implementations described in the present invention are examples and do not limit the scope of the present invention in any way. For the sake of brevity of the specification, descriptions of conventional electronic components, control systems, software, and other functional aspects of the systems may be omitted. In addition, the connections or connection members of lines between components shown in the drawings exemplify functional connections and/or physical or circuit connections, and in actual devices, various functional connections or physical connections may be replaced or added. Can be represented as connections, or circuit connections. Additionally, if there is no specific mention such as “essential,” “important,” etc., it may not be a necessary component for the application of the present invention.

Therefore, the spirit of the present invention should not be limited to the above-described embodiments, and the scope of the patent claims described below as well as all scopes equivalent to or equivalently changed from the scope of the claims are within the scope of the spirit of the present invention. It will be said to belong to

Claims (1)

In the active compensation device that actively compensates for noise occurring in common mode in each of at least two large current paths connected to the first device,
at least two high current paths for transmitting a large current supplied by a second device to the first device;
a sensing unit that senses a common mode noise current in the high current path and generates a plurality of output signals in parallel based on the noise current;
a plurality of amplifier units respectively corresponding to the plurality of output signals, which amplify each of the plurality of output signals to generate a plurality of amplified signals in parallel;
An active compensation device comprising: a compensation unit that draws compensation current from the high current path based on the plurality of amplified signals or generates a compensation voltage on the high current path.