KR20230166037A - Bridge combiners and filters for radio frequency applications - Google Patents

Abstract

The coupling circuit can be configured to couple the common node to a first group of filters via a first path and to couple the common node to a second group of one or more filters via a second path. The coupling circuit is such that for a signal in each band of the second group the impedance provided by each filter of the first group is such that the signal is sufficiently excluded from the first path, and The impedance provided by each filter in the second group to the signal in the band may be configured to result in the signal being sufficiently excluded from the second path. The first path may present a first impedance to the coupling circuit, and the second path may present a second impedance to the coupling circuit, such that the complex portion of the first impedance is the conjugate of the complex portion of the second impedance. am.

Description

Bridge combiners and filters for radio frequency applications

[Cross-reference to related applications]

This application claims priority to U.S. Provisional Patent Application No. 63/005, 421, filed April 5, 2020, entitled “BRIDGE COMBINERS AND FILTERS FOR RADIO-FREQUENCY APPLICATIONS” The disclosure is hereby expressly incorporated by reference in its entirety.

[Technology field]

The present invention relates to bridge combiners and related circuits for radio-frequency (RF) applications.

In radio frequency (RF) applications, a signal with multiple frequency components can be routed from a common path to separate paths. Conversely, multiple signals can be routed from their respective paths to a common path. Either or both of these functionalities allow, for example, carrier aggregation of multiple RF signals.

According to many implementations, the present disclosure provides a first group of filters, each configured to support a band, such that a first frequency range covers a respective plurality of bands, and a second frequency range covers a respective plurality of bands. A radio frequency architecture comprising a second group of one or more filters, each configured to support one band, to cover. Each filter in the first group is configured to provide an impedance at or near the short circuit impedance for the signal in the respective band in the second group, and each filter in the second group is configured to provide an impedance in the respective band of the first group. It is configured to provide an impedance at or near the short circuit impedance for a signal at. The radio frequency architecture has a common node and a coupling circuit configured to couple the common node to one of the first and second groups through a first path and to couple the common node to the other group through a second path. coupling circuit) is additionally included. The coupling circuit is further configured such that the impedance provided by each filter of the first group for the signal in each band of the second group results in sufficient exclusion of the signal from the first path.

In some embodiments, the first and second groups of filters may be implemented as one or more multiplexers, the coupling circuit may include a resonator, and/or the radio frequency architecture may include the first and second groups of filters. It may further include switching circuitry configured to provide filter selection functionality along either or both of the paths.

In some embodiments, the coupling circuit is further configured such that the impedance provided by each filter in the second group for the signal in each band of the first group results in the signal being sufficiently excluded from the second path. It can be configured.

In some embodiments, the first path may provide a first impedance Z1 to the coupling circuit and the second path may provide a second impedance Z2 to the coupling circuit, such that the complex portion of Z1 is It is the conjugate of the complex part. In some embodiments, the first impedance Z1 may be one of a capacitive impedance and an inductive impedance, and the second impedance Z2 may be the other of a capacitive impedance and an inductive impedance.

In some embodiments, each of the first and second paths may include a phase shifter. In some embodiments, the radio frequency architecture may further include a third group of one or more filters each configured to support one band such that the third frequency range covers its respective one or more bands. The phase shifters of the first and second paths may be configured to reduce the mutual loading between each filter of the third group and each filter of either or both the first and second groups. there is. In some embodiments, the radio frequency architecture may further include a third group of one or more filters each configured to support one band such that the third frequency range covers its respective one or more bands. Each filter in the third group can be configured to provide an impedance at or near the short circuit impedance for the signal in the respective band of the first and second groups, and each filter in the first and second groups may be further configured to provide an impedance at or near the short circuit impedance for signals in each band of the third group.

In some embodiments, the coupling circuit may include a resonator, such as an acoustic resonator. In some embodiments, the coupling circuit may include a first circuit and a second circuit coupling the common node to ground in parallel, the first circuit having a first inductance L1 in series between the common node and ground. and a capacitance, wherein the second circuit includes a second inductance L2 and a resonator in series between the common node and ground.

In some embodiments, the radio frequency architecture may further include switching circuitry implemented to provide filter selection functionality along either or both the first and second paths. In some embodiments, the switching circuit may include a switch configured to allow selection of a filter among a plurality of filters within the same group such that the selected filter is coupled to a respective one of the first and second paths. In some embodiments, the switching circuitry includes first and second filters in each group or a third group of one or more filters each configured to support one band such that the third frequency range covers each one or more bands. It may include a switch configured to allow coupling of a selected one of the paths.

In some embodiments, the coupling circuit may include a first LC circuit and a second LC circuit coupling the common node to ground in parallel, the first LC circuit having a first inductance L1 and a first inductance L1 in series. It includes a capacitance C1, and the second LC circuit includes a second capacitance C2 and a second inductance L2 in series. The first path may be coupled to the coupling circuit at the node between L1 and C1, and the second path may be coupled to the coupling circuit at the node between C2 and L2.

In some implementations, the present disclosure relates to a packaged module including a packaging substrate configured to receive a plurality of components, and a radio frequency circuitry implemented on the packaging substrate. The radio frequency circuit includes a first group of a plurality of filters, each configured to support a band such that the first frequency range covers a respective plurality of bands, and each group of filters configured to support a band such that the second frequency range covers a respective plurality of bands. and a second group of one or more filters configured to support the band. Each filter in the first group is configured to provide an impedance at or near the short circuit impedance for the signal in the respective band in the second group, and each filter in the second group is configured to provide an impedance in the respective band of the first group. It is configured to provide an impedance at or near the short circuit impedance for a signal at. The radio frequency circuit has a common node and further includes a coupling circuit configured to couple the common node to one of the first and second groups via a first path and to couple the common node to the other group via a second path. do. The coupling circuit is further configured such that the impedance provided by each filter of the first group for the signal in each band of the second group results in sufficient exclusion of the signal from the first path.

In some embodiments, the coupling circuit is further configured such that the impedance provided by each filter in the second group for the signal in each band of the first group results in the signal being sufficiently excluded from the second path. It can be configured.

In some embodiments, the first and second groups of filters may be implemented as one or more multiplexers, the coupling circuit may include a resonator, and/or the radio frequency architecture may include the first and second groups of filters. It may further include switching circuitry configured to provide filter selection functionality along either or both of the paths.

In some embodiments, the first path may provide a first impedance Z1 to the coupling circuit and the second path may provide a second impedance Z2 to the coupling circuit, such that the complex portion of Z1 is It is the conjugate of the complex part.

In some implementations, the present disclosure relates to a wireless device that includes one or more antennas and a front end module in communication with the one or more antennas. The front-end module includes a first group of plurality of filters, each configured to support one band, such that the first frequency range covers each plurality of bands, and each group of filters configured to support one band, such that the second frequency range covers each one or more bands. and a radio frequency circuit having a second group of one or more filters configured to support the band. Each filter in the first group is configured to provide an impedance at or near the short circuit impedance for the signal in the respective band in the second group, and each filter in the second group is configured to provide an impedance in the respective band of the first group. It is configured to provide an impedance at or near the short circuit impedance for a signal at. The radio frequency circuit includes a common node and further includes a coupling circuit configured to couple the common node to one of the first and second groups via a first path and to couple the common node to the other group via a second path. Includes. The coupling circuit is further configured such that the impedance provided by each filter of the first group for the signal in each band of the second group results in sufficient exclusion of the signal from the first path. The wireless device further includes a receiver in communication with the front end module and configured to process one or more signals associated with the first and second groups.

For purposes of summarizing the disclosure, certain aspects, advantages and novel features of the invention are described herein. It should be understood that not all of these advantages will necessarily be achieved in accordance with any particular embodiment of the invention. Accordingly, the invention may be embodied or accomplished in a manner that achieves or optimizes one advantage or group of advantages taught herein without necessarily achieving other advantages taught or implied herein.

1 depicts an architecture that may be implemented utilizing a coupling circuit having one or more features as described herein.
Figure 2 shows a normalized Smith chart providing a visual representation of impedance.
3A and 3B depict example impedances of FIG. 1 on the normalized Smith chart of FIG. 2.
Figure 4 illustrates an architecture that can be implemented similarly to the example of Figure 1, where a first filter group includes three filters to support three bands, and a second filter group supports two bands. Includes two filters to do this.
Figure 5 shows an architecture where a first filter group includes two filters to support two bands and a second filter group includes one filter to support one band.
6 illustrates that in some embodiments a filter in a first group of filter(s) and a filter in a second group of filter(s) provide first and second paths of the coupling circuit. 2 It is shown that impedances can be constructed to have complex parts that are conjugates or approximately conjugates of each other.
Figure 7 shows an architecture similar to the examples of Figures 4 and 5 and that may be implemented with one or more phase shifters.
Figure 8 shows an architecture utilizing multiple coupling circuits with multiple filter groups, where at least one group includes multiple filters to support different bands.
Figure 9 shows an example of an architecture in which a common signal node of the coupling circuit is coupled to an antenna and first and second paths from the coupling circuit are coupled to one or more multiplexers.
Figure 10 shows another example of an architecture where the common signal node of the coupling circuit is coupled to an antenna and the first and second paths from the coupling circuit are coupled to one or more multiplexers.
Figure 11 shows another example of an architecture in which the common signal node of the coupling circuit is coupled to an antenna and the first and second paths from the coupling circuit are coupled to one or more multiplexers.
Figure 12 shows an architecture that may be a more specific example of the architecture of Figure 9.
Figure 13 shows an architecture that may be another more specific example of the architecture of Figure 9.
Figure 14 shows an architecture that may be a more specific example of the architecture of Figure 10.
Figure 15 shows an architecture that may be another more specific example of the architecture of Figure 10.
FIG. 16 illustrates that in some embodiments an architecture having one or more features as described herein may include a coupling circuit that includes two LC circuits that couple an input node to ground.
FIG. 17A illustrates that in some embodiments an architecture having one or more features as described herein may include a coupling circuit with a resonator.
FIG. 17B illustrates that in some embodiments the resonator of the coupling circuit of FIG. 17A may include an acoustic resonator.
18A and 18B illustrate that in some embodiments an architecture having one or more features as described herein may include coupling circuitry with a half bridge configuration.
FIG. 19A shows an example architecture including the half bridge coupling circuit of FIG. 18A.
FIG. 19B shows an example architecture including the half bridge coupling circuit of FIG. 18B.
Figure 20 shows an architecture that is a more specific example of the architecture of Figure 4, utilizing the coupling circuit of Figure 16.
FIG. 21 shows a scan of impedances for the example architecture of FIG. 20.
Figure 22 shows an example of how phase shifting functionality can be utilized in an architecture that includes coupling circuitry as described herein.
Figure 23 shows another example of how phase shifting functionality can be utilized in an architecture that includes coupling circuitry as described herein.
Figure 24 shows an architecture that may be a more specific example of the architecture of Figure 8 in which multiple coupling circuits may be utilized.
Figure 25 shows an architecture that may be a more specific example of the architectures of Figures 9 and 12.
Figure 26 shows an architecture that may be a more specific example of the architectures of Figures 9 and 13.
FIG. 27 illustrates an architecture with the switching functionality described herein with reference to FIGS. 11, 13, and 14.
FIG. 28 shows an example architecture including switching functionality that allows multiple coupling circuits to share a common antenna and also share a common filter group.
Figure 29 shows an architecture that may be a more specific example of the architecture of Figure 19A.
Figure 30 depicts an example architecture utilizing many of the features described herein.
31 illustrates that in some embodiments a radio frequency (RF) module may include one or more features as described herein.
Figure 32 depicts an example wireless device having one or more advantageous features described herein.

The introductory text, if any, provided herein is for convenience only and does not necessarily affect the scope or meaning of the claimed invention.

Among other things, PCT Publication No. WO2016/033427 (International Application No. PCT/US2015/047378, entitled “DOMINO CIRCUIT AND RELATED ARCHITECTURES AND METHODS FOR CARRIER AGGREGATION”) discloses a device that can be utilized for carrier aggregation operations. Circuits, architectures, and methods related to coupling circuits are disclosed. For purposes of explanation, such coupling circuit may also be referred to as a bridge circuit, Domino circuit, or Domino bridge circuit.

1 depicts an architecture 700 that may be implemented utilizing coupling circuit 100 having one or more features as described herein. In some embodiments, such coupling circuit may include one or more of the examples disclosed in the aforementioned PCT Publication No. WO2016/033427.

In the example architecture 700 of FIG. 1 , coupling circuit 100 connects common signal node 102 to a first signal processing component 701 (a band A component, such as a band A filter) and a second signal processing component ( 702) (a band B component such as a band B filter). Constructed in the manner described above, the impedance Zin1 presented to the coupling circuit 100 may be equal to (or approximately equal to) the load impedance of the Band A filter for the Band A signal (e.g., 50 ohms), It may be equal to (or approximately equal to) zero for the Band B signal. Similarly, the impedance Zin2 presented to coupling circuit 100 may be equal to (or approximately equal to) the load impedance of the Band B filter (e.g., 50 ohms) for the Band B signal, and May be equal to (or approximately equal to) zero.

As disclosed in PCT Publication No. WO2016/033427, coupling circuit 100 combines the above-described first and second signal paths associated with the Band A and Band B filters to form a first signal path (Band A filter so that approximately zero impedance presented to the signal in the second frequency band (Band B signal) results in the signal in the second frequency band (Band B signal) being substantially excluded from the first signal path. , and approximately zero impedance presented to the signal in the first frequency band (Band A signal) by the second signal path (having a Band B filter) is such that the signal in the first frequency band (Band A signal) is reduced by the second signal path. It can be configured to result in substantial exclusion from the path.

In the example of Figure 1, as well as some of the other examples described herein, the impedances presented by the respective filters are first (band A) and second (band B) from a common signal node (102 in Figure 1). Depicted in the context of the flow of signal(s) to either or both first and second signal paths associated with the filters. However, as disclosed in PCT Publication No. WO2016/033427, it will be understood that one or more features of the present disclosure may also be implemented in a configuration where the flow of signal(s) is reverse to the configuration described above.

Figure 2 shows a normalized Smith chart 710 that provides a visual representation of impedance Z = R + jX, where R is resistance and X is reactance. For pure capacitance, reactance is the same as where ω=2πf, and for pure inductance, the reactance Note that it is the same as . Therefore, for pure resistance, Z=R; For pure capacitance, ; and for pure inductance, am. Additionally, the impedance in the area above the horizontal line of the Smith chart 710 has a positive imaginary value and represents an inductive impedance, and the impedance in the area below the horizontal line of the Smith chart 710 has a negative imaginary value and represents a capacitive impedance. Note that it represents impedance.

Referring to Figure 2, the above-described horizontal line segment is shown to bisect the outermost circle, the left end of the horizontal line segment represents a short circuit (Z = 0) state, and the right end of the horizontal line segment represents an open circuit ( ) Expresses the state. The midpoint of the horizontal line segment (and thus the center of the outermost circle) represents the matched impedance state. This matched impedance state has the value Z=1 in the normalized representation. In denormalized representation, this matched impedance state may have a value of Z=50 ohms, for example.

In the normalized Smith chart of Figure 2, the solid circles are constant resistance circles 712 at exemplary normalized values. For example, the outermost circle referenced above has a constant resistance value of zero, and successively smaller circles have constant resistance values of 0.2, 0.5, 1, 2, 3, 4, 5, and 10. All of these constant resistance circles share their rightmost points at the right end of the horizontal segment referenced above (open circuit state).

In the normalized Smith chart 710 of FIG. 2, the dash-line arcs are constant reactance arcs 714 at exemplary normalized values. For example, the horizontal line segment referenced above (the arc of an infinite radius circle) has a constant reactance value of zero, while the arcs of successively smaller radius circles have a reactance value of 0.2, 0.5, 1, 2, 3, 4, 5 and 10. It has certain reactance values. Such constant reactance arcs may be provided above and below the horizontal line segment. For arcs on a horizontal segment, the arcs share their lowest points at the right end of the horizontal segment (open circuit state). For arcs below a horizontal segment, the arcs share their highest points at the right end of the horizontal segment (open circuit state).

Figures 3A and 3B depict the exemplary impedances Zin1 and Zin2 of Figure 1, respectively, on the normalized Smith chart of Figure 2. More specifically, FIG. 3A shows an impedance region in which Zn1 is at or approximately in a matched impedance state (Z = 1 + i0) comprising impedance values associated with the frequency range of the first frequency band (Band A). , and an impedance region at or approximately in a short-circuit state (Z = 0 + i0) comprising impedance values associated with the frequency range of the second frequency band (Band B). Similarly, Figure 3b shows an impedance region in which Zn2 is at or approximately in a matched impedance state (Z = 1 + i0) comprising impedance values associated with the frequency range of the second frequency band (Band B), and It is shown that there is an impedance region at or approximately in the short circuit state (Z = 0 + i0) comprising impedance values associated with the frequency range of the first frequency band (band A).

Referring to the example of FIGS. 1 and 3, note that the impedance states for Zin1 and Zin2 in FIGS. 3A and 3B can be considered ideal impedance states. However, in some embodiments, the band A filter of the example of FIG. 1 may be part of a group having multiple filters to support multiple respective bands, with the filters in the group having two filters associated with coupling circuit 100. It is connected to the first of the paths (eg, the upper path associated with Zin1). Similarly, the Band B filter of the example of FIG. 1 may be part of a group having a plurality of filters to support a plurality of respective bands, the filters of the group being connected to the second of the two paths associated with coupling circuit 100. (e.g., the subpath associated with Zin2).

For example, Figure 4 illustrates an architecture 720 that may be implemented similarly to the example of Figure 1, but where the first filter group 721 supports three bands (Band 1A, Band 1B, and Band 1C). The second filter group 722 includes two filters to support two bands (band 2A, band 2B). In such an architecture, coupling circuit 100 is shown coupling common signal node 102 to first filter group 721 and second filter group 722. When configured in the manner described above, the impedance values for Zin1 are for signals in the band corresponding to the filter selected from the filters of the first filter group 721 and for the selected filter from the filters from the second filter group 722. The signal in the corresponding band is presented to the coupling circuit 100. Similarly, the impedance values for Zin2 are is presented to the coupling circuit 100 for a signal of

In the example of Figure 4, the first filter group 721 is described as having three filters, and the second filter group 722 is described as having two filters. It will be appreciated that each of the first and second filter groups may also be implemented with a different number of filters.

In the example of FIG. 4, each of the first and second filter groups 721 and 722 is described as having a plurality of filters. It will be appreciated that in some embodiments, one group may include multiple filters and another group may include a single filter.

For example, Figure 5 shows that the first filter group 721 includes two filters to support two bands (band 1A, band 1B) and the second filter group 722 includes one band (band 2). An architecture 720 is shown that includes one filter to support. In such an architecture, the coupling circuit 100 is shown coupling the common signal node 102 to single filters of the first group 721 and the second group 722. Constructed in the manner described above, the impedance values for Zin1 are is presented to the coupling circuit 100 for a signal of Similarly, the impedance values for Zin2 are It is presented in coupling circuit 100.

In the examples of FIGS. 4 and 5 , the selected filter in first group 721 and the selected filter in second group 722 may be configured to provide ideal impedance conditions similar to the examples of FIGS. 1 and 3 . However, in this configuration where the two selected filters are optimized, performance may deteriorate significantly when using the other (unselected) filter(s) of the first and second groups 721, 722.

In many applications, and especially when a filter group involves a wide frequency range, it is difficult or impossible to achieve ideal impedance states (ideal matched impedance state and/or ideal short circuit state) for all filters in the group. Please note this. However, in some embodiments, even if impedances Zin1 and Zin2 are not in ideal impedance states, the real parts of complex impedances Zin1 and Zin2 are close enough to their respective real parts of ideal impedance states and complex impedances Zin1 and Zin2 Desired or acceptable performance can be achieved when the imaginary parts of Zin2 are properly configured as described herein.

In some embodiments, each filter in the first group of filter(s) and the second group of filter(s) is configured such that the first and second impedances provided for the first and second paths of the coupling circuit are relative to each other. It may be constructed to have complex parts that are conjugates or approximately conjugates. More specifically, the first impedance provided for the first path of the coupling circuit is Can be expressed as, and the second impedance provided for the second path of the coupling circuit is It can be expressed as, where -jX is is the conjugate of +jX.

FIG. 6 illustrates the complex partial-conjugate impedances described above in terms of first and second impedances Zin1 and Zin2 corresponding to the example architecture 720 of FIG. 4 . In the example of FIG. 4, the three filters (band 1A, band 1B, band 1C) of the first group 721 may each have frequency bands F1A < F1B < F1C, and the two filters of the second group 722 may have frequency bands F1A < F1B < F1C. The filters (Band 2A, Band 2B) can each have frequency bands F2A < F2B, so F1A < F1B < F1C < F2A < F2B.

With the above-described configurations of the filters of the first and second groups 721, 722, Figure 6 depicts Smith charts for the impedances Zin1 and Zin1 of Figure 4.

Referring to FIG. 6, the impedances Zin1 for the signals in the three bands (band 1A, band 1B, band 1C) of the first group 721 are the matched impedance values (e.g., in the normalized Smith chart) Z=1), the impedances Zin1 for the signals in the two bands (band 2A, band 2B) of the second group 722 are at the short circuit value (e.g. , is shown to be in the regions at or close to Z=0) on the normalized Smith chart. Similarly, the impedances Zin2 for the signals in the two bands of the second group 722 (band 2A, band 2B) are shown to be in regions at or close to the matched impedance value, and the first group 722 The impedances Zin2 for signals in the three bands (Band 1A, Band 1B, Band 1C) of 721 are shown to be in the regions at or close to the short circuit value.

In the example of Figure 6, each filter has a matched impedance state ( ) and short circuit condition ( ) and the associated real parts, and complex parts that are conjugate to each other, respectively. More specifically, for band 1A, as depicted by arrow 724a: ( and Lim), and ( and is), and of Zin1 and Zin2 and are conjugates of each other. For band 1B, as depicted by arrow 724b, ( and Lim), and ( and is), and of Zin1 and Zin2 and are conjugates of each other. For band 1C, as depicted by arrow 724c, ( and Lim), and ( and is), and of Zin1 and Zin2 and are conjugates of each other.

Similarly, for band 2A, as depicted by arrow 724d: ( and Lim), and ( and is), and of Zin2 and Zin1 and are conjugates of each other. For band 2A, as depicted by arrow 724e, ( and Lim), and ( and ), and of Zin2 and Zin1 and are conjugates of each other.

In the above examples of Zin1 and Zin2 for the five bands in Figure 6, if Zin1 for a given band is capacitive (i.e., the impedance is in the area below the horizontal line of the Smith chart), then Zin2 for the same band is inductive. Note that the impedance is in the area above the horizontal line of the Smith chart. Similarly, if Zin1 for a given band is inductive, Zin2 for the same band is capacitive.

4 and 6, each filter of a given group (e.g., first group 721) has the Zin1 and Zin2 impedances described above for the first and second paths of coupling circuit 100. It is assumed that it is configured to provide. In some embodiments, architecture 720 may be configured such that some or all of the capacitive and inductive impedances of Zin1 and Zin2 are rotated toward the desired location(s) on the Smith chart. For example, a capacitive or inductive impedance that is close to a short circuit condition can be rotated toward that short circuit condition to provide an impedance that is equal to or approximately equal to the short circuit impedance. In another example, a capacitive or inductive impedance close to the matched impedance state may be rotated toward the matched impedance state to provide an impedance that is equal to or approximately equal to the matched impedance.

In some embodiments, the above-described rotation of the Zin1 and Zin2 impedances for a given group of filters, for example, the configuration of another group (e.g., second group 722), of one or more phase shifting components. It may be implemented by introduction, or some combination thereof. Examples of such phase shifting components are described in more detail herein.

Figures 7-15 illustrate examples of architectures that may be implemented utilizing one or more features described with reference to the examples of Figures 4-6.

For example, Figure 7 shows an architecture 730 that may be implemented similarly to the examples of Figures 4 and 6, where a first filter group 721 includes a plurality of filters, and a second filter group 721 includes a plurality of filters. 722 contains a plurality of filters. 7 shows that in some embodiments architecture 730 includes a first phase shifter 103 implemented between coupling circuit 100 and a first filter group 721, and a first phase shifter 103 implemented between coupling circuit 100 and a second filter group. It is shown that a second phase shifter 105 implemented between the groups 722 may be additionally included. Additional examples related to architecture 730 of FIG. 7 are described in greater detail herein.

In another example, Figure 8 shows an architecture 732 utilizing multiple coupling circuits 100a, 100b with multiple filter groups, where at least one group includes multiple filters to support different bands. Includes. In the example of Figure 8, first coupling circuit 100a is shown coupling common signal node 102 to first and second paths, the first path comprising a group of one or more filters 723. And the second path includes a common signal node for the second coupling circuit 100b. The second coupling circuit 100b is shown coupling its common signal node to its first and second paths, the first path comprising a group of one or more filters 722 and the second path comprising one It includes the above group of filters (721).

In the example of Figure 8, phase shifters 103a, 103b are shown as being provided along first and second paths associated with first coupling circuit 100a. Similarly, phase shifters 103c, 103d are shown as being provided along first and second paths associated with second coupling circuit 100b. It will be appreciated that in some embodiments, some or all of those paths associated with coupling circuits 100a, 100b may be implemented without phase shifter(s). Additional examples related to architecture 732 of Figure 8 are described in greater detail herein.

In still other examples, FIGS. 9-11 illustrate that the common signal node 102 of the coupling circuit 100 is coupled to an antenna and the first and second paths from the coupling circuit 100 are connected to one or more multiplexers 701. ) shows the architectures combined. For purposes of explanation, one or more such multiplexers 701 may include one or more filter groups, where at least one of such group(s) includes a plurality of different band filters. Although each path from the respective coupling circuit is shown as including a phase shifter, it will be understood that such path may or may not include a phase shifter.

In the example of FIG. 9 , architecture 734 may include switching circuitry 107 implemented along the path between coupling circuit 100 and multiplexer(s) 701 . Figures 12 and 13 show more specific examples of such architecture.

In the example of FIG. 10 , architecture 736 may include switching circuitry 109 implemented between coupling circuitry 100 and one or more antennas. Figures 14 and 15 show more specific examples of such architecture.

In the example of Figure 11, architecture 738 includes switching circuitry 107 implemented along the path between coupling circuit 100 and multiplexer(s) 701, as well as coupling circuit 100 and one or more antennas. It may also include a switching circuit 109 implemented in between. Additional examples of such architectures are described herein.

Figure 12 shows architecture 734, which may be a more specific example of architecture 734 of Figure 9. In the example of FIG. 12 , a switch 107 may be implemented between coupling circuit 100 and filter group 722 to allow selection of a filter among filters within the same group 722. For example, assume that filter group 722 includes band 2A and band 2B filters. Switch 107 may be configured to allow coupling circuit 100 to be coupled to either of those two filters.

Figure 13 shows architecture 734, which may be another more specific example of architecture 734 of Figure 9. In the example of FIG. 13 , a switch 107 may be implemented between the coupling circuit 100 and the plurality of filter groups 722 to allow selection of one of the groups. For example, assume that architecture 734 includes three filter groups 721, 722, and 723. Switch 107 may be configured to allow coupling circuit 100 to be coupled to group 721 or group 722, for example. It will be appreciated that group 723 may also be switchably coupled to coupling circuit 100 in a similar manner.

In some embodiments, architecture 734 of Figure 13 may include one or more switching function blocks to allow switchable selection of one filter within a given group. Similarly, in some embodiments, architecture 734 of FIG. 12 may include one or more switching functional blocks to allow switchable selection of one of a plurality of groups. It will be appreciated that in some embodiments, such filter group selection and filter selection functionality (within a given group) may be achieved by a suitably configured switching network. Examples related to such switching networks are described in greater detail herein.

Figure 14 shows architecture 736, which may be a more specific example of architecture 736 of Figure 10. In the example of FIG. 14 , a switch 109 is implemented between the coupling circuit 100 and a plurality of antennas (e.g., ANT1, ANT2) to select an antenna to be coupled to a common signal node of the coupling circuit 100. can be allowed. 14, the first and second paths from coupling circuit 100 may be coupled to one or more multiplexers 701 as described herein.

Figure 15 shows architecture 736, which may be another more specific example of architecture 736 of Figure 10. In the example of Figure 15, a switch 109 may be implemented between a common antenna (ANT) and a plurality of coupling circuits (eg, 100a, 100b). This configuration may allow the common antenna (ANT) to be coupled to the common signal node of either of the coupling circuits 100a and 100b. In the example of Figure 15, each of the first and second paths from each coupling circuit 100a or 100b is coupled to a filter, multiplexer, another coupling circuit, switch, etc., including various examples described herein. It can be.

16-18 show various examples of coupling circuits 100 that may be utilized in various architectures as described herein. FIG. 16 illustrates that in some embodiments an architecture having one or more features as described herein may include the coupling circuit 100 disclosed in PCT Publication No. WO2016/033427. More specifically, coupling circuit 100 may include two LC circuits that couple input node 102 to ground. The first LC circuit may include a first inductance L1 (on the input side) in series with a first capacitance C1 (on the ground side). The second LC circuit may include a second capacitance C2 (on the input side) in series with a second inductance L2 (on the ground side). The node between L1 and C1 is shown as coupled to the first path, and the node between C2 and L2 is shown as coupled to the second path.

FIG. 17A illustrates that in some embodiments an architecture having one or more features as described herein may include a coupling circuit 100 with a resonator 111 . In some embodiments, such a resonator may replace the capacitance or inductance in coupling circuit 100 of FIG. 16. For example, the coupling circuit 100 of FIG. 17A is shown as including a resonator 111 that replaces the capacitance C2 of the coupling circuit 100 of FIG. 16. Each of the other elements L1, C1, and L2 of the coupling circuit 100 of FIG. 17A may or may not have the same value as the corresponding counterpart element L1, C1, or L2 of the coupling circuit 100 of FIG. 16. You will understand that it exists.

FIG. 17B shows that in some embodiments, the resonator 111 of the coupling circuit 100 of FIG. 17A may be an acoustic resonator such as a bulk acoustic wave (BAW) resonator, any other BAW-based resonator, or a surface acoustic wave (SAW) resonator ( For example, temperature-compensated SAW (TC-SAW) resonator, leaky SAW (LSAW) resonator, longitudinal LSAW (LLSAW) resonator, trapped SAW resonator), any acoustic device with a piezoelectric layer below 2 μm on the interface of the support substrate. It is shown that it may include a resonator, or any combination thereof. An example of an architecture having such a resonator in a coupling circuit is described in greater detail herein.

18A and 18B illustrate that in some embodiments an architecture having one or more features as described herein may include coupling circuit 100 with a half bridge configuration. As disclosed in PCT Publication No. WO2016/033427, coupling circuit 100 of FIG. 18A may be configured to provide triode low-pass filter functionality for the path coupled to the node between L1 and C1. Examples of architectures with such half-bridge coupling circuits are described in more detail herein.

Similarly, coupling circuit 100 of FIG. 18B can be configured to provide three-pole high-pass filter functionality for the path coupled to the node between C2 and L2. Examples of architectures with such half-bridge coupling circuits are described in more detail herein.

FIG. 19A shows an example architecture 740 including the half bridge coupling circuit 100 of FIG. 18A. In the example of Figure 19A, coupling circuit 100 couples common signal node 102 to first filter group 701 via the node between L1 and C1. Common signal node 102 is also shown as directly coupled to second filter group 702.

In the example of FIG. 19A , a phase shifter 103 is shown as being provided between the coupling circuit 100 and the first filter group 701 . In some embodiments, such phase shifter may be configured to accommodate or compensate for the phase shift associated with the filter in first group 701.

FIG. 19B shows an example architecture 742 including the half bridge coupling circuit 100 of FIG. 18B. In the example of FIG. 19B, coupling circuit 100 couples common signal node 102 to second filter group 702 via the node between C2 and L2. Common signal node 102 is also shown as directly coupled to first filter group 701.

In the example of FIG. 19A , a phase shifter 103 is shown as being provided between the coupling circuit 100 and the second filter group 702 . In some embodiments, such phase shifter may be configured to accommodate or compensate for the phase shift associated with the filter in the second group 702.

FIG. 20 shows architecture 720, which is a more specific example of architecture 720 of FIG. 4, utilizing coupling circuit 100 of FIG. 16. In the example of Figure 20, the first filter group 721 includes three low frequency band duplexers for three bands F1, F2, and F3, each with its own transmit (Tx) filter and receive (Rx) filter. It is shown as doing so. Accordingly, the first filter group 721 includes three Rx filters for the F1_Rx, F2_Rx, and F3_Rx bands, and three Tx filters for the F1_Tx, F2_Tx, and F3_Tx bands. Similarly, the second filter group 722 is shown as comprising two high frequency band duplexers for two bands F4, F5, each having its own transmit (Tx) filter and receive (Rx) filter. . Accordingly, the second filter group 722 includes two Rx filters for the F4_Rx, F5_Rx bands, and two Tx filters for the F4_Tx, F5_Tx bands. For purposes of explanation of the example of Figure 20, the frequency bands F1, F2, F3, F4, F5 have successively higher frequency values (e.g., intermediate frequency values within a given band), so F1 < F2 < F3 < F4. We will assume that < F5.

In the example of Figure 20, coupling circuit 100 is shown as including a common signal node 102 between inductance L1 and capacitance C2. Common signal node 102 is shown coupled to antenna 760. The first node between inductance L1 and capacitance C1 is shown coupled to the first filter group 721, such that it is presented with a first impedance Zin1. The second node between the capacitance C2 and the inductance L2 is shown coupled to the second filter group 722, such that it presents a second impedance Zin2. The node between capacitance C1 and inductance L2 is shown coupled to ground.

Referring to the example of FIG. 20, the receiving operation involves the signal being received via antenna 760, and the selected Rx filters in each of the first and second groups 721 and 722 are coupled for carrier aggregation. Assume that it is coupled to the circuit 100. In such an example context, each of such selected filters may be configured such that the impedances Zin1 and Zin2 associated with coupling circuit 100 are as described herein with reference to FIGS. 4 and 6. Accordingly, Figure 21 shows a scan of the Zin1 and Zin2 impedances for the example architecture 720 of Figure 20, showing the various complex partial conjugate properties of Zin1 and Zin2 for each band.

22 and 23 show examples of how phase shifting functionality can be utilized in architectures that include coupling circuitry as described herein. For example, Figure 22 shows an architecture 730 that is similar to architecture 720 of Figure 20, but where one or more phase shifters may be utilized to better separate a group of bands from one or more other groups of bands. .

In the example of Figure 22, similar to the example of Figure 20, the first filter group 721 is shown as comprising three low frequency band duplexers, and the second filter group 722 is shown as comprising two high frequency band duplexers. It is shown as For groups of such filters (e.g., low-frequency band filters for bands F1, F2, F3 and high-frequency band filters for bands F4, F5), the impedances Zin1 and Zin2 are similar to the examples in Figures 20 and 21. It may be similar to

In the example of FIG. 22 , the first phase shifter 103 may be implemented between the coupling circuit 100 and the first filter group 721, and the second phase shifter 105 may be implemented between the coupling circuit 100 and the first filter group 721. It can be implemented between the second filter group 722. These first and second phase shifters may be configured to provide improved separation between the third filter group (eg, intermediate frequency band) and the first and second groups 721 and 722, respectively. For example, phase shifter 103 may provide a shift in phase such that the impedance Zin3 after phase shifter 103 is approximately an open circuit impedance for mid-frequency band signals and a capacitive impedance for high frequency band signals. You can. Phase shifter 105 may provide a shift in phase such that the impedance Zin4 after phase shifter 105 is approximately the open circuit impedance for mid-frequency band signals and the inductive impedance for low frequency band signals. Note that the above-described phase shifting configuration minimizes or reduces the mutual loading between the mid-frequency band and the high-frequency band.

In another example, Figure 23 is similar to the architecture 730 of Figure 22, but the phase shifting functionality is band specific for at least some of the bands supported by the first and second filter groups 721, 722. It shows an architecture 730 that can be implemented to be efficient. In some embodiments, phase shifting elements 770, such as transmission lines, L/C components, and/or resonators, may be configured for band-specific implementation. In some embodiments, such band-specific phase shifting functionality may result in improved performance of coupling circuit 100.

For example, for the first filter group 721 in the architecture 730 of FIG. 23, an inductance element and a transmission line may be configured and implemented for the Tx and Rx filters of the first band F1, and the transmission line The rows may be configured and implemented for both the Tx and Rx filters of the second band (F1), and the transmission line and inductance elements may be configured and implemented for the Tx and Rx filters of the third band (F3).

For the second filter group 722 in the architecture 730 of FIG. 23, inductance elements and transmission lines can be configured and implemented for the Tx and Rx filters of the first band (F4), transmission lines and resonators. Can be configured and implemented for the Tx and Rx filters of the second band (F5).

Figure 23 also shows that in some embodiments a phase shifting element, such as a resonator, may be implemented as part of the coupling circuit. For example, the coupling circuit 100 is shown as including a resonator 111 implemented to replace a capacitance (eg, C1 in FIG. 22). In some embodiments, resonator 111 of coupling circuit 100 and resonator associated with band-specific phase shifting elements 770 may be operatively configured to function to provide improved functionality of the coupling circuit. You can.

In some embodiments, each of the above-described resonators is an acoustic resonator, such as, for example, a bulk acoustic wave (BAW) resonator or a surface acoustic wave (SAW) resonator (e.g., a temperature-compensated (TC) SAW resonator). It can be implemented as:

Figure 24 shows an architecture 732, which may be a more specific example of the architecture 732 of Figure 8, in which multiple coupling circuits may be utilized. In the example of Figure 24, the first filter group 721 is shown as including one low-frequency band duplexer, the second filter group 722 is shown as including two mid-frequency band duplexers, and 3 Filter group 723 is shown as comprising two high frequency band duplexers.

24, architecture 732 includes a first coupling circuit 100a having a common signal node 102 coupled to antenna 760, a second coupling circuit (from the node between L1 and C1), 100b), a first path coupled to a common signal node (between L3 and C4), and a second path coupled to a third filter group 723 (from the node between C2 and L2). The second coupling circuit 100b has its first path coupled to the first filter group 721 (from the node between L3 and C3) and the second filter group 722 (from the node between C4 and L4). It is shown as having its second path coupled to .

Constructed in the manner described above, the impedance of Zin3 is presented to the first path of first coupling circuit 100a, and the impedance of Zin4 is presented to the second path of first coupling circuit 100a. Similarly, the impedance of Zin1 is presented to the first path of the second coupling circuit 100b, and the impedance of Zin2 is presented to the second path of the second coupling circuit 100b.

In the example of Figure 24, the group of filters associated with the first path of the first coupling circuit 100a can be considered to include filters 721 in low frequency bands and filters 722 in intermediate frequency bands. . Accordingly, the impedance Zin3 may have a value at or close to load-matched impedance for the low and mid frequency bands, and a value at or close to a short circuit condition for the high frequency bands. The impedance Zin4 may have a value at or close to load-matched impedance for the high frequency bands, and a value at or close to a short circuit condition for the low and intermediate frequency bands.

Also in the example of Figure 24, the second coupling circuit 100b is shown supporting low frequency band filters 721 and intermediate frequency band filters 722 via its first and second paths. Accordingly, the impedance Zin1 may have a value at or close to load-matched impedance for low frequency bands, and a value at or close to a short circuit condition for mid-frequency bands. Impedance Zin2 may have a value at or close to load-matched impedance for mid-frequency bands, and a value at or close to a short circuit condition for low-frequency bands.

In the example of Figure 24, a phase shifter is shown as being provided for each path of each coupling circuit. More specifically, phase shifters 103b and 103a are shown as being provided for the first and second paths of the first coupling circuit 100a, and phase shifters 103d and 103c are shown for the second path. It is shown as being provided for the first and second paths of the coupling circuit 100b. In some embodiments, such phase shifters may be selected to provide one or more desirable functionality as described herein. It will be appreciated that in some embodiments, an architecture similar to the example of Figure 24 may include none of such phase shifters, some of such phase shifters, or all of such phase shifters.

Figures 25-28 illustrate examples of architectures with one or more switching functionality described herein with reference to Figures 9-15. For example, Figure 25 shows architecture 734, which may be a more specific example of architecture 734 of Figures 9 and 12. In the example of FIG. 25 , the coupling circuit 100 connects the common signal node 102 via a first path to a first filter group 721 with three low-frequency band duplexers F1, F2, and F3, and It is shown coupled via a second path to a second filter group 722 with two high frequency band duplexers (F4, F5). This second path is shown to include a switch 780 configured to allow selection of a high frequency band (F4 or F5) from among the bands of the second group 722.

In another example, Figure 26 shows architecture 734, which may be a more specific example of architecture 734 of Figures 9 and 13. In the example of FIG. 26 , the coupling circuit 100 connects the common signal node 102 via a first path to the first filter group 721 (with two low-frequency band duplexers) or the first filter group 721 (with two low-frequency band duplexers). is shown coupled to a second filter group 722 (having a high frequency band duplexer) and via a second path to a third filter group 723 (having a high frequency band duplexer). The first path is shown as including a switch 782 configured to allow selection of a first filter group 721 or a second filter group 722.

In another example, Figure 27 shows architecture 738 with the switching functionality described herein with reference to Figures 11, 13, and 14. In the example of Figure 27, the first group of low-frequency band filters 721a is shown as comprising two low-frequency band duplexers, and the second group of low-frequency band filters 721b is shown as comprising two low-frequency band duplexers. It is shown as The first group of high frequency band filters 722a is shown as including a high frequency band duplexer, and the second group of high frequency band filters 722b is shown as including a high frequency band duplexer. Accordingly, groups of such filters may have a first group with low frequency band duplexers 721a, 721b coupled to coupling circuit 100 via a first path and a first group coupled to coupling circuit 100 via a second path. They can be grouped to be a second group with high frequency band duplexers 722a and 722b.

In the example of Figure 27, switching network 786 is shown implemented to provide switching functionality between coupling circuit 100 and the first and second filter groups described above. More specifically, the switches S1 and S2 of the switching network 786 provide (via the first path) a first group of low-frequency band filters 721a or a second group of low-frequency band filters to the coupling circuit 100. It can be operated to provide coupling of fields 721b. Similarly, the switches S3 and S4 of the switching network 786 (via the second path) provide a first group of high-frequency band filters 722a or a second group of high-frequency band filters (via the second path) to the coupling circuit 100. 722b) may be operated to provide the coupling.

In the example of FIG. 27 , switching network 788 is shown implemented to allow common signal node 102 of coupling circuit 100 to be coupled to first antenna 760a or to second antenna 760b. do. For example, switch S11 may be closed and switch S12 may be open to couple the common signal node 102 to the first antenna 760a. Similarly, switch S11 may be open and switch S12 closed to couple common signal node 102 to second antenna 760b.

Referring to the example of Figure 27, it will be appreciated that the switching networks 786, 788 described above may be implemented in a number of ways. In some embodiments, switching networks 786 and 788 may be part of a switching circuit indicated at 784, which may be implemented on a die or module, for example.

FIG. 28 shows an example architecture 738 that includes switching functionality that allows multiple coupling circuits 100a, 100b to share a common antenna 760 and also share a common filter group 722. It is assumed that the architectural design includes carrier aggregation capability between low and high frequency bands. If those low-frequency bands span a sufficiently wide range in frequency, it may be desirable to split the low-frequency bands into two subgroups of low-frequency bands and pair each subgroup with a group of high-frequency bands using their respective coupling circuits. You can.

Accordingly, in the example of Figure 28, common filter group 722 may include one or more high frequency bands. The first subgroup of low-frequency filters may be 721a, and the second subgroup of low-frequency filters may be 721b. Once configured in the manner described above, the first subgroup 721a of filters and the common filter group 722 are connected to a first coupling circuit 100a with appropriate L1, C1, C2, L2 values selected to accommodate those groups of filters. ) can be coupled to the common signal node 102a. Similarly, the second subgroup of filters 721b and the common filter group 722 have the appropriate L3, C3, C4, L4 values selected to accommodate the common signal of the second coupling circuit 100b. It may be coupled to node 102b. In some embodiments, phase shifters 103a, 105a, 103b, 105b may be provided as shown and configured to provide desirable phase shifts for improved performance.

Referring to the example of FIG. 28, low-band/high-band carrier aggregation may involve a first subgroup 721a or a second subgroup 721b. Accordingly, if the first subgroup 721a is being utilized, the switch 790 connects the second path of the first coupling circuit 100a to the common filter group 722 and the second coupling circuit 100b. The second path of may be allowed to disconnect from the common filter group 722. Similarly, if the second subgroup 721b is being utilized, switch 790 causes the second path of the first coupling circuit 100a to be disconnected from the common filter group 722 and the second coupling circuit ( The second path of 100b) may be allowed to be connected to the common filter group 722.

In the example of Figure 28, architecture 738 is shown utilizing a common antenna 760. Accordingly, if first coupling circuit 100a is being utilized, its common signal node 102a may be coupled to antenna 760 by switch 792 and the common signal node 102a of second coupling circuit 100b may be coupled to antenna 760 by switch 792. Signal node 102b can be disconnected from antenna 760 by switch 792. Similarly, if second coupling circuit 100b is being utilized, its common signal node 102b may be coupled to antenna 760 by switch 792 and the Common signal node 102a can be disconnected from antenna 760 by switch 792.

Figure 29 shows architecture 740, which may be a more specific example of architecture 740 of Figure 19A. In the example of Figure 29, architecture 740 is shown as including a first filter group 721 with three mid-frequency band duplexers and a second filter group 722 with two high-frequency band duplexers. Half bridge coupling circuit 100 is shown with its common signal node 102 coupled to antenna 760. The node between L1 and C1 of the coupling circuit 100 is shown as coupled to the first filter group 721 via the phase shifter 103. The second filter group 722 is shown coupled to the common signal node 102.

Constructed in the manner described above, impedance Zin1 is presented to the first filter group 721 by the first path, impedance Zin2 is presented to the second filter group 722 by the second path, impedance Zin3 is presented to the inductance L1 is presented to the common signal node 102 by . Therefore, at an intermediate band frequency (for one of the intermediate frequency bands in group 721), Zin1 and Zn3 each have a value at or close to the matched load impedance, and Zin2 has an open circuit value. At high band frequencies (for one of the high frequency bands in group 722), Zin2 has a value at or close to the matched load impedance, Zin1 has a short circuit value, and Zn3 has an open circuit value.

Figure 30 shows an example architecture 800 utilizing many of the features described herein. In the example of Figure 30, two coupling circuits 100a, 100b are shown providing couplings between the common antenna 760 and respective groups of filters. More specifically, first coupling circuit 100a is shown providing coupling between antenna 760 and groups of filters 721a, 722; and a second coupling circuit 100b is shown providing coupling between the antenna 760 and the groups 721b and 722 of filters.

Referring to FIG. 30, filter group 721a is shown as including multiple intermediate frequency band filters including duplexers for the B3Tx/B3Rx and B1Tx/B1Rx bands and a B32Rx band filter. Filter group 721b is shown to include multiple intermediate frequency band filters including duplexers for the B66Tx/B66Rx and B25Tx/B25Rx bands. Filter group 722 includes duplexers for the B7Tx/B7Rx and B30Tx/B30Rx bands, and a number of high frequency band filters including filters B40TRx and B41TRx configured to support Tx and Rx operations in the respective bands. It is shown as Accordingly, the grouping of filters described above utilizes at least some of the features of the example of Figure 28, where the group of filters (low frequency band filters in Figure 28 and mid frequency band filters in Figure 30) are divided into subgroups of filters. Multiple coupling circuits may be utilized to accommodate splitting.

Accordingly, in the example of FIG. 30, the first coupling circuit 100a may include inductances LMB, LHB and capacitances CMB, CHB as shown to support the mid-frequency band and high-frequency band filters described above. Similarly, the second coupling circuit 100b may include inductances LMB, LHB and capacitances CMB, CHB as shown to support the mid-frequency band and high-frequency band filters described above. It will be understood that each of LMB, LHB, CMB, and CHB of the first coupling circuit 100a may or may not have the same value as each of LMB, LHB, CMB, and CHB of the second coupling circuit 100b.

In the example of FIG. 30 , architecture 800 is configured to allow at least some of the filters of group 722 to be shared between first and second coupling circuits 100a and 100b. More specifically, switch 802 may allow the B7Tx/B7Rx duplexer and B41TRx filter to be coupled to the second path of first coupling circuit 100a, or to the second path of second coupling circuit 100b. You can.

In the example of FIG. 30 , switching circuit 804 (e.g., implemented as an antenna switching module (ASM)) connects antenna 760 to first coupling circuit 100a or to second coupling circuit 100b. It can be configured to allow coupling of. More specifically, the common signal node 102a of the first coupling circuit 100a may be coupled to the antenna 760 by appropriate operation of the switching circuit 804. Similarly, common signal node 102b of second coupling circuit 100b may be coupled to antenna 760 by appropriate operation of switching circuit 804.

In the example of Figure 30, architecture 800 may include one or more circuits that do not utilize coupling circuitry. For example, filter group 806 may include time-domain duplexing (TDD) filters, such as intermediate frequency bands B34 and B39. Such a filter group is shown coupled to antenna 760 via switching circuitry 804 without coupling circuitry. In some embodiments, some or all of such TDD bands utilize antenna 760, individually, together with each other, and another frequency-domain duplexing (FDD) band (e.g., one or more filters of group 722). It may be present together with, or in some combination thereof.

In some embodiments, architecture 800 of FIG. 30 includes functionality associated with either or both first and second coupling circuits 100a, 100b, transmission lines configured to provide desirable functionality. , L/C components and/or phase shifting elements such as resonators.

FIG. 31 shows that, in some embodiments, one or more features as described herein may be implemented in a radio-frequency (RF) module 300 (e.g., a front-end module or an LNA module). Module 300 may include a packaging substrate 302, such as a laminate substrate. ]These modules may include one or more LNAs 308. At least one of these LNAs may be configured to operate in CA mode as described herein.

Module 300 may further include a carrier aggregation (CA) circuit 100 having one or more features as described herein. This CA circuit may be configured to provide CA functionality to the LNA 308 via the diplexer/filter assembly 306. Transmission lines 304 may be configured to provide desired phase shifts in various signal paths, including, for example, those associated with the inputs and output(s) of diplexer/filter assembly 306. . Although not shown, module 300 may further include switches for grounding CA circuit 100 to facilitate CA and non-CA operations as described herein.

In some implementations, an architecture, device, and/or circuit having one or more features described herein may be included in an RF device, such as a wireless device. Such architectures, devices and/or circuits may be implemented directly as wireless devices, in the form of one or more modules as described herein, or in some combination thereof. In some embodiments, such wireless devices may include, for example, cellular phones, smartphones, handheld wireless devices with or without phone functionality, wireless tablets, wireless routers, wireless access points, wireless base stations, etc. there is. Although described in the context of a wireless device, it will be understood that one or more features of the present disclosure may also be implemented in other RF systems, such as base stations.

Figure 32 depicts an example wireless device 500 having one or more advantageous features described herein. In some embodiments, these advantageous features may be implemented in a front-end (FE) or LNA module 300 as described herein. Such modules may include CA circuitry 100 having one or more features as described herein. In some embodiments, this module may include more or fewer components than indicated by the dashed box.

PAs within PA module 512 may receive their respective RF signals from transceiver 510, which may be configured and operative to amplify and generate RF signals to be transmitted and process the received signals. Transceiver 510 is shown interacting with baseband subsystem 508 configured to provide conversion between data and/or voice signals suitable for a user and RF signals suitable for transceiver 510. Transceiver 510 is also shown as connected to a power management component 506 configured to manage power for operation of wireless device 500. This power management may also control the operations of baseband subsystem 508 and other components of wireless device 500.

Baseband subsystem 508 is shown as connected to user interface 502 to facilitate various input and output of voice and/or data provided to and received from a user. Baseband subsystem 508 may also be connected to memory 504 configured to store data and/or instructions to facilitate operation of the wireless device and/or to provide storage of information for a user.

In the example wireless device 500, module 300 may include one or more carrier aggregation capable signal paths configured to provide one or more functionality as described herein. In some embodiments, at least some of the signals received via diversity antenna 530 may be routed to one or more low-noise amplifiers (LNAs) 308 via these carrier aggregation capable signal path(s). there is. Amplified signals from LNA 308 are shown being routed to transceiver 510.

A number of different wireless device configurations may utilize one or more features described herein. For example, a wireless device is not necessarily a multi-band device. In another example, a wireless device may include additional antennas, such as a diversity antenna, and additional connectivity features such as Wi-Fi, Bluetooth, and GPS.

One or more features of the disclosure may be implemented in various cellular frequency bands as described herein. Examples of these bands are listed in Table 1. It will be appreciated that at least some of the bands may be divided into subbands. It will also be appreciated that one or more features of the disclosure may be implemented in frequency ranges that do not have designations such as the examples in Table 1.

Although various examples herein have been described in the context of carrier aggregation of two or three bands, one or more features of the disclosure may also be implemented in configurations involving carrier aggregation of different numbers of bands. Be careful.

Unless the context clearly requires otherwise, throughout the description and claims, the words “comprise,” “comprising,” and the like are used in an inclusive rather than exclusive or exhaustive sense. must be interpreted in terms of meaning; That is, it means “including but not limited to.” As commonly used herein, the word "coupled" refers to two or more elements that may be connected directly or by one or more intermediate elements. Additionally, the terms “herein,” “above,” “below,” and words of similar meaning, when used in this application, refer to this application and not to any specific portion of this application. will be referred to as a whole. Where the context permits, words in the above detailed description using the singular or plural number may also include the plural or singular number, respectively. The word “or” referring to a list of two or more items covers all of the following interpretations of the word: any of the items in the list, all of the items in the list, and any combination of items in the list.

The above detailed description of embodiments of the invention is not intended to be exhaustive or to limit the invention to the precise form disclosed above. Although specific embodiments and examples of the invention have been described above for purposes of illustration, various equivalent modifications are possible within the scope of the invention, as those skilled in the art will recognize. For example, although processes or blocks are presented in a given order, alternative embodiments may employ systems that perform routines or have blocks with steps in a different order, with some processes or blocks being deleted, moved, Can be added, subdivided, combined, and/or modified. Each of these processes or blocks may be implemented in a variety of different ways. Additionally, although processes or blocks are sometimes shown as being performed in series, these processes or blocks may instead be performed in parallel, or may be performed at different times.

The teachings of the invention provided herein may be applied to other systems, not necessarily just those described above. Elements and acts of the various embodiments described above may be combined to provide additional embodiments.

Although some embodiments of the invention have been described, these embodiments are presented by way of example only and are not intended to limit the scope of the disclosure. In fact, the new methods and systems described herein may be embodied in a variety of different forms; Moreover, various omissions, substitutions and changes may be made in the form of the methods and systems described herein without departing from the spirit of the disclosure. The appended claims and their equivalents are intended to cover all such forms or modifications as fall within the scope and spirit of the present disclosure.

Claims (45)

As a radio frequency architecture:
a first group of plural filters each configured to support one band such that the first frequency range covers each plurality of bands;
a second group of one or more filters each configured to support one band such that the second frequency range covers each one or more bands, each filter in the first group being configured to respond to signals in each band in the second group and configured to provide an impedance at or near the short-circuit impedance for the signal in the respective band of the first group, wherein each filter in the second group provides an impedance at or near the short-circuit impedance. configured -; and
a coupling circuit comprising a common node and configured to couple the common node to one of the first and second groups via a first path and to couple the common node to the other group via a second path - the couple The ring circuit is further configured such that the impedance provided by each filter of the first group for a signal in each band of the second group results in sufficient exclusion of the signal from the first path. Radio frequency architecture including: 2. The method of claim 1, wherein the coupling circuit is such that the impedance provided by each filter of the second group for a signal in each band of the first group is such that the signal is sufficiently excluded from the second path. A radio frequency architecture further configured to produce. 3. The method of claim 2, wherein the first and second groups of filters are implemented as one or more multiplexers, the coupling circuit includes a resonator, and/or the radio frequency architecture is configured to form one of the first and second paths. A radio frequency architecture further comprising switching circuitry configured to provide filter selection functionality along either or both. 4. The method of claim 3, wherein the first path presents a first impedance Z1 to the coupling circuit, and the second path presents a second impedance to the coupling circuit such that the complex part of Z1 is a conjugate of the complex part of Z1. Radio frequency architecture presenting impedance Z2. 5. The radio frequency architecture of claim 4, wherein the first impedance Z1 is one of the capacitive impedance and the inductive impedance, and the second impedance Z2 is the other one of the capacitive impedance and the inductive impedance. 5. The radio frequency architecture of claim 4, wherein the complex portion of Z1 is approximately zero and the complex portion of Z2 is approximately zero. 5. The method of claim 4, wherein at least some of the filters in the first group and the second group are configured to provide the first impedance Z1 to the first path and the second impedance Z2 to the second path. Radio frequency architecture. 8. The radio frequency architecture of claim 7, wherein both the first group and the second group of filters are configured to provide the first impedance Z1 for the first path and the second impedance Z2 for the second path. . 4. The radio frequency architecture of claim 3, wherein each of the first and second paths includes a phase shifter. 10. The method of claim 9, further comprising a third group of one or more filters each configured to support one band such that a third frequency range covers the respective one or more bands, wherein the phase of the first and second paths A radio frequency architecture wherein shifters are configured to reduce mutual loading between each filter of the third group and each filter of one or both of the first and second groups. 11. The method of claim 10, wherein the plurality of bands supported by the first group are low frequency bands and the one or more bands supported by the second group are high frequency band(s) and supported by the third group. A radio frequency architecture wherein the one or more bands are intermediate frequency band(s). 4. The method of claim 3, wherein the third frequency range further comprises a third group of one or more filters each configured to support one band such that the third frequency range covers the respective one or more bands, wherein each filter of the third group is configured to support one or more bands. configured to provide an impedance at or near a short-circuit impedance for signals in the respective bands of the first and second groups, wherein each filter of the first and second groups has a respective filter of the third group. A radio frequency architecture further configured to provide an impedance at or near the short circuit impedance for signals in the band. 13. The circuit of claim 12, comprising a common node and configured to couple its common node to a common node of the coupling circuit via a third path and to couple its common node to the third group via a fourth path. further comprising another coupling circuit, wherein the other coupling circuit is such that the impedance provided by each filter of the first and second groups for the signal in each band of the third group is such that the signal is 3 results in sufficient exclusion from the path, and the impedance provided by each filter of the third group for a signal in each band of the first and second groups sufficiently excludes the signal from the fourth path. A radio frequency architecture further configured to result in 14. The radio frequency architecture of claim 13, wherein the common node of the different coupling circuits is an antenna node. 14. The method of claim 13, wherein the plurality of bands supported by the first group are low frequency bands and the one or more bands supported by the second group are mid-frequency band(s) and by the third group A radio frequency architecture wherein the one or more bands supported are high frequency band(s). 4. The method of claim 3, wherein the first path is coupled to the first group such that a phase shifting element is provided between the first path and each of the plurality of filters, and the second path is coupled to the first group such that a phase shifting element is provided between the first path and each of the plurality of filters. A radio frequency architecture coupled to the second group to provide between two paths and each of the one or more filters. 17. The radio frequency architecture of claim 16, wherein each phase shifting element comprises a transmission line, LC component, or resonator. 18. The radio frequency architecture of claim 17, wherein the resonator comprises an acoustic resonator. 17. The radio frequency architecture of claim 16, wherein the coupling circuit includes a resonator. 20. The radio frequency architecture of claim 19, wherein the resonator comprises an acoustic resonator. 20. The method of claim 19, wherein the coupling circuit includes a first circuit and a second circuit coupling the common node to ground in parallel, the first circuit being a second circuit in series between the common node and the ground. 1. A radio frequency architecture comprising an inductance L1 and a capacitance, and the second circuit comprising the resonator and a second inductance L2 in series between the common node and the ground. 4. The radio frequency architecture of claim 3, wherein the radio frequency architecture further comprises switching circuitry implemented to provide filter selection functionality along either or both the first path and the second path. 23. The radio frequency architecture of claim 22, wherein the switching circuitry includes a switch configured to allow selection of a filter from a plurality of filters within the same group such that the selected filter is coupled to a respective one of the first and second paths. 23. The method of claim 22, wherein the switching circuitry allows coupling of a selected one of the first and second paths to or to a third group of one or more filters each configured to support a band. A radio frequency architecture comprising a switch configured so that a third frequency range covers the respective one or more bands. 25. The method of claim 24, wherein each filter of the third group is at or near a short circuit impedance for a signal in each band of the group corresponding to an unselected path of the first and second paths. configured to provide an impedance, wherein each filter of the group corresponding to an unselected path of the first and second paths is at or near a short circuit impedance for a signal in each band of the third group. A radio frequency architecture further configured to provide an impedance at . 26. The radio frequency architecture of claim 25, wherein the group corresponding to a selected one of the first and second paths and the third group are subgroups within a frequency range corresponding to a low frequency range, a mid frequency range, or a high frequency range. 23. The radio frequency architecture of claim 22, wherein the switching circuitry includes a switch configured to allow selection of an antenna from a plurality of antennas such that the selected antenna is coupled to a common node of the coupling circuit. 23. The radio frequency architecture of claim 22, further comprising a third group of one or more filters each configured to support one band such that the third frequency range covers the respective one or more bands. 29. The method of claim 28, wherein each filter in the third group is configured to provide an impedance at or near a short circuit impedance for a signal in each band in the second group, and wherein each filter in the second group is configured to provide an impedance at or near the short circuit impedance. and the filter is further configured to provide an impedance at or near a short circuit impedance for signals in each band of said third group. 30. Another coupling according to claim 29, comprising a common node and configured to couple its common node to the third group via a third path and to couple its common node to the second group via a fourth path. A radio frequency architecture that additionally includes circuitry. 31. The method of claim 30, wherein the other coupling circuit is such that the impedance provided by each filter of the second group for the signal in each band of the third group is such that the signal is sufficiently excluded from the third path. Resulting in an impedance provided by each filter in the third group for a signal in each band of the second group such that the signal is sufficiently excluded from the fourth path. Frequency architecture. 32. The method of claim 31, wherein the first group and the third group are subgroups within a frequency range corresponding to a low frequency range, a middle frequency range, or a high frequency range, and the second group is a subgroup within the low frequency range, the middle frequency range, and the high frequency range. A radio frequency architecture within a frequency range other than the corresponding range of the range. 31. The method of claim 30, wherein the switching circuit is such that the coupling circuit is coupled to the second group through the second path, or the other coupling circuit is coupled to the second group through the fourth path. A radio frequency architecture that includes switches configured to accept. 31. The radio frequency architecture of claim 30, wherein the switching circuitry includes a switch configured to allow a common node of the coupling circuit to be coupled to an antenna, or a common node of the other coupling circuit to be coupled to the antenna. 4. The method of claim 3, wherein the coupling circuit includes a first LC circuit and a second LC circuit coupling the common node to ground in parallel, the first LC circuit comprising a first inductance L1 and a second inductance L1 in series. 1. A radio frequency architecture comprising a capacitance C1, and the second LC circuit comprising a second capacitance C2 and a second inductance L2 in series. 36. The radio frequency architecture of claim 35, wherein the first path is coupled to the coupling circuit at a node between LI and C1 and the second path is coupled to the coupling circuit at a node between C2 and L2. As a packaged module:
A packaging substrate configured to receive a plurality of components; and
A first group of a plurality of filters implemented on the packaging substrate and each configured to support one band such that the first frequency range covers the respective plurality of bands, and the second frequency range covers the respective one or more bands. A radio frequency circuit comprising a second group of one or more filters, each filter configured to support a band, such that each filter in the first group has a short-circuit impedance for a signal in a respective band of the second group or configured to provide an impedance at or near the short circuit impedance for a signal in each band of the first group, wherein each filter in the second group is configured to provide an impedance at or near the short circuit impedance, and wherein the radio frequency The circuit includes a common node and a coupling circuit configured to couple the common node to one of the first and second groups via a first path and to couple the common node to the other group via a second path. and wherein the coupling circuit is such that the impedance provided by each filter of the first group for a signal in each band of the second group is such that the signal is sufficiently excluded from the first path. Further configured to produce - A packaged module containing a . 38. The method of claim 37, wherein the coupling circuit is such that an impedance provided by each filter of the second group for a signal in each band of the first group is sufficient to exclude the signal from the second path. A packaged module further configured to produce a . 9. The method of claim 8, wherein the first and second groups of filters are implemented as one or more multiplexers, the coupling circuit includes a resonator, and/or the radio frequency architecture is configured to form one of the first and second paths. A packaged module further comprising switching circuitry configured to provide filter selection functionality along either or both. 40. The method of claim 39, wherein the first path presents a first impedance Z1 to the coupling circuit, and the second path presents a second impedance to the coupling circuit such that the complex portion of Z1 is the conjugate of the complex portion of Z1. Packaged module presenting impedance Z2. 41. The packaged module of claim 40, wherein the first impedance Z1 is one of the capacitive impedance and the inductive impedance, and the second impedance Z2 is the other one of the capacitive impedance and the inductive impedance. 42. The packaged module of claim 41, wherein the complex portion of Z1 is approximately zero and the complex portion of Z2 is approximately zero. 40. The packaged module of claim 39, wherein the radio frequency circuitry is configured to support carrier aggregation operation. 40. The packaged module of claim 39, wherein the radio frequency circuitry is configured to support receive operations involving diversity antennas. As a wireless device:
one or more antennas;
A first group of filters in communication with the one or more antennas and each configured to support a band such that the first frequency range covers the respective plurality of bands, and the second frequency range covers the respective one or more bands A front-end module comprising a radio frequency circuitry having a second group of one or more filters, each configured to support a band, to cover a signal in a respective band of the second group, each filter in the first group and configured to provide an impedance at or near the short-circuit impedance for the signal in each band of the first group, wherein each filter in the second group provides an impedance at or near the short-circuit impedance. and the radio frequency circuit is configured to include a common node and couple the common node to one of the first and second groups through a first path and to couple the common node to the other group through a second path. and further comprising a coupling circuit configured to couple, wherein the coupling circuit is such that the impedance provided by each filter of the first group for the signal in each band of the second group is such that the signal is 1 is further constructed to result in sufficient exclusion from the path -; and
A wireless device comprising a receiver in communication with the front end module and configured to process one or more signals associated with the first and second groups.

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