KR20210045911A - An electronic device comprising a resonant charging circuit - Google Patents

Abstract

According to an embodiment disclosed in this document, is provided an electronic device, which includes a battery, a power management module, and a processor electrically connected to the power management module. The power management module includes a charging circuit comprising a plurality of switches, at least one capacitor, and at least one inductor, and configured to receive power from an external power supply. The power management module checks electrical connection between the charging circuit and the external power supply device, operates in a first mode to charge the battery when a type of the external power supply device is a first type, and operates in a second mode to charge the battery when the type of the external power supply device is a second type. In addition to this, various embodiments identified through the specification are possible. According to the present invention, a resonant SCVD can be configured using a flying capacitor having a relatively small capacity.

Description

An electronic device comprising a resonant charging circuit

Various embodiments disclosed in this document relate to an electronic device including a resonant charging circuit.

An electronic device such as a smartphone or a tablet PC may operate using power provided from a battery. The power management module (eg, a power management integrated circuit (PMIC)) may transfer power provided from a battery to various components (eg, a processor, a memory, or a communication chip) inside the electronic device.

The battery inside the electronic device may be charged through an external power source. Recently, various charging methods, wired or wireless, have been applied for fast charging. Among the fast charging methods, in the direct charging technology, an external power device (eg, a power adapter) performs constant voltage or constant current control for a battery inside the electronic device, and a charging circuit inside the electronic device can be simplified. In addition, the direct charging technology can reduce heat generation in the electronic device and charge the battery with a high current.

The electronic device may support charging by direct charging technology using a switched capacitor voltage divider (SCVD) circuit. Unlike general switching converters, the SCVD circuit can achieve high efficiency of about 96% or more to reduce heat generation of electronic devices, but the voltage conversion ratio may be fixed depending on the circuit configuration. Accordingly, compatibility with various types of power devices or charging devices may be limited.

For example, when connected to a legacy power adapter that supplies a fixed voltage of about 5V or 9V, the SCVD circuit cannot perform a charging operation, so a separate switching charger may need to be installed. Accordingly, a space for mounting parts inside the electronic device may be reduced, and the price of the electronic device may increase due to the additional parts.

An electronic device according to various embodiments of the present disclosure includes a battery, a power management module electrically connected to the battery, and managing charging or discharging of the battery, and a processor electrically connected to the power management module, and the power management module A charging circuit comprising a plurality of switches, at least one capacitor, and at least one inductor, and configured to receive power from an external power supply device, wherein the power management module performs electrical connection between the charging circuit and the external power supply device. Check, determine the type of the connected external power supply device, and when the type of the external device is a first type, the plurality of charging circuits may have a fixed voltage conversion ratio due to resonance of the capacitor and the inductor. When the type of the external power supply is a second type, the plurality of charging circuits change the voltage conversion ratio in response to the charging ratio of the battery when the battery is charged by operating in a first mode of controlling the switches of The battery may be charged by operating in a second mode for controlling the switches of.

The electronic device according to various embodiments disclosed in the present document may correspond to both a power supply device supporting direct charging or a legacy power adapter that does not support direct charging by using one resonance type SCVD.

The electronic device according to various embodiments disclosed in this document may support charging of a plurality of types of power supply devices with one resonance type SCVD by using switching control signals having different operating frequencies or different duty cycles. .

An electronic device according to various embodiments disclosed in this document may configure a resonance type SCVD using a flying capacitor having a relatively small capacity.

An electronic device according to various embodiments disclosed in this document may configure a 3-level buck converter using a resonant SCVD circuit.

The electronic device according to various embodiments disclosed in this document may control switching by using a current flowing through an inductor of a resonance type SCVD or a voltage across a flying capacitor. Through this, power conversion efficiency during charging can be increased, and EMI reduction and system efficiency can be improved due to the operation of the resonant converter.

1 is an electronic device in a network environment, according to various embodiments.
2 is a block diagram of a power management module and a battery according to various embodiments.
3 is a flowchart illustrating a method of charging an electronic device according to types of external power devices according to various embodiments of the present disclosure.
4 shows a configuration of a charging circuit according to various embodiments.
5 illustrates an operation of a first mode of a charging circuit according to various embodiments.
6 illustrates an operation in a second mode according to various embodiments.
7A illustrates a switching control circuit according to various embodiments.
7B illustrates generation of a switching control signal in a second mode according to various embodiments.
8 illustrates a switching control circuit in a second mode according to various embodiments.
9 illustrates a control circuit additionally using a voltage across a flying capacitor according to various embodiments.
10 illustrates a change in a voltage control method switching signal in a first state of a second mode according to various embodiments of the present disclosure.
11 illustrates a change in a voltage control method switching signal in a second state of a second mode according to various embodiments of the present disclosure.
12 illustrates a change in a voltage control method switching signal in a third state of a second mode according to various embodiments of the present disclosure.
13 illustrates a change in a switching signal of a voltage control scheme in a fourth state of a second mode according to various embodiments of the present disclosure.
14 illustrates a switching control circuit of a current control method in a second mode according to various embodiments.
15 illustrates a control circuit additionally using voltages across both ends of a flying capacitor according to various embodiments of the present disclosure.
16 illustrates changes in a switching signal of a current control method in a first state of a second mode according to various embodiments of the present disclosure.
17 illustrates a change in a switching signal of a current control method in a second state of a second mode according to various embodiments of the present disclosure.
18 illustrates a change in a switching signal of a current control method in a third state of a second mode according to various embodiments of the present disclosure.
19 illustrates a change in a switching signal of a current control method in a fourth state of a second mode according to various embodiments of the present disclosure.
In connection with the description of the drawings, the same or similar reference numerals may be used for the same or similar components.

Hereinafter, various embodiments of the present document will be described with reference to the accompanying drawings. However, this is not intended to limit the techniques described in this document to specific embodiments, and should be understood to include various modifications, equivalents, and/or alternatives of the embodiments of this document. . In connection with the description of the drawings, similar reference numerals may be used for similar elements.

1 is a block diagram of an electronic device 101 in a network environment 100 according to various embodiments. An electronic device according to various embodiments disclosed in this document may be a device of various types. The electronic device is, for example, a portable communication device (eg, a smartphone), a computer device (eg, a personal digital assistant (PDA), a tablet PC (tablet PC)), a laptop PC (desktop PC, workstation, or server), It may include at least one of a portable multimedia device (eg, an electronic book reader or MP3 player), a portable medical device (eg, a heart rate, blood sugar, blood pressure, or body temperature meter), a camera, or a wearable device. (E.g. watches, rings, bracelets, anklets, necklaces, glasses, contact lenses, or head-mounted-devices (HMD)), fabric or clothing integrals (e.g. electronic clothing), body-attached (e.g. : A skin pad or a tattoo), or a bio-implantable circuit In some embodiments, the electronic device is, for example, a television, a digital video disk (DVD) player, an audio device, an audio accessory. Devices (e.g. speakers, headphones, or headsets), refrigerators, air conditioners, vacuum cleaners, ovens, microwaves, washing machines, air purifiers, set-top boxes, home automation control panels, security control panels, game consoles, electronic dictionaries, electronic keys, It may include at least one of a camcorder or an electronic picture frame.

In another embodiment, the electronic device is a navigation device, a global navigation satellite system (GNSS), an event data recorder (EDR) (e.g., a black box for a vehicle/ship/airplane), and an automobile infotainment device. (E.g. head-up displays for vehicles), industrial or home robots, drones, automated teller machines (ATMs), point of sales (POS) devices, measuring devices (e.g. water, electricity, or gas measuring devices), Alternatively, it may include at least one of IoT devices (eg, a light bulb, a sprinkler device, a fire alarm, a temperature controller, or a street light). The electronic device according to the embodiment of the present document is not limited to the above-described devices, and, for example, as in the case of a smartphone equipped with a function of measuring personal biometric information (eg, heart rate or blood sugar), a plurality of It is possible to provide complex functions of devices. In this document, the term user may refer to a person using an electronic device or a device (eg, an artificial intelligence electronic device) using an electronic device.

In the network environment 100, the electronic device 101 communicates with the electronic device 102 through a first network 198 (for example, a short-range wireless communication network), or a second network 199 (for example, a long-distance wireless communication network). Network) through the electronic device 104 or the server 108. According to an embodiment, the electronic device 101 may communicate with the electronic device 104 through the server 108. According to an embodiment, the electronic device 101 includes a processor 120, a memory 130, an input device 150, an audio output device 155, a display device 160, an audio module 170, and a sensor module ( 176, interface 177, haptic module 179, camera module 180, power management module 210, battery 189, communication module 190, subscriber identification module 196, or antenna module 197 ) Can be included. In some embodiments, at least one of these components (for example, the display device 160 or the camera module 180) may be omitted or one or more other components may be added to the electronic device 101. In some embodiments, some of these components may be implemented as one integrated circuit. For example, the sensor module 176 (eg, a fingerprint sensor, an iris sensor, or an illuminance sensor) may be implemented while being embedded in the display device 160 (eg, a display).

The processor 120, for example, executes software (eg, a program 140) to configure at least one other component (eg, a hardware or software component) of the electronic device 101 connected to the processor 120. It can be controlled and can perform various data processing or operations. According to an embodiment, as at least a part of data processing or operation, the processor 120 may transfer commands or data received from other components (eg, the sensor module 176 or the communication module 190) to the volatile memory 132. It is loaded into, processes commands or data stored in the volatile memory 132, and the result data may be stored in the nonvolatile memory 134. According to an embodiment, the processor 120 includes a main processor 121 (eg, a central processing unit or an application processor), and a secondary processor 123 (eg, a graphic processing unit, an image signal processor) that can be operated independently or together. , A sensor hub processor, or a communication processor). Additionally or alternatively, the coprocessor 123 may be set to use lower power than the main processor 121 or to be specialized for a designated function. The secondary processor 123 may be implemented separately from the main processor 121 or as a part thereof.

The co-processor 123 is, for example, in place of the main processor 121 while the main processor 121 is in an inactive (eg, sleep) state, or the main processor 121 is active (eg, executing an application). ) While in the state, together with the main processor 121, at least one of the components of the electronic device 101 (for example, the display device 160, the sensor module 176, or the communication module 190) It is possible to control at least some of the functions or states associated with it. According to an embodiment, the coprocessor 123 (eg, an image signal processor or a communication processor) may be implemented as a part of other functionally related components (eg, the camera module 180 or the communication module 190). have.

The memory 130 may store various data used by at least one component of the electronic device 101 (eg, the processor 120 or the sensor module 176 ). The data may include, for example, software (eg, the program 140) and input data or output data for commands related thereto. The memory 130 may include a volatile memory 132 or a nonvolatile memory 134.

The program 140 may be stored as software in the memory 130, and may include, for example, an operating system 142, middleware 144, or an application 146.

The input device 150 may receive a command or data to be used for a component of the electronic device 101 (eg, the processor 120) from outside (eg, a user) of the electronic device 101. The input device 150 may include, for example, a microphone, a mouse, a keyboard, or a digital pen (eg, a stylus pen).

The sound output device 155 may output an sound signal to the outside of the electronic device 101. The sound output device 155 may include, for example, a speaker or a receiver. The speaker can be used for general purposes such as multimedia playback or recording playback, and the receiver can be used to receive incoming calls. According to one embodiment, the receiver may be implemented separately from the speaker or as part of the speaker.

The display device 160 may visually provide information to the outside of the electronic device 101 (eg, a user). The display device 160 may include, for example, a display, a hologram device, or a projector and a control circuit for controlling the device. According to an embodiment, the display device 160 may include a touch circuitry set to sense a touch, or a sensor circuit (eg, a pressure sensor) set to measure the strength of a force generated by the touch. have.

The audio module 170 may convert sound into an electrical signal, or conversely, may convert an electrical signal into sound. According to an embodiment, the audio module 170 acquires sound through the input device 150, the sound output device 155, or an external electronic device (eg: Sound may be output through the electronic device 102 (for example, a speaker or headphones).

The sensor module 176 detects an operating state (eg, power or temperature) of the electronic device 101, or an external environmental state (eg, a user state), and generates an electrical signal or data value corresponding to the detected state. can do. According to an embodiment, the sensor module 176 is, for example, a gesture sensor, a gyro sensor, an atmospheric pressure sensor, a magnetic sensor, an acceleration sensor, a grip sensor, a proximity sensor, a color sensor, an infrared (IR) sensor, a biometric sensor, It may include a temperature sensor, a humidity sensor, or an illuminance sensor.

The interface 177 may support one or more designated protocols that may be used for the electronic device 101 to directly or wirelessly connect with an external electronic device (eg, the electronic device 102). According to an embodiment, the interface 177 may include, for example, a high definition multimedia interface (HDMI), a universal serial bus (USB) interface, an SD card interface, or an audio interface.

The connection terminal 178 may include a connector through which the electronic device 101 can be physically connected to an external electronic device (eg, the electronic device 102). According to an embodiment, the connection terminal 178 may include, for example, an HDMI connector, a USB connector, an SD card connector, or an audio connector (eg, a headphone connector).

The haptic module 179 may convert an electrical signal into a mechanical stimulus (eg, vibration or movement) or an electrical stimulus that a user can perceive through tactile or motor sensations. According to an embodiment, the haptic module 179 may include, for example, a motor, a piezoelectric element, or an electrical stimulation device.

The camera module 180 may capture a still image and a video. According to an embodiment, the camera module 180 may include one or more lenses, image sensors, image signal processors, or flashes.

The power management module 188 may manage power supplied to the electronic device 101. According to an embodiment, the power management module 188 may be implemented as at least a part of, for example, a power management integrated circuit (PMIC).

The battery 189 may supply power to at least one component of the electronic device 101. According to an embodiment, the battery 189 may include, for example, a non-rechargeable primary cell, a rechargeable secondary cell, or a fuel cell.

The communication module 190 includes a direct (eg, wired) communication channel or a wireless communication channel between the electronic device 101 and an external electronic device (eg, the electronic device 102, the electronic device 104, or the server 108). It is possible to support establishment and communication through the established communication channel. The communication module 190 operates independently of the processor 120 (eg, an application processor) and may include one or more communication processors supporting direct (eg, wired) communication or wireless communication. According to an embodiment, the communication module 190 is a wireless communication module 192 (eg, a cellular communication module, a short-range wireless communication module, or a global navigation satellite system (GNSS) communication module) or a wired communication module 194 (eg : A local area network (LAN) communication module, or a power line communication module) may be included. Among these communication modules, a corresponding communication module is a first network 198 (for example, a short-range communication network such as Bluetooth, WiFi direct or IrDA (infrared data association)) or a second network 199 (for example, a cellular network, the Internet, or It may communicate with the external electronic device 104 through a computer network (for example, a telecommunication network such as a LAN or WAN). These various types of communication modules may be integrated into a single component (eg, a single chip), or may be implemented as a plurality of separate components (eg, multiple chips). The wireless communication module 192 uses subscriber information stored in the subscriber identification module 196 (eg, International Mobile Subscriber Identifier (IMSI)) in a communication network such as the first network 198 or the second network 199. The electronic device 101 can be checked and authenticated.

The antenna module 197 may transmit a signal or power to the outside (eg, an external electronic device) or receive from the outside. According to an embodiment, the antenna module 197 may include one antenna including a conductor formed on a substrate (eg, a PCB) or a radiator formed of a conductive pattern. According to an embodiment, the antenna module 197 may include a plurality of antennas. In this case, at least one antenna suitable for a communication method used in a communication network such as the first network 198 or the second network 199 is, for example, provided by the communication module 190 from the plurality of antennas. Can be chosen. The signal or power may be transmitted or received between the communication module 190 and an external electronic device through the at least one selected antenna. According to some embodiments, other components (eg, RFIC) other than the radiator may be additionally formed as part of the antenna module 197.

At least some of the components are connected to each other through a communication method (e.g., a bus, general purpose input and output (GPIO), serial peripheral interface (SPI), or mobile industry processor interface (MIPI))) between peripheral devices and a signal ( E.g. commands or data) can be exchanged with each other.

According to an embodiment, commands or data may be transmitted or received between the electronic device 101 and the external electronic device 104 through the server 108 connected to the second network 199. Each of the external electronic devices 102 and 104 may be a device of the same or different type as the electronic device 101. According to an embodiment, all or part of the operations executed by the electronic device 101 may be executed by one or more of the external electronic devices 102, 104, or 108. For example, when the electronic device 101 needs to perform a function or service automatically or in response to a request from a user or another device, the electronic device 101 In addition or in addition, it is possible to request one or more external electronic devices to perform the function or at least part of the service. One or more external electronic devices receiving the request may execute at least a part of the requested function or service, or an additional function or service related to the request, and transmit a result of the execution to the electronic device 101. The electronic device 101 may process the result as it is or additionally and provide it as at least a part of a response to the request. For this, for example, cloud computing, distributed computing, or client-server computing technology may be used.

2 is a block diagram of a power management module and a battery according to various embodiments.

Referring to FIG. 2, the electronic device 201 (eg, the electronic device 101 of FIG. 1) includes a power management module 210 (eg, the power management module 188 of FIG. 1) and a battery 220 (eg, : It may include a battery 189 of FIG. 1 ). According to various embodiments, the power management module 210 (eg, Charger IC, or PMIC) includes a charging circuit 230, and a current output from the battery 220 and/or a current flowing into the battery 220 Can control the flow of.

The power management module 210 may utilize power received from the battery 220 as a system supply source. The power management module 210 may supply power suitable for a voltage level required for each element inside the electronic device 201.

The power management module 210 may charge the battery 220 with power provided from the external power supply 202. For example, the external power supply 202 may be a fast charging power adapter, a travel adapter (TA), a battery pack, or a wireless power transmission device (eg, a wireless charging pad or an electronic device).

According to various embodiments, the power management module 210 may further include a separate operation element (or control unit) therein. An operation element (eg, a logic circuit or a micro controller unit (MCU)) inside the power management module 210 may perform calculations and controls related to charging or discharging the battery 220. According to an embodiment, the operation element may control a plurality of switches in the charging circuit 230. According to another embodiment, the operation element controls a plurality of switches inside the charging circuit 230 according to a control signal provided from a processor (eg, the processor 120 of FIG. 1) inside the electronic device 201. can do.

According to various embodiments, the charging circuit 230 may charge the battery 220 using power supplied from the external power supply 202 for the electronic device 201.

According to various embodiments, the charging circuit 230 may include a plurality of switches 250, a flying capacitor 260 and/or an inductor 280. The flying capacitor 260 may mean a capacitor used to increase a voltage. The charging circuit 230 may operate as a voltage distribution circuit due to resonance of the flying capacitor 260 and the inductor 280.

According to various embodiments, the charging circuit 230 may operate in different modes depending on the type of the external power supply device 202.

According to an embodiment, when the external power supply 202 supports direct charging among the fast charging methods, the charging circuit 230 operates in a first mode having a fixed voltage conversion ratio (eg, about 2:1). can do. The direct charging technology may be a charging method in which the external power device 202 (eg, a power adapter) performs constant voltage or constant current control for the battery 220 inside the electronic device 201. For example, the electronic device 101 and the external power supply 202 may transmit and receive signals related to charging of the battery 220 through power delivery (PD) communication. In an embodiment, the external power supply 202 may perform constant voltage or constant current control for charging the battery 220 by using a programmable power supply (PPS) function of USB PD 3.0.

When the external power supply 202 supports direct charging, constant voltage or constant current control is performed inside the external power supply 202, and the charging circuit 230 has a fixed voltage conversion ratio (eg, about 2:1). According to the voltage, the battery 220 may be charged. In the first mode, the charging circuit 230 may operate with a relatively high charging efficiency (eg, about 96% or more), and heat generation of the charging circuit 230 may be reduced. In addition, in the first mode, in the charging circuit 230, the switching signal may have a sinusoidal characteristic, and the switching loss may be reduced.

According to another embodiment, when the external power supply 202 is a legacy power adapter that does not support direct charging, the charging circuit 230 adjusts the voltage conversion ratio according to the degree of charge of the battery 220 It is possible to operate in the second mode to be used. For example, in the second mode, the charging circuit 230 may operate as a 3-level buck converter in which the power conversion ratio is adjusted in a pulse width modulation (PWM) method. have.

In the second mode, the switching operation of the plurality of switches 250 may be controlled based on the current flowing into the battery 220 or the voltage across the battery 220. The flying capacitor 260 may operate in one of a charge state, an idle state, or a discharge state according to the switching of the plurality of switches 250 (FIG. 6, FIG. 7A or FIG. 7b). The battery 220 may be charged with power provided by the external power supply 202. The battery 220 may supply power required for the operation of the electronic device 201. The battery 220 may include, for example, a lithium-ion battery or a rechargeable battery.

3 is a flowchart illustrating a method of charging an electronic device according to a type of an external power supply device according to various embodiments of the present disclosure.

Referring to FIG. 3, in operation 310, the power management module 210 of the electronic device 201 may check the electrical connection of the external power supply device 202. For example, the electronic device 201 may be connected to the external power supply 202 by wire or wirelessly through an interface (eg, the interface 177 of FIG. 1 ). The power management module 210 may receive power from the external power supply 202.

In operation 320, the power management module 210 is a first type of power supply device (for example, power supply unit 202) performs constant voltage or constant current control for charging the battery 220 by the external power supply unit 202. adapter).

According to an embodiment, the power management module 210 may determine that the external power device 202 is a first type of power device if power delivery (PD) communication is possible with the connected external power device 202. For example, the power management module 210 may determine whether the external power device 202 is a first type power device by using a programmable power supply (PPS) function of USB PD 3.0.

According to an embodiment, when the power management module 210 is unable to communicate with the connected external power supply 202 and PD (power delivery), the external power supply 202 is a second type power supply device (eg, direct charging). It can be determined that it is a legacy power adapter that does not support. The second type of external power supply device 202 cannot perform constant voltage or constant current control on the battery 220 inside the electronic device 201 and may be a device that provides a fixed voltage. For example, the second type of power supply may be a legacy power adapter that supplies a fixed voltage of about 5V or 9V. The charging circuit 230 inside the electronic device 201 may change the voltage conversion ratio according to the degree of charging of the battery 220.

In operation 330, when the external power supply 202 is a first type of power supply, the power management module 210 controls the charging circuit 230 to charge by operating in a first mode having a fixed voltage conversion ratio. I can. For example, in the first mode, the voltage conversion ratio of the charging circuit 230 may be fixed to about 2:1. When the maximum current capacity of the standard USB type C cable is 3A, the first type power supply may supply power to the battery 220 while maintaining the maximum input current to about 3A or less. The charging circuit 230 having a voltage conversion ratio of 2:1 may step down the voltage of power delivered from the power adapter to about 1/2 to increase the current by about doubling and transfer the current to the battery 220. Through this, while maintaining the maximum current capacity of the standard USB type C cable, it is possible to charge the battery 220 with high power. In the first mode, the charging circuit 230 can obtain relatively high efficiency (eg, about 96% or more), and can perform fast charging while reducing heat generation.

According to an embodiment, in the first mode, the power management module 210 is a charging circuit based on a signal having a fixed first duty cycle (eg, about 50%) and a first frequency (eg, about 500KHz). 230) can be controlled. The first frequency may be set to a value equal to the resonant frequency of the flying capacitor 260 and the inductor 280 of the output terminal.

According to an embodiment, the charging circuit 230 may reduce switching loss by resonant operation of the flying capacitor 260 and the inductor 280 of the output terminal (see FIG. 5 ).

In operation 340, when the external power supply 202 is a second type of power supply (eg, a legacy power adapter that does not support direct charging), the power management module 210 is The voltage conversion ratio may be controlled to be charged by operating in a second mode in which the voltage conversion ratio is adjusted according to the charging rate of the battery 220.

According to an embodiment, in the second mode, the power management module 210 transmits to the charging circuit 230 based on a signal having a variable second duty cycle and a second frequency (eg, about 5 GHz) by a PWM method. You can control the included switch. According to an embodiment, the second frequency may be greater than the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal (about 5 to 10 times) (see FIG. 6 ).

According to another embodiment, the second frequency may be the same as or similar to the resonance frequency (eg, about 500 KHz) of the flying capacitor 260 and the inductor 280 of the output terminal (see FIGS. 9 to 13 ).

4 shows a configuration of a charging circuit according to various embodiments. 4 is an example and is not limited thereto.

Referring to FIG. 4, the charging circuit 230 may transfer power delivered from the external power supply 202 to the battery 220. The battery 220 may be charged by power delivered from the external power supply 202.

The charging circuit 230 may be configured as a resonant switched capacitor voltage divider (SCVD) circuit. The charging circuit 230 may include first to fourth switches 251 to 254, a flying capacitor C _FLY 260, and an inductor Lr 280.

According to an embodiment, the first to fourth switches 251 to 254 may be sequentially connected. The first switch 251 may be electrically connected between the power supply 202a of the external power supply 202 and the first node 410. The second switch 252 may be electrically connected between the first node 410 and the second node 420. The third switch 253 may be electrically connected between the second node 420 and the third node 430. The fourth switch 254 may be electrically connected between the third node 430 and the ground unit 440.

The first to fourth switches 251 to 254 may operate according to the control of a control unit inside the power management module 210 or a processor inside the electronic device 201.

The flying capacitor 260 may be electrically connected between the first node 410 and the third node 430.

The inductor 280 may be electrically connected between the second node 420 between the second switch 252 and the third switch 253 and the first pole (eg, + pole) 450 of the battery 220. have.

The first pole (eg, + pole) 450 of the battery 220 may be electrically connected to the inductor 280, and the second pole (eg,-pole) may be electrically connected to the fourth node 440. .

The charging circuit 230 may operate in a first mode or a second mode according to the type of the external power supply 202. The first mode may be a mode operating at a fixed voltage conversion ratio (see FIG. 5), and the second mode may be a mode operating at a voltage conversion ratio that changes according to the state of charge of the battery 220 (see FIG. 6). .

5 illustrates an operation of a first mode of a charging circuit according to various embodiments.

Referring to FIG. 5, the charging circuit 230 may be connected to a first type of external power supply 202 that performs constant voltage or constant current control by the external power supply 202. For example, the external power supply 202 may operate as a constant current source.

In the first mode, the charging circuit 230 may operate to have a fixed voltage conversion ratio. In the first mode, the power management module 210 includes a first control signal G1 or a second control signal G2 of a first frequency (eg, about 500 KHz) having a fixed duty cycle (eg, about 50%). Accordingly, the first to fourth switches 251 to 254 may be controlled. For example, the first frequency may be set to a value equal to the resonant frequency of the flying capacitor 260 and the inductor 280 of the output terminal.

Current flowing through the first and second switches Q1 and 251 and Q2 and 252 due to the resonance of the flying capacitor 260 and the inductor 280 of the output terminal (for example, I _{Q1 and I Q2} ) is at least partially It may be in the form of a sine wave.

A typical SCVD circuit that does not include the inductor 280 uses a flying capacitor having a relatively large capacitance of about 40 uF or more when switching at a frequency of about 500 KHz, whereas the resonant charging circuit 230 including the inductor 280 is about A flying capacitor 260 having a relatively small capacitance of 1uF can be used.

In the signal flow diagram, the first switch 251 and the third switch 253 may be operated by the first control signal G1. The first control signal G1 may have a first frequency (eg, f _s = about 500 _{KHz) equal to the resonance frequency (eg, f R} = about 500 KHz) of the flying capacitor 260 and the inductor 280 of the output terminal. . The first control signal G1 may have a fixed duty cycle (eg, about 50%) in one period T.

_{The current I Q1} flowing through the first switch 251 by switching may be in the form of a half wave. Due to the influence of the inductor 280, the current I _Q1 flowing through the first switch 251 may have a sine wave characteristic rather than an exponentially decreasing form. Through this, loss due to switching can be reduced.

The second switch 252 and the fourth switch 254 may operate according to the second control signal G2. The second control signal G2 may have a phase opposite to the first control signal G1. The second control signal G2 may have a first frequency (eg, about 500 KHz) equal to the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal. The second control signal G2 may have the same fixed duty cycle (eg, about 50%) as the first control signal G1.

_{The current I Q2} flowing through the second switch 252 due to switching may be in the form of a half wave. _{The current I Q2} flowing through the second switch 252 may be alternating _{with the current I Q1} flowing through the first switch 251. _{For example, the current I Q1} flowing through the first switch 251 flows in the first section s1, and the current I _Q2 flowing through the second switch 252 flows in the second section s2. have. Due to the influence of the inductor 280, the current I _Q2 flowing through the second switch 252 may have a sine wave characteristic rather than an exponentially decreasing form. Through this, loss due to switching can be reduced.

In the first period s1, the first switch 251 and the third switch 253 may be turned on, and the second switch 252 and the fourth switch 254 may be turned off. _{In the flying capacitor 260, the current I CF} flowing toward the first node 410 may have a negative value. Through this, the flying capacitor 260 may be charged. _{The voltage V CF} across the flying capacitor 260 may gradually increase. In the first period s1, the current I _L flowing through the inductor 280 may be zero. For example, in the first section s1, the battery 220 may be in a state in which it is not charged.

In the second period s2, the first switch 251 and the third switch 253 may be turned off, and the second switch 252 and the fourth switch 254 may be turned on. In the flying capacitor 260, the current I _CF flowing toward the first node 410 may have a positive value. Through this, the flying capacitor 260 may be discharged. _{The voltage V CF} across the flying capacitor 260 may gradually decrease. In the first period s1 and the second period s2, the current I _L flowing through the inductor 280 may be (+). For example, in the first period s1, the battery 220 may be charged by the _{current I Q1 flowing through the first switch 251.} In the second period s2, the battery 220 may be charged by the _{current I Q2 flowing through the second switch 252.}

_{The voltage V IN} of the external power supply 202 by the switching operation of the first to fourth switches 251 to 254 may be about twice (2V _BAT ) of the voltage V _{BAT of the battery 220.} (Approximately 2:1 voltage conversion ratio).

6 illustrates an operation in a second mode according to various embodiments.

Referring to FIG. 6, the charging circuit 230 may be connected to an external power supply 202 that supplies a fixed voltage (eg, a 10V voltage source). The charging circuit 230 may operate in the second mode, and the voltage conversion ratio may be changed according to the degree of charge of the battery 220.

According to an embodiment, in the second mode, the charging circuit 230 may operate as a 3-level buck converter in which a power conversion ratio is adjusted in a PWM method. The switches inside the charging circuit 230 are operated by control signals (G1, G2, G3, and G4) having a frequency greater than the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal (for example, about 5 GHz). can do. Through this, the current flowing through the inductor 280 may have a form of linear increase or decrease of a general PWM converter rather than a resonance form.

In the second mode, the charging circuit 230 may operate to change the voltage conversion ratio according to the duty cycle D of the control signals G1, G2, G3, and G4. For example, it may have a relationship of _{V BAT} = D * V _{IN (V BAT} : voltage of the battery 220, V _IN : voltage of the external power supply 202).

In the signal flow diagram, the first switch 251 may operate according to the first control signal G1, and the second switch 252 may operate according to the second control signal G2. The third switch 253 may operate according to the third control signal G3, and the fourth switch 252 may operate according to the fourth control signal G4. The flying capacitor 260 may operate in one of a charge state, an idle state, or a discharge state according to switching of the first to fourth switches 251 to 254. For example, when the first switch to 251 and the third switch 253 are turned on, and the second switch 252 and the fourth switch 254 are turned off, the flying capacitor 260 is charged. ) State. When the second switch 252 and the fourth switch 254 are turned on, and the first switch to 251 and the third switch 253 are turned off, the flying capacitor 260 may be in a discharge state. have. Alternatively, when the first switch 251 and the second switch 252 are turned on, and the third switch 253 and the fourth switch 254 are turned off, the flying capacitor 260 is idle. It can be a state.

The first control signal G1 may have a phase opposite to that of the fourth control signal G4.

The second control signal G2 may be a signal in which the first control signal G1 is delayed by a half period T/2. Accordingly, the first control signal G1 may be a signal in which the state is changed in the first period s1, and the second control signal G2 may be a signal in which the state is changed in the second period s2.

The second control signal G2 may have a phase opposite to that of the third control signal G3. _{The current I Q1} flowing through the first switch 251 by switching may operate in response to the first control signal G1. In response to a state change of the first control signal G1, a state of the current I _Q1 flowing through the first switch 251 may be changed.

_{The current I Q2} flowing through the second switch 252 by switching may operate in response to the second control signal G2. In response to a state change of the second control signal G2, a state of the current I _Q2 flowing through the second switch 252 may be changed.

In the first period s1, the flying capacitor 260 may be charged. _{The voltage V CF} across the flying capacitor 260 may gradually increase. In the second period s2, the flying capacitor 260 may be discharged. _{The voltage V CF} of both ends of the flying capacitor 260 may gradually decrease.

In each of the first section (s1) and the second section (s2) _{, the state of the voltage V LX} across the inductor 280 may be changed, and the current I _L flowing through the inductor 280 is the inductor 280 Corresponding to a change in the voltage at both ends (V _LX ) may have a ripple shape.

7A illustrates a switching control circuit according to various embodiments. 7A is an example and is not limited thereto.

Referring to FIG. 7A, the power management module 210 may further include a control circuit 701 that controls the charging circuit 230. In an embodiment, the control circuit 701 of the power management module 210 may generate a signal for controlling the first to fourth switches 251 to 254 of the charging circuit 230.

In the first mode, the control circuit 701 includes a first control signal G1 and a second switch for controlling the first switch 251 based on the first clock generator CLK1 and the second clock generator CLK2. A second control signal G2 for controlling 252, a third control signal G3 for controlling the third switch 253, and a fourth control signal G4 for controlling the fourth switch 254 may be generated. have.

In the first mode, the first control signal G1 may be the same as the third control signal G3, and the second control signal G2 may be the same as the fourth control signal G4. In the first mode, the second control signal G2 may have a phase opposite to the first control signal G1.

In the first mode, the first control signal G1 and the second control signal G2 may each have a fixed first duty cycle (eg, about 50%) and a first frequency (eg, about 500 KHz). The first frequency (eg, about 500 KHz) may be set to the same value as the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal.

In the second mode, the control circuit 701 may determine the duty control voltage V _{ctrl based on the voltage V BAT} at both ends of the battery 220 and the current I _{BAT flowing into the battery 220.} .

According to an embodiment, the control circuit 701 may amplify a voltage value difference between the voltage _{V BAT} across the battery 220 and the set reference voltage V _{ref through the first error amplifier 710.} The control circuit 701 may amplify a difference in a current value between the current _{I BAT} flowing into the battery 220 and the set reference current I _{ref through the second error amplifier 720.} The reference voltage V _ref and the reference current I _ref may be set by reflecting charging characteristics of the battery 220.

The control circuit 701 compares the output of the first error amplifier 710 and the output of the second error amplifier 720 through the comparator 730, and determines the _{duty control voltage V ctrl based on a small value.} I can. In FIG. 7A, a case in which the duty control voltage V _ctrl is determined by using both the voltage at both ends of the battery 220 (V _BAT ) and the current flowing into the battery 220 (I _{BAT) is illustrated.} It is not limited thereto. For example, the duty control voltage V _ctrl may be determined _{using one of the voltage V BAT} of both ends of the battery 220 and the current I _{BAT flowing into the battery 220.}

According to various embodiments, in the second mode, the control circuit 701 compares the duty control voltage V _ctrl with the first triangular wave, or the duty control voltage V _ctrl with the second triangular wave. Fourth control signals G1 to G4 may be generated (see FIG. 7B).

7B illustrates generation of a switching control signal in a second mode according to various embodiments. 7B is an example and is not limited thereto.

Referring to FIG. 7B, the control circuit 701 compares the duty control voltage V _ctrl and the first triangle wave V _saw1 to generate a first control signal G1 for controlling the first switch 251. I can. The first triangle wave V _saw1 may be generated in response to the first clock signal CLK1. The control circuit 701 may _keep the first control signal G1 high when the _{duty control voltage V ctrl} is greater than the first triangle wave V saw1. The control circuit 701 may _keep the first control signal G1 low when the _{duty control voltage V ctrl} is smaller than the first triangle wave V saw1.

According to an embodiment, the fourth control signal G4 controlling the fourth switch 254 may have a phase opposite to the first control signal G1. For example, when the duty control voltage (V _ctrl ) is greater than the first triangle wave (V _saw1 ), the control circuit 701 maintains the fourth control signal (G4) Low, and the duty control voltage (V _ctrl ) When it is smaller than the first triangle wave V _saw1 , the fourth control signal G4 may be kept high.

The control circuit 701 may generate a second control signal G2 for controlling the second switch 252 by comparing the _{duty control voltage V ctrl} and the second triangle wave V _saw2. The second triangle wave V _saw2 may be generated in response to the second clock signal CLK2. The control circuit 701 may _keep the second control signal G2 high when the _{duty control voltage V ctrl} is greater than the second triangle wave V saw2. The control circuit 701 may _keep the second control signal G2 low when the _{duty control voltage V ctrl} is smaller than the second triangle wave V saw2. The second clock signal CLK2 may be a signal delayed by a half period T/2 from the first clock signal CLK1.

According to an embodiment, the third control signal G3 for controlling the third switch 253 may have a phase opposite to the second control signal G2. For example, when the duty control voltage (V _ctrl ) is greater than the second triangle wave (V _saw2 ), the control circuit 701 maintains the third control signal (G3) Low, and the duty control voltage (V _ctrl ) When it is smaller than the second triangle wave (V _saw2 ), the third control signal (G3) may be kept high.

8 illustrates a switching control circuit in a second mode according to various embodiments. 8 is an example and is not limited thereto.

Referring to FIG. 8, the power management module 210 may further include a control circuit 801 that controls the charging circuit 230. In an embodiment, the control circuit 801 of the power management module 210 may generate a signal for controlling the first to fourth switches 251 to 254 of the charging circuit 230.

In the first mode, the control circuit 801 includes a first control signal G1 for controlling the first switch based on the signal 801a of the clock generator CLK and the inverted signal 801b of the clock generator CLK, A second control signal G2 for controlling the second switch, a third control signal G1 for controlling the third switch, and a fourth signal G4 for controlling the fourth switch 254 may be generated.

In the first mode, the first control signal G1 may be the same as the third control signal G3, and the second control signal G2 may be the same as the fourth control signal G4. The second control signal G2 may have a phase opposite to the first control signal G1.

In the first mode, the first control signal G1 and the second control signal G2 may each have a fixed first duty cycle (eg, about 50%) and a first frequency (eg, about 500 KHz). The first frequency (eg, about 500 KHz) may be set to the same value as the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal.

In the second mode, the control circuit 801 may determine the duty control voltage V _{ctrl based on the voltage V BAT} at both ends of the battery 220 and the current I _{BAT flowing into the battery 220.} .

According to an embodiment, the control circuit 801 may amplify a voltage value difference between the voltage _{at both ends of the battery 220 (V BAT} ) and a set reference voltage (V _{ref) through the first error amplifier 810.} . The control circuit 801 may amplify a difference in a current value between the current _{I BAT} flowing into the battery 220 and the set reference current I _{ref through the second error amplifier 820.} The control circuit 801 compares the output of the first error amplifier 810 and the output of the second error amplifier 820 through the comparator 830 and determines the _{duty control voltage V ctrl based on a small value.} I can. In FIG. 8, a case in which the duty control voltage V _ctrl is determined by using both the voltage across the battery 220 (V _BAT ) and the current flowing into the battery 220 (I _{BAT) is illustrated.} It is not limited. For example, the duty control voltage V _ctrl may be determined _{using one of the voltage V BAT} across the battery 220 and the current I _{BAT flowing into the battery 220.}

According to various embodiments, in the second mode, the control circuit 801 uses first to fourth control signals using a _{duty control voltage (V ctrl} ), a first triangle wave (V _saw1 ), or a second triangle wave (V _{saw2 ).} (G1 to G4) can be produced.

According to various embodiments, the control circuit 801 may generate a first control signal G1 for controlling the first switch 251 by comparing the _{duty control voltage V ctrl} and the first triangle wave V _saw1. I can.

According to an embodiment, the control circuit 801 may change the first control signal G1 from the first state (low) to the second state (high) in response to the clock signals CLK and 801a. For example, the control circuit 801 may provide the toggling signal of the clock signal CLK to the S input 881a of the flip-flop 881. When the duty control voltage V _ctrl is greater than the first triangle wave V _saw1 , the control circuit 801 may cause the first control signal G1 to maintain the second state high.

According to an embodiment, when the duty control voltage V _ctrl is smaller than the first triangle wave V _saw1 , the control circuit 801 transmits the first control signal G1 from the second state high to the first state. It can be changed to (low). For example, the control circuit 801 transmits the signal of the output terminal 851a of the combiner 851 that combines the _{duty control voltage V ctrl} and the first triangular wave V _{saw1 to the R input 881b of the flip-flop 881.} ) Can be provided.

According to various embodiments, the control circuit 801 may generate a second control signal G2 for controlling the second switch 252 by comparing the _{duty control voltage V ctrl} and the second triangle wave V _saw2. I can. Second triangular wave (V _saw2) may signal the movement of the first triangular wave (V _saw1) half period.

According to an embodiment, the control circuit 801 changes the second control signal G2 from the first state (low) to the second state (high) in response to the inverting signal 801b of the clock signal CLK. I can. For example, the control circuit 801 may provide the inverted signal 801b of the clock signal CLK as the S input 882a of the flip-flop 882. When the duty control voltage V _ctrl is greater than the second triangle wave V _saw2 , the control circuit 801 may maintain the second control signal G2 in the second state (high).

According to an embodiment, when the duty control voltage V _ctrl is smaller than the second triangle wave (V _saw2 ), the control circuit 801 transmits the second control signal G2 from the second state (high) to the first state. It can be changed to (low). For example, the control circuit 801 transmits the signal of the output terminal 852a of the combiner 852 that combines the _{duty control voltage V ctrl} and the second triangle wave V _{saw2 to the R input 882b of the flip-flop 882.} ) Can be provided.

According to various embodiments, the control circuit 801 may generate the fourth control signal G4 by inverting the phase of the first control signal G1. The control circuit 801 may generate a third control signal G3 by inverting the phase of the second control signal G2.

9 illustrates a control circuit additionally using a voltage across a flying capacitor according to various embodiments.

Referring to FIG. 9, the power management module 210 may include a voltage sensing unit 910 as a control circuit 801 that controls the charging circuit 230. The voltage detector 910 may control a switching operation of the third switch 253 or the fourth switch 254 to increase switching efficiency. According to an embodiment, in the second mode, the power management module 210 uses the voltage sensing unit 910 to set the switching frequency to the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal (for example, about 500KHz) can be set the same or similar.

According to various embodiments, the voltage detector 910 may control a switching operation of the third switch 253 or the fourth switch 254 by using the voltage Vc of both ends of the flying capacitor 260. According to an embodiment, the voltage sensing unit 910 is a third switch according to whether the voltage Vc of both ends of the flying capacitor 260 is clamped to a ground voltage (0V) or an input voltage (V _{IN ).} The turn-on timing of 253 or the turn-on timing of the fourth switch 254 may be adjusted.

For example, when the third switch 253 is turned on, the voltage VCA of the first node 410 is zero crossing point (or the voltage Vc of both ends of the flying capacitor 260 is grounded). It may be determined by a faster signal among a voltage clamping time) and a signal at which the second switch 252 is turned off (for example, a signal provided to the R input 882b of the flip-flop 882) (see FIG. 12). ).

For example, the turn-on time of the fourth switch 254 is a zero crossing point (or the voltage Vc across the flying capacitor 260) is the input voltage. (V _IN ) clamping time) and a signal at which the first switch 251 is turned off (eg, a signal provided to the R input 881b of the flip-flop 881), which may be determined by the fastest signal ( 12).

According to various embodiments, the voltage sensing unit 910 has a current flowing through the inductor 280 (hereinafter, inductor current) (I _L ) (or, a sensing voltage (Vcs) proportional to the _{inductor current (I L )) is 0.} The switching operation of the third switch 253 or the fourth switch 254 may be controlled by using this time point.

For example, when the third switch 253 is turned off, a signal at which the second switch 252 is turned on (eg, a signal provided to the S input 882a of the flip-flop 882) and the first switch ( While 251 is conducting (turned on), it may be determined by the fastest signal among the zero point of the _{inductor current I L (or the point at which the sensing voltage Vcs crosses to zero).} Through this, _{it is possible to prevent the inductor current I L} from falling below 0 (see FIG. 11 ).

According to various embodiments, the turn-off timing of the fourth switch 254 includes a signal at which the first switch 251 is turned on (for example, a signal provided to the S input 881a of the flip-flop 881) and the second While the switch 252 is conducting (turned on), it may be determined by the fastest signal among the zero point of the _{inductor current I L (or the point at which the sensing voltage Vcs crosses zero).} Through this, _{it is possible to prevent the inductor current I L} from falling below 0 (see FIG. 11 ).

10 illustrates a change in a voltage control method switching signal in a first state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 10, the first state may be a state in which the inductor current I _L exceeds 0 and clamping does not occur in the voltage across the flying capacitor 260.

According to various embodiments, the turn-on timing and the turn-off timing of the first switch 251 may be determined by the _{duty control voltage V ctrl} and the first triangle wave V _saw1. For example, the first switch 251 may be turned on at a first time t1 when _{the first triangle wave V saw1} is smaller than the duty control voltage V _ctrl. The second switch 252 may be in an on state at the first time t1. The first switch 251 may be turned off at a fourth time t4 when the first triangle wave V _saw1 is greater than the duty control voltage V _ctrl. At the fourth time t4, the second switch 252 may be in an on state.

The turn-on and turn-off times of the second switch 252 may be determined by the _{duty control voltage V ctrl} and the second triangle wave V _saw2. Second triangular wave (V _saw2) is the first triangle wave (V _saw1) a half-period (for example, the first half period (T1-1)) can be a signal of the mobile. For example, the second switch 252 may be turned off at a second time t2 when _{the second triangle wave V saw2} is greater than the duty control voltage V _ctrl. At the second time t2, the first switch 251 may be in an on state. The second switch 252 may be turned on at a third time t3 when the second triangle wave V _saw2 becomes smaller than the duty control voltage V _ctrl. At the third time t3, the first switch 251 may be in an on state.

_{In the first half cycle (T1-1} ) of the first triangle wave (V saw1 ), the first switch 251 is turned on (occurs at the first time t1) and the second switch 252 is turned off (the second time (occurs at t2)) may occur. In the second half-period (T1-2) of the first triangular wave (V _saw1 ), the second switch 252 is turned on (occurs at the third time t3) and the first switch 251 is turned off (the fourth time (occurs at t4)) may occur.

According to various embodiments, the control signal G3 of the third switch 253 may have a form opposite to the control signal G2 of the second switch 252. For example, the third switch 253 may be turned off when the second switch 252 is turned on, and may be turned on when the second switch 252 is turned off.

According to various embodiments, the control signal G4 of the fourth switch 254 may have a form opposite to the control signal G1 of the first switch 251. For example, the fourth switch 254 may be turned off when the first switch 251 is turned on, and may be turned on when the first switch 251 is turned off.

According to various embodiments, the turn-off timing of the third switch 253 and the fourth switch 254 _{may be changed to prevent the inductor current I L} from falling below zero (see FIG. 11 ). Turn-on timings of the third and fourth switches 253 and 254 may be changed by clamping the flying capacitor 260 (see FIG. 12 ).

11 illustrates a change in a voltage control method switching signal in a second state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 11, the second state is a state in which a zero current section _{of the inductor current I L (eg, a section in which I L} is 0) is included, and clamping does not occur in the voltage across the flying capacitor 260. I can. For example, the inductor current I _L may be changed according to a load (eg, battery 220). When the load decreases, the inductor current I _L can be operated in a discontinuous conduction mode (DCM) in which there is a period in which the inductor current I L becomes zero (second state). The inductor current I _L decreases in a period in which the current value becomes 0 as the load increases, and thus the inductor current I L can operate in a continuous conduction mode (CCM) in which a zero current period does not exist (first state, FIG. 10 ).

According to various embodiments, in the second state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, in the second state, the turn-on time of the third switch 253 may be the same as the turn-off time of the second switch 252, and the turn-on time of the fourth switch 254 is the first switch. It may be the same as the turn-off point of 251. Turn-on timings of the third and fourth switches 253 and 254 may be changed by clamping voltages across the flying capacitor 260 (see FIG. 12 ).

According to various embodiments, the control circuit 801 may control the turn-off timing of the third switch 253 or the fourth switch 254 by using the point in time when the _{inductor current I L becomes zero.} In this case, the third switch 253 or the fourth switch 254 may operate as an ideal diode. Through this, it is possible to prevent the _{inductor current I L from becoming a negative value.}

According to various embodiments, in the first half cycle _{T1-1 of} the first triangle wave V saw1, the first switch 251 is turned on at the fifth time t5 when the _{inductor current I L becomes 0.} If yes, the third switch 253 may be turned off. Accordingly, the third switch 253 may be turned off before the second switch 252 is turned on.

According to various embodiments, the second switch 252 is turned on at the sixth time t6 when the _{inductor current I L} becomes 0 in the second half cycle T1-2 of the first triangle wave V _saw1 If yes, the fourth switch 254 may be turned off. Accordingly, the fourth switch 254 may be turned off before the first switch 251 is turned on.

12 illustrates a change in a voltage control method switching signal in a third state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 12, the third state is a state in which clamping occurs in the voltage across the flying capacitor 260 without including a zero current section _{of the inductor current I L (eg, a section in which I L is 0).} I can.

According to various embodiments, in the third state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, the control circuit 801 uses _{a time point when the voltage Vc of both ends of the flying capacitor 260 is clamped to the input voltage V IN} or the ground voltage 0V, and the third switch 253 Alternatively, the turn-on timing of the fourth switch 254 may be controlled. When the voltage across the flying capacitor 260 _{is clamped to the input voltage (V IN} ) or the ground voltage (0V), if the third switch 253 and the fourth switch 254 are not turned on, the third switch 253 And a current may flow through the body diode inside the fourth switch 254, and a switching loss may increase. The control circuit 801 turns on the third switch 253 and the fourth switch 254 when the voltage across the flying capacitor 260 _{is clamped to the input voltage (V IN) or the ground voltage (0V),} It is possible to reduce losses due to current flowing through the body diodes inside the 3 switch 253 and the fourth switch 254.

According to various embodiments, the voltage of the flying capacitor 260 is in a floating state, and the control circuit 801 does not directly sense the voltage Vc of both ends of the flying capacitor 260, but the upper voltage of the flying capacitor 260 By detecting the zero crossing point of (VCA) (voltage of the first node 410) and the zero crossing point of the bottom voltage (VCB) (voltage of the third node 430) , Turn-on timings of the third switch 253 and the fourth switch 254 may be determined.

_{According to various embodiments, in the first half period (T1-1} ) of the first triangle wave (V saw1 ), the fourth switch 254 has a voltage (VCB) of the third node 430 at zero crossing (flying capacitor 260 The voltage Vc of) may be turned on at a seventh time t7 when the _{voltage Vc of) is clamped to the input voltage V IN.} Accordingly, the fourth switch 254 may be turned on before the first switch 251 is turned off. The seventh time t7 may be a time point at which the body diode inside the fourth switch 254 starts to conduct.

According to various embodiments, in the second half cycle T1-2 of the first triangle wave V _saw1 , the third switch 253 has a voltage VCA of the first node 410 at zero crossing (flying capacitor 260 The voltage Vc of) may be turned on at the eighth time t8 when the voltage Vc is clamped to the ground voltage 0V. Accordingly, the third switch 253 may be turned on before the second switch 252 is turned off. The eighth time t8 may be a time point when the body diode inside the third switch 253 starts to conduct.

According to various embodiments, the turn-off time of the third switch 253 may be the same as the turn-on time of the second switch 252, and the turn-off time of the fourth switch 254 is the first switch 251. It may be the same as the turn-on time.

13 illustrates a change in a switching signal in a fourth state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 13, the fourth state includes a zero current section (eg _{, a section in which I L is 0) of the inductor current I L} , and clamping occurs in the voltage across the flying capacitor 260. have.

According to various embodiments, in the fourth state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, the turn-on operation of the third switch 253 and the fourth switch 254 is performed in which the voltage Vc of both ends of the flying capacitor 260 _{is clamped to the input voltage V IN} or the ground voltage 0V. It can be changed by the viewpoint. The turn-on operation of the third switch 253 and the fourth switch 254 may be the same as that of FIG. 12, and the turn-off operation of the third switch 253 and the fourth switch 254 may be the same as that of FIG. 11. .

_{For example, in the first half period (T1-1} ) of the first triangle wave (V saw1 ), the voltage (VCB) of the third node 430 is zero crossing (the voltage (Vc) at both ends of the flying capacitor 260 is input The fourth switch 254 may be turned on at a seventh time t7 in which the voltage V _{IN is clamped.} The fourth switch 254 may be turned on before the first switch 251 is turned off.

When the first switch 251 is turned on at the fifth time t5 when the _{inductor current I L} becomes 0 in the first half cycle _{T1-1 of} the first triangle wave V saw1, the third switch 253 can be turned off. The third switch 253 may be turned off before the second switch 252 is turned on.

In the second half period (T1-2) of the first triangle wave (V _saw1 ), the voltage (VCA) of the first node 410 is zero crossing (the voltage (Vc) of both ends of the flying capacitor 260 is the ground voltage (0V)) The third switch 253 may be turned on at the eighth time t8 that is clamped to. The third switch 253 may be turned on before the second switch 252 is turned off.

A second switch to the sixth time for the (sense voltage (Vcs) is zero, for example) (t6) (the first triangle wave at the second half period (T1-2) of (V _saw1), the inductor current (I _L) is zero, When 252 is in the on state, the fourth switch 254 may be turned off. The fourth switch 254 may be turned off before the first switch 251 is turned on.

14 illustrates a switching control circuit of a current control method in a second mode according to various embodiments. 14 is an example and is not limited thereto. The charging circuit 230 in FIG. 14 may correspond to the charging circuit 230 operating in the second mode.

Referring to FIG. 14, in the second mode, the charging circuit 230 may adjust a voltage conversion ratio according to the degree of charge of the battery 220. For example, in the second mode, the charging circuit 230 may operate as a 3-level buck circuit in which the power conversion ratio is adjusted in a pulse width modulation (PWM) method. have. In the second mode, the charging circuit 230 may operate according to the degree of charge of the battery 220.

In the second mode, a switching operation of the plurality of switches 251 to 254 of the charging circuit 230 may be controlled based on a current flowing into the battery 220 or a voltage across the battery 220. The flying capacitor 260 of the charging circuit 230 may operate in one of a charge state, an idle state, or a discharge state according to the switching of the plurality of switches 251 to 254. .

The control circuit 1401 may generate a signal for controlling the first to fourth switches 251 to 254.

In the first mode, the control circuit 1401 may generate the first control signal G1 by using the signal of the first clock generator CLK1 and 1401a having a 50% duty cycle. The control circuit 1401 may generate a second control signal G2 for controlling the second switch based on the signal of the second clock generator CLK2 1401b having a 50% duty cycle. The signal from the second clock generator (CLK2) 1401b may be a signal obtained by inverting the signal from the first clock generator (CLK1) 1401a.

In the first mode, the third control signal G3 may be the same as the first control signal G1. The fourth control signal G4 for controlling the fourth switch 254 may be the same as the second control signal G2. The second control signal G2 may have a phase opposite to the first control signal G1.

In the first mode, the first control signal G1 and the second control signal G2 may each have a fixed first duty cycle (eg, about 50%) and a first frequency (eg, about 500 KHz). The first frequency (eg, about 500 KHz) may be set to the same value as the resonance frequency of the flying capacitor 260 and the inductor 280 of the output terminal.

In the second mode, the control circuit 1401 may determine the duty control voltage Vctrl based on the _{voltage V BAT} at both ends of the battery 220 and the current I _{BAT flowing into the battery 220.}

According to an embodiment, the control circuit 1401 may _{amplify a voltage value difference between the voltage at both ends of the battery 220 (V BAT} ) and the set reference voltage (Vref) through the first error amplifier 1410. The control circuit 1401 may _{amplify a difference in a current value between the current I BAT} flowing into the battery 220 and the set reference current Iref through the second error amplifier 1420. The control circuit 1401 may determine the duty control voltage Vctrl based on a small value by comparing the output of the first error amplifier 1410 and the output of the second error amplifier 1420 through the comparator 1430. have. In FIG. 14, a case of determining the duty control voltage Vctrl by using both the voltage at both ends of the battery 220 (V _BAT ) and the current flowing into the battery 220 (I _{BAT) is illustrated.} It is not limited. For example, the duty control voltage Vctrl may be determined using one of a _{voltage V BAT} of both ends of the battery 220 and a current I _{BAT flowing into the battery 220.}

According to various embodiments, in the second mode, the control circuit 1401 is _{based on the inductor current I L} flowing through the inductor 280 included in the charging circuit 230, based on the first to fourth current mode control methods. The switches 251 to 254 can be controlled. According to an embodiment, the control circuit 1401 may adjust the switching frequencies of the first to fourth switches 251 to 254 using a sensing voltage Vcs proportional to the sensed _{inductor current I L.} The current control method using the inductor current I _L may enable more precise switching control than the voltage control method in FIG. 8.

According to various embodiments, when the inductor current I _L is used in the second mode, the switching frequencies of the first to fourth switches 251 to 254 may be the same as or similar to the switching frequency of the first mode. Accordingly, in the second mode of the current mode control method, power conversion efficiency may be relatively high, and EMI reduction and system efficiency may be improved due to the operation of the resonant converter. In addition, in the second mode of the current mode control method, the switching frequency is automatically reduced according to load fluctuations, thereby improving efficiency under light load.

The control circuit 1401 may apply a hysteresis voltage VH to the duty control voltage Vctrl. The control circuit 1401 adds a hysteresis voltage (VH) 1441 to the duty control voltage Vctrl to apply a first band voltage (hereinafter, band upper limit voltage) (Vctrl+VH) to the first cross detector 1451. You can enter. The control circuit 1401 transmits a second band voltage (hereinafter, band lower limit voltage) (Vctrl-VH) generated by lowering the hysteresis voltage (VH) 1442 to the duty control voltage Vctrl to the second cross detector 1452. You can enter.

According to various embodiments, the control circuit 1401 may change the hysteresis voltage VH to determine a switching frequency and a ripple of the _{inductor current I L.} For example, the control circuit 1401 may vary the hysteresis voltage VH (eg, 1441 and/or 1442) using a PLL circuit.

The control circuit 1401 may generate an inductor sensing voltage Vcs generated based on the _{inductor current I L.} According to an embodiment, the inductor current I _L and the inductor sensing voltage Vcs may have a linear relationship (Vcs=k*I _L ). The inductor sensing voltage Vcs _{may be determined by a time point at which the sensing signal of the inductor current I L} reaches the upper limit value and the lower limit value, respectively.

The inductor sensing voltage Vcs may be input to the first cross detector 1451 and the second cross detector 1452, respectively. The first cross detector 1451 may generate a first trigger signal through the output terminal 1451a at a timing when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. The second cross detector 1452 may generate a second trigger signal through the output terminal 1452a at a timing when the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH are the same.

According to various embodiments, the control circuit 1401 may turn on the first switch 251 and the second switch 252 at different timings based on the second trigger signal. For example, the first switch 251 is turned on by the second trigger signal in the first period of the inductor sensing voltage Vcs, and the second switch 252 is turned on in the second period (the second period of the inductor sensing voltage Vcs). It may be turned on by the second trigger signal in the next period consecutive to one period).

According to various embodiments, the control circuit 1401 may turn off the first switch 251 and the second switch 252 at different timings based on the first trigger signal. In the previous example, the first switch 251 is turned off by the first trigger signal in the second period of the inductor sensing voltage Vcs, and the second switch 252 is the third period of the inductor sensing voltage Vcs. It may be turned off by the first trigger signal in (the next period following the second period).

According to various embodiments, the first signal divider 1471 may receive the first trigger signal through the output terminal 1451a of the first cross detector 1451. The first signal divider 1471 may include a toggle flip-flop operating the first trigger signal as a clock signal. The first output terminal 1471a of the first signal divider 1471 may generate a signal for turning off the second switch 252. For example, the first output terminal 1471a may be connected to the R terminal of the SR flip-flop 1482 for generating the second control signal G2. The second output terminal 1471b of the first signal divider 1471 may generate a signal for turning off the first switch 251. For example, the second output terminal 1471b of the first signal divider 1471 may be connected to the R terminal of the SR flip-flop 1481 for generating the first control signal G1.

According to various embodiments, the second signal divider 1472 may receive the second trigger signal through the output terminal 1452a of the second cross detector 1452. The second signal divider 1472 may include a toggle flip-flop operating the second trigger signal as a clock signal. The first output terminal 1472a of the second signal divider 1472 may generate a signal for turning on the second switch 252. For example, the first output terminal 1472a may be connected to the S terminal of the SR flip-flop 1482 for generating the second control signal G2. The second output terminal 1472b of the second signal divider 1472 may generate a signal for turning on the first switch 251. For example, the second output terminal 1472b of the second signal divider 1472 may be connected to the S terminal of the SR flip-flop 1481 for generating the first control signal G1.

15 illustrates a control circuit additionally using voltages across both ends of a flying capacitor according to various embodiments.

Referring to FIG. 15, the control circuit 1401 may further include a voltage sensing unit 1510.

The voltage detector 1510 may control a switching operation of the third switch 253 or the fourth switch 254 by using the voltage Vc of both ends of the flying capacitor 260. In addition, the voltage detector 1510 may control a switching operation of the third switch 253 or the fourth switch 254 using a time point when the sensing voltage Vcs becomes zero.

The voltage detector 1510 may control a switching operation of the third switch 253 or the fourth switch 254 by using the voltage Vc of both ends of the flying capacitor 260. According to an embodiment, the voltage sensing unit 1510 may be configured with a third switch according to whether the voltage Vc across the flying capacitor 260 is clamped to a ground voltage (0V) or an input voltage (V _{IN ).} The turn-on timing of the fourth switch 254 or the turn-on timing of the fourth switch 254 may be adjusted.

For example, the turn-on point of the third switch 253 is a zero crossing point (or the voltage V _CF across the flying capacitor 260 is grounded). It may be determined by a faster signal among a time point clamped by voltage) and a signal at which the second switch 252 is turned off (eg, a signal from the first output terminal 1471a of the first signal divider 1471) (Fig. 18).

For example, the turn-on time of the fourth switch 254 is a zero crossing point (or a voltage V _{CF across the flying capacitor 260) at which the voltage VB of the third node 430 crosses to zero.} It is determined by the fastest of the voltage (V _IN ) clamping time) and the signal at which the first switch 251 is turned off (for example, the signal at the second output terminal 1471b of the first signal divider 1471). Can (see Fig. 18).

According to various embodiments, the voltage sensing unit 1510 uses a point in time when the inductor current I _L flowing through the inductor 280 (or the sensing voltage Vcs in proportion to the inductor current I _{L) becomes zero.} Thus, the switching operation of the third switch 253 or the fourth switch 254 may be controlled.

For example, when the third switch 253 is turned off, a signal at which the second switch 252 is turned on (eg, a signal from the first output terminal 1472a of the second signal divider 1472) and the first While the switch 251 is conducting (turned on), the inductor current I _L may be determined by the fastest signal among the 0 points (when the sensing voltage Vcs crosses to zero). Through this, _{it is possible to prevent the inductor current I L} from falling below 0 (see FIG. 17).

According to various embodiments, the turn-off timing of the fourth switch 254 includes a signal at which the first switch 251 is turned on (eg, a signal of the second output terminal 1472b of the second signal divider 1472), While the second switch 252 is conducting (turned on), the inductor current I _L may be determined by the fastest signal among the 0 points (when the sensing voltage Vcs crosses to zero). Through this, _{it is possible to prevent the inductor current I L} from falling below 0 (see FIG. 17).

16 illustrates a change in a switching signal of a current control method in a first state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 16, the first state may be a state in which the inductor current I _L exceeds 0 and clamping does not occur in the voltage across the flying capacitor 260.

According to various embodiments, the turn-on timing of the first switch 251 and the turn-on timing of the second switch 252 may be determined by the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH. For example, in the first period (T1) of the sensing voltage (Vcs), the first switch 251 is at a first time (t1) when the inductor sensing voltage (Vcs) and the band lower limit voltage (Vctrl-VH) are the same. Can be turned on. The second switch 252 may be in an on state at the first time t1. In the second period T2 of the sensing voltage Vcs, the second switch 252 may be turned on at a third time t3 when the inductor sensing voltage Vcs and the band lower limit voltage Vctrl-VH are the same. . At the third time t3, the first switch 251 may be in an on state.

According to various embodiments, the turn-off time of the first switch 251 and the turn-off time of the second switch 252 may be determined by the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH. For example, in the first period T1, the second switch 252 may be turned off at a second time t2 when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. At the second time t2, the first switch 251 may be in an on state. In the second period T2, the first switch 251 may be turned off at a fourth time t4 when the inductor sensing voltage Vcs and the band upper limit voltage Vctrl+VH are the same. At the fourth time t4, the second switch 252 may be in an on state.

In the first period (T1) and the second period (T2), the first switch 251 is turned on (occurs at the first time t1), and the second switch 252 is turned off (the second time t2). Occurs at), turn-on of the second switch 252 (occurs at a third time t3), and turn-off of the first switch 251 (occurs at a fourth time t4) may occur sequentially.

According to various embodiments, the control signal G3 of the third switch 253 may have a form opposite to the control signal G2 of the second switch 252. For example, the third switch 253 may be turned off when the second switch 252 is turned on, and may be turned on when the second switch 252 is turned off.

According to various embodiments, the control signal G4 of the fourth switch 254 may have a form opposite to the control signal G1 of the first switch 251. For example, the fourth switch 254 may be turned off when the first switch 251 is turned on, and may be turned on when the first switch 251 is turned off.

According to various embodiments, the turn-off timing of the third switch 253 and the fourth switch 254 _{may be changed to prevent the inductor current I L} from falling below zero (see FIG. 17 ). Turn-on timings of the third and fourth switches 253 and 254 may be changed by clamping (see FIG. 18).

17 illustrates a change in a switching signal of a current control method in a second state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 17, the second state may include a zero current period (eg, a period in which I _{L is 0) in the inductor current (I L} ), and clamping does not occur in the voltage across the flying capacitor 260. It can be a state. For example, the inductor current I _L may be changed according to a load (eg, battery 220). When the load decreases, the inductor current I _L can be operated in a discontinuous conduction mode (DCM) in which there is a period in which the current I L becomes zero (second state). The inductor current I _L decreases in a period in which the current value becomes 0 as the load increases, and thus the inductor current I L may operate in a continuous conduction mode (CCM) in which a zero current period does not exist (first state, FIG. 16 ).

According to various embodiments, in the second state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, in the second state, the turn-on time of the third switch 253 may be the same as the turn-off time of the second switch 252, and the turn-on time of the fourth switch 254 is the first switch. It may be the same as the turn-off point of 251. The turn-on timing of the third switch 253 and the fourth switch 254 may be changed by clamping the voltage across the flying capacitor 260 (see FIG. 18).

According to various embodiments, the turn-on timing of the third switch 253 and the fourth switch 254 may be changed by clamping (see FIG. 12 ).

According to various embodiments, the control circuit 1401 may control the turn-off timing of the third switch 253 or the fourth switch 254 by using a point in time when the _{inductor current I L becomes zero.} In this case, the third switch 253 or the fourth switch 254 may operate as an ideal diode. Through this, it is possible to prevent the _{inductor current I L from becoming a negative value.}

According to various embodiments, in the first period T1, the first switch 251 is turned on at a fifth time t5 when the _{inductor current I L becomes 0 (eg, the sensing voltage Vcs is 0).} In this state, the third switch 253 may be turned off. Accordingly, the third switch 253 may be turned off before the second switch 252 is turned on.

According to various embodiments, in the second period T2, the second switch 252 is turned on at the sixth time t6 when the _{inductor current I L becomes 0 (eg, the sensing voltage Vcs is 0).} In the case of the state, the fourth switch 254 may be turned off. Accordingly, the fourth switch 254 may be turned off before the first switch 251 is turned on.

18 illustrates a change in a switching signal of a current control method in a third state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 18, the third state is a state in which the inductor current I _L does not include a zero current section (eg _{, a section in which I L} is 0), and clamping occurs in the voltage across the flying capacitor 260. I can.

According to various embodiments, in the third state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, the control circuit 1401 uses the time when the voltage across the flying capacitor 260 _{is clamped to the input voltage (V IN} ) or the ground voltage (0V), the third switch 253 or the fourth The turn-on timing of the switch 254 can be controlled. When the voltage across the flying capacitor 260 _{is clamped to the input voltage (V IN} ) or the ground voltage (0V), if the third switch 253 and the fourth switch 254 are not turned on, the third switch 253 And a current may flow through the body diode inside the fourth switch 254, and a switching loss may increase. When the voltage across the flying capacitor 260 _{is clamped to the input voltage (V IN} ) or the ground voltage (0V), the control circuit 1401 turns on the third switch 253 and the fourth switch 254, It is possible to reduce losses due to current flowing through the body diodes inside the 3 switch 253 and the fourth switch 254.

According to various embodiments, since the voltage of the flying capacitor 260 is in a floating state, the control circuit 1401 does not directly sense the voltage of the flying capacitor 260, but the upper voltage VCA of the flying capacitor 260 ( By detecting the zero crossing point of the voltage of the first node 410) and the zero crossing point of the voltage of the lower voltage VB (the voltage of the third node 430), the third switch Turn-on timings of the 253 and the fourth switch 254 may be determined.

According to various embodiments, in the first period (T1), the voltage (VCB) of the third node (430) of the fourth switch (254) is zero crossing (for example, the voltage (Vc) of both ends of the flying capacitor (260) is It may be turned on at the seventh time t7 when clamped to the input voltage V _IN. Accordingly, the fourth switch 254 may be turned on before the first switch 251 is turned off. For example, the seventh time t7 may be a time point at which the body diode inside the fourth switch 254 starts to conduct.

According to various embodiments, in the second period T2, when the third switch 253 is turned on, the voltage VCA of the first node 410 is zero crossing (the voltage Vc of both ends of the flying capacitor 260). It may be turned on at the eighth time t8 when clamped to the ground voltage (0V). Accordingly, the third switch 253 may be turned on before the second switch 252 is turned off. For example, the eighth time t8 may be a time point when the body diode inside the third switch 253 starts to conduct.

According to various embodiments, the turn-off time of the third switch 253 may be the same as the turn-on time of the second switch 252, and the turn-off time of the fourth switch 254 is the first switch 251. It may be the same as the turn-on time.

19 illustrates a change in a switching signal of a current control method in a fourth state of a second mode according to various embodiments of the present disclosure.

Referring to FIG. 19, the fourth state may be a state in which the inductor current I _L includes a zero current period (eg, a period in which I _L is 0), and clamping occurs in the voltage across the flying capacitor 260. have.

According to various embodiments, in the fourth state, the switching operation of the first switch 251 and the second switch 252 may be the same as that of FIG. 10 in the first state.

According to various embodiments, the turn-on operation of the third switch 253 and the fourth switch 254 is performed in which the voltage Vc of both ends of the flying capacitor 260 _{is clamped to the input voltage V IN} or the ground voltage 0V. It can be changed by the viewpoint. The turn-on operation of the third switch 253 and the fourth switch 254 may be the same as that of FIG. 18, and the turn-off operation of the third switch 253 and the fourth switch 254 may be the same as that of FIG. 17. .

For example, in the first period (T1), when the fourth switch 254 is turned on, the voltage (VCB) of the third node 430 is zero crossing (for example, the voltage (Vc) of both ends of the flying capacitor 260) It may be turned on at a seventh time t7 that is clamped to the input voltage V _IN. The fourth switch 254 may be turned on before the first switch 251 is turned off.

In the first period T1, when the first switch 251 is turned on at the fifth time t5 when the _{inductor current I L becomes 0 (eg, the sensing voltage Vcs is 0), the third} The switch 253 may be turned off. The third switch 253 may be turned off before the second switch 252 is turned on.

In the second period T2, the turn-on time of the third switch 253 may be turned on at the eighth time t8 when the voltage VCA of the first node 410 is clamped to the ground voltage 0V. The third switch 253 may be turned on before the second switch 252 is turned off.

In the second period T2, when the second switch 252 is turned on at the sixth time t6 when the _{inductor current I L becomes 0 (eg, the sensing voltage Vcs is 0), the fourth} The switch 254 can be turned off. The fourth switch 254 may be turned off before the first switch 251 is turned on.

An electronic device according to various embodiments disclosed in this document may be a device of various types. The electronic device may include, for example, a portable communication device (eg, a smartphone), a computer device, a portable multimedia device, a portable medical device, a camera, a wearable device, or a home appliance. The electronic device according to the embodiment of the present document is not limited to the above-described devices.

Various embodiments of the present document and terms used therein are not intended to limit the technical features described in this document to specific embodiments, and should be understood to include various modifications, equivalents, or substitutes of the corresponding embodiment. In connection with the description of the drawings, similar reference numerals may be used for similar or related components. The singular form of a noun corresponding to an item may include one or more of the above items unless clearly indicated otherwise in a related context. In this document, “A or B”, “at least one of A and B”, “at least one of A or B”, “A, B or C”, “at least one of A, B and C”, and “A Each of phrases such as "at least one of, B, or C" may include any one of the items listed together in the corresponding one of the phrases, or all possible combinations thereof. Terms such as "first", "second", or "first" or "second" may be used simply to distinguish the component from other Order) is not limited. Some (eg, first) component is referred to as “coupled” or “connected” to another (eg, second) component, with or without the terms “functionally” or “communicatively”. When mentioned, it means that any of the above components may be connected to the other components directly (eg by wire), wirelessly, or via a third component.

The term "module" used in this document may include a unit implemented in hardware, software, or firmware, and may be used interchangeably with terms such as logic, logic blocks, parts, or circuits. The module may be an integrally configured component or a minimum unit of the component or a part thereof that performs one or more functions. For example, according to an embodiment, the module may be implemented in the form of an application-specific integrated circuit (ASIC).

Various embodiments of the present document include one or more instructions stored in a storage medium (eg, internal memory 136 or external memory 138) that can be read by a machine (eg, electronic device 101). It may be implemented as software (for example, the program 140) including them. For example, the processor (eg, the processor 120) of the device (eg, the electronic device 801) may call and execute at least one command among one or more commands stored from a storage medium. This enables the device to be operated to perform at least one function according to the at least one command invoked. The one or more instructions may include code generated by a compiler or code executable by an interpreter. The device-readable storage medium may be provided in the form of a non-transitory storage medium. Here,'non-transient' only means that the storage medium is a tangible device and does not contain a signal (e.g., electromagnetic waves). It does not distinguish between temporary storage cases.

According to an embodiment, a method according to various embodiments disclosed in the present document may be provided by being included in a computer program product. Computer program products can be traded between sellers and buyers as commodities. The computer program product is distributed in the form of a device-readable storage medium (e.g. compact disc read only memory (CD-ROM)), or through an application store (e.g. Play Store ^TM ) or two user devices (e.g., compact disc read only memory (CD-ROM)). It can be distributed (e.g., downloaded or uploaded) directly between, e.g. smart phones). In the case of online distribution, at least a part of the computer program product may be temporarily stored or temporarily generated in a storage medium that can be read by a device such as a server of a manufacturer, a server of an application store, or a memory of a relay server.

An electronic device according to various embodiments (eg, the electronic device 101 of FIG. 1, the electronic device 201 of FIG. 2) includes a battery (eg, the battery 189 of FIG. 1, the battery 220 of FIG. 2 ), Electrically connected to the battery (e.g., battery 189 of FIG. 1, battery 220 of FIG. 2), and charging of the battery (e.g., battery 189 of FIG. 1, battery 220 of FIG. 2) Or a power management module that manages discharge (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2 ), and the power management module (eg, the power management module 188 of FIG. 1 ), A processor (eg, the processor 120 of FIG. 1) electrically connected to the power management module 210 of FIG. 2 is included, and the power management module (eg, the power management module 188 of FIG. 1) and the power management module 210 of FIG. The power management module 210 includes a plurality of switches (eg, a plurality of switches 250 of FIG. 2), at least one capacitor (eg, a flying capacitor 260 of FIG. 2), and at least one inductor (eg, a plurality of switches 250 of FIG. 2). : Includes the inductor 280 of FIG. 2 ), and includes a charging circuit configured to receive power from an external power supply (eg, the charging circuit 230 of FIG. 2 ), and the power management module (eg, of FIG. 1 ). The power management module 188 and the power management module 210 of FIG. 2 check the electrical connection between the charging circuit (eg, the charging circuit 230 of FIG. 2) and the external power supply device, and the connected external power supply device When the type of is determined and the type of the external power supply is the first type, the charging circuit (eg, the charging circuit 230 of FIG. 2) is the capacitor (eg, the flying capacitor 260 of FIG. 2) and A first mode for controlling the plurality of switches (eg, the plurality of switches 250 of FIG. 2) to have a fixed voltage conversion ratio due to resonance of the inductor (eg, the inductor 280 of FIG. 2) To charge the battery (e.g., the battery 189 of FIG. 1, the battery 220 of FIG. 2), and when the type of the external power supply is a second type, the charging The plurality of switches so that the voltage conversion ratio is changed in response to the charging ratio of the circuit (eg, the charging circuit 230 of FIG. 2) of the battery (eg, the battery 189 of FIG. 1 and the battery 220 of FIG. 2). The battery (e.g., the battery 189 of FIG. 1, the battery 220 of FIG. 2) can be charged by operating in a second mode for controlling the plurality of switches 250 of FIG. 2. have.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1 and the power management module 210 of FIG. 2) selects the type of the external power supply device based on power delivery (PD) communication. I can judge.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is based on a signal having a fixed duty cycle in the first mode. The plurality of switches (eg, the plurality of switches 250 of FIG. 2) may be controlled.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) transmits the signal having a 50% duty cycle in the first mode. Based on the plurality of switches (for example, the plurality of switches 250 of FIG. 2) may be controlled.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is configured to provide the signal to the capacitor (eg, the flying capacitor 260 of FIG. 2 ). ) And the inductor (for example, the inductor 280 of FIG. 2) may have the same frequency as the resonant frequency.

According to various embodiments, the current flowing through the capacitor (eg, the flying capacitor 260 of FIG. 2) and the voltage across the capacitor (eg, the flying capacitor 260 of FIG. 2) have a sine wave characteristic in the first mode. I can have it.

According to various embodiments, the current flowing through the inductor (for example, the inductor 280 of FIG. 2) may have a half wave characteristic of a sine wave in the first mode.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is in the second mode, the battery (eg, the battery of FIG. 1 ). 189), the plurality of switches (for example, the plurality of switches 250 of FIG. 2) can be controlled based on a signal having a duty cycle that varies in response to the charging rate of the battery 220 of FIG. 2. have.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is You can change the duty cycle.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is in the second mode, wherein the signal is the capacitor (eg, FIG. 2 ). It may be controlled to have the same frequency as the resonant frequency of the flying capacitor 260 of FIG. and the inductor (eg, the inductor 280 of FIG. 2 ).

According to various embodiments, the plurality of switches (for example, the plurality of switches 250 in FIG. 2) are a power supply unit (for example, the power supply unit 202a in FIG. 4) and a first node (for example, the plurality of switches 250 of FIG. 2 ). A first switch electrically connected between the first node 410 of FIG. 4 (eg, the first switch 251 of FIG. 4), and the first node (eg, the first node 410 of FIG. 4) And a second switch (eg, the second switch 252 of FIG. 4) electrically connected between the second node (eg, the second node 420 of FIG. 4 ), and the second node (eg, the second node 420 of FIG. 4 ). A third switch (eg, the third switch 253 in FIG. 4) electrically connected between the second node 420) and a third node (eg, the third node 430 in FIG. 4), and the third node The fourth switch (eg, the fourth switch of FIG. 4) electrically connected between the three node (eg, the third node 430 of FIG. 4) and the ground part (eg, the ground part 440 of FIG. 4) 254), and one end of the capacitor (eg, the flying capacitor 260 of FIG. 2) is connected to the first node (eg, the first node 410 of FIG. 4), and the capacitor (eg: The other end of the flying capacitor 260 of FIG. 2 is connected to the third node (eg, the third node 430 of FIG. 4), and one end of the inductor (eg, the inductor 280 of FIG. 2) is It is connected to a second node (for example, the second node 420 of FIG. 4), and the other end of the inductor (for example, the inductor 280 of FIG. 2) is It may be connected to the charging terminal (eg, the first electrode (eg, + electrode) 450) of the battery 220 of 2.

According to various embodiments, in the first mode, controlling the first switch (eg, the first switch 251 in FIG. 4) and the third switch (eg, the third switch 253 in FIG. 4 ). The first control signal is opposite to the second control signal for controlling the second switch (eg, the second switch 252 in FIG. 4) and the fourth switch (eg, the fourth switch 254 in FIG. 4). It can have a phase of becoming.

According to various embodiments, in the second mode, the first switch switch (eg, the first switch 251 of FIG. 4) is operated by a first control signal, and the second switch (eg, the first switch 251 of FIG. 4) is operated by a first control signal. The second switch 252 is operated by a second control signal, the third switch (eg, the third switch 253 in FIG. 4) is operated by a third control signal, and a fourth switch (eg. : The fourth switch 254 of FIG. 4 is operated by a fourth control signal, the first control signal has a phase opposite to that of the fourth control signal, and the second control signal is the third control It can have a phase opposite to the signal.

According to various embodiments, the first to fourth control signals may have a duty cycle that is variable in response to a charging rate of the battery (eg, the battery 189 of FIG. 1, the battery 220 of FIG. 2 ). have.

According to various embodiments, the power management module (for example, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) may be configured to include the first to the first to each other according to pulse width modulation (PWM). The duty cycle of the fourth control signal may be changed.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is received by the processor (eg, the processor 120 of FIG. 1). The plurality of switches (eg, the plurality of switches 250 of FIG. 2) may be controlled based on a control signal.

According to various embodiments, the power management module (for example, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is configured to include the external power supply and the battery (eg, the battery 189 of FIG. 1 ). ), when a circuit for controlling a constant voltage or a constant current for the battery 220 of FIG. 2 is included, the external power supply device may be determined as the first type.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is configured to include the plurality of switches (eg, the power management module 188 of FIG. 2) in the second mode. The switching frequency controlling the plurality of switches 250 may be controlled faster than the switching frequency controlling the plurality of switches (eg, the plurality of switches 250 of FIG. 2) in the first mode.

A method of charging a battery (eg, the battery 189 of FIG. 1, the battery 220 of FIG. 2) according to various embodiments of the present disclosure includes an electronic device (eg, the electronic device 101 of FIG. 1, the electronic device of FIG. 2 ). 201)) of the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2 ), and the power management module (eg, the power management module 188 of FIG. 1) , Checking the electrical connection of the external power device to the charging circuit (for example, the charging circuit 230 of FIG. 2) included in the power management module 210 of FIG. 2, and the connected external power device is a first type. In this case, due to resonance of the capacitor (eg, the flying capacitor 260 of FIG. 2) and the inductor (eg, the inductor 280 of FIG. 2) included in the charging circuit (eg, the charging circuit 230 of FIG. 2). An operation of controlling a plurality of switches (eg, a plurality of switches 250 of FIG. 2) included in the charging circuit (eg, the charging circuit 230 of FIG. 2) to have a fixed voltage conversion ratio, and When the connected external power supply is of the second type, the plurality of switches are configured to change the voltage conversion ratio in response to a charging ratio of the battery (eg, the battery 189 in FIG. 1 and the battery 220 in FIG. 2 ). (For example, it may include an operation of controlling the plurality of switches 250 of FIG. 2 ).

According to various embodiments, the plurality of switches (for example, the plurality of switches 250 of FIG. 2) are a first switch electrically connected between a power supply of the external power supply and a first node, and the first node. And a second switch electrically connected between the second node and the second node, a third switch electrically connected between the second node and the third node, and a fourth switch electrically connected between the third node and the ground part. Including, one end of the capacitor (for example, the flying capacitor 260 of FIG. 2) is connected to the first node, and the other end of the capacitor (for example, the flying capacitor 260 of FIG. 2) is connected to the third node. Is connected, one end of the inductor (eg, inductor 280 of FIG. 2) is connected to the second node, and the other end of the inductor (eg, inductor 280 of FIG. 2) is connected to the battery (eg, inductor 280 of FIG. 2). The battery 189 of FIG. 2 and the charging terminal of the battery 220 of FIG. 2 (eg, a first electrode (eg, a + electrode) 450) may be connected.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is the battery (eg, the battery 189 of FIG. 1, A control voltage is determined based on a voltage of the charging terminal of the battery 220 or a current flowing into the charging terminal, and the first switch (eg, the first switch of FIG. 4) is based on a first triangle wave and the control voltage. (251)) is turned on or off, and the second switch (eg, the second switch 252 in FIG. 4) is turned on or off based on the second triangle wave and the control voltage, and the second triangle wave is It may be a signal shifted by a half cycle of the first triangle wave.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is Turning on a switch (eg, the first switch 251 in FIG. 4) and turning off the first switch (eg, the first switch 251 in FIG. 4) when the control voltage is greater than the first triangle wave And, when the control voltage becomes smaller than the second triangle wave, the second switch (for example, the second switch 252 of FIG. 4) is turned on, and when the control voltage is greater than the second triangle wave, the second 2 The switch (eg, the second switch 252 of FIG. 4) may be turned off.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is the third switch (eg, the third switch 253 of FIG. 4 ). ) Is operated as a control signal having a phase opposite to that of the control signal of the second switch (eg, the second switch 252 of FIG. 4), and the fourth switch (eg, the fourth switch 254 of FIG. 4) May be operated as a control signal having a phase opposite to that of the control signal of the first switch (eg, the first switch 251 of FIG. 4 ).

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is the second switch (eg, the second switch 252 of FIG. 4 ). ) Before the inductor (eg, inductor 280 of FIG. 2) is turned on, when the current flowing through the inductor (eg, inductor 280 of FIG. 2) becomes 0, the third switch (eg, inductor 280 of FIG. Turning off the third switch 253, and before the first switch (eg, the first switch 251 of FIG. 4) is turned on, the current of the inductor (eg, the inductor 280 of FIG. 2) is 0 In this case, the fourth switch (eg, the fourth switch 254 of FIG. 4) may be turned off.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is the second switch (eg, the second switch 252 of FIG. 4 ). ) Before being turned off, when the voltage of the first node (eg, the first node 410 of FIG. 4) is the same as the ground voltage, the third switch (eg, the third switch 253 of FIG. 4) Is turned on, and before the first switch (eg, the first switch 251 of FIG. 4) is turned off, the voltage of the third node (eg, the third node 430 of FIG. 4) is equal to the ground voltage. In the same case, the fourth switch (eg, the fourth switch 254 of FIG. 4) may be turned on.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is the second switch (eg, the second switch 252 of FIG. 4 ). ) Before the inductor (eg, the inductor 280 of FIG. 2) is turned on, when the current flowing through the inductor (eg, the inductor 280 of FIG. 2) becomes 0, the third switch (eg, the inductor 280 of FIG. Turning off the third switch 253, and before the first switch (eg, the first switch 251 of FIG. 4) is turned on, the current of the inductor (eg, the inductor 280 of FIG. 2) is 0 In this case, the fourth switch (eg, the fourth switch 254 of FIG. 4) may be turned off.

According to various embodiments, the power management module (eg, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) controls the plurality of switches based on a control signal received from the processor. can do.

According to various embodiments, the power management module (for example, the power management module 188 of FIG. 1, the power management module 210 of FIG. 2) is configured to include the external power supply and the battery (eg, the battery 189 of FIG. 1 ). ), when a circuit for controlling a constant voltage or a constant current for the battery 220 of FIG. 2 is included, the external power supply device may be determined as the first type.

Power management modules (eg, the power management module 188 of FIG. 1, the power management of FIG. 2) of an electronic device (eg, the electronic device 101 of FIG. 1, and the electronic device 201 of FIG. 2) according to various embodiments In a method of charging a battery (eg, the battery 189 of FIG. 1, the battery 220 of FIG. 2) performed by the module 210, the power management module (eg, the power management module 188 of FIG. 1) ), checking the electrical connection of the external power device to the charging circuit (eg, the charging circuit 230 of FIG. 2) included in the power management module 210 of FIG. 2, the connected external power device is a first type In the case of, the resonance of the capacitor (eg, the flying capacitor 260 of FIG. 2) and the inductor (eg, the inductor 280 of FIG. 2) included in the charging circuit (eg, the charging circuit 230 of FIG. 2) An operation of controlling a plurality of switches (eg, a plurality of switches 250 of FIG. 2) included in the charging circuit (eg, the charging circuit 230 of FIG. 2) to have a fixed voltage conversion ratio by When the connected external power supply is of the second type, the plurality of switches are configured to change the voltage conversion ratio in response to a charging ratio of the battery (eg, the battery 189 in FIG. 1 and the battery 220 in FIG. 2 ). (For example, it may include an operation of controlling the plurality of switches 250 of FIG. 2 ).

According to various embodiments, each component (eg, module or program) of the above-described components may include a singular number or a plurality of entities. According to various embodiments, one or more components or operations among the above-described corresponding components may be omitted, or one or more other components or operations may be added. Alternatively or additionally, a plurality of components (eg, a module or program) may be integrated into one component. In this case, the integrated component may perform one or more functions of each component of the plurality of components in the same or similar to that performed by the corresponding component among the plurality of components prior to the integration. . According to various embodiments, operations performed by a module, program, or other component may be sequentially, parallel, repeatedly, or heuristically executed, or one or more of the operations may be executed in a different order or omitted. Or one or more other actions may be added.

Claims (23)

In the electronic device,
battery;
A power management module electrically connected to the battery and managing charging or discharging of the battery; And
Includes; a processor electrically connected to the power management module,
The power management module
A charging circuit comprising a plurality of switches, at least one capacitor and at least one inductor, and configured to receive power from an external power supply device,
The power management module
Check the electrical connection between the charging circuit and the external power supply,
Determine the type of the connected external power supply device,
When the type of the external power supply is a first type, the charging circuit operates in a first mode of controlling the plurality of switches to have a fixed voltage conversion ratio due to resonance of the capacitor and the inductor, thereby operating the battery. Charge it,
When the type of the external power supply is a second type, the charging circuit operates in a second mode for controlling the plurality of switches so that the voltage conversion ratio is changed in response to the charging ratio of the battery to charge the battery Device. The method of claim 1, wherein the power management module
An electronic device that determines the type of the external power supply device based on power delivery (PD) communication. The method of claim 1, wherein the power management module
In the first mode, an electronic device that controls the plurality of switches based on a signal having a fixed duty cycle. The method of claim 3, wherein the power management module
In the first mode, an electronic device that controls the plurality of switches based on the signal having a duty cycle of 50%. The method of claim 3, wherein the power management module
An electronic device controlling the signal to have the same frequency as the resonant frequency of the capacitor and the inductor. The method of claim 1, wherein a current flowing through the capacitor and a voltage across the capacitor are
In the first mode, an electronic device having a sine wave characteristic. The method of claim 1, wherein the power management module
In the second mode, an electronic device that controls the plurality of switches based on a signal having a duty cycle that varies according to a charging rate of the battery. The method of claim 7, wherein the power management module
An electronic device that changes the duty cycle of the signal according to pulse width modulation (PWM). The method of claim 8, wherein the power management module
In the second mode, the electronic device controls the signal to have the same frequency as the resonant frequency of the capacitor and the inductor. The method of claim 1, wherein the plurality of switches
A first switch electrically connected between the power supply unit of the external power supply and a first node, a second switch electrically connected between the first node and the second node, and electrically between the second node and the third node A third switch connected, and the fourth switch electrically connected between the third node and the ground,
One end of the capacitor is connected to the first node,
The other end of the capacitor is connected to the third node,
One end of the inductor is connected to the second node, and the other end of the inductor is connected to a charging terminal of the battery. The method of claim 10,
In the first mode, the first control signal for controlling the first switch and the third switch has a phase opposite to the second control signal for controlling the second switch and the fourth switch. The method of claim 10,
In the second mode, the first switch is operated by a first control signal, the second switch is operated by a second control signal, the third switch is operated by a third control signal, and 4 switch is operated by the fourth control signal,
The first control signal has a phase opposite to the fourth control signal,
The second control signal has a phase opposite to the third control signal. The method of claim 12, wherein the first to fourth control signals are
An electronic device having a duty cycle that varies according to a charging rate of the battery. The method of claim 13, wherein the power management module
An electronic device that changes the duty cycle of the first to fourth control signals according to pulse width modulation (PWM). The method of claim 10, wherein the power management module
Determine a control voltage based on the voltage of the charging terminal of the battery or the current flowing into the charging terminal,
Turning on or off the first switch based on a first triangle wave and the control voltage,
Turning on or off the second switch based on a second triangle wave and the control voltage,
The second triangular wave is a signal shifted by half a period of the first triangular wave. The method of claim 15, wherein the power management module
When the control voltage becomes smaller than the first triangle wave, the first switch is turned on,
When the control voltage is greater than the first triangle wave, the first switch is turned off,
When the control voltage becomes smaller than the second triangle wave, the second switch is turned on,
When the control voltage is greater than the second triangle wave, the electronic device turns off the second switch. The method of claim 15, wherein the power management module
Operating the third switch with a control signal having a phase opposite to that of the control signal of the second switch,
An electronic device that operates the fourth switch with a control signal having a phase opposite to that of the control signal of the first switch. The method of claim 15, wherein the power management module
When the inductor current flowing through the inductor becomes 0 before the second switch is turned on, the third switch is turned off,
When the inductor current becomes 0 before the first switch is turned on, the electronic device turns off the fourth switch. The method of claim 15, wherein the power management module
When the voltage of the first node is the same as the ground voltage before the second switch is turned off, turning on the third switch,
When the voltage of the third node is the same as the ground voltage before the first switch is turned off, the electronic device turns on the fourth switch. The method of claim 19, wherein the power management module
When the inductor current flowing through the inductor becomes 0 before the second switch is turned on, the third switch is turned off,
When the inductor current becomes 0 before the first switch is turned on, the electronic device turns off the fourth switch. The method of claim 1, wherein the power management module
An electronic device that controls the plurality of switches based on a control signal received from the processor. The method of claim 1, wherein the power management module
When the external power supply includes a circuit for controlling a constant voltage or a constant current for the battery, the electronic device determines the external power supply as the first type. A method of charging a battery performed in a power management module of an electronic device, the method comprising:
Checking an electrical connection of an external power supply device to a charging circuit included in the power management module;
When the connected external power supply is of the first type, controlling a plurality of switches included in the charging circuit to have a fixed voltage conversion ratio due to resonance of a capacitor and an inductor included in the charging circuit; And
And when the connected external power supply is of the second type, controlling the plurality of switches to change the voltage conversion ratio in response to a charging ratio of the battery.

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