KR20160059996A - In-band full duplex transceiver and interference cancealation method thereof - Google Patents

In-band full duplex transceiver and interference cancealation method thereof Download PDF

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KR20160059996A
KR20160059996A KR1020150162809A KR20150162809A KR20160059996A KR 20160059996 A KR20160059996 A KR 20160059996A KR 1020150162809 A KR1020150162809 A KR 1020150162809A KR 20150162809 A KR20150162809 A KR 20150162809A KR 20160059996 A KR20160059996 A KR 20160059996A
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signal
interference
domain
self
digital
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Korean (ko)
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주형식
김선애
장갑석
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한국전자통신연구원
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/54—Circuits using the same frequency for two directions of communication
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B15/00—Suppression or limitation of noise or interference
    • H04B15/02—Reducing interference from electric apparatus by means located at or near the interfering apparatus
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/022—Channel estimation of frequency response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03159—Arrangements for removing intersymbol interference operating in the frequency domain

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  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Power Engineering (AREA)
  • Noise Elimination (AREA)

Abstract

An in-band full duplex transceiver and a method for canceling interference thereof are disclosed. The same-band full-duplex transceiver may include an antenna, a distributor for sending a transmission signal to the antenna, and for transmitting a reception signal received through the antenna to a reception module via a reception output terminal, and a digital SIC unit. Here, the digital SIC unit estimates a frequency domain channel for the harmonic component of the self-transmission interference signal using the time-domain signal of the transmission signal and the frequency-domain signal of the self-transmission interference signal included in the signal output from the reception output terminal . And the digital SIC unit can remove the self-transmitted interference signal using the estimated frequency-domain channel.

Description

≪ Desc / Clms Page number 1 > IN-BAND FULL DUPLEX TRANSCEIVER AND INTERFERENCE CANCEALATION METHOD THEREOF &

The present invention relates to a same-band full duplex transceiver and a method of canceling interference.

Currently, the wireless communication system adopts most of the half duplex method. The half-duplex scheme is able to maintain orthogonality between transmission and reception by transmitting or receiving time or frequency division. However, this half-duplex scheme not only wastes resources (time or frequency) but also has a difficulty in multi-hop relay between mobile small cells, and a separate overhead is required to solve the hidden node problem .

The in-band Full Duplex scheme is presented as a solution to overcome the inefficiency of the half-duplex scheme. The same-band full-duplex scheme is a technology capable of transmitting and receiving simultaneously in the same band. The same-band full-duplex scheme can theoretically increase the link capacity up to twice, which is indispensable technology for achieving the 1000 times traffic capacity required for 5G mobile communication.

However, the same-band full-duplex scheme has a disadvantage in that a self-transmitted signal flows into a receiver, and a self-transmitted signal acts as a magnetic interference signal much stronger than an effective received signal. For this self-interference cancellation (SIC), the SIC technology in the analog circuit area and the SIC technology in the digital domain are used together with the antenna area SIC technology, which physically separates the transmission and reception antennas physically . In order to apply the same-band full-duplex scheme to a small-sized apparatus, it is required that each antenna can simultaneously transmit and receive signals of the same band without physical separation between the antennas. In this case, not only the SIC in the analog circuit area (RF analog circuit area / baseband analog circuit area) but also the SIC in the digital area is more important.

SUMMARY OF THE INVENTION It is an object of the present invention to provide a same-band full duplex transceiver that eliminates interference and a method of canceling interference.

According to an embodiment of the present invention, a same-band full duplex transceiver is provided. The same band full duplex transceiver includes an antenna and a divider for transmitting a transmission signal to the antenna and for transmitting a reception signal received through the antenna to a reception module through a reception output terminal, a time domain signal of the transmission signal, Estimating a frequency-domain channel for a harmonic component of the self-transmitting interfering signal using a frequency-domain signal of a self-transmitting interfering signal contained in a signal to be transmitted, and using the estimated frequency- And a digital SIC (Self-Interference Cancellation) unit for removing the digital SIC.

According to the embodiment of the present invention, even if a nonlinear component exists in a channel of a magnetic interference signal, it can be processed like a signal component, thereby providing excellent channel performance.

According to another embodiment of the present invention, both the linear and nonlinear components of the magnetic interference signal can be removed with low complexity.

1 is a diagram of a same-band full duplex transceiver 100 in accordance with an embodiment of the present invention.
2 is a diagram illustrating a same-band full duplex transceiver 100a according to another embodiment of the present invention.
3 is a diagram illustrating a same-band full duplex transceiver 100b in accordance with another embodiment of the present invention.
4 is a diagram illustrating a same-band full duplex transceiver 100c in accordance with another embodiment of the present invention.
5 is a diagram illustrating a same-band full duplex transceiver 100d in accordance with another embodiment of the present invention.
6 is a diagram showing an m-th harmonic eliminator 250d_2.

Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings so that those skilled in the art can easily carry out the present invention. The present invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. In order to clearly illustrate the present invention, parts not related to the description are omitted, and similar parts are denoted by like reference characters throughout the specification.

Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings so that those skilled in the art can easily carry out the present invention. The present invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. In order to clearly illustrate the present invention, parts not related to the description are omitted, and similar parts are denoted by like reference characters throughout the specification.

Throughout the specification, a terminal is referred to as a mobile terminal (MT), a mobile station (MS), an advanced mobile station (AMS), a high reliability mobile station ), A subscriber station (SS), a portable subscriber station (PSS), an access terminal (AT), a user equipment (UE) AMS, HR-MS, SS, PSS, AT, UE, and the like.

Also, a base station (BS) is an advanced base station (ABS), a high reliability base station (HR-BS), a node B, an evolved node B, eNodeB), an access point (AP), a radio access station (RAS), a base transceiver station (BTS), a mobile multihop relay (MMR) BS, RS, HR, RS, etc.) may be referred to as a high reliability relay station (HR-RS) -RS, and the like.

Throughout the specification, a transceiver may be a terminal, a mobile terminal (MT), a mobile station (MS), an advanced mobile station (AMS), a high reliability mobile station , An HR-MS, a subscriber station (SS), a portable subscriber station (PSS), an access terminal (AT), user equipment (UE) MS, AMS, HR-MS, SS, PSS, AT, UE, and the like.

In addition, the transceiver includes a base station (BS), an advanced base station (ABS), a high reliability base station (HR-BS), a node B, an evolved node B, an eNodeB, an access point (AP), a radio access station (RAS), a base transceiver station (BTS), a mobile multihop relay (MMR) And may be referred to as a relay station (RS), a high reliability relay station (HR-RS) serving as a base station, etc., and may be referred to as an ABS, a Node B, an eNodeB, an AP, a RAS, a BTS, BS, RS, HR-RS, and the like.

1 is a diagram of a same-band full duplex transceiver 100 in accordance with an embodiment of the present invention.

1, the same-band full duplex transceiver 100 according to an embodiment of the present invention includes an Inverse Discrete Fourier Transform (IDFT) 110, a Digital-to-Analog Converter (DAC) A mixer 130, a power amplifier (PA) 140, a distributor 150, an antenna 160, a first signal combiner 170, a low noise amplifier (LNA) 180 An integrator 190, an analog-to-digital converter (ADC) 200, a discrete Fourier transform (DFT) 210, a second signal combiner 220, An analog SIC (Self-Interference Cancellation) unit 240, and a digital SIC unit 250.

IDFT (110) converts the transmitted signal (X) in the frequency domain by the transmitted signal (x) in the time domain. The DAC 120 converts an analog signal into a digital signal in a time domain and the mixer 130 converts a baseband frequency signal into a radio frequency band signal using a carrier frequency f C. The PA 140 amplifies and outputs the RF band signal. The IDFT 110, the DAC 120, the mixer 130, and the PA 140 constitute a part of the transmission module.

The distributor 150 is connected to the antenna 160 and sends a transmission signal to the antenna 160. Then, the distributor 150 sends the received signal received from the antenna 160 to the receiving module (the signal combiner 170, the LNA 180, etc.) of FIG. That is, the distributor 150 according to the embodiment of the present invention sends the transmission signal to the antenna 160 and sends the reception signal to the reception module. The distributor 150 may be implemented as a circulator or an electrical balance duplex (EBD). The circulator and the EBD will be apparent to those skilled in the art, and will not be described in detail.

The antenna 160 simultaneously performs the reception function as well as the transmission function for the same-band full-duplex manner. That is, the transmission signal is transmitted through the antenna 160 and the reception signal is received.

The signal output from the divider 150 to the signal combiner 170 includes not only the self-received signal of the same-band full duplex transceiver 100 but also a self-transmitted interference signal. The transmission signal transmitted through the antenna 160 is transmitted to the antenna 160 through the distributor 150, but a part of the transmission signal flows into the reception module (LNA or the like) and acts as an interference signal. The interference signal is a self- . This is because the transceiver according to the embodiment of the present invention operates in the same band full duplex manner. In the embodiment of the present invention, the magnetic transmission interference signal is primarily removed through the analog SIC unit 240. The analog SIC 240 receives the output signal of the power amplifier PA and outputs a signal for minimizing the self interference interference signal in the analog domain. The analog SIC 240 may be implemented as an FIR (Finite Impulse Response) filter, and a method for removing a self-transmitted interference signal through an FIR filter is known to those skilled in the art. A detailed description will be omitted.

The first signal combiner 170 combines the received signal and the output signal of the analog SIC unit 240, and outputs the combined signal to the LNA 180. The first signal combiner 170 subtracts the signal output from the analog SIC unit 240 from the received signal and combines the two signals. As described above, the analog SIC unit 240 outputs a signal that minimizes the self-interference signal in the analog domain. Thus, the first signal combiner 170 can remove the self-interference signal from the received signal, To the LNA 180.

The LNA 180 receives the reception signal from which the self interference interference signal is removed from the signal combiner 170 in the analog domain, and removes and amplifies noise from the input signal. The integrator 190 converts the RF band signal into a baseband signal using the carrier frequency f C. The ADC 200 converts an analog baseband signal into a digital signal, and the DFT 210 converts the time domain received signal into a frequency domain signal.

The digital SIC unit 250 according to an embodiment of the present invention receives a transmission signal in a time domain and a reception signal in a frequency domain, estimates a channel, and generates and outputs a signal that minimizes a self interference interference signal in a digital domain. The method by which the digital SIC unit 250 estimates the channel in the digital domain and minimizes the self interference interference signal will be described in detail below.

The second signal combiner 220 combines the output signal of the DFT 210 and the output signal of the digital SIC unit 250 and outputs the combined signal to the decoder 230. The second signal combiner 220 subtracts the signal output from the digital SIC unit 250 from the received signal and combines the two signals. At this time, as described below, the digital SIC unit 250 outputs a signal for minimizing the self interference interference signal in the digital domain, so that the second signal combiner 220 removes the self interference interference signal from the received signal, To the LNA 180. Then, the decoder 230 demodulates the reception signal finally removed by the digital SIC unit 250.

Hereinafter, a method for estimating a channel in the digital domain and minimizing the self interference interference signal according to an embodiment of the present invention will be described.

The time domain signal y [n] sampled by the ADC 200 after the transmission signal x of the same-band full duplex transceiver 100 has passed through the analog SIC 240, And the remaining self interference interference signal after being removed by the analog SIC unit 240) is expressed by Equation 1 below.

Figure pat00001

In Equation (1), x [n] is the time-domain transmit signal of the same-band full duplex transceiver 100,

Figure pat00002
Is the m-th harmonic signal of x [n]. Also,
Figure pat00003
Is a time-domain channel observed by passing an n-th sample time signal applied to the m-th harmonic, and N denotes a size of the DFT 210 and the IDFT 110.
Figure pat00004
Represents a reception noise. In the embodiment of the present invention, Taylor's series is employed for harmonic modeling as shown in Equation 1
Figure pat00005
Represents the weight of the mth harmonic, but all harmonic component modeling techniques can be used.

In Equation 1,

Figure pat00006
Point DFT by the DFT 210, the vector of the transmission signal of the full-duplex transceiver in the frequency domain (i.e., the self-transmission interference signal)
Figure pat00007
Respectively. At this time, the reception signal at the k-th subcarrier in the frequency domain is expressed by Equation (2) below.

Figure pat00008

In Equation (2)

Figure pat00009
Is a frequency-domain channel in the k-th subcarrier for the m-th harmonic signal,
Figure pat00010
Is the frequency-domain noise component at the k-th subcarrier. The frequency domain received signal of Equation (2) can be represented as a vector form as shown in Equation (3) below.

Figure pat00011

In Equation 3,

Figure pat00012
Is the kth diagonal entry
Figure pat00013
Diagonal matrix. Also,
Figure pat00014
, Where M is the maximum order of the harmonic signal. And,
Figure pat00015
Lt;
Figure pat00016
to be.

remind

Figure pat00017
The estimated value for
Figure pat00018
In this case,
Figure pat00019
The recovered SI using
Figure pat00020
to be. The error vector between the received signal in the actual frequency domain (i.e., the self-transmitted interference signal) and the recovered SI is
Figure pat00021
to be. At this time, the MSE (Mean Squared Error) between the actual SI and the recovered SI is expressed by Equation (4) below.

Figure pat00022

In Equation (4)

Figure pat00023
,
Figure pat00024
, And
Figure pat00025
Is expressed by the following equation (5).

Figure pat00026

As can be seen from equation (4), the MSE between the actual SI and the recovered SI is

Figure pat00027
Is a concave function. therefore,
Figure pat00028
To become
Figure pat00029
Is an estimated channel of SI that minimizes the MSE. Such
Figure pat00030
&Quot; (6) "

Figure pat00031

Equation 6

Figure pat00032
, SI removal in the digital domain
Figure pat00033
. That is, the digital SIC unit 250
Figure pat00034
Wow
Figure pat00035
Using
Figure pat00036
And
Figure pat00037
And the second signal combiner 220 outputs
Figure pat00038
To remove the self-transmitted interference signal in the digital domain. At this time, as shown in Equation (5)
Figure pat00039
Wow
Figure pat00040
Lt; / RTI >
Figure pat00041
≪ / RTI >
Figure pat00042
And a received signal vector (i.e., a magnetic transmission interference signal)
Figure pat00043
Lt; RTI ID = 0.0 > Samples < / RTI >

In the embodiment of the present invention shown in FIG. 1, a method of estimating channels for harmonic signals of all orders at one time has been described. However, it is necessary to separately determine the channel of the linear component of SI (i.e., m = 1) and the channel of the nonlinear component (i.e., m > 1). In the following FIG. 2, a method for separating and estimating channels for the linear and non-linear components of SI and eliminating the self-transmitted interference signal will be described.

2 is a diagram illustrating a same-band full duplex transceiver 100a according to another embodiment of the present invention.

As shown in FIG. 2, the same-band full-duplex transceiver 100a according to another embodiment of the present invention includes a digital SIC unit 250a that separately estimates channels for linear and nonlinear components of SI, 1, so that redundant description will be omitted. In FIG. 2, a part for estimating a channel for a linear component of SI and removing a self-transmitted interference signal is denoted by 250a_1, and a part for estimating a channel for a nonlinear component and removing a self-transmitted interference signal is denoted by 250a_2.

The digital SIC unit 250a according to another embodiment of the present invention first removes the linear component of the SI in the frequency domain and then removes the nonlinear component of the SI in the frequency domain.

First, the analog SIC 240 samples a received signal (i.e., a self-transmitted interference signal) of the same-band full duplex transceiver in which the SI is partially removed in the analog domain,

Figure pat00044
. Then, through the DFT 210
Figure pat00045
Point DFT on the frequency domain received signal < RTI ID = 0.0 >
Figure pat00046
Can be obtained.

Next, the digital SIC unit 250a compares the SI channel of the linear component for eliminating the linear component of the SI

Figure pat00047
. At this time,
Figure pat00048
The method of Equation (6) described above can be used. To obtain the linear component channel of the SI, the time-
Figure pat00049
The matrix defined in Equation (3)
Figure pat00050
And
Figure pat00051
Using all of
Figure pat00052
Can be obtained. At this time,
Figure pat00053
I do not use it all
Figure pat00054
medium
Figure pat00055
, Or by using both of them in the frequency axis
Figure pat00056
Can be obtained.
Figure pat00057
Is extracted and used, the time-domain transmission signal
Figure pat00058
Using
Figure pat00059
Instead of obtaining the frequency-domain transmission signal
Figure pat00060
Using
Figure pat00061
Can be obtained.

To remove the SI of the nonlinear component,

Figure pat00062
and
Figure pat00063
Lt; / RTI >
Figure pat00064
. At this time,
Figure pat00065
Can be obtained by the following Equation (7).

Figure pat00066

In Equation (7)

Figure pat00067
Wow
Figure pat00068
The
Figure pat00069
Wow
Figure pat00070
(8) " (8) "

Figure pat00071

The nonlinear component of SI is expressed by Equation (7)

Figure pat00072
Using
Figure pat00073
Lt; / RTI > can be removed in the digital domain. At this time, as shown in Equation (8)
Figure pat00074
Wow
Figure pat00075
The
Figure pat00076
and
Figure pat00077
Lt; RTI ID = 0.0 > Samples < / RTI >

3 is a diagram illustrating a same-band full duplex transceiver 100b in accordance with another embodiment of the present invention.

As shown in FIG. 3, the same-band full duplex transceiver 100b according to another embodiment of the present invention is similar to that of FIG. 1 except for the digital SIC unit 250b, and thus a duplicate description will be omitted.

First, the analog SIC unit 240 samples the received signal (i.e., the self-transmitted interference signal) of the same-band full duplex transceiver 100b in which the SI is partially removed in the analog domain,

Figure pat00078
. Then, through the DFT 210
Figure pat00079
Point DFT on the frequency domain received signal < RTI ID = 0.0 >
Figure pat00080
Can be obtained.

The digital SIC unit 250b

Figure pat00081
Band transceiver 100b of the same-band full-duplex transceiver 100b
Figure pat00082
, And, if necessary, a frequency domain transmit signal
Figure pat00083
To obtain a first-order estimation value of the frequency-domain SI channel. At this time, a first-order estimation value of the estimated frequency-domain SI channel is expressed as Equation (9) below.

Figure pat00084

In Equation (9)

Figure pat00085
Denotes a frequency domain channel for the m-th harmonic signal in the SI signal,
Figure pat00086
About
Figure pat00087
. At this time,
Figure pat00088
The method described in Equation (7) may be used or the method described in Equation (6) may be used.

The digital SIC unit 250b compares the estimated

Figure pat00089
And sequentially performs N-point IDFT for each of N blocks divided into M blocks. That is, the digital SIC unit 250b
Figure pat00090
RTI ID = 0.0 > IDFT < / RTI > Accordingly, the digital SIC unit 250b generates the sampled time-domain channel for the m < th > harmonic signal of the SI signal,
Figure pat00091
.

At this time, the estimated channel

Figure pat00092
The most important part of the SI
Figure pat00093
And the remaining estimates are mainly generated by noise. In order to eliminate the influence of the noise, the digital SIC unit 250b calculates
Figure pat00094
.

Figure pat00095

In Equation (10)

Figure pat00096
Is a predetermined value.

Next, the digital SIC unit 250b

Figure pat00097
Point DFT for each < RTI ID = 0.0 > m < / RTI >
Figure pat00098
. The digital SIC unit 250b uses this
Figure pat00099
. this
Figure pat00100
Is the frequency domain channel of the SI to be finally estimated,
Figure pat00101
Is a signal in which the SI is removed in the digital domain.

3,

Figure pat00102
The method of Equation (6) is used as a method of estimating the channel state of the mobile station. However, by using the algorithm of FIG. 2,
Figure pat00103
May be used. In Equation 10,
Figure pat00104
A variety of methods can be used for obtaining the data
Figure pat00105
Other methods of inserting a value of zero into the time domain estimation channel may be used,
Figure pat00106
To get
Figure pat00107
on
Figure pat00108
Point IDFT / DFT for the IDFT / DFT block may be performed in parallel using a plurality of IDFT / DFT blocks, but the IDFT / DFT block may be used for time-division.

4 is a diagram illustrating a same-band full duplex transceiver 100c in accordance with another embodiment of the present invention.

4, the same-band full-duplex transceiver 100c according to another embodiment of the present invention includes a digital SIC unit 250c that separately estimates channels for the linear and nonlinear components of SI, 3, except for the fact that it is removed. In FIG. 4, the part for estimating the channel for the linear component of SI and removing the self-transmitted interference signal is denoted by 250c_1, and the part for estimating the channel for the nonlinear component and removing the self-transmitted interference signal is denoted by 250c_2.

The digital SIC unit 250c according to another embodiment of the present invention first removes the linear component of the SI from the frequency domain and then removes the nonlinear component of the SI from the frequency domain.

First, the analog SIC unit 240 samples the reception signal (i.e., the self-transmission interference signal) of the same-band full duplex transceiver 100c in which the SI is partially removed in the analog domain,

Figure pat00109
. Then, through the DFT 210
Figure pat00110
Point DFT on the frequency domain received signal < RTI ID = 0.0 >
Figure pat00111
Can be obtained.

The digital SIC unit 250c performs a linear estimation of the SI channel of the linear component to remove the linear component of the SI,

Figure pat00112
. At this time,
Figure pat00113
Various methods may be used, and for each method, a time-domain transmit signal < RTI ID = 0.0 >
Figure pat00114
Quot;
Figure pat00115
(Shown as Input 1 in Fig. 4) and the frequency domain transmit signal
Figure pat00116
(Denoted by Input 2 in Fig. 4) may optionally be used. Such
Figure pat00117
The method of Equation (6) can be used.

The digital SIC unit 250c compares the estimated

Figure pat00118
Point IDFT on the sampled time domain channel < RTI ID = 0.0 >
Figure pat00119
. Then, the digital SIC unit 250c
Figure pat00120
In order to eliminate the influence of noise in estimating the noise,
Figure pat00121
.

Figure pat00122

In Equation (11)

Figure pat00123
Is a predetermined value.

The digital SIC unit 250c

Figure pat00124
Point DFT on the frequency domain channel < RTI ID = 0.0 >
Figure pat00125
. The digital SIC unit 250c
Figure pat00126
To calculate the linear component of SI as the frequency domain received signal
Figure pat00127
.

The digital SIC unit 250c removes the SI of the linear component

Figure pat00128
and
Figure pat00129
The first-order estimation value for the SI channel of the non-linear component
Figure pat00130
. here,
Figure pat00131
The method of Equation (6) or Equation (7) may be used. The digital SIC unit 250c includes
Figure pat00132
RTI ID = 0.0 > N-point < / RTI > IDFT on the sampled time domain channel <
Figure pat00133
In order to eliminate the influence of noise,
Figure pat00134
.

Figure pat00135

In Equation (12)

Figure pat00136
Is a predetermined value.

Next, the digital SIC unit 250c

Figure pat00137
Point DFT for each < RTI ID = 0.0 > SI < / RTI >
Figure pat00138
. The digital SIC unit 250c uses this
Figure pat00139
. this
Figure pat00140
Is the frequency domain channel of the SI to be finally estimated,
Figure pat00141
Is a signal in which the SI is removed in the digital domain.

On the other hand, in the description of FIG. 4

Figure pat00142
And
Figure pat00143
The method of Equation (6) or Equation (7) is used as a method of estimating the frequency-domain SI channel
Figure pat00144
May be used. In Equation (11) and Equation (12)
Figure pat00145
A variety of methods can be used for obtaining the data
Figure pat00146
Other methods of inserting a value of zero into the time domain estimation channel may be used,
Figure pat00147
To get
Figure pat00148
Point IDFT / DFT for the IDFT / DFT block may be performed in parallel using a plurality of IDFT / DFT blocks, but the IDFT / DFT block may be used for time-division.

5 is a diagram illustrating a same-band full duplex transceiver 100d in accordance with another embodiment of the present invention.

As shown in FIG. 5, the same-band full duplex transceiver 100d according to another embodiment of the present invention is similar to that of FIG. 1 except for the digital SIC unit 250d, and thus a duplicate description will be omitted.

The digital SIC unit 250d according to another embodiment of the present invention reflects the fact that the power of the SI due to the harmonic signal becomes smaller as the order of the harmonics signal becomes larger so as to continuously remove the SI from the harmonic signal of the lower order do. Accordingly, the digital SIC unit 250d includes a plurality of harmonic eliminators.

6 is a diagram showing an m-th harmonic eliminator 250d_2. That is, m-th harmonics remover (250d_2) of Figure 6 corresponds to each of the 3 rd Harmonics Canceller, M th Harmonics Caneller of Fig. In FIG. 6, when m = 1, the harmonic signal means an SI signal of a linear component, which corresponds to a linear SIC eliminator (Linear SI Canceller, 250d_1).

First, the analog SIC 240 samples a received signal (i.e., a self-transmitted interference signal) of the same-band full duplex transceiver 100d whose SI is partially removed in the analog domain,

Figure pat00149
. Then, through the DFT 210
Figure pat00150
Point DFT on the frequency domain received signal < RTI ID = 0.0 >
Figure pat00151
Can be obtained.

Next, the digital SIC unit 250d removes the m-order harmonic signal from the low order by using the m-th harmonic signal canceller of Fig.

6,

Figure pat00152
Means a signal in which all SIs from the first to m-2nd harmonic signals in the frequency domain received signal are removed.

As shown in Fig. 6,

Figure pat00153
Is input to the mth harmonic eliminator 250d_2, the mth harmonic eliminator 250d_2
Figure pat00154
And a matrix obtained from the time-domain transmission signal
Figure pat00155
The first-order estimation value of the channel for the m-th harmonic signal
Figure pat00156
. At this time,
Figure pat00157
The method of Equation (6) or Equation (7) may be used. The mth harmonics eliminator 250d_2 estimates
Figure pat00158
Point IDFT on the sampled time domain channel < RTI ID = 0.0 >
Figure pat00159
. Then, the mth harmonic eliminator 250d_2
Figure pat00160
In order to eliminate the influence of noise in estimating the noise,
Figure pat00161
.

Figure pat00162

In Equation (13)

Figure pat00163
Is a predetermined value.

The mth harmonic eliminator 250d_2

Figure pat00164
Point DFT on the frequency domain second order estimation channel for the m < th > harmonics of SI,
Figure pat00165
. Then, the mth harmonic eliminator 250d_2
Figure pat00166
. By performing the above process from m = 1 to m = M, it is possible to eliminate all SIs for harmonic signals of all orders.

On the other hand, in the description of Figs. 5 and 6

Figure pat00167
The method of Equation (6) or Equation (7) is used as a method of estimating the channel harmonics of the m-order harmonics among the SI components in the frequency domain using the algorithm of FIGS. 5 and 6. However,
Figure pat00168
May be used. In Equation 13,
Figure pat00169
A variety of methods can be used for obtaining the data
Figure pat00170
Other methods of inserting a value of zero into the time domain estimation channel may be used,

While the present invention has been particularly shown and described with reference to exemplary embodiments thereof, it is to be understood that the invention is not limited to the disclosed exemplary embodiments, It belongs to the scope of right.

Claims (1)

antenna,
A distributor for transmitting a transmission signal to the antenna and for transmitting a reception signal received through the antenna to a reception module via a reception output terminal,
Estimating a frequency domain channel for a harmonic component of the magnetic transmission interference signal using a time domain signal of the transmission signal and a frequency domain signal of a self transmission interference signal included in a signal output from the reception output terminal, And a digital SIC (Self-Interference Cancellation) unit for removing the self-transmitted interference signal using the estimated frequency-domain channel
The same - band full duplex transceiver.
KR1020150162809A 2014-11-19 2015-11-19 In-band full duplex transceiver and interference cancealation method thereof KR20160059996A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2020045876A1 (en) * 2018-08-28 2020-03-05 삼성전자 주식회사 Electronic device and method for checking components corresponding to designated frequency band included in transmission signal

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2020045876A1 (en) * 2018-08-28 2020-03-05 삼성전자 주식회사 Electronic device and method for checking components corresponding to designated frequency band included in transmission signal
US11671137B2 (en) 2018-08-28 2023-06-06 Samsung Electronics Co., Ltd. Electronic device and method for identifying components corresponding to designated frequency band included in transmission signal

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