KR20150060455A - Power Supply Apparatus And LED Lighting Apparatus Using the Same - Google Patents

Abstract

A power supply device and an LED lighting device using the same are disclosed. The device facilitates a control of an output voltage and an output current by allowing a common usage for a reference potential of the output voltage and a grounding voltage potential of a driving unit, by connecting a location of an inductor between the grounding potential and an input voltage of the driving unit, and enables a free decision for an output voltage irrelevant of a size of the input voltage, by supplying an inductor current stored in an inductor to a capacitor as an output voltage, by using an equipped diode.

Description

TECHNICAL FIELD [0001] The present invention relates to a power supply apparatus and an LED illumination apparatus using the same,

The present embodiment relates to a power supply apparatus and an LED illumination apparatus using the same.

It should be noted that the following description merely provides background information related to the present embodiment and does not constitute the prior art.

Embodiments of the generic description of the topology of the power supply circuit exist in various forms. Typically, a buck type, a boost type, a buck-boost type, a flyback type, and the like exist.

1A is a circuit diagram showing a power supply device using a general buck method.

The input voltage V _IN of a general buck type power supply may be a direct current (DC) power source, but it may also be used by rectifying an alternating voltage (AC). The main feature of the buck-type power supply is that the output load is located between the inductor (L) and the input voltage (V _IN ). When the switch (SW) is turned on at both ends of the inductor (L), the input voltage (V _IN) voltage minus the output voltage (V _O) from - the two applied (V _IN V _O) inductor current (I _L) is V _IN - V _O voltage is gradually increased by the slope of the inductor capacity value (inductance), and the charge current flows in the output load current and the output capacitor. When the switch is turned off, the diode D is conducted by the flow of the inductor current I _L and the output voltage V _O is applied to the inductor inversely so that the inductor current I _{L changes} the output voltage V _O to the inductor capacity (Inductance), and the output current which is reduced due to the decrease of the inductor current I _L is supplied from the output capacitor C and replenished.

The advantage of a typical buck-based power supply is that the output current and inductor current I _L are applied to the switch SW of the switch SW on interval under conditions that use an input voltage V _IN greater than the output voltage V _O The current flowing to the output load can be kept constant even if a small value of the output capacitor is used.

However, such a power supply of buck method is the input voltage (V _IN) to be larger than the output voltage (V _O) than there is no current in the inductor to flow normally when low output voltage (V _O) of the input voltage (V _IN) I can not. That is, even if the switch SW is turned on during a period when the rectified voltage is lower than the output voltage V _O when the AC voltage is rectified to the input voltage V _IN , the output voltage V _O from the input voltage V _The inductor current I _L can not be increased normally because the voltage (V _O - V _IN ) minus _IN is applied in reverse. Further, the input voltage (V _IN) to the case of using by rectifying the AC voltage even when proportionally the size of the switch (SW) current to the magnitude of the rectified voltage control for the power factor (Power Factor) improvement of the input current input voltage (V _IN) Is smaller than the output voltage (V _O ), the switch (SW) current can not flow normally and a limited period occurs in the power factor improving operation. For the reason described above, in the case of an LED lighting device using a buck-type power supply device, the forward conduction voltage of the LED light emitting portion corresponding to the output voltage (V _O ) can not be increased. As a result, the number of LEDs that can be connected in series in the LED light emitting portion is limited. When the AC voltage is rectified and used as the input voltage (V _IN ), the power factor of the input current can not be obtained beyond a limited level.

1B is a circuit diagram showing a power supply apparatus using a general 'boost mode'.

The input voltage (V _IN ) of the power supply of a general boost type may be a DC power source, but it may also be used by rectifying an AC voltage (AC). The most important feature of the boost type power supply is that the output load is connected in parallel with the switch SW through the diode D and in series with the inductor L by the diode. When the switch SW is turned on, the input voltage V _IN is applied to both ends of the inductor L so that the inductor current I _L gradually increases with the slope of the input voltage V _IN divided by the inductor capacity value (inductance) . The output load current of this section is purely dependent on the output capacitor. When the switch SW is turned off, the diode D is conducted by the flow of the inductor current I _L and a value (V _O - V _IN ) obtained by subtracting the input voltage V _IN from the output voltage V _O The inductor current I _L is gradually reduced to the slope of the V _O - V _IN voltage divided by the inductance value (inductance), and the current charged in the inductor in the switch SW on period is passed through the diode The output capacitor is charged.

An advantage of a general boost type power supply is that it can be applied under the condition of using an output voltage (V _O ) that is larger than the input voltage (V _IN ), and the reference potential of the output voltage (V _O ) Therefore, the output voltage control and the output current control can be easily and accurately implemented.

However, since the inductor current I _L can not flow normally when the output voltage V _O is lower than the input voltage V _IN , the power supply of the boost type has a higher output voltage V _O than the input voltage V _IN Can not be set small. Therefore, when rectifying the AC voltage with the input voltage V _IN and using it, the output voltage V _O is limited to a voltage that is larger than the peak value of the rectified voltage. Output voltage (V _O) output from the input voltage (V _IN) in the lower section switches (SW) is the direction to the input voltage (V _IN), such as when the two ends is the switch (SW) on the off even when the inductor (L) Since the voltage (V _IN - V _O ) obtained by subtracting the voltage (V _O ) is applied, the inductor can not normally transmit the stored energy to the output. Further, the input voltage (V _IN) exchange if used to rectify the voltage, even in proportion to the size of the switch (SW) current to the magnitude of the rectified voltage control for power factor correction of an input current input and the output voltage (V _O) voltage to the ( V _IN ), the normal operation can not be performed. Therefore, a limited period occurs in the power factor improving operation. For the reason described above, in the case of an LED lighting device using a boost power supply device, the forward conduction voltage of the LED light emitting portion corresponding to the output voltage (V _O ) can not be lowered. As a result, there is a problem of limiting the usable output capacitor type to electrolytic capacitors having short life span.

1C is a circuit diagram showing a power supply using a general buck-boost scheme.

The input voltage (V _IN ) of a general buck-boost type power supply may be DC power, but it may also be used by rectifying AC voltage (AC). Typical buck-best feature of the power supply of the boost system is the input voltage (V _IN) and a switch inductor current regardless of the magnitude of the input power source voltage in is only connected in series with the inductor (L) between the (SW) (I _L Can flow. The output voltage V _O is connected in parallel with the inductor through the diode D and the reference potential of the output voltage V _O is not used in common with the ground potential of the driving unit. When the switch SW is turned on, the input voltage V _IN is applied to both ends of the inductor L so that the inductor current I _L gradually increases with the slope of the input voltage V _IN divided by the inductor capacity value (inductance) do.

During the switch (SW) ON period, the output load current flows purely depending on the output capacitor (C). When the switch SW is turned off, the diode D is turned on by the flow of the inductor current I _L and the output voltage V _O is applied to both ends of the inductor _L , voltage (V _O) to be gradually decreased as the slope divided by the inductor capacitance (inductance) was charged to the inductor current from the switch (SW) is on interval is by way of the diode to charge the output capacitor (C).

The advantage of a typical buck-boost power supply is that the output voltage (V _O ) is independent of the input voltage (V _IN ), since no other device is located between the input voltage (V _IN ) and the switch It is possible to set. The inductor current I _L can normally flow even in a section where the rectified voltage is low and a section in which the rectified voltage is high even when the AC voltage is rectified to the input voltage V _IN . Further, when the AC voltage is rectified to be used as the input voltage V _IN for the reasons described above, when the magnitude of the switch current is controlled to be proportional to the magnitude of the rectified voltage, .

However, since the reference voltage of the output voltage (V _O ) is unavailable in common with the ground potential of the driving unit, a direct output voltage sensing and output current can not be controlled by the driving unit in a general buck-boost power supply. There is a problem that it is difficult to control the light emitting current of the LED light emitting portion in the case of an LED lighting device using a general buck-boost type power supply device for the reasons described above.

1D is a circuit diagram showing a flyback type power supply apparatus using a transformer.

FIG. 1D is a view illustrating a configuration of a flyback type power supply apparatus having a transformer most commonly used in an isolation type power supply apparatus. FIG. The power supply apparatus using the buck-boost scheme shown in FIG. 1C has the same structure in principle except that a transformer is used instead of the inductor. The operation principle of the switch on / off section is also the same as that of the buck-boost method. The description of operating the separate switch SW on or off is omitted.

The advantage of a typical flyback power supply is that when the transformer is used, the magnetizing inductance value of the transformer replaces the role of the inductor and the output voltage delivered to the output load is the primary winding P and the secondary winding S1 ). ≪ / RTI > In addition, the power supply voltage of the driving unit can be received using the secondary side winding S2. This separate secondary side winding voltage magnitude and output voltage (V _O ) are determined by the winding ratios of S1 and S2 as shown in Equation (1). When the secondary winding voltage is kept constant, the output voltage (V _O ) of the output load can be controlled constantly.

Here, the 'output voltage delivered to the windings of the S2 V _S2' 'N _S1: the S1 turns "," N _S2:: in S2 turns "," V _S1 output voltage delivered to the windings of the S1', it means.

However, the flyback type power supply requires a bulky transformer, and the output voltage is controlled through a separate secondary winding (Primary Side Regulation), so that an accurate output voltage (V _O ) and an output load There is a problem that current control is not easy.

This embodiment connects the position of the inductor to the ground potential of the driving unit and the input voltage so that the reference potential of the output voltage and the ground potential of the driving unit can be commonly used to facilitate the control of the output voltage and the output current, The present invention provides a power supply device that can supply an inductor current stored in an inductor as an output voltage to a capacitor and freely set an output voltage irrespective of the magnitude of an input voltage using the inductor, and an LED lighting device using the same.

According to an aspect of the present invention, there is provided a plasma display apparatus including: a switch SW receiving an input voltage V _IN and performing switching based on a driving signal applied from a driving unit; An inductor L for performing charge and discharge in accordance with the on or off state of the switch SW; A diode D; And one end of the inductor L and one end of the switch SW and one end of the capacitor C are connected to a common ground, And the other end of the inductor L and the other end of the switch SW are connected to an input power source and one end of the diode D is connected to a contact point of the inductor L and the input power source, And the other end of the diode (D) is connected to the other end of the capacitor (C).

According to another aspect of the present invention, there is provided a plasma display apparatus including: a switch SW receiving an input voltage V _IN and performing switching based on a driving signal applied from a driving unit; An inductor L for performing charge and discharge in accordance with the on or off state of the switch SW; A diode D; A capacitor C for charging / discharging according to whether the diode D conducts; An LED light emitting unit operated by electric power discharged from the capacitor (C); And a current source for determining a light emission current of the LED light emitting unit, wherein one end of the inductor L, one end of the switch SW, one end of the capacitor C, and one end of the current source are grounded to a common ground, The other end of the inductor L and the other end of the switch SW are connected to an input power source and one end of the diode D is connected to a contact point of the inductor L and the input power source, One end of the LED light emitting unit is connected to the contact point of the diode D and the capacitor C and the other end of the LED light emitting unit is connected to the current source And an LED illumination device.

As described above, according to the present embodiment, by connecting the position of the inductor between the ground potential and the input voltage of the driving unit, the reference potential of the output voltage and the ground potential of the driving unit can be commonly used to control the output voltage and the output current And the inductor current stored in the inductor is supplied to the capacitor as an output voltage by using the diode so that the output voltage can be freely set regardless of the magnitude of the input voltage.

Further, according to the present embodiment, it is possible to provide an LED lighting device using a power supply circuit topology. Since the light emitting current of the LED light emitting portion is directly controlled by the light emitting current adjusting portion through the current source whose output current is adjusted, precise control is possible without error. The output voltage control can also easily control the output voltage by sensing the voltage across the current source. Further, it is advantageous to control the brightness of various LED light emitting units.

Further, when the alternating-current voltage is used as the input voltage by full-wave rectification, the power factor of the input current can be controlled close to 1 by improving the power factor so that the input current is controlled to be proportional to the detected voltage by using a separate rectified voltage detection circuit. In addition, since the output voltage is constantly controlled regardless of the instantaneous magnitude of the rectified voltage and the light emission current can be maintained constant, the flicker problem of the AC direct type LED lighting device does not occur. In addition, since the output voltage can be determined regardless of the magnitude of the input voltage, the output voltage can be lowered and the required voltage of the output capacitor (C) can be lowered. Therefore, instead of using the electrolytic capacitor C having a short life time as the output capacitor C, a tantalum capacitor C having the same capacity and a long life can be substituted.

1A to 1D are circuit diagrams showing a general power supply circuit device.
2 is a circuit diagram showing a novel buck-boost type power supply having a non-inverting output voltage according to the present embodiment.
3A and 3B are diagrams illustrating a switch on / off operation of the power supply according to the present embodiment.
FIGS. 4A and 4B are views showing a continuous current mode and a discontinuous current mode in an ON / OFF period of a switch of a power supply device according to the present embodiment.
5 is a diagram showing the main waveforms in the boundary condition of the continuous discontinuous operation mode of the inductor current I _L of the power supply device according to the present embodiment.
FIG. 6A is a circuit diagram of a power supply apparatus including a zero current sensing circuit according to the present embodiment, and FIG. 6B is a waveform diagram of an inductor end waveform for sensing a zero current of the power supply apparatus.
FIG. 7A is a circuit diagram of a power supply apparatus including a driving unit power supply voltage supply circuit according to the present embodiment, and FIG. 7B is a diagram showing an inductor (L) voltage waveform of the power supply apparatus.
8 is a circuit diagram showing a power supply apparatus having a function of improving the backflow using the rectified voltage detection signal according to the present embodiment.
9 is a graph showing an inductor current (I _L ) waveform and an input current waveform when the power factor improving function is applied to the power supply apparatus according to the present embodiment.
10 is a circuit diagram showing a rectified voltage detecting circuit of a power supply apparatus using a power supply circuit topology according to the present embodiment.
11 is a circuit diagram showing an LED illumination device using a power supply circuit topology according to the present embodiment.
12 is a circuit diagram for explaining a TRIAC dimming method of an LED lighting device using a power supply circuit topology according to the present embodiment.
13 is a diagram showing a TRAIC Dimmer output waveform and a current source driving (on / off) signal.
FIG. 14 is a circuit diagram showing analog dimming of an LED lighting device using a power supply circuit topology according to the present embodiment.
15 is a circuit diagram showing a combination of a plurality of parallel LED light emitting sub-current sources using the power supply circuit topology according to the present embodiment, and an LED lighting device having a light emitting current regulator and a minimum value determiner.

Hereinafter, the present embodiment will be described in detail with reference to the accompanying drawings.

Hereinafter, among the elements described in this embodiment, the capacitor means a charge / discharge element, the diode means a rectifier element, and the resistor can be interpreted as a concept collectively referred to as a resistance element.

2 is a circuit diagram showing a novel buck-boost type power supply having a non-inverting output voltage according to the present embodiment.

The power supply 200 according to the present embodiment includes a switch SW, a driving unit 210, an inductor L, a diode D and a capacitor C. The components included in the power supply 200 are not necessarily limited thereto.

The switch SW receives the input voltage V _IN . In addition, the switch SW performs switching based on the driving signal applied from the driving unit 210. The driving unit 210 generates a driving signal. The inductor L performs charging and discharging in accordance with the ON or OFF state of the switch SW. The capacitor C performs charging and discharging according to whether the diode D conducts.

One end of the inductor L, one end of the switch SW, and one end of the capacitor C are grounded to a common ground. The other end of the inductor L and the other end of the switch SW are connected to the input power source. One end of the diode D is connected to the contact of the inductor L and the input power source. The other end of the diode D is connected to the other end of the capacitor C.

Hereinafter, the power supply apparatus 200 of FIG. 2 will be further described.

The power supply apparatus 200 according to the present embodiment connects the inductor L between the ground potential of the driving unit and the low potential terminal (- terminal) of the input voltage V _IN and outputs the output voltage V _O ) is connected in parallel with the inductor (L). The reference potential of the output voltage V _O can be used in common with the ground potential of the driving unit by the above-described configuration, so that it is possible to easily and accurately control the output voltage V _O and the output current I _OUT . The output voltage V _o can be freely set regardless of the magnitude of the input voltage V _IN since the current stored in the inductor L is supplied to the output capacitor C in the same manner as the general buck-boost mode. In other words, the inductor current I _L can not flow normally under the condition that the input voltage V _IN of the buck type power supply device is lower than the output voltage V _O by the same number of basic elements as compared with the conventional method And the output voltage and output current (I _OUT ) can not be controlled because the use of the low output voltage in the power supply of the boost type and the reference potential of the output voltage of the conventional general buck- It is possible to solve the disadvantages which are difficult to be solved at the same time. In addition, there is an advantage that the output voltage (V _O ) and the output current (I _OUT ) can be controlled more easily and accurately without using a flyback having a large volume and a high price, as in a flyback power supply.

3A and 3B are diagrams illustrating a switch on / off operation of the power supply according to the present embodiment.

3A, when the switch SW is turned on based on the drive signal, the inductor current I _L flowing in the inductor _L is increased by the input voltage V _IN , L is charged with the inductor current I _L. When the switch SW is turned on, the input voltage V _IN is applied between both ends of the inductor L. [ The inductor current I _L is gradually increased to a slope obtained by dividing the input voltage V _IN by the inductor capacity value and the voltage obtained by adding the output voltage V _O and the input voltage V _IN to the diode D The diode D is turned off.

3B, when the switch SW is turned OFF based on the drive signal, the inductor current I _L is supplied to the output voltage V _O to charge the capacitor C. When the switch SW is turned off, the diode D is conducted by the flow of the inductor current I _L. Therefore, the inductor opposite to the output voltage (V _O) is the applied to the inductor current (I _L), the output voltage (V _O), the inductor capacitance (inductance) at the time (L), the switch (SW) operated on the And is charged into the capacitor C via the diode D while gradually decreasing at a divisional slope.

FIGS. 4A and 4B are views showing a continuous current mode and a discontinuous current mode in an ON / OFF period of a switch of a power supply device according to the present embodiment.

4A, there is an operation mode (continuous current mode) in which the inductor current I _L maintains a value of '0' or more during the entire switching period T _S. Also, there is an operating mode (Discontinuous Current Mode) in which the inductor current I _L does not flow during a part of the switch-off period, as shown in Fig. 4B. In addition, as shown in FIG. 5, it can be classified into an operation method (Boundary Condition Mode) for maintaining the boundary conditions of the two operation methods of FIGS. 4A and 4B.

Than "0" while the output current (I _OUT) is larger or the switching cycle the inductor capacitance (inductance), if necessary, a large value (T _S), the shorter the cycle switching of the total inductor current (I _L) (T _S) And continuously flows in a large value. In this case, it is a continuous current mode to increase the average value of the inductor current (I _L) peak (Peak) the paper even if the height of the inductor current value (I _L) as shown in Figure 4a advantageously.

4B, when a large value of the output current I _OUT is not required, a period in which the inductor current I _L is maintained in a state where the inductor current I _L falls from '0' A discontinuous current mode may be advantageous to prevent power dissipation consumed in reverse recovery that may occur when diode D is turned off with forward diode current D flowing.

The two operating conditions (FIGS. 4A and 4B) have advantages and disadvantages, and it is generally desirable to operate under the boundary conditions of two operating conditions.

4A, when the inductor current I _L is continuously supplied with a current larger than '0' during the entire switching period, a reverse recovery current is generated at the instant when the diode D is turned on and off Flows. In such a case, a large reverse current flows in a state where the combined voltage of the input voltage V _IN and the output voltage V _O is applied to the diode D during the reverse recovery time, thereby causing a power loss, which is not preferable .

4 (b), when the inductor current I _L falls to '0' during a part of the switch SW off interval, the inductor current I _L is increased for the same output current I _OUT , The conduction loss of the conductor due to the increase of the inductor current (I _L ) can be further increased since the peak value must be large. Therefore, in general, it is preferable to drive the switch SW at the boundary between the above two operating conditions as shown in Fig. 5 which will be described later.

5 is of the continuous voltage across the discontinuous operation mode boundary condition diagram (Fig. 4 and the inductor (L) shows the waveform of the key in the (V _L) of the inductor current (I _L) of the power supply according to this embodiment The polarity is changed and displayed).

As shown in FIG. 5, the inductor current I _L is decreased to '0' during a period in which the switch SW is off. The forward current of the diode D becomes '0' when the switch SW is turned on immediately after the inductor current I _L becomes '0'. Accordingly, it is possible to prevent the power loss consumed in the reverse recovery of the diode D before the transition of the diode D from the ON state to the OFF state, and to prevent the loss of the inductor current (I _L ) To reduce the peak current of the inductor current with respect to the same output current (I _OUT ), thereby reducing the conduction loss of the conductor. The detection signal for the point where the inductor current (I _L) drops to zero in order to operate in the boundary condition of constant current mode and discontinuous current mode of the inductor current (I _L) is required.

FIG. 6A is a circuit diagram of a power supply apparatus including a zero current sensing circuit according to the present embodiment, and FIG. 6B is a waveform diagram of an inductor end waveform for sensing a zero current of the power supply apparatus.

The power supply 600 includes a switch SW, a driving unit 210, an inductor L, a diode D, a capacitor C, a Zero Current Detection Circuit 620, . The components included in the power supply 600 are not limited thereto.

The connection relationship between the switch SW, the inductor L, the diode D and the capacitor C is the same as in Fig. 2, and thus description thereof is omitted.

One end of the zero current sensing circuit 620 is connected to the input power source and the contact point of the inductor L and the other end of the zero current sensing circuit 620 is connected to the driving unit 210.

The zero current sensing circuit 620 may include a first resistor R ₁ , a second resistor R ₂ , and a first diode D ₁ . The first resistor (R ₁ ) and the second resistor (R ₂ ) are connected in series with the diode (D). One end of the first diode D ₁ is connected to the contact point of the first resistor R ₁ and the second resistor R ₂ and the other end of the first diode D ₁ is connected to the second resistor R 2 and the common ground Respectively. The driving unit 210 uses the output of the contact point of the first resistor R ₁ and the second resistor R ₂ as a zero current detection signal.

The zero current detection circuit 620 outputs the voltage V _L applied to the inductor L as the sense voltage V ₁ by the resistance distribution of the first resistor R ₁ and the second resistor R ₂ , The detection voltage V ₁ is input to the driving unit 210 as a zero current sensing signal and the driving unit 210 determines the on time of the switch SW.

Hereinafter, the power supply apparatus 600 of FIG. 6A will be further described.

In the case of a power supply device using a new buck-boost type power supply circuit topology having a non-inverted output voltage according to this embodiment, as shown in FIG. 6A, the first resistor R ₁ and the second resistor R ₂ It is possible to detect a point where the inductor current I _L drops to '0' by detecting the moment when the voltage V _L across both ends of the inductor L falls to '0'.

When the inductor current I _L falls to '0', the current flowing through the diode D drops to '0', so that the current flowing to the diode D becomes '0' and the voltage V _L across the inductor _L Becomes " 0 " at the output voltage (V _O ). Since the voltage applied to the inductor L is the voltage obtained through the resistance distribution, the sensing voltage V ₁ falls to '0' as the voltage across the inductor L is V _L. The driving unit 210 may input the driving current to the driving unit 210 using the zero current sensing signal to determine the on time of the switch SW. The first rectifying diode D ₁ between the ground potential and the sensing voltage V ₁ is connected to the zero current sensing voltage input side which may occur when the voltage of the sensing voltage V ₁ terminal drops to a value of ' In order to prevent malfunction of the motor.

FIG. 7A is a circuit diagram of a power supply apparatus including a driving unit power supply voltage supply circuit according to the present embodiment, and FIG. 7B is a diagram showing an inductor (L) voltage waveform of the power supply apparatus.

The power supply 700 according to the present embodiment includes a switch SW, a driver 210, an inductor L, a diode D, a capacitor C, and a driver power supply voltage supply circuit 720. The components included in the power supply 700 are not necessarily limited thereto.

The connection relationship between the switch SW, the driver 210, the inductor L, the diode D and the capacitor C is the same as in Fig.

One end of the driving unit power supply voltage supply circuit 720 is connected to the contact point of the input power supply and the inductor L and the other end of the driving power supply voltage supply circuit 720 is connected to the driving unit 210.

The driver power supply voltage supply circuit 720 includes a first capacitor C ₁ , a first diode D ₁ and a second capacitor C ₂ . The first capacitor C ₁ is connected in series with the diode D. The first diode D ₁ is connected in series with the first capacitor C ₁ . One end of the second capacitor C ₂ is connected to the other end of the first diode D ₁ and the other end of the second capacitor C ₂ is grounded to a common ground.

The driving unit power supply voltage supply circuit 720 inputs the output from the contact point of the first diode D ₁ and the second capacitor C ₂ to the driving unit 210 with the power supply voltage. The driving unit power supply voltage supply circuit 720 may separately supply the driving voltage to the driving unit 210 while the driving unit 210 performs switching using the pulse-shaped output voltage V _O charged in the inductor L, And supplies the power supply voltage to the driving unit 210. The power supply voltage supply circuit 720 transfers the pulse-like output voltage V _O charged in the inductor L to the second capacitor C ₂ using the first diode D ₁ .

Hereinafter, the power supply 700 of FIG. 7A will be further described.

Generally, the power supply unit requires a power supply voltage for operating the driving unit. And supplies a power supply voltage necessary for starting the driving unit operation through a resistor having a reasonably large value at the input voltage V _IN . If the power supply voltage supplying method is continuously used even while the driving unit 210 is being operated, continuous power loss occurs when the input voltage is large.

In the case of the power supply apparatus using a new buck-boost type power supply circuit topology having a non-inverted output voltage according to the present embodiment, as shown in FIG. 7A, The power source voltage of the driving unit can be separately supplied while the driving unit 210 is performing the switching operation by using the pulse-like output voltage V _O. The driving unit power supply voltage supply circuit 720 according to the present embodiment supplies the pulse-like output voltage V _O charged in the inductor L to the power supply voltage capacitor C ₂ via the resistor and the first rectifying diode D ₁ ). However, when using a resistor, it is preferable to transfer the voltage to the power supply voltage capacitor C ₂ via the first capacitor C ₁ and the first rectifying diode D ₁ in consideration of the loss occurring in the resistor.

8 is a circuit diagram showing a power supply apparatus having a function of improving the backflow using the rectified voltage detection signal according to the present embodiment.

The power supply device 800 according to the present embodiment includes a switch SW, an inductor L, a diode D, a capacitor C, a rectifying part 810, and a driving part 820. The components included in the power supply device 800 are not limited thereto.

The connection relationship between the switch SW, the inductor L, the diode D and the capacitor C is the same as in Fig. 2, and thus description thereof is omitted.

The rectifying unit 810 is connected to the output of the AC voltage AC, rectifies the AC current to a DC current, and supplies the DC current to the input voltage V _IN . One end of the input end of the rectifying part 810 is connected to one end of the AC voltage AC and the other end of the rectifying part 810 is connected to the other end of the AC voltage AC. One end of the output end of the rectifying part 810 is connected to one end of the switch SW and the other end of the rectifying part 810 is connected to one end of the inductor L.

The driving unit 820 is connected to one end of the output terminal of the rectifying unit 810 and the contact point of the inductor L and is connected to one end of the output load and the other end of the switch SW. The driving unit 820 includes a rectified voltage detection circuit 830. The rectified voltage detecting circuit 830 receives the input voltage V _IN from one side of the output end of the rectifying unit 810 and delivers the output to the switch SW.

The driving unit 820 generates a driving signal by using the rectified voltage detection signal output from the rectified voltage detection circuit 830. [ The driving unit 820 controls the ON period of the switch such that the switch current I _s flowing when the switch SW is turned on is proportional to the rectified voltage so that the input current has a predetermined power factor.

Hereinafter, the power supply apparatus 800 of FIG. 8 will be further described.

As shown in FIG. 8, in the case of the power supply device, when rectified and rectified AC voltage is used as an input voltage, a rectified voltage detection circuit 830 may be added to detect a rectified voltage. The power supply device 800 controls the switch SW using the rectified voltage detection circuit 830. When the switch current flowing in the ON period of the switch SW is proportional to the rectified voltage detected by the rectification part 810 The input current can be controlled to have a power factor close to 1 as shown in FIG.

9 is a graph showing an inductor current (I _L ) waveform and an input current waveform when the power factor improving function is applied to the power supply apparatus according to the present embodiment.

In general, the ratio of the current flowing to the switch SW to the rectified voltage detection signal is determined by the output current I _OUT of the output load, which is the same as the component of the driver 820 shown in FIG. 8, Is multiplied by the output signal of the error amplifier (Error AMP) used for controlling the output voltage, and the corresponding value is set to a reference value (IREF) of the current of the switch SW on period.

10 is a circuit diagram showing a rectified voltage detecting circuit of a power supply apparatus using a power supply circuit topology according to the present embodiment.

The rectified voltage detection circuit 830 includes a first diode D ₁ , a second diode D ₂ , a first resistor R ₁ , a second resistor R ₂ and a first capacitor C ₁ .

8 is a circuit diagram for the rectified voltage detecting circuit 830 in Fig. 8, and therefore the description of the switch SW, the inductor L, the diode D, the rectifying section 810, and the capacitor C shown in Fig. Is omitted.

One end of the first diode D ₁ is connected to one end of the input end of the rectifying unit 810. One end of the second diode D ₂ is connected to the other end of the input end of the rectifying unit 810. The other end of the first diode D _{1 is} connected to the other end of the second diode D ₂ . The first end of the resistor (R ₁₎ is connected to the contacts of the other end of the first diode (D ₁₎ and the other end of the second diode (D _2), the other end of the first resistor (R ₁₎ has a second resistance (R ₂ ). One end of the inductor L is connected to one side of the output end of the rectifying unit 810. And the other end of the inductor L is connected to the other end of the second resistor R ₂ . The first capacitor C ₁ is connected in parallel with the second resistor R ₂ . The other end of the second resistor (R ₂ ) and the other end of the inductor (L) are grounded to a common ground. The rectified voltage detection circuit 830 uses the output of the contacts of the first resistor R ₁ and the second resistor R ₂ as a rectified voltage detection signal.

Hereinafter, the rectified voltage detecting circuit 830 of FIG. 10 will be further described.

In the case of the power supply apparatus according to the present embodiment, the rectified voltage can be detected using the rectified voltage detection circuit 830 configured as shown in FIG. The rectified voltage detecting circuit 830 according to the present embodiment includes a first rectifying diode D ₁ and a second rectifying diode D ₂ and a first resistor R ₁ and a second resistor R ₂ And may further include additional elements.

11 is a circuit diagram showing an LED illumination device using a power supply circuit topology according to the present embodiment.

The LED illumination device 1100 according to the present embodiment includes a switch SW, an inductor L, a diode D, a capacitor C, an LED light emitting portion 1110, a current source 1120, and a driver 130 do. The components included in the power supply 1110 are not limited thereto.

The connection relationship between the switch SW, the inductor L, the diode D and the capacitor C is the same as in Fig. 2, and thus description thereof is omitted.

The LED light emitting portion 1110 includes one or more LEDs connected in series or in parallel. The LED emission section 1110 operates with the electric power discharged from the capacitor C. The current source 1120 is connected in series to the LED light emitting portion 1110. The current source 1120 determines the light emission current of the LED light emitting portion 1110.

The driving unit 1130 receives the output voltage from the current source 1120 and generates a driving signal for controlling the switching of the switch SW. The driving unit 1130 includes an output voltage control unit 1132 and a light emission current control unit 1134. One end of the output voltage control unit 1132 is connected to the contact point of the LED light emitting unit 1110 and the current source 1120. The other end of the output voltage controller 1132 is connected to the input terminal of the switch SW to generate a driving signal. The light emission current regulator 1134 controls the current of the current source 1120. [

Hereinafter, the connection relationship of elements included in the LED illumination device 1100 will be described. One end of the inductor L, one end of the switch SW, one end of the capacitor C, and one end of the current source are grounded to the common ground. The other end of the inductor L and the other end of the switch SW are connected to the input power source. One end of the diode D is connected to the contact point of the inductor L and the input power source and the other end of the diode D is connected to the other end of the capacitor C. One end of the LED light emitting portion 1110 is connected to the contact point of the diode D and the capacitor C and the other end of the LED light emitting portion 1110 is connected to the current source 1120.

Hereinafter, the LED illumination device 1100 of Fig. 11 will be further described.

The LED illumination device 1100 according to the present embodiment can commonly use the reference potential of the output voltage and the ground potential of the driver 1130. [ 11, an LED light emitting unit 1110 is used as an output load.

The current source 1120 and the current source 1120 are connected in series to the LED light emitting portion 1110 and between the LED light emitting portion 1110 and the reference potential of the output voltage to determine the light emitting current of the LED light emitting portion 1110, And a light emitting current control unit 1130 for controlling the light emitting device 1100. [

In the case of the LED illumination device 1100 according to the present embodiment, the light emission current of the LED light emitting portion 1110 is directly controlled by the current source 1120 whose output current I _OUT is adjusted by the light emission current adjustment portion 1134 . As a result, it is possible to accurately control without any error, and the output voltage control for securing the forward conduction voltage of the LED light emitting portion 1110 can also be controlled by sensing a voltage applied to one end of the current source 1120.

In the case of the LED illumination device 1100 according to the present embodiment, when the alternating-current voltage AC is subjected to full-wave rectification and used as an input voltage, the power factor of the input current is improved to 1 by improving the power factor using the rectified voltage detection circuit 830 Can be closely controlled. In addition, the output voltage can be controlled constantly regardless of the instantaneous magnitude of the rectified voltage, and the emission current can also be kept constant. Further, the problem of flicker of the AC direct type LED illumination device 1100 does not occur.

In the case of the LED illumination device 1100 according to the present embodiment, the output voltage can be determined regardless of the magnitude of the input voltage. The output voltage can be lowered and the required voltage of the output capacitor C can be lowered. Therefore, instead of using the electrolytic capacitor C having a short life span as the output capacitor C, it is possible to replace the electrolytic capacitor C having a short life span by a tantalum capacitor C having a long life and the same capacity. The LED lighting device 1100 using the new buck-boost type power supply circuit topology having the non-inverted output voltage according to the present embodiment can have many advantages that the conventional LED lighting device can not have.

12 is a circuit diagram for explaining a TRIAC dimming method of an LED lighting device using a power supply circuit topology according to the present embodiment.

The power supply 1200 according to the present embodiment includes a switch SW, an inductor L, a diode D, a capacitor C, a rectifier 1210, a TRIAC dimmer 1220, A light emitting portion 1230, a current source 1240, and a driver 1250. The components included in the power supply 1200 are not limited thereto.

The connection relationship between the switch SW, the inductor L, the diode D and the capacitor C is the same as in Fig. 2, and thus description thereof is omitted.

The rectifying unit 1210 is connected to the output of the AC voltage AC to rectify the AC current to a DC current and to supply the DC current to the input voltage V _IN . One end of the input end of the rectifying part 1210 is connected to one end of the AC voltage AC and the other end of the rectifying part 1210 is connected to the other end of the AC voltage AC. One end of the output end of the rectifying part 1210 is connected to one end of the switch SW and the other end of the rectifying part 1210 is connected to one end of the inductor L.

The triac brightness controller 1220 is connected to the output of the ac voltage AC. The rectifying unit 1210 is connected to the triac brightness controller 1220, rectifies the alternating current to a direct current, and supplies the direct current to the input voltage V _IN . The other end of the rectifying part 1210 is connected to the other end of the AC voltage AC. One end of the output end of the rectifying part 1210 is connected to the current input end of the switch SW and the other end of the output end of the rectifying part 1210 is grounded to the common ground.

The LED light emitting unit 1230 operates with the electric power discharged from the capacitor C. The current source 1240 is connected in series to the LED light emitting portion 1230 and determines the light emitting current of the LED light emitting portion 1230.

The driving unit 1250 includes an output voltage control unit 1252, a summing unit 1254, and a light emission current control unit 1256. One end of the output voltage control unit 1252 is connected to the contact point of the LED light emitting unit 1230 and the current source 1240. The other end of the output voltage controller 1252 is connected to the input terminal of the switch SW to generate a driving signal. The light emission current regulator 1256 controls the current of the current source 1240. One end of the summing unit 1254 is connected to one end of the input end of the rectifying unit 1210. The other end of the summing unit 1254 is connected to the light emitting current regulating unit 1256. The summing unit 1254 generates a summation signal by summing the period detection signal and the period interval compensation signal when the triac brightness controller 1220 is turned on. The light emission current controller 1256 operates the current source 1240 only when the sum signal exists and stops the operation of the current source 1240 during the remaining period.

Hereinafter, the connection relationship of the elements included in the LED illumination apparatus 1200 will be described. One end of the inductor L, one end of the switch SW, one end of the capacitor C, and one end of the current source are grounded to the common ground. The other end of the inductor L and the other end of the switch SW are connected to the input power source. One end of the diode D is connected to the contact point of the inductor L and the input power source and the other end of the diode D is connected to the other end of the capacitor C. One end of the LED light emitting portion 1210 is connected to the contact point of the diode D and the capacitor C and the other end of the LED light emitting portion 1210 is connected to the current source 1120.

Hereinafter, the LED illumination device 1200 of FIG. 12 will be further described.

12, when the AC voltage AC is rectified by the full wave rectification in the LED lighting apparatus 1200 according to the present embodiment, as shown in FIG. 12, when the triac brightness controller 1220 is turned on, And a periodic interval compensation signal for the interval between the respective periods of the rectified voltage. The brightness of the LED light using the triac brightness controller 1220 is controlled in such a manner that the current source 1240 is operated in the light emission current control unit 1256 only when the sum signal exists and the operation of the current source 1240 is stopped during the remaining period. Control (TRIAC Dimming) is possible.

Specifically, the voltage waveform corresponding to a part of the input AC voltage waveform output to the triac brightness controller 1220 is compared with a predetermined constant reference voltage with respect to the rectified voltage subjected to full wave rectification, and the triac brightness controller 1220 is turned on It is possible to generate an interval detection signal. In addition, a periodic interval compensation signal, which is maintained for a predetermined period at the time when the interval detection signal disappears, may be generated to generate a period interval compensation signal for intervals between the respective periods of the rectified voltage.

The summing unit 1254 performs an OR operation on the period interval compensation signals for the period intervals of the period detection signal and the rectified voltage when the above-described triac brightness controller 1220 is operated on to generate a sum signal . When the triac brightness controller 1220 is turned on for the entire period of the rectified voltage or when the triac brightness controller 1220 is not used, It is possible to compensate for a missing portion detection signal when the brightness controller 1220 is turned on.

Of course, when the reference voltage, which is compared with the output voltage of the triac brightness controller 1220 used in the process of generating the interval sensing signal when the triac brightness controller 1220 is turned on, is made close to '0' Each periodic interval compensation signal of the rectified voltage may not be needed. However, in consideration of a reference voltage to be realized as a feasible circuit, a periodic interval compensation signal is generated and a signal obtained by performing a logical sum operation on the period interval compensation signal with the period detection signal when the triac brightness controller 1220 is turned on, It is preferable that the current source 1240 is operated. The circuit for obtaining the section detection signal when the triac brightness controller 1220 is operated on may use the rectified voltage detection circuit 830 shown in Fig. 10 described above.

13 is a diagram showing a TRAIC Dimmer output waveform and a current source driving (on / off) signal.

The LED lighting device 1200 using a new buck-boost type power supply circuit topology having a non-inverted output voltage according to the present embodiment is configured such that the period when the triac brightness controller 1220 operates on, The TRIG brightness controller 1220 controls the dimming (Dimming) by the TRIG brightness controller 1220 in such a manner that the OR gates of the sensing signal and the periodic interval compensation signal for the rectified voltage period interval are sensed by the light emission current regulator 1256 and the current source 1240 is turned on or off. ) Is possible.

However, in the conventional LED lighting device 1200, the current source 1240 can not be placed between the LED light emitting portion 1230 and the reference potential of the output voltage at the output terminal. Therefore, it is necessary to use a method of stopping the operation of the switch SW in a section where there is no output of the triac brightness controller 1220 simply. Even if the operation of the switch SW is stopped, accurate LED dimming control can not be performed because the LED light emitting unit 1230 is continuously turned on until the charge stored in the output capacitor C is sufficiently discharged.

14 is a circuit diagram showing analog dimming of an LED illumination device using a power supply circuit topology according to the present embodiment.

The light emitting current regulator 1256 includes a first resistor R ₁ , a photocoupler, a current mirror, and a second resistor R ₂ .

One end of the first resistor R ₁ is connected to _one end of the analog voltage generator. The other end of the first resistor R ₁ is connected to _one end of the photocoupler. The other end of the photocoupler is connected to one end of the current mirror. And the other end of the current mirror is connected to one end of the second resistor R ₂ . The other end of the second resistor R ₂ is grounded to a common ground.

The current source 1240 includes an operational amplifier AMP, a switching element Q ₁ , and a third resistor R ₃ . The + input of the OP amp (AMP) is connected to the contact of the current mirror and the second resistor (R ₂ ). The switching element Q ₁ includes an input terminal, a current input terminal, and a current lead terminal. The input terminal is connected to the output terminal of the operational amplifier AMP. The current input terminal is connected to the LED light emitting portion 1230. Is connected to the third resistor (R ₃ ). The - input terminal of the operational amplifier AMP is connected to the contact point of the switching element Q ₁ and the third resistor R ₃ .

The analog dimming will be described below. The LED lighting device 1200 using a new buck-boost type power supply circuit topology having a non-inverting output voltage can control the output current I _OUT from the light emission current control part 1256 to control the light emission current of the LED light emission part 1230, A current source 1240 is used. Analog dimming is possible in such a manner that the output current I _{OUT of the} current source 1240 is adjusted through the light emission current regulator 1256 in proportion to (or in inverse proportion to) the analog voltage signal generated from the separate dimming device. It is preferable to use an insulated signal transfer device (for example, a photocoupler) or the like as shown in Fig. 14 because the reference of the input analog voltage signal may be different from the ground potential of the driver 1250. [ The light emitting current regulating unit 1256 and the current source 1240 shown in FIG. 14 are only one embodiment of the light emitting current regulating unit 1256 and the current source 1240 for analog dimming.

The PWM dimming will be described below. The LED lighting device 1200 using a new buck-boost type power supply circuit topology having a non-inverting output voltage receives the PWM input signal and adjusts the light emission current of the LED light emitting portion 1230 only in a period in which the signal is high The brightness of the LED light emitting unit 1230 can be controlled because the current source 1240 is turned on (or vice versa). The configuration for brightness control of the LED light emitting unit 1230 using the PWM input signal may be realized by performing a logical sum operation on the period detection signal and the period interval compensation signal when the triac brightness controller 1220 is turned on in the triac dimming configuration The input PWM signal can be directly used as an on / off drive signal of the current source 1240 instead of being used as the on / off drive signal of the current source 1240.

15 is a circuit diagram showing a combination of a plurality of parallel LED light emitting units 1510 and current sources 1520 using a power supply circuit topology according to the present embodiment, and an LED lighting apparatus having a light emitting current controlling unit and a minimum value determining unit.

The LED illumination device 1500 according to the present embodiment includes a switch SW, an inductor L, a diode D, a capacitor C, an LED light emitting portion 1510, a current source 1520, and a driver 1530 do. The components included in the LED illumination device 1500 are not limited thereto.

The connection relationship between the switch SW, the inductor L, the diode D and the capacitor C in the LED lighting apparatus 1500 is the same as that in Fig.

The LED light emitting portion 1510 includes a plurality of light emitting diode arrays 1512, 1514, and 1546. The current sources 1520 are connected in series for each of the light emitting diode arrays 1512, 1514 and 1546.

The driving unit 1530 includes an output voltage control unit 1534, a minimum value determination unit 1536, and a light emission current control unit 1538. The light emitting current regulator 1538 controls the current of the current source 1520. One end of the minimum value determining unit 1536 is connected to the contact point of the LED light emitting unit 1510 and the current source 1520. The other end of the minimum value determination unit 1536 is connected to one end of the output voltage control unit 1534. The minimum value determining unit 1536 determines the minimum value of the voltages of the current sources 1520 so that the output voltage V _O charged in the inductor L becomes equal to or greater than the forward conduction voltages of the light emitting diode arrays 1512, 1514, And is input to the output voltage controller 1534 for controlling the output voltage V _o . The output voltage control unit 1534 receives the minimum of the voltages (for example, V ₁ to V _N ) of the current source 1520 from the minimum value determination unit 1536 and controls the switching of the switch SW based on the received minimum value Lt; / RTI >

Hereinafter, the connection relationship of elements included in the LED illumination device 1500 will be described. One end of the inductor L, one end of the switch SW, one end of the capacitor C, and one end of the current source are grounded to the common ground. The other end of the inductor L and the other end of the switch SW are connected to the input power source. One end of the diode D is connected to the contact point of the inductor L and the input power source and the other end of the diode D is connected to the other end of the capacitor C. One end of the LED light emitting portion 1510 is connected to the contact point of the diode D and the capacitor C and the other end of the LED light emitting portion 1510 is connected to the current source 1520.

Hereinafter, the LED illumination device 1500 of FIG. 15 will be further described.

As shown in FIG. 15, the LED lighting device 1500 using a new buck-boost type power supply circuit topology having a non-inverted output voltage is connected to the LED light emitting portion 1510 and each LED light emitting portion 1510 in series A plurality of current sources 1520 controlled by the light emission current controller 1538 may be provided. The combination of the respective LED light emitting units 1510 and 1520 may be connected in parallel so that the output voltage may be greater than the forward conduction voltage of all the LED light emitting units 1510. [ A minimum value determiner (Loser Takes All) may be provided so that the lowest value among the voltages applied to one end of the plurality of current sources 1520 connected in parallel is transmitted to the input of the output voltage controller 1534 for controlling the output voltage. When a minimum value determining unit is provided, the present invention can be applied to an LED lighting device 1500 having an LED light emitting unit 1510 in which a plurality of light emitting currents are controlled.

15, the color of each LED light emitting portion 1510 may be different from each other (for example, three primary colors red, green, and blue) It is possible to illuminate LEDs of various colors according to the ratio of the light emission current flowing in the LED 1510. In this case, the number of LEDs connected in series for each color may be different in consideration of the different forward conduction voltages of the LED light emitting units 1510 having different colors, so that the forward conduction voltages may be substantially the same.

The foregoing description is merely illustrative of the technical idea of the present embodiment, and various modifications and changes may be made to those skilled in the art without departing from the essential characteristics of the embodiments. Therefore, the present embodiments are to be construed as illustrative rather than restrictive, and the scope of the technical idea of the present embodiment is not limited by these embodiments. The scope of protection of the present embodiment should be construed according to the following claims, and all technical ideas within the scope of equivalents thereof should be construed as being included in the scope of the present invention.

210, 820, and 1130:
620: Zero current sensing circuit
720: Driver power supply voltage supply circuit
830: Current voltage detection circuit
1110, 1230, 1510:
1120, 1240, 1520: current source
1132, 1252. 1534: Output voltage control section
1134, 1256, and 1534:
1210:
1220: Triac brightness controller
1254:
1536:

Claims (23)

A switch SW receiving the input voltage V _IN and performing switching based on the driving signal applied from the driving unit;
An inductor L for performing charge and discharge in accordance with the on or off state of the switch SW;
A diode D; And
And a capacitor (C) performing charging / discharging according to whether the diode (D) is conductive,
One end of the inductor L, one end of the switch SW and one end of the capacitor C are grounded to a common ground. The other end of the inductor L and the other end of the switch SW are connected to an input power source Wherein one end of the diode D is connected to the contact point of the inductor L and the input power source and the other end of the diode D is connected to the other end of the capacitor C. [ . The method according to claim 1,
In, while the inductor current (I _L) flowing through the inductor (L) by the input voltage (V _IN) is increased, the inductor (L) when operating with the switch (SW) on the basis of the driving signal The inductor current I _L is charged,
Wherein the inductor current (I _L ) is supplied to the output voltage (V _O ) to charge the capacitor (C) when the switch (SW) is turned off based on the drive signal . 3. The method of claim 2,
When the switch SW is turned on,
The input voltage V _IN is applied between both ends of the inductor L so that the inductor current I _L gradually increases to a slope obtained by dividing the input voltage V _IN by an inductor capacity value And the diode (D) is turned off because the sum of the output voltage (V _O ) and the input voltage (V _IN ) is applied to the diode (D) in the reverse direction. 3. The method of claim 2,
When the switch SW is turned off, the diode D is conducted by the flow of the inductor current I _L and the reverse direction when the switch SW operates on the inductor L in the capacitor to the output voltage (V _O) it is applied via the diode (D) and gradually decreases in a slope of the inductor current (I _L) divided by the output voltage (V _O) to the inductor capacitance (inductance) (C). ≪ / RTI > The method according to claim 1,
Further comprising a zero current sensing circuit including a first resistor (R ₁ ), a second resistor (R ₂ ) and a first diode (D ₁ )
The first resistor R ₁ and the second resistor R ₂ are connected in series with the diode D,
One end of the first diode D ₁ is connected to the contact point of the first resistor R ₁ and the second resistor R ₂ and the other end of the first diode D ₁ is connected to the second resistor R ₁ , R ₂ ) and is grounded to a common ground,
Wherein the driving unit uses the output of the contact point of the first resistor (R ₁ ) and the second resistor (R ₂ ) as a zero current detection signal. 6. The method of claim 5,
Wherein the zero current sensing circuit comprises:
A voltage V _L applied to the inductor L is output as a sense voltage V ₁ by resistance distribution of the first resistor R ₁ and the second resistor R ₂ , V ₁ ) is input to the driving unit as the zero current sensing signal, and the driving unit determines the on-time of the switch SW. The method according to claim 1,
Further comprising a driver power supply voltage supply circuit including a first capacitor (C ₁ ), a first diode (D ₁ ) and a second capacitor (C ₂ )
The first capacitor C ₁ is connected in series with the diode D and the first diode D ₁ is connected in series with the first capacitor C ₁ and the second capacitor C ₂ ) Is connected to the other end of the first diode (D ₁ ), the other end of the second capacitor (C ₂ ) is grounded to a common ground,
Wherein the driving unit power supply voltage supply circuit inputs the output from the contact point of the first diode (D ₁ ) and the second capacitor (C ₂ ) to the driving unit with a power supply voltage. The method according to claim 1,
Further comprising a driver power supply voltage supply circuit including a first resistor (R ₁ ), a first diode (D ₁ ) and a second resistor (R ₂ )
Wherein the first resistor R ₁ is connected in series with the diode D and the first diode D ₁ is connected in series with the first resistor R ₁ and the second resistor R ₂ ) Is connected to the other end of the first diode (D ₁ ), the other end of the second resistor (R ₂ ) is grounded to the common ground,
Wherein the drive unit power supply voltage supply circuit inputs the output from the contact point of the first diode (D ₁ ) and the second resistor (R ₂ ) to the drive unit with a power supply voltage. 8. The method of claim 7,
The driving unit power supply voltage supply circuit includes:
When the switch SW is turned off, the power supply voltage is separately supplied to the driving unit while the driving unit performs switching using the pulse-shaped output voltage V _O charged in the inductor L Features a power supply. 8. The method of claim 7,
The power supply voltage supply circuit includes:
And a pulse type output voltage V _O charged in the inductor L is transferred to the second capacitor C ₂ using the first diode D ₁ . The method according to claim 1,
A rectifying part connected to the output of the AC voltage (AC) for rectifying the AC current to a DC current and supplying the DC current to the input voltage (V _IN )
Further comprising a power supply. 12. The method of claim 11,
The driving unit includes:
And a rectified voltage detection circuit receiving the input voltage (V _IN ) to the rectification part and delivering an output to the switch (SW)
Wherein the driving unit generates the driving signal by using the rectified voltage detection signal output from the rectified voltage detection circuit. 13. The method of claim 12,
The driving unit includes:
And controls the input current to have a preset power factor when the switch current flowing when the switch SW is turned on is proportional to the rectified voltage. 13. The method of claim 12,
The rectified voltage detection circuit includes a first diode (D ₁ ), a second diode (D ₂ ), a first resistor (R ₁ ), a second resistor (R ₂ ) and a first capacitor (C ₁ )
Said first diode (D ₁₎ of the one end is connected to one end of the input power, and the second diode (D ₂₎ of the one end is connected to the other terminal of the input power, the other of the first diode (D ₁₎ And the other end of the second diode (D ₂ ) are connected to each other,
The other end of the first end of the resistor (R ₁₎ is connected to the contacts of the other end of the first diode (D ₁₎ and the other end of the second diode (D _2), the first resistor (R ₁₎ is the Connected to one end of the second resistor (R ₂ )
The first capacitor (C ₁ ) is connected in parallel with the second resistor (R ₂ )
The other end of the second resistor (R ₂ ) is grounded to a common ground, and the rectified voltage detecting circuit outputs an output of a contact between the first resistor (R ₁ ) and the second resistor (R ₂ ) Power supply unit. A switch SW receiving the input voltage V _IN and performing switching based on the driving signal applied from the driving unit;
An inductor L for performing charge and discharge in accordance with the on or off state of the switch SW;
A diode D;
A capacitor C for charging / discharging according to whether the diode D conducts;
An LED light emitting unit operated by electric power discharged from the capacitor (C); And
A current source for determining a light emission current of the LED light-
Wherein one end of the inductor L, one end of the switch SW, one end of the capacitor C and one end of the current source are grounded to a common ground, and the other end of the inductor L, SW is connected to an input power source and one end of the diode D is connected to a contact point of the inductor L and the input power source and the other end of the diode D is connected to the other end of the capacitor C Connected,
Wherein one end of the LED light emitting unit is connected to the contact point of the diode (D) and the capacitor (C), and the other end of the LED light emitting unit is connected to the current source. 16. The method of claim 15,
Wherein the driving unit includes an output voltage control unit and a light emission current control unit,
One end of the output voltage control unit is connected to the contact point of the LED light emitting unit and the current source and the other end of the output voltage control unit is connected to the input terminal of the switch SW to generate the driving signal,
And the light emission current controller controls the current of the current source. 16. The method of claim 15,
A TRIAC dimmer, a rectifier,
The triac brightness controller is connected to the output of the ac voltage AC and the rectifier is connected to the triac brightness controller to rectify the alternating current into a direct current and to convert the direct current into the input voltage V _IN Supply,
The other end of the rectifier is connected to the other end of the AC voltage, the output end of the rectifier is connected to a current input terminal of the switch SW, and the output end of the rectifier is grounded to a common ground. LED lighting device. 18. The method of claim 17,
The driving unit includes an output voltage control unit, a summation unit, and a light emission current control unit,
One end of the output voltage control unit is connected to the contact point of the LED light emitting unit and the current source and the other end of the output voltage control unit is connected to the input terminal of the switch SW to generate the driving signal,
The light emission current controller controls the current of the current source,
The triac brightness controller is connected to one end of the input section of the rectifying section, the other end of the summing section is connected to the light emission current control section, and the interval detection signal when the triac brightness controller is turned on And generates a summation signal by summing the periodic interval compensation signals. 19. The method of claim 18,
Wherein the light emission current controller activates the current source only when the sum signal is present and stops the operation of the current source for the remaining period. 16. The method of claim 15,
The driving unit includes a light emitting current regulator including a first resistor R ₁ , a photocoupler, a current mirror, and a second resistor R ₂ ,
One end of the first resistor (R ₁ ) is connected to _one end of the analog voltage generator, the other end of the first resistor (R ₁ ) is connected to one end of the photocoupler, And the other end of the current mirror is connected to one end of the second resistor (R ₂ ), and the other end of the second resistor (R ₂ ) is grounded to a common ground. 16. The method of claim 15,
The current source includes an operational amplifier (AMP), a switching element (Q ₁ ), and a third resistor (R ₃ )
The + input terminal of the operational amplifier AMP is connected to the contact of the current mirror and the second resistor R ₂ ,
The switching element Q ₁ includes an input terminal, a current input terminal, and a current output terminal, the input terminal is connected to the output terminal of the OP amp AMP, the current input terminal is connected to the LED light emitting unit, The current lead is connected to the third resistor (R ₃ )
Wherein the - input terminal of the operational amplifier (AMP) is connected to the contact point of the switching element (Q ₁ ) and the third resistor (R ₃ ). 16. The method of claim 15,
Wherein the LED light emitting unit includes a plurality of light emitting diode arrays, and the current sources are connected in series for each of the light emitting diode arrays. 23. The method of claim 22,
The driving unit includes an output voltage control unit, a minimum value determination unit, and a light emission current control unit,
The light emission current controller controls the current of the current source,
One end of the minimum value determination unit is connected to the contact point of the LED light emitting unit and the current source, the other end of the minimum value determination unit is connected to one end of the output voltage control unit,
The lowest value of the voltage of the current source is set to be higher than the output voltage V _O for controlling the output voltage V _O so that the output voltage V _O charged in the inductor L becomes equal to or higher than the forward conduction voltage of each of the LED arrays. To be input to the control unit,
And the other end of the output voltage control unit is connected to an input terminal of the switch SW so that the output voltage V _O is determined.

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