KR20090027133A - Radio frequency repeating system for wireless communication using cross dipole array circular polarization antenna - Google Patents

Abstract

A radio frequency repeating system for wireless communication using a cross dipole array circular polarization antenna is provided to maximize a difference of left/right of a main lobe to minimize a sub lobe copied to a rear side of an antenna, thereby minimizing interference due to reflecting waves. A circular polarization link antenna(2310) transmits and receives a radio signal with a base station system. A circular polarization service antenna(2320) transmits and receives a radio signal with a mobile communications terminal. A repeating device(2330) amplifies a signal received from the circular polarization link antenna. The repeating device transmits the amplified signal to the circular polarization service antenna. The repeating device amplifies the signal through received through the circular polarization service antenna and transmits the amplified signal to the circular polarization link antenna.

Description

Radio frequency repeating system for wireless communication using cross dipole array circular polarization antenna

The present invention relates to a mobile communication repeater using an orthogonal dipole array circular polarization antenna, and more particularly, to a wireless communication relay system using a dipole array circular polarization antenna.

In the wireless network of the mobile communication system, the intensity of radio waves is weakened due to natural and artificial obstacles such as mountains, buildings, tunnels, interiors of buildings, etc., and thus, partial shadowed areas are generated in which radio frequency reception by mobile terminals is impossible. Radio repeater (RF Repeater) is a system that covers the shadow area existing within the service range of the base station by re-amplifying the base station signal, and relays the system to receive high quality service anytime and anywhere.

In such a wireless relay system, a link antenna for transmitting and receiving a wireless signal with a base station and a service antenna for transmitting and receiving a wireless signal with a terminal are connected. The downlink signal from the base station to the terminal is received by the link antenna and amplified in the wireless relay system, and then transmitted to the terminal through the service antenna. The uplink signal from the terminal to the base station is received and amplified in the wireless relay system. It is then delivered to the base station via the link antenna.

Typically, since such link antennas and service antennas are directional, it is ideal that the radio waves are radiated only in the direction in which the antennas are directed. However, in the case of the actual antenna, the radio wave is radiated not only in the direction in which the antenna is facing, but also partially radiated in the rear. At this time, the intensity of the radio wave radiated forward and the intensity of radio wave radiated backward is referred to as the front and rear ratio, the higher the front and rear ratio, that is, the stronger the strength of radio waves radiated to the front becomes an ideal relay antenna.

In the case of a wireless relay system, the link antenna and the service antenna are directed in opposite directions. Since the transmit and receive frequencies of the antennas are the same, the signal and link antenna (or service antenna) transmitted from the service antenna (or link antenna) are the same. The frequency of the signal received by) is the same. Therefore, in the conventional wireless relay system, a main beam transmitted from one antenna may be fed back to another antenna and input, thereby causing the repeater to oscillate, thereby preventing normal operation. To prevent this, it is necessary to improve the isolation between the two antennas (that is, the extent to which a plurality of adjacent antennas do not interfere with each other) by further improving the front and rear ratios of the link antenna and the service antenna itself.

1 is a view showing the configuration of a conventional wireless relay system.

Referring to FIG. 1, a conventional wireless relay system includes a link antenna 110, a service antenna 120, and a relay unit 130.

The link antenna 110 receives the radio frequency signal from the base station 140 or transmits the radio frequency signal received from the radio terminal 150 through the service antenna 120 to the base station 140. The service antenna 120 receives a radio frequency signal from the radio terminal 150 or transmits a radio frequency signal received from the base station 140 through the link antenna 110 to the radio terminal 150. The relay unit 130 filters and amplifies the radio frequency signal between the link antenna 110 and the service antenna 120.

In the conventional wireless relay system having such a configuration, if the separation between the linear polarization link antenna 110 and the service antenna 120 is not sufficiently secured, the radio frequency signal is amplified and then retransmitted through the service antenna 120. The signal may be fed back to the link antenna 110 to cause the amplifier to oscillate. Therefore, the maximum isolation between the two antennas (typically 60 ~ 70dB) is used to determine the amplification gain within the range where oscillation of the power amplifier does not occur. At this time, since the oscillation of the repeater is fatal to the network and the system, the gain of the amplifier is set to operate with a margin of 15 to 20 dB lower than the obtained isolation. Therefore, the gain of the amplifier is about 40-55dB, which limits the basic function of the repeater, that is, sufficient coverage expansion or the function of supplementing the radio shadow area, which is the biggest disadvantage of the wireless repeater.

In addition, in the conventional wireless relay system, since the linearly polarized link antenna 110 and the service antenna 120 are disposed on the same plane, the side lobe direction of each antenna is horizontal at the same height as the adjacent antenna. Is formed to cause interference. Furthermore, in the conventional wireless relay system, there is a problem in that the main beam directly reflected by the surrounding buildings or objects is radiated vertically in the opposite direction in the direction of radiation, causing interference. 2 shows the radiation characteristics of a typical antenna.

In terrestrial operations such as a conventional wireless relay system or an interference cancellation system (ICS), it is important to reduce the side lobes generated from an antenna. An ICS relay system is typically capable of removing about 30dB of the fading signal from the multi-path itself. However, when the main beam reflection signal or the side lobe is present in the antenna itself, the function of eliminating interference by the ICS relay system itself becomes very poor, making it difficult to perform the functions unique to the ISC relay system. In addition, since the conventional wireless relay system is more affected by interference than the ICS relay system, operational difficulties are greater. In the array antenna pattern, the largest intended beam pattern is called a main lobe, and other incidental components are called side lobes. And the null angle between each lobe becomes an area which does not serve as an antenna. In this case, the side lobe may be used in some cases, so it is the designer's discretion to control the side lobe. However, this side lobe acts as a very serious interference source when the WCDMA wireless repeater is operated on the ground, so it is necessary to design an antenna having a wide null angle.

To this end, a SBF antenna has been proposed using linear polarization. SBF antennas using linear polarization provide wide null angles and zero signal transmission in unnecessary directions, resulting in excellent isolation characteristics and ideal beam patterns. However, in the case of the conventional SBF antenna using a linear polarization, it is necessary to install multiple rear shield plates in order to improve the isolation, thereby increasing the weight and size of the antenna device and causing secondary side lobes to the front. . In addition, when the antenna device is installed on the roof of a building, there is a problem in that a separate shield such as a copper plate must be installed on the surface of the rooftop in order to reduce the electromagnetic wave damage to the human body, and further, the installation is affected by the surrounding environment.

The technical problem to be achieved by the present invention is to provide a relay system for wireless communication using an orthogonal dipole array circularly polarized antenna that can form a circular polarization pattern having a relatively large left and right polarization ratio, while achieving interference isolation and high isolation. have.

In accordance with another aspect of the present invention, a repeater for a wireless communication includes a circularly polarized link antenna for transmitting and receiving a radio signal with a base station system constituting a mobile communication system; A circular polarization service antenna for transmitting and receiving a radio signal with a mobile communication terminal; And a repeater for amplifying a signal received from the circular polarization link antenna and transmitting the signal to the circular polarization service antenna, and amplifying the signal received through the circular polarization service antenna and transmitting the signal to the circular polarization link antenna. The circular polarization link antenna and the circular polarization service antenna each include a plurality of orthogonal composite elements for antennas that emit electromagnetic waves, and radiate members facing each other among a plurality of radiating members constituting each of the orthogonal composite elements for the antenna. A coaxial cable is connected to each of the feeding members to be connected, and the length of the coaxial cable connected to the orthogonal composite elements for the antenna increases sequentially in the clockwise or counterclockwise direction, respectively. Coaxial Cables of Orthogonal Composite Elements for Antennas The length of is determined to increase sequentially in the opposite direction so that the polarization direction of the radiation wave radiated from each circularly polarized antenna is opposite to each other, the length of each of the coaxial cable is determined by the following equation.

Where L _ij is the length of the coaxial cable (where i is the arrangement order in the clockwise or counterclockwise direction of each of the orthogonal composite elements for the antenna arranged in a rhombus shape, and j is the clockwise direction of each of the orthogonal composite elements for the antenna). VF is the speed factor of the coaxial cable, and λ is the lower frequency wavelength of the band used.

According to the present invention, a repeater for wireless communication using an orthogonal dipole array circularly polarized antenna minimizes the main lobe and the sublobe radiated to the rear of the antenna, thereby minimizing the interference by the reflected wave of the main lobe reflected by obstacles around the antenna. In addition, it is possible to reduce the size of the antenna and reduce the antenna manufacturing cost by applying a feeding method that can simultaneously achieve impedance matching and circular polarization. In addition, it is possible to manufacture an orthogonal dipole array circular polarization antenna for a wireless repeater which can form a circular polarization pattern having a large polarization ratio and a large left and right polarization ratio while achieving interference elimination and high isolation.

Hereinafter, an orthogonal dipole array circular polarization antenna for a wireless repeater and a wireless communication repeater using the same according to the present invention will be described in detail with reference to the accompanying drawings.

3 and 4 are respectively a plan view and an exploded perspective view of an embodiment of an orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention.

3 and 4, the orthogonal dipole array circularly polarized antenna for a wireless repeater according to the present invention is orthogonal composite elements for four antennas (310, 312, 314, 316), rear choke 320, first reflection patch An element 330, a first dummy patch element 340, a second dummy patch element 350, and a second reflective patch element 360 are provided.

Four orthogonal composite elements 310, 312, 314, and 316 for four antennas are spaced at regular intervals and disposed on the rear choke 320. The rear choke 320 is a rectangular plate-shaped body made of aluminum or white chromate-treated metal, and the orthogonal composite elements 310, 312, 314, and 316 for antennas are fixed thereto. The rear choke 320 is installed on the bottom surface of the first reflection patch element 330 to reflect the electromagnetic wave radiated backward from the orthogonal composite elements 310, 312, 314, 316 for the antenna to the front, and the first reflection The electromagnetic wave flowing to the bottom surface of the patch element 330 is absorbed or canceled. The rear choke 320 includes a first reflection choke 322, a dummy choke 324, a second reflection choke 326, and a plurality of insertion chokes 328. The first reflection choke 322 and the second reflection choke 326 reflect the electromagnetic waves radiated backward from the four quadrature orthogonal composite elements 310, 312, 314, and 316 to the front. The length of each side of the first reflecting choke 322 and the second reflecting choke 326 is shorter by 1/2 of the lower frequency wavelength of the use band than the length of the side of the first reflecting patch element 330. In addition, the first reflection choke 322 and the second reflection choke 326 together with the dummy choke 324 are radiated backward from four orthogonal composite elements 310, 312, 314, and 316 for the first reflection patch. Absorb or offset electromagnetic waves flowing to the bottom surface of the device 330. The dummy choke 324 is positioned between the first reflection choke 322 and the second reflection choke 326, and radiated and radiated backward from four orthogonal composite elements 310, 312, 314, and 316 for antennas. The counter phases are generated in order to cancel each other out. The dummy choke 324 has a shape in which a rectangular protrusion is formed at each corner of the rectangular plate shorter than the first reflection choke 322 by the length of each side of the lower frequency wavelength of the use band. At this time, the length of each end of the neighboring protrusion is 1/4 of the lower frequency wavelength of the use band, the width is 1/4 of the upper frequency wavelength of the use band. The insertion choke 328 is between the first reflection choke 322 and the dummy choke 324, between the dummy choke 324 and the second reflection choke 326, the second reflection choke 326 and the first reflection patch element ( Inserted between the 330 to maintain the gap. The length of each side of the insertion choke 328 is half as short as the lower frequency wavelength of the use band compared to the length of the side of the first reflection patch element 330. Noise power is greatly reduced by the action of the first reflection choke 322, the dummy choke 324, and the second reflection choke 326.

In this case, each of the orthogonal composite elements 310, 312, 314, and 316 for the antennas is disposed in a rhombus shape, and when the dipole antenna for the repeater is installed, a plane perpendicular to the ground surface of each antenna is used for each of the orthogonal composite elements for the antennas 310, 312, and 316. 314, 316 to match the diagonal of the rhombus. In addition, the center distance of each of the orthogonal composite elements 310, 312, 314, and 316 for each antenna is 1/2 of the lower frequency wavelength of the use band, and each of the orthogonal composite elements 310, 312, 314, and 316 of each antenna is used. The distance from the center to the nearest sidewall of the first reflection patch element 330 is 1/4 to 1/2 of the lower frequency wavelength of the use band (preferably 0.35 to 0.5 times the lower frequency wavelength of the use band). The reason why the minimum distance from the center of each of the orthogonal composite elements 310, 312, 314, and 316 for each antenna to the nearest side wall of the first reflection patch element 330 is set to 0.35 times the lower frequency wavelength of the use band. When the size of the first reflection patch element 330 is downsized, the edges formed by the neighboring sidewalls of the first reflection patch element 330 meet from the center of each of the orthogonal hybrid elements 310, 312, 314, and 316 for the antenna. This is to ensure that the distance to the nearest edge is 1/2 of the lower frequency wavelength of the band used. Furthermore, a coaxial cable is connected to each of the power supply members connecting the radiation members facing each other among the plurality of radiation members constituting the orthogonal composite elements 310, 312, 314, and 316 for each antenna.

5A to 5C show a detailed configuration of an antenna orthogonal composite element constituting an orthogonal dipole array circular polarization antenna for a wireless repeater, respectively.

5A through 5C, each of the orthogonal composite elements 310, 312, 314, and 316 for an antenna includes four radiation members 510 and two power feeding members 540 and 570.

형태로 서로 마주보는 한 쌍의 복사부재는 각각의 복사부재의 하단에 위치한 평행부들의 종단 사이의 거리가 사용대역의 하위 주파수의 파장(λ)의 1/2이 되도록 서로 이격되어 배치된다. Each radiation member 510 has the same shape and is composed of a radiating portion 520 and a leg portion 530. The radiating part 520 is disposed perpendicularly to the pair of parallel parts 522 and 524 and the pair of parallel parts 522 and 524 spaced apart from each other in the vertical direction and spaced apart from each other. , 524 is connected to each end of the connection portion. At this time, the length of the first parallel portion 524 located below the pair of parallel portions 522 and 524 is less than 1/4 of the wavelength? Of the low frequency F _L of the use band, The length of the second parallel portion 522 located at is less than 1/4 of the wavelength λ of the high frequency (F _H ) of use. At this time

The pair of radiation members facing each other in a form are spaced apart from each other such that the distance between the ends of the parallel portions located at the bottom of each radiation member is 1/2 of the wavelength? Of the lower frequency of the use band.

Meanwhile, one end of the second parallel portion 522 protrudes upward. Accordingly, the length from the upper end of the first parallel portion 524 to the end of the protrusion of the second parallel portion 522 is one quarter of the wavelength? Of the lower frequency of the use band. The length from the upper end to the upper end of the end where the protrusion of the second parallel portion 522 is not formed is 1/8 to 1/4 of the wavelength? Of the lower frequency of the use band. In addition, the leg portion 530 is formed extending from the radiating portion 520, the length of the leg portion is 1/4 of the wavelength (λ) of the lower frequency of the use band. Each copy member 510 having such a shape is spaced apart at 90 ° intervals. In addition, each radiation member 510 is made of the same material as the rear choke 320, which is made of a plate-like body that absorbs or offsets electromagnetic waves flowing to the bottom surface of the first reflection patch element 330 (eg, aluminum). , White chromated metal, etc.). When the radiation member 510 is made of the same material as the rear choke, the potential difference does not occur between the orthogonal composite elements 310, 312, 314, and 316 for the antenna and the rear choke 320, thereby improving durability. In the case of aluminum material, there is an advantage that the overall antenna can be reduced in weight.

The feeding members 540 and 570 are first supporting portions 550 and 580 attached to parallel portions disposed below each leg portion and a pair of parallel portions of any one of the radiating members to be connected to each other. Second support portions 522 and 582 attached to parallel portions disposed below a pair of parallel portions of other radiation members among the radiating members to be connected, and connecting portions 560 and 590 interconnecting upper ends of the supporting portions. Is done. At this time, the length from the end of the first support portion 550, 580 to the center of the connection portion 560, 590 is 1/4 of the wavelength of the lower frequency of the band used for radiation. In addition, the center portion of the first feed member 540 of the feed member (540, 570) is formed to protrude upward, the center portion of the second feed member 570 is formed to protrude downward, each of the feed member (540, 570 is configured not to contact each other. The power feeding members 540 and 570 are made of a metal containing copper (eg, bronze, brass, etc.).

The orthogonal composite device for a wireless repeater antenna including a plurality of radiation members 510 and power feeding members 540 and 570 having the shape and size as described above has a height and a width of l / 2 of the lower frequency wavelength of the use band. Will have a length. The orthogonal composite device for a wireless repeater antenna is used as a basic element for forming a circularly polarized wave orthogonal dipole array circular polarization antenna for a wireless repeater. In this case, an insulator made of PTFE is inserted between the feed members 540 and 570 and the radiating member 510 connected thereto so as to prevent a short circuit between the feed members 540 and 570 and the radiating member 510 connected thereto. The bolts for fastening the power supply members 540 and 570 and the radiation member 510 are made of polycarbonate. Polycarbonate is a thermoplastic resin produced by reacting bisphenol A with phosgene. It has high mechanical strength, excellent heat resistance and electrical insulation.

Meanwhile, in order for the orthogonal composite device for a wireless repeater antenna described with reference to FIGS. 5A to 5C to operate correctly, first, impedance matching of components of a composite device including a pair of radiating members and a feeding member must be performed. A phase delay is needed to generate polarization.

First, the impedance matching process for the components of the composite device will be described. The simplest way to do this is to simply connect the components of the two composite devices in parallel. For example, if the components of two 50Ω composite elements are connected in parallel, the impedance at the connection point is 25Ω. However, there is a problem in that impedance matching is not performed with devices connected to components of a composite device such as a coaxial cable or an amplifier. In this situation, it is necessary to match the impedance combining the components of the two composite devices while maintaining the standing wave ratio (SWR) of 1.5: 1 or less. This means that a 50Ω coaxial cable must be matched to 50Ω at the connection point of the components of the two composite devices. Therefore, the components of each composite device should theoretically match 50Ω, in which case the components of the two composite devices should each have an impedance of 100Ω. As a result, the impedance at the connection point should be matched to 50Ω, and the present invention achieves 50Ω impedance matching by using a matching stub between the components of the two composite elements and the common common coaxial cable. In this case, impedance matching is performed using an impedance changer (for example, 1 × 2, 1 × 4, 1 × 8 in-phase divider) between a coaxial cable having a specific length and components of two composite devices as a matching stub. .

To match two different impedances, first calculate the intermediate impedance of a λ / 4 (Quarter wave) coaxial cable using the following λ / 4 (Quarter wave) formula:

For example, the impedance matching method in the combination of two antenna elements having an impedance termination point of 40Ω when the impedance must be matched to Z = 50Ω is as follows.

First, a new impedance Z is calculated by Equation 1 to combine the components of two composite devices having an impedance termination point of 40Ω by using a λ / 4 coaxial cable. Next, an impedance converter matching the calculated impedance Z is designed and matched to 50Ω. At this time, if Z1 is 50Ω as the impedance of the component of the composite device and Z2 is 40Ω as the endpoint impedance, the new impedance Z is about 44.7Ω by Equation (1). Thus, as shown in FIGS. 6A and 6B, the impedance of the component of each composite element connected to the λ / 4 coaxial cable is about 44.7 Ω. As described above, in order to match the components of the two composite devices having an impedance of 44.7Ω with 50Ω, first, the components of the two composite devices are combined as shown in FIG. 6C to manufacture an orthogonal composite device for a wireless repeater antenna. When two λ / 4 coaxial cables are connected in parallel to an orthogonal composite device for a wireless repeater antenna manufactured by combining the components of two composite devices having an impedance of 44.7Ω, the impedance becomes 22.4Ω. This impedance is connected to an impedance converter (in-phase divider or quadrature hybrid combiner and divider) to match the final 50 Ω.

As described above, in order to construct a total matching stub for impedance matching of an orthogonal composite device for a wireless repeater antenna, which is a component of two composite devices having an impedance of 44.7Ω, the pattern connected to the impedance converter is 27.6Ω. shall. When the matching pattern is configured as described above, an orthogonal composite element for a wireless repeater antenna having an impedance of 22.4Ω is combined and finally matched to a 50Ω port, and inversely separated from a 50Ω port to be matched to a 22.4Ω port. As such, a matching stub is used to match different impedances using an impedance converter and a coaxial cable, and impedance matching of a single or multiple antennas is possible using a matching stub.

At this time, the length of the coaxial cable connected to the feed member constituting the orthogonal composite device for a wireless repeater antenna is determined by the following process.

First, select a coaxial cable made of 40Ω. At this point, the impedance difference between 40Ω and 50Ω is very small, so you can choose a 50Ω coaxial cable (50Ω Nominal SF-085 coaxial cable) that is generally available. The velocity factor (VF) of the SF-085 coaxial cable is 0.66, which means that the propagation speed of electromagnetic waves in the coaxial cable corresponds to 0.66 times the propagation speed in free space. Next, the wavelength lambda is calculated from the operating frequency. For example, if the operating frequency is 2.0 GHz, which is the 3G frequency band, the wavelength is 150 mm. Next, [lambda] / 4 is obtained, and [lambda] / 4 is 37.5 mm at the 2.0 GHz frequency. Finally, when calculating the electrical λ / 4 (EQ), the length of the coaxial cable is 24.8 mm. Proper sheathing should be done to connect the coaxial cable of this length to the dipole. At this time, the length of exposed insulator should be 0.8 ± 0.2mm, the length of exposed outer conductor should be 9.2 ± 0.2mm, and the length of exposed inner conductor should be 1.0 ± 0.2mm.

7A to 7C are diagrams illustrating current distribution, radiation form, and horizontal radiation pattern of the quadrature composite element for the wireless repeater antenna according to the present invention shown in FIG. 6C, respectively.

7A to 7C, the directions of currents flowing to the radiation members facing each other are opposite, and the current density is the maximum at the center of the orthogonal composite element for the wireless repeater antenna. In addition, a current flow is formed in each of the parallel portions arranged in a direction perpendicular to the radial direction of the radio waves. Unlike the conventional 'a' shaped orthogonal composite device for antenna having a circular rotation, which rotates by one such structure, the 'F' shaped dipole orthogonal composite device as shown in FIG. Radiate polarization Therefore, the orthogonal composite device for the wireless repeater antenna can obtain high performance in terms of rotational force of circular polarization. In addition, as can be seen in Figure 7c 'orthogonal composite device for the F-shaped wireless repeater antenna has a front and rear ratio of about 32dB, the conventional' b 'shaped dipole antenna in that the generation of the side lobe and the rear lobe is minimized Better performance than orthogonal composite devices. The characteristic variables of the orthogonal composite device for the 'F' type of wireless repeater antenna are as follows.

Cλ = πDλ = 0.75λ ~ 1.33λ

Sλ = 0.2126λ ~ 0.2867λ

AR = (2n + 1) 2n

Where Cλ is the circumferential length of the circular polarization, Dλ is the diameter of the circular polarization, Sλ is the axial length of one rotation, AR is the axial ratio, and n is the number of rotations of the circular polarization.

Orthogonal composite elements for a wireless repeater antenna having the above-described configuration are disposed on the rear choke 320 which is located on the bottom surface of the first reflective patch element 330 in various forms depending on the number used.

8A and 8B show the most basic arrangement of an orthogonal dipole array circularly polarized antenna composed of four orthogonal composite elements for four wireless repeater antennas, respectively. At this time, in order to ensure that the horizontal radiation characteristics are formed at a desired angle, the components constituting the orthogonal composite elements for each of the wireless repeater antennas are configured to cross vertically and horizontally with respect to the ground surface when the wireless repeater antennas are installed. The orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 8A includes four orthogonal composite elements for the four wireless repeater antennas on a straight line connecting centers of two opposite sides of the bottom plate of the first reflection patch element 800. 820, 830, and 840 are disposed, and a rhombus is formed by connecting the centers of four orthogonal composite elements 810, 820, 830, and 840 for the antenna of the four wireless repeaters. At this time, the distance between the centers of the orthogonal composite elements 810, 820, 830, and 840 for each of the wireless repeater antennas is 1/2 of the lower frequency wavelength of the use band, and each of the orthogonal composite elements for the antennas 810, 820, 830, and 840 Distance from the center of the first reflection patch element 800 to the nearest sidewall of the first reflection patch element 800 is 1/4 to 1/2 (preferably 0.35 to 0.5 times the lower frequency wavelength of the use band). to be. In the arrangement shown in FIG. 8A, coaxial cables of length as shown in Table 1 are connected to the components of the respective composite elements 810, 820, 830, and 840 according to the rotation direction of the circular polarization.

In addition, in the orthogonal dipole array circular polarization antenna illustrated in FIG. 8B, four orthogonal composite elements 860, 870, 880, and 890 for four repeater antennas are disposed on a diagonal of the first reflection patch element 850. Rhombus is formed by connecting the centers of the orthogonal composite elements 860, 870, 880, and 890 for the repeater antenna. At this time, the distance between the centers of the orthogonal composite elements 860, 870, 880, and 890 for each of the wireless repeater antennas is 1/2 of the lower frequency wavelength of the use band, and the orthogonal composite elements for each of the wireless repeater antennas (860, 870, and 880). 890, the distance from the center of the first reflection patch element 850 to the nearest side wall is 1/4 to 1/2 (preferably, 0.35 to 0.5 of the lower frequency wavelength of the use band). Pear). As shown in FIGS. 8A and 8B, the circular radiation pattern characteristic is best when the distance between the centers of the orthogonal composite elements for the four wireless repeater antennas is set to 1/2 of the lower frequency wavelength of the use band. In the arrangement shown in FIG. 8B, coaxial cables of length as shown in Table 1 are connected to the components of the respective composite elements 860, 870, 880, 890 according to the rotation direction of the circular polarization.

8A and 8B, when the quadrature composite elements for the wireless repeater antennas are arranged in the most basic arrangement constituting the circularly polarized antenna, there are two methods of designing the HPBW differently. One method is to arrange the orthogonal composite elements for the wireless repeater antenna such that the distance from the center of the orthogonal composite element for the antenna to the nearest side wall of the first reflection patch element 330 is 1/2 of the lower frequency wavelength of the use band. In the 1.9 GHz band, the HPBW of the horizontal radiation pattern is 45 ° and the HPBW of the vertical radiation pattern is 22 °. The other is the distance from the nearest sidewall of the first reflection patch element 330 to the center of the orthogonal composite element for the wireless repeater antenna, which is 1/4 of the lower frequency wavelength of the use band (preferably, the lower frequency wavelength of the use band). Orthogonal composite elements for a wireless repeater antenna so that the beam width is extended by about 10 ° to 15 ° in the 1.9 GHz band and the HPBW of the horizontal radiation pattern is 55 ° to 60 ° The HPBW of the pattern is about 22 ° to 30 °. This means that the diagonal distance from the center of the orthogonal composite element for the wireless repeater antenna to the nearest side wall portion of the first reflection patch element 330 is 1/4 of the lower frequency wavelength of the use band (preferably, the lower part of the use band). Same as the case of arranging orthogonal composite elements for a wireless repeater antenna to be 0.35 times the frequency wavelength).

9A and 9B, four orthogonal composite elements for a wireless repeater antenna are arranged vertically, respectively. 9A and 9B, when the orthogonal dipole array circular polarization antenna for the wireless repeater is configured, the gain is not large, but the horizontal characteristic of the HPBW is wider. In the orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 9A, the first reflection patch element 900 has a rectangular shape, and the distance between the centers of the orthogonal composite elements 910, 920, 930, and 940 for each antenna is 1/2 of the lower frequency wavelength of the band used. Also, the distance from the center of each of the orthogonal composite elements 910, 920, 930, and 940 for each antenna to the nearest edge of the first reflective patch element 900 is 1/4 to 1/2 of the lower frequency wavelength of the band used. Preferably, 0.35 to 0.5 times the lower frequency wavelength of the use band). At this time, the line extending the antenna elements constituting the orthogonal composite elements 910, 920, 930, and 940 for each antenna has an angle of 45 ° or 135 ° with respect to the side of the first reflection patch element 900.

In addition, in the case of the power feeding method, two composite elements 910 and 920 positioned at the top are supplied with phases of 0 ° and 90 ° to respective components, and two composite elements 930 and 940 located at the bottom thereof are respectively provided. The component is fed in phases of 180 ° and 270 °. Accordingly, the first coaxial cables (that is, connected to the radiation member located at the upper left of each composite element) connected to the component fed at a phase of 0 ° among the components of the two composite elements 910 and 920 positioned at the top. Coaxial cable) is the same length. In addition, the second coaxial cables (that is, connected to the radiation member located on the upper right side of each composite element) connected to the component that is fed in the phase of 90 ° of each component of the two composite elements 910, 920 located on the upper The length of the coaxial cable) is also the same, and in order to achieve a phase difference of 90 °, the length of the first coaxial cable must be 1/4 of the lower frequency wavelength of the band used. The length and the connection relationship of the coaxial cable are the same for the two composite elements 930 and 940 located below, except that the lengths of the coaxial cables connected to the radiation members located under the right side of each composite element 930 and 940 are the same. The length of the first coaxial cable should be 1/2 of the lower frequency wavelength of the use band, and the length of the coaxial cables connected to the radiation member located at the lower left is 3 / of the lower frequency wavelength of the use band than the length of the first coaxial cable. It must be as long as four.

The orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 9A has a horizontal radiation pattern of HPBW of 70 ° and a vertical radiation pattern of HPBW of 35 ° in a 2.2 GHz band.

In addition, in the orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 9B, a line extending from the composite element components constituting each of the orthogonal composite elements 960, 970, 980, and 990 for each antenna has a first reflection patch element ( The only difference is that it has an angle of 90 ° or 180 ° with respect to the sidewall of 950, and the rest of the configuration is the same. In this case, the beam width is extended by about 10 ° in the 2.2 GHz band so that the HPBW of the horizontal radiation pattern is 80 ° and the HPBW of the vertical radiation pattern is about 40 °. This is the same as the case of arranging orthogonal composite elements for an antenna such that the distance from the center of the composite element to the nearest sidewall of the first reflective patch element 950 is 1/4 of the lower frequency wavelength of the use band.

FIG. 10 shows an intersection between the orthogonal composite elements 1010, 1020, 1030, and 1040 for each antenna arranged with the orthogonal dipole array circularly polarized antenna for the wireless repeater shown in FIG. 8A and the vertices of the first reflection patch element 1000. The form in which the orthogonal composite elements 1050, 1060, 1070, and 1080 for the antenna are arranged is shown. The arrangement of the antenna shown in FIG. 10 is applied to the link antenna as a loop arrangement. In this case, the distance from each of the additional antenna quadrature composite elements 1050, 1060, 1070, and 1080 to the nearest side wall among the sidewalls of the first reflection patch element 1000 is 1/4 to 1/2 of the lower frequency wavelength of the band. Preferably, 0.35 to 0.5 times the lower frequency wavelength of the use band). In addition, the distance between the centers of the orthogonal composite elements 1050 and 1060, 1060 and 1070, 1070 and 1080, 1080 and 1050 adjacent to each other is preferably arranged to be 1.5 times the wavelength of the lower frequency of the use band. In the orthogonal dipole array circular polarization antenna for the wireless repeater shown in FIG. 10, each of the additional orthogonal hybrid elements 1050, 1060, 1070, and 1080 for each antenna from the sidewall of the first reflective patch element 1000 to the nearest sidewall is shown. When the distance is 1/2 of the lower frequency wavelength of the band used, the HPBW of the horizontal radiation pattern is about 25 °. This is nearly half as narrow as the HPPW compared to the horizontal radiation pattern of the orthogonal dipole array circular polarization antenna for wireless repeaters having the arrangement of the type shown in FIG. 8A, thus increasing the gain by more than 3 dB.

In the case of the feeding method of the dipole array circular polarization antenna shown in FIG. 10, the feeding method to the four composite elements 1010, 1020, 1030, and 1040 located at the vertex of the rhombus is shown in FIGS. 8A and 8B. Same as the power feeding method of the antenna. Each of the additional composite devices 1050, 1060, 1070, and 1080 is fed by the same feeding method as the composite device located closest to the four composite devices 1010, 1020, 1030, and 1040 located at the vertex of the rhombus.

11A and 11B illustrate vertical arrangements applied to service antennas, respectively. When the orthogonal dipole array circular polarization antenna for the wireless repeater is configured as shown in FIGS. 11A and 11B, the antenna overall gain is 3 dB or more higher than the orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. Increase, and the beam width becomes relatively narrow accordingly. The arrangement of the dipole antenna shown in FIG. 11A is a copy of the arrangement shown in FIG. 8A in the same form, and each of the orthogonal composite elements 1120, 1122, 1124, 1126, 1140, 1142, 1144, and 1146 for each antenna is illustrated. Is arranged at the vertex of the rhombus, and when installed, a straight line connecting the upper and lower vertices of the rhombus forms a plurality of antenna groups 1110 and 1130 perpendicular to the ground surface. And an orthogonal composite element for an antenna located at a position closest to another group among the orthogonal hybrid elements 1120, 1122, 1124, 1126, 1140, 1142, 1144, and 1146 constituting each antenna group 1110 and 1130. The distance from the center of the quadrature composite elements 1120, 1122, 1124, 1142, 1144, and 1146 for the remaining antennas except for (1126, 1140) to the nearest sidewall of the first reflective patch element 1100 is the lower frequency wavelength of the use band. 1/4 to 1/2 (preferably 0.35 to 0.5 times the lower frequency wavelength of the band used). Further, the distance between the ends of the parallel portions of the composite elements 1126 and 1140 at the position closest to the other antenna groups 1110 and 1130 is 1/20 to 1/8 of the wavelength of the lower frequency of the band used (preferably 1). / 16). This is equal to the distance between the ends of parallel portions of the adjacent composite elements among the composite elements 1120, 1122, 1124, 1126, 1140, 1142, 1144, and 1146 constituting each antenna group 1110 and 1130. The orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 11A has a horizontal radiation pattern of about 45 ° and a vertical radiation pattern of about 22 ° in the 2.2 GHz band.

In the arrangement of the orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 11B, an additional dipole antenna is disposed on the top and the bottom, respectively, in the arrangement illustrated in FIG. 8A. In this case, among the orthogonal hybrid elements 1160, 1162, 1164, and 1166 arranged in a rhombus shape, the orthogonal hybrid elements 1160 and 1164 and the first reflection patch element 1150 positioned on a straight line perpendicular to the ground surface. Additional quadrature composite elements 1170 and 1172 for antennas are disposed between sides of the antenna. Further, the distance between the ends of the parallel portions of each of the additional antennas orthogonal composite elements 1170 and 1172 from the ends of the parallel portions of the orthogonal hybrid elements 1160 and 1164 for the nearest antenna is from 1/20 to the wavelength of the lower frequency of the band used. 1/8 (preferably 1/16). This is equal to the distance between the ends of parallel portions of the adjacent composite elements among the composite elements 1160, 1162, 1164, and 1166 arranged in a rhombus shape. In addition, the distance from each of the additional orthogonal composite elements 1170 and 1172 for the antenna to the nearest side wall of the first reflection patch element 1150 is 1/2 of the lower frequency wavelength of the use band. In this case, the beam width is extended by about 10 ° in the 2.2 GHz band so that the HPBW of the horizontal radiation pattern is 55 ° and the HPBW of the vertical radiation pattern is about 25 °. In the orthogonal dipole array circular polarization antenna for the wireless repeater shown in FIG. 11A, the distance in the diagonal direction from the center of the orthogonal composite element for antennas to the nearest edge portion of the first reflection patch element 1150 is the lower frequency of the use band. It is the same as the case of arranging the orthogonal composite elements for the antenna to be 1/2 of the wavelength, and the gain is increased by 3 dB or more than the orthogonal dipole array circular polarization antenna for the wireless repeater shown in FIG.

In the case of the feeding method of the dipole array circular polarization antenna shown in FIG. 11A, a method of feeding the respective antenna groups 1110 and 1130 to the composite elements 1120, 1122, 1124, 1126, 1140, 1142, 1144, and 1146 is illustrated in FIG. 11A. The power feeding method of the dipole array circular polarization antenna shown in 8a and 8b is the same. In addition, in the power feeding method of the dipole array circular polarization antenna shown in FIG. 11B, the feeding method to the composite elements 1160, 1162, 1164, and 1166 located at the vertex of the rhombus is shown in FIGS. 8A and 8B. It is the same as the feeding method of, and each of the additional composite devices 1170 and 1172 is fed by the same feeding method as the composite device located closest among the four composite devices 1160, 1162, 1164, and 1166 located at the vertex of the rhombus. do.

The first reflective patch element 330 is manufactured in the form of a box having an open top, and the orthogonal composite elements 310, 312, 314 and 316 for the antenna are fixed to the bottom surface of the first reflective patch element 330. A rear choke 320 having a structure for absorbing electromagnetic waves is installed on the bottom surface of the first reflection patch element 330, and the rear choke 320 is rearward of the orthogonal composite elements 310, 312, 314, and 316 for the antenna. Absorb or offset the radiated electromagnetic waves to achieve maximum radiation forward. In addition, the distance between the side wall of the first reflective patch element 330 and the center of the orthogonal composite elements 310, 312, 314, and 316 for antennas (eg, 1/4 to 1/2 of the lower frequency wavelength of the band used). You can change the Half Power Beam Width by adjusting the selected distance within the range. The first reflection patch element 330 has a square or rectangular shape according to the arrangement of the orthogonal composite element for the antenna described with reference to FIGS. 8A to 11B.

The first dummy patch element 340 is manufactured in the form of a box having an open top, and accommodates the first reflective patch element 330. Each sidewall of the first dummy patch element 340 is formed with at least one cross-shaped slit penetrating the inner side and the outer side of the sidewall. At this time, the width of the cross slit is 1/20 to 1/8 of the lower frequency wavelength of the use band. In particular, the width of the cross-shaped slit is preferably 1/16 of the lower frequency wavelength of the use band. In this case, if the lower frequency wavelength of the use band is 1.9 GHz, the width of the cross-shaped slit is about 10 mm. In addition, the cross slit has the length of the horizontal slit twice the length of the vertical slit, and the length of the vertical slit is 1/4 of the lower frequency wavelength of the use band. In addition, the first pile patch element 340 is inclined with respect to the side wall (eg, 3 °, 5 °) downward from the end of the first wing portion and the first wing portion extending vertically outward from the top of each side wall Etc.) and a wing portion formed of a second wing portion which is bent to extend. At this time, the length of the second wing is 1/4 of the lower frequency wavelength of the band used. The wing portion is turned so as to face the bottom surface of the first dummy patch element 340 so that the electromagnetic wave passing through the cross slit is reflected and does not flow back into the cross slit.

12A and 12B show a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIGS. 8A and 8B, respectively. It is. 12A and 12B, one cross slit 1210 is formed on each sidewall of the first dummy patch device 1200. 13A and 13B are a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIGS. 9A and 9B, respectively. . 13A and 13B, one cross-shaped slit 1310 is formed on sidewalls of the first dummy patch device 1300 positioned on a straight line connecting the centers of the orthogonal composite elements for the antenna. Two cross-shaped slits 1320 and 1330 are formed on sidewalls positioned in a direction perpendicular to a straight line connecting the centers of the orthogonal composite devices. At this time, the size of the cross slit 1310, 1320, 1330 is as described above, the distance between the center of the cross slit 1320, 1330 formed on the same side wall is 1.5 times the lower frequency wavelength of the use band. Meanwhile, the first dummy patch element applied to the orthogonal dipole array circular polarization antenna for the wireless repeater having the arrangement of the orthogonal composite elements for the antenna as shown in FIGS. 11A and 11B also has the first dummy shown in FIGS. 13A and 13B. It has the same shape as the patch element 1300, but only its size is changed.

14A and 14B are respectively a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIG. 10. 14A and 14B, two cross-shaped slits 1410 and 1420 are formed on each sidewall of the first dummy patch device 1400. At this time, the size and the distance between the cross-shaped slits 1410 and 1420 are the same as described with reference to FIGS. 13A and 13B.

On the other hand, when a plurality of cross-shaped slits are formed on the same sidewall of the first dummy patch element 340, a part of the wing portion (particularly, the second wing portion) is removed, and the removal length is the lower frequency wavelength of the use band. It is preferable that n (n is a positive integer) times 1/4 of the ratio. As such, by removing a portion of the wing portion of the first dummy patch element 340, a phenomenon in which electromagnetic waves are induced between two cross-shaped slits positioned at the portion where the wing portion is removed can be prevented. In terms of structure, since the edge of the wing portion of the first dummy patch element 340 is in an open state, electromagnetic waves are induced and returned. In this case, the portion of the wing portion of the first dummy patch element 340 where the synthesis of the electromagnetic waves occurs is the largest. Central. Accordingly, by removing a portion of the wing portion of the first dummy patch element 340, the portion where the electromagnetic wave is synthesized is dispersed, and the electromagnetic wave is induced in two cross-shaped slits located at the portion where the wing portion of the first dummy patch element 340 is removed. This can minimize the phenomenon.

The second dummy patch element 350 is manufactured in the form of a box having an open top, and accommodates the first dummy patch element 340. The second dummy patch element 350 extends downwardly from an end portion of the first wing portion along a direction perpendicular to the first wing portion, and extends downwardly from the top of the side wall to the first wing portion. It has a wing portion consisting of a second wing portion spaced apart at predetermined intervals along the longitudinal direction of the portion. At this time, the length of one side of the second wing portion is preferably set to 1/4 of the lower frequency wavelength of the use band, the spacing between the second wing portion is the lower frequency of the use band from the edge formed by the adjacent side wall to a certain number It is set to 1/4 of the wavelength. As described above, the second wing portion formed in the second dummy patch element 350 has a current transfer path of one of the lower frequency wavelengths of the use band compared to the second reflective patch element 360 positioned outside the second dummy patch element 350. Since the length becomes about 2, the phases of the electromagnetic waves formed in the second dummy patch element 350 and the second reflective patch element 360 are different by 180 °, and the effects of canceling each other can be obtained. As a result, the second dummy patch element 350 having such a structure absorbs or cancels the second wave or the electromagnetic waves from the first dummy patch element 340. On the other hand, between the first dummy patch element 340 and the second dummy patch element 350 is composed of a mechanical structure of 1/4 or 1/2 of the lower frequency wavelength of the band used to the second dummy patch element 350 A first corner choke made of aluminum or white chromated metal is installed to absorb or offset the electromagnetic waves. An example of the first corner choke is shown in FIG. 15, and the first corner choke is installed at the corner of the bottom surface of the second dummy patch element 350.

FIG. 16 illustrates an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIGS. 8A and 8B. Referring to FIG. 16, the second wing portions 1610, 1620, 1630, and 1640 protruding outward of each sidewall of the second dummy patch element 1600 have a length of each side equal to one-third of the lower frequency wavelength of the use band. It has a quadrangular shape of four. In this case, it is preferable that the interval between the two second wing portions 1610 and 1620, 1630, and 1640 from the edge formed by the adjacent sidewall is n times n (n is a positive integer) of 1/4 of the lower frequency wavelength of the use band. Do. In addition, FIG. 17 illustrates an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as illustrated in FIG. 10. Referring to FIG. 17, the second wing portions 1710, 1720, 1730, 1740, 1750, and 1760 protruding to the outside of each sidewall of the second dummy patch device 1700 have a lower frequency of each band. It has a square shape that is 1/4 of the wavelength. At this time, the interval between the three second wing portions 1710 and 1720 and 1730, 1740 and 1750 and 1760 from the edge formed by the neighboring side wall is n of the lower frequency wavelength of the band used (n is a positive integer) It is preferable that it is) times.

FIG. 18 shows an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIGS. 9A and 9B. Referring to FIG. 18, three second wing portions 1810 are formed on the sidewalls of the second dummy patch device 1800 positioned on a straight line connecting the centers of the orthogonal composite elements for the antenna from edges formed by neighboring sidewalls. And 1820 and 1830, 1840 and 1850 and 1860 are 1/4 of the lower frequency wavelength of the band used. On the other hand, the second wing portions 1870 and 1880 are formed on sidewalls positioned in a direction perpendicular to a straight line connecting the centers of the orthogonal composite elements for the antenna, from edges formed by neighboring sidewalls. 19 illustrates an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIGS. 11A and 11B. The second dummy patch element shown in FIG. 19 is similar in shape to the second dummy patch element shown in FIG. However, two second wings each having a quarter of each other from the corners formed by the sidewalls adjacent to the sidewalls located in a direction perpendicular to the straight line connecting the centers of the orthogonal composite elements for the antenna with each other. 1970 and 1975, 1980 and 1985) are formed, and the gap between the second wing parts 1930 and 1940 located at the outer side of the three second wing parts spaced one quarter of the radiation propagation is wider. There is a difference.

The second reflective patch element 360 is manufactured in the form of a box having an open upper portion, and accommodates the second dummy patch element 350. The second reflection patch element 360 blocks the side lobe or the posterior lobe generated by the orthogonal composite elements 310, 312, 314, and 316 for the antenna, and radiates the other electromagnetic waves to the front, thereby allowing the first reflection patch element ( 330 to maximize the electromagnetic radiation forward. Between the second reflecting patch element 360 and the second dummy patch element 350 has a mechanical structure of 1/4 or 1/2 of the lower frequency wavelength of the band used, absorbs or cancels the electromagnetic radiation radiated backward A second corner choke of aluminum or white chromate treated metal is installed. An example of the second corner choke is shown in FIG. 20, and the second corner choke is installed at a corner of the bottom surface of the second reflective patch element 360.

On the other hand, the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention as described above in order to radiate the circular polarization phase of the electromagnetic wave fed to each antenna orthogonal composite element constituting the orthogonal dipole array circular polarization antenna for a wireless repeater These shall be 0 °, 90 °, 180 ° and 270 ° respectively. In the present invention, this is achieved by adjusting the length of the coaxial cable connected to each antenna orthogonal composite element. The length of the coaxial cable for generating circular polarization is determined by the following equation.

Where L _ij is the length of the coaxial cable (where i is the arrangement order in the clockwise or counterclockwise direction of each of the orthogonal composite elements for the antenna arranged in a rhombus shape, and j is the clockwise direction of each of the orthogonal composite elements for the antenna). VF is the speed factor of the coaxial cable, and λ is the lower frequency wavelength of the band used.

When viewing the dipole antenna array from the rear side of the first reflection patch element, a polarized wave that rotates in a clockwise direction is called a right polarized wave and a polarized wave that rotates in a counterclockwise direction is called a right polarized wave when the lower frequency wavelength of the band used is 37.5 mm. The length of the coaxial cable calculated by Equation 2 is as follows.

Polarization type Coaxial cable number Coaxial Cable Length (mm)     Right-handed circular polarization L ₁₁ 99 L ₁₂ 124 L ₂₁ 124 L ₂₂ 149 L ₃₁ 149 L ₃₂ 173 L ₄₁ 173 L ₄₂ 198     Left-handed circular polarization L ₁₂ 99 L ₁₁ 124 L ₄₂ 124 L ₄₁ 149 L ₃₂ 149 L ₃₁ 173 L ₂₂ 173 L ₂₁ 198

In Table 1, the superscript of the coaxial cable number is sequentially given in clockwise order from the lowermost quadrature composite element for the antenna, and the coaxial cable number sequentially in the clockwise direction among the coaxial cables connected to one orthogonal composite element for one antenna. A subscript is given. In addition, the value n is set for the first cable connected to the lowest quadrature composite element for the antenna. In addition, each coaxial cable is connected to a ¼-wave hybrid impedance converter to which a matching coaxial cable having an impedance of 50Ω is connected to form a matching stub for impedance matching. This matching stub is shown in FIG. 21.

Eight coaxial cables having a length as described in Table 1 are connected in combination, two to each orthogonal composite element for one antenna. In addition, the difference in length of the coaxial cable having a length of λ / 4 causes the phase difference to occur at 90 ° intervals of the electromagnetic waves fed to the orthogonal composite elements for each antenna. Therefore, assuming that the quadrature composite element for the antenna located at the lowermost side has a phase difference of 0 to 90 ° when forming the right polarized wave, the orthogonal composite elements for the antenna arranged clockwise therefrom are 90 ° to 180 ° and 180 ° respectively. The phase difference of 270 ° to 270 ° to 360 ° causes the radiation to rotate as a whole.

The orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention as described above has no side lobe or rear lobe structurally and has a front and rear ratio of 40 dB or more. Therefore, when the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention is applied to a link antenna and a service antenna of a wireless communication relay system, excellent isolation characteristics can be obtained between the two antennas, thereby enabling stable operation of the relay system. There is this. 22A illustrates a horizontal radiation when the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention includes a first reflection patch element 330, a first dummy patch element 340, and a second reflection patch element 360. FIG. 22B is a view illustrating a pattern, and FIG. 22B illustrates a cross reflection antenna including a first reflection patch element 330, a first dummy patch element 340, and a second dummy patch element 350. And a horizontal radiation pattern when all of the second reflective patch elements 360 are provided. Referring to FIGS. 22A and 22B, it can be seen that even when there is no second dummy patch element 350, the side lobe removal effect can be obtained to a certain degree, and when the second dummy patch element 350 is provided, it is almost perfect. It can be seen that the side lobe is removed.

On the other hand, the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention can be configured only with the rear choke 320 and the first reflection patch element 330, in addition to the first dummy patch element 340, the second At least one element element among the dummy patch element 350, the second reflection patch element 360, and the corner choke may be added. In addition, one antenna orthogonal composite element may be disposed in the center of the rear choke 320, and in this case, the distance from the center of the antenna orthogonal composite element to each side wall of the first reflection patch element 330 may be determined by the use band. 1/4 to 1/2 (preferably 0.35 to 0.5) times the lower frequency wavelength.

FIG. 23 shows a preferred embodiment of the repeater for mobile communication employing the orthogonal dipole array circular polarization antenna for the wireless repeater as the link antenna and the service antenna as described above.

Referring to FIG. 23, a repeater for mobile communication according to the present invention includes a link antenna 2310, a service antenna 2320, and a relay unit 2330.

The link antenna 2310 transmits and receives a radio signal with a base station system constituting the entire mobile communication system. The service antenna 2320 transmits and receives a radio signal with the mobile communication terminal. The link antenna 2310 and the service antenna 2320 are configured as the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention as described above. The relay unit 2330 amplifies the signal received from the link antenna 2310 and transmits the signal to the service antenna 2320, and amplifies the signal received through the service antenna 2320 and transmits the signal to the link antenna 2310. The detailed configuration and function of the relay unit 2330 is well known to those skilled in the art to which the present invention pertains, and thus detailed description thereof will be omitted.

The link antenna and the service antenna constituting the repeater for mobile communication according to the present invention as shown in FIG. 23 vary the polarization directions of the link antenna 2310 and the service antenna 2320 according to the propagation environment of the point where the repeater is installed. In this case, if the polarity (that is, the polarization direction) of the two antennas is reversed in an area where isolation between antennas is large, the back to back effect between the two antennas can be minimized. Adjustment of the polarization direction of the two antennas can be made by adjusting the length of the coaxial cable connected to the orthogonal composite element for the antenna constituting each antenna, the length of this coaxial cable is determined by the equation (2).

Although the preferred embodiments of the present invention have been shown and described above, the present invention is not limited to the specific preferred embodiments described above, and the present invention belongs to the present invention without departing from the gist of the present invention as claimed in the claims. Various modifications can be made by those skilled in the art, and such changes are within the scope of the claims.

1 is a view showing the configuration of a conventional wireless relay system,

2 is a diagram illustrating radiation characteristics of a general antenna;

3 and 4 are a plan view and an exploded perspective view of an embodiment of an orthogonal dipole array circular polarization antenna for a wireless repeater, respectively, according to the present invention;

5A to 5C are diagrams showing the detailed configuration of components constituting the orthogonal dipole antenna for the wireless repeater, respectively;

6a to 6c show an orthogonal composite element for an antenna fabricated by combining two antenna elements with each antenna element connected with a λ / 4 coaxial cable, respectively;

7A to 7C are diagrams showing current distribution, radiation form and horizontal radiation pattern of the quadrature composite element for an antenna according to the present invention shown in FIG. 6C, respectively;

8A and 8B are diagrams illustrating the most basic arrangement of an orthogonal dipole array circular polarization antenna for a wireless repeater each having four orthogonal composite elements for an antenna;

9A and 9B are diagrams each showing four antennas orthogonal composite elements arranged vertically;

FIG. 10 illustrates a form in which an additional orthogonal composite element for an antenna is disposed between a vertex of each orthogonal composite element for each antenna and a first reflection patch element arranged such as the orthogonal dipole array circular polarization antenna for the wireless repeater illustrated in FIG. 8A. One drawing,

11A and 11B illustrate a vertical arrangement form applied to a service antenna, respectively.

12A and 12B are a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIGS. 8A and 8B, respectively;

13A and 13B are a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIGS. 9A and 9B, respectively;

14A and 14B are respectively a perspective view and a side view of a first dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIG. 10;

15 is a view showing an example of a first corner choke;

FIG. 16 is a view showing an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIGS. 8A and 8B;

FIG. 17 is a view showing an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIG. 10;

FIG. 18 illustrates an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having an arrangement form of an orthogonal composite element for an antenna as shown in FIGS. 9A and 9B;

FIG. 19 illustrates an example of a second dummy patch element applied to an orthogonal dipole array circular polarization antenna for a wireless repeater having a configuration of an orthogonal composite element for an antenna as shown in FIGS. 11A and 11B;

20 is a view showing an example of a second corner choke;

21 is a diagram illustrating an impedance matching state of multiple antennas using a matching stub.

22A illustrates a horizontal radiation pattern when the orthogonal dipole array circular polarization antenna for a wireless repeater according to the present invention includes a first reflection patch element, a first dummy patch element, and a second reflection patch element;

22B illustrates a horizontal radiation pattern when the orthogonal dipole array circular polarization antenna for a wireless repeater includes all of the first reflection patch element, the first dummy patch element, the second dummy patch element, and the second reflection patch element. Figure shown, and

FIG. 23 is a diagram illustrating a preferred embodiment of a mobile communication relay system employing the orthogonal dipole array circular polarization antenna for a wireless repeater as a link antenna and a service antenna according to the present invention as described above.

Claims (9)

A circularly polarized link antenna for transmitting and receiving a radio signal with a base station system constituting a wireless communication system; A circular polarization service antenna for transmitting and receiving a radio signal with a mobile communication terminal; And A repeater for amplifying a signal received from the circular polarization link antenna and transmitting the signal to the circular polarization service antenna, and amplifying the signal received through the circular polarization service antenna and transmitting the signal to the circular polarization link antenna. The circularly polarized link antenna and the circularly polarized wave service antenna are each provided with a plurality of orthogonal composite elements for antennas emitting electromagnetic waves, A coaxial cable is connected to each of the power supply members connecting the radiation members facing each other among the plurality of radiation members constituting each of the orthogonal composite elements for the antenna, The length of the coaxial cable connected to the orthogonal composite elements for the antenna is sequentially increased in the clockwise or counterclockwise direction, but the length of the coaxial cable of the orthogonal composite elements for the antenna constituting the link antenna and the service antenna is Decide to increase sequentially in opposite directions so that the polarization directions of the radiation waves radiated from each antenna are opposite to each other, The length of each of the coaxial cable is a wireless communication relay system, characterized in that determined by the following equation:

Where L _ij is the length of the coaxial cable (where i is the arrangement order in the clockwise or counterclockwise direction of each of the orthogonal composite elements for the antenna arranged in a rhombus shape, and j is the clockwise direction of each of the orthogonal composite elements for the antenna). VF is the speed factor of the coaxial cable, and λ is the lower frequency wavelength of the band used. The method of claim 1, A reflective patch element having a box shape having an open top, fixed to the bottom of the orthogonal composite elements for the antenna, and absorbing or blocking electromagnetic waves radiated backward from the orthogonal composite element for the antenna; And And a dummy patch element for accommodating the reflective patch element and primarily absorbing or canceling electromagnetic waves from the reflective patch element. The method of claim 2, The dummy patch element, A base portion formed of a square plate shape; A plurality of side walls extending vertically upward from the sides of the base to the same height, each of the side walls corresponding to each side of the base; And A plurality of first wings formed vertically outwardly extending from an upper portion of each of the side wall portions, each corresponding to each of the side wall portions, and corresponding to each of the first wing portions downward from an end of each of the first wing portions; It is bent to be inclined with respect to the side wall portion is formed extending; a wing portion each consisting of a plurality of second wings corresponding to each of the first wing portion; At least one cross-shaped slit formed through the outer surface and the inner surface of the side wall portion includes a vertical slit disposed along a height direction of the side wall portion and a horizontal slit disposed in a direction orthogonal to the vertical slit. Wireless communication relay system, characterized in that. The method of claim 2, The orthogonal composite element for the antenna is fixed and installed on the bottom surface of the reflective patch element to reflect electromagnetic waves radiated backward from the orthogonal composite element for the antenna to the front, and absorb the electromagnetic waves flowing to the bottom surface of the reflective patch element. Or a rear choke for canceling or offsetting. The method of claim 1, A reflective patch device having a box shape having an open top, fixed to the bottom of the orthogonal composite elements for the antenna, and absorbing or blocking electromagnetic waves radiated backward from the orthogonal composite element for the antenna; And The orthogonal composite element for the antenna is fixed and installed on the bottom surface of the reflective patch element to reflect electromagnetic waves radiated backward from the orthogonal composite element for the antenna to the front, and absorb the electromagnetic waves flowing to the bottom surface of the reflective patch element. Or a rear choke to offset or offset; wireless communication relay system comprising a. The method according to claim 4 or 5, The rear choke, A plurality of reflection chokes for reflecting forward electromagnetic waves radiated backward from the quadrature composite element for the antenna; A dummy choke positioned between the reflective chokes and offsetting each other by generating a phase difference in electromagnetic waves radiated backward from the orthogonal composite element for the antenna and flowing to the bottom surface of the reflective patch element; And And an insertion choke inserted between the reflective choke and the dummy chokes and between the reflective choke and the reflective patch element to maintain a gap therebetween. The method of claim 6, The reflective choke has a quadrangular shape, and the length of each side facing each sidewall of the reflective patch element is shorter than the length of the sidewall of the reflective patch element by 1/2 of the lower frequency wavelength of the use band. Orthogonal dipole array circularly polarized antenna for wireless repeater. The method according to any one of claims 1 to 5, The orthogonal composite elements for the antennas are arranged so that the shape connecting the center points to the upper surface of the reflective patch element is a rhombus, and the distance between the centers of the neighboring orthogonal composite elements for the antennas is 1 / of the lower frequency wavelength of the use band. Orthogonal dipole array circularly polarized antenna for wireless repeater, characterized in that 2. The method of claim 8, Orthogonal dipole array for wireless repeater, characterized in that the distance from the center of each of the orthogonal composite elements for the antenna to the nearest sidewall of the reflective patch element is 1/4 to 1/2 of the lower frequency wavelength of the band used Circularly polarized antenna.

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