KR20080095731A - Method for generating sequence and method for transmitting signal based on sequence in mobile communication system - Google Patents

Abstract

A method for generating a sequence and a method for transmitting a signal based on the sequence in a mobile communication system are provided to reduce an amount of operations in transmitting and receiving terminals and to increase an amount of transmission information. Two sequences or more are divided into a real part and an imaginary part. The sequence is mapped on a channel and the mapped sequence is transmitted. Two sequences or more are compounded in a localized structure and interleaved structure and are mapped on the channel. The sequences are mapped by using an in-phase component and a quadrature component and are transmitted.

Description

Method for generating sequence and method for transmitting signal based on sequence in mobile communication system

This document relates to a communication system, in particular, a mobile communication system, and more particularly, to a sequence generation method and a sequence-based signal transmission method used in a mobile communication system.

The following description relates to a method for generating two or more sequence sets that can be applied to a specific channel and a sequence generation method therefor.

1 is a view for explaining an example of a two-stage sequence generation method.

Within limited resources, a two-layered sequence such as the method disclosed in FIG. 1 may be used to increase the amount of information to be transmitted. In general, a two-stage sequence consists of a combination of a scramble sequence and an orthogonal sequence. That is, the two-stage sequence may be composed of a vector product of the scrambled sequence and the orthogonal sequence as shown in FIG.

This two-stage sequence can transmit a large amount of information, but it requires too much computation on the receiving end. For example, the total sequence length is N, the amount of information from scramble sequence is Msc, and the amount of information from orthogonal sequence is Mor. Assume

In this case, the total amount of information that can be transmitted is Msc * Mor. However, in order to detect this information at the receiving end, a total of Msc * Mor correlation operations are required.

More specifically, assuming that N = 64, the scrambled sequence is a Zadoff-Chu (ZC) sequence (Msc = 32), and the orthogonal sequence is a Hadamard sequence (Mor = 64). The possible amount of information is 32 * 64 = 2048, which requires a total of 2048 correlations.

In the background as described above, the embodiments disclosed in the present document aim to provide a sequence generation method and a sequence-based channel signal transmission method that can more easily detect a signal at a receiving end.

In addition, the embodiments disclosed in the present document are to provide a sequence generation method and a sequence-based channel signal transmission method that can reduce the amount of computation of the transmitting and receiving end and increase the amount of transmission information.

In accordance with one aspect of the present invention, a method for transmitting a sequence-based signal in a communication system includes selecting one or more sequences and injecting the selected one or more sequences into in-phase components of the channel. And transmitting the channel signal by mapping to a Quadrature Component and a Quadrature Component.

Here, some elements of each of the one or more sequences may be mapped to the in-phase component, and the remaining elements of the sequence may be mapped to the orthogonal component.

In addition, when the selected sequence is two or more, one of the selected sequences may be mapped to the in-phase component, and the other of the one or more sequences may be mapped to the orthogonal component.

At least one of the selected sequences uses a sequence generated according to the above-described embodiment of the present invention, that is, a first sequence and a second sequence, and each of the selected sequences is a binary based sequence. The second sequence may consist of a real part, and the second sequence may be a sequence in the form of a complex sum consisting of an imaginary part of the sequence.

In addition, when the first sequence and the second sequence are each used as complex-based sequences, the real part of the first sequence and the imaginary part of the second sequence are composed of the real part of the sequence, and the imaginary part of the first sequence. The real part of the part and the second sequence may be a sequence in the form of a complex sum of imaginary parts of the sequence.

In this case, one or more of the selected sequence may be configured such that a third sequence and a fourth sequence are multiplied in addition to each of the first sequence and the second sequence. Here, the third sequence and the fourth sequence may be the same sequence, and in this case, it may be regarded that the third sequence is multiplied by the complex sum of the first sequence and the second sequence. Here, the third sequence may be a scrambled sequence.

Also, the first sequence and the second sequence may be homologous or heterologous to each other.

When mapping sequences according to the above-described channel signal transmission method, one or more sequences may be mapped by applying a predetermined sequence combination method.

Here, the sequence combining method may be a method in which one sequence and another sequence are sequentially mapped to the channel on the subcarrier axis.

In addition, the sequence combining method may be a method of mapping elements of one sequence and another sequence to the channel alternately on the subcarrier axis.

According to another aspect of the present invention, there is provided a method of generating a sequence, the method comprising: selecting a first sequence and a second sequence, adding the first sequence and the second sequence to generate a sequence, and forming a imaginary unit in the second sequence. j) multiplying. Here, the imaginary unit (j) represents a number that is squared to -1.

The sequence may include one of a form in which a third sequence and a fourth sequence are multiplied by a first sequence and a second sequence, and a form in which a third sequence is multiplied by a complex sum of the first and second sequences. . In addition, each sequence element of at least one of the first sequence, the second sequence, and the third sequence may be a complex signal including at least one of a real part and an imaginary part.

At least one of the first sequence, the second sequence, and the third sequence may be configured as one of a scrambled sequence and an orthogonal sequence. Also, the first sequence and the second sequence may be homologous or heterologous.

In another embodiment of the present invention, a method for transmitting a sequence-based channel signal in a mobile communication system includes selecting a sequence and using the selected sequence, an in-phase channel and a quadrature channel of the channel. Transmitting the signal by using both.

As another embodiment of the present invention, a method for transmitting a signal in a mobile communication system includes selecting a sequence and transmitting a signal using the selected sequence, wherein the sequence includes two or more different sequences. The real part and the imaginary part of the sequence may be configured in different sequences.

In another embodiment of the present invention, in a communication system, a method of generating a sequence, wherein the sequence is generated using one or more sequences, and the sequence is generated by configuring one or more sequences as one of a real part and an imaginary part. Can be.

As another embodiment of the present invention, a method for transmitting a signal in a communication system including a plurality of cells uses at least one of a different sequence generation method and a sequence-based channel signal transmission method for each of the plurality of cells. Here, the sequence generation method may be a method of generating a sequence by configuring two or more sequences into a real part and an imaginary part, and the sequence-based channel signal transmission method divides one or more sequences into in-phase and quadrature components of the channel. It may be a method of mapping and transmitting.

Each element of the sequence may be a complex signal configured to include one or more of real and imaginary parts.

Through the embodiments disclosed in this document, it is easier to detect a signal at a receiving end. In addition, through the embodiments disclosed in this document, it is possible to reduce the amount of computation of the transmitting and receiving end and increase the amount of transmission information.

Hereinafter, exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings. The detailed description set forth below in conjunction with the appended drawings is intended to explain exemplary embodiments of the present invention and is not intended to represent the only embodiments in which the present invention may be practiced. The following detailed description includes specific details to assist in a thorough understanding of the present invention. However, those skilled in the art will appreciate that the invention may be practiced without these specific details. For example, the following description will focus on certain terms, but need not be limited to these terms and may refer to the same meaning even when referred to as any term.

In some instances, well-known structures and / or devices may be omitted in order to avoid obscuring the concepts of the present invention, and may be represented in the form of block diagrams and / or flowcharts showing the core functions of each structure and / or device. have. In addition, the same components will be described with the same reference numerals throughout the present specification.

Embodiments described below transmit channel signals using one or more sequences, but transmit two or more component signals that are distinguishable at a receiving end. For example, in channel mapping, a channel may be divided into an in-phase component and an orthogonal component and mapped to the channel. This may be regarded as being able to map to a channel by dividing into I and Q channels when channel mapping. In this case, the elements of the sequences that become in-phase components and orthogonal components may be determined by various methods.

In addition, when configuring the final sequence to be mapped to the channel, two or more sequences may be combined, but each may be configured as a real part and an imaginary part to be divided into in-phase components and orthogonal components and mapped to the channel as described above.

In this case, when a sequence is divided into in-phase components and quadrature components and mapped to a channel, or when two or more sequences are combined, each sequence may be continuously or alternately configured on the frequency axis.

To this end, a description will be given of a mobile communication system to which embodiments of the present invention can be applied, and in particular, a sequence used in a multi-carrier system such as OFDM, OFDMA and 3GPP LTE systems, and IEEE 802.16e / m.

Recently, the demand for high-speed data transmission is increasing, and OFDM is suitable as a method for the high-speed transmission, and has been adopted as a transmission method of various high-speed communication systems. Hereinafter, orthogonal frequency division multiplexing (OFDM) will be described. The basic principle of OFDM is to divide a high-rate data stream into a large number of low-rate data streams, which are transmitted simultaneously using multiple carriers. Each of the plurality of carriers is called a sub carrier. Since orthogonality exists between the multiple carriers of the OFDM, the frequency components of the carriers can be detected at the receiving side even if they overlap each other. The high data rate data stream is converted into a plurality of low data rate data streams through a serial to parallel converter, and each subcarrier is converted into the plurality of data streams converted in parallel. After is multiplied, each data string is summed and sent to the receiver. OFDMA is a multiple access method for allocating subcarriers according to a transmission rate required by multiple users in the OFDM.

The OFDM scheme has a disadvantage in that a Peak-to-Average-Power Ratio (PAPR) or a cubic metric (CM) of a transmission signal is very large. Since data is transmitted using multiple carriers through an inverse fast fourier transform (IFFT) in the frequency domain, the amplitude of the OFDM signal amplitude may be expressed as the sum of the sizes of the multiple carriers. However, if the phases of each of the multiple carriers coincide, the OFDM signal has a signal having a high maximum value such as an impulse, and thus has a very high PAPR or CM. Such a transmission signal according to the OFDM method lowers the efficiency of the high output linear amplifier and causes the signal to operate in the nonlinear region of the high output amplifier, causing distortion of the signal.

Meanwhile, a channel and a sequence used in the 3rd Generation Partnership Project (3GPP) Long Term Evolution (LTE) system newly proposed will be described below.

In general, the first thing the terminal performs to communicate with the base station is to perform synchronization with the base station on a synchronization channel (hereinafter referred to as "SCH") and perform a cell search. Such an SCH may have a hierarchical structure, and thus may be divided into a primary sync channel (hereinafter referred to as "P-SCH") and an auxiliary sync channel (hereinafter referred to as "S-SCH").

A series of processes for synchronizing with a base station and acquiring a cell ID to which a terminal belongs is called a cell search. In general, the cell search includes an initial cell search performed when the initial UE is powered on, and a neighbor cell where the UE in a connection or idle mode searches for an adjacent base station. It is classified as a neighbor cell search.

The SCH used in a communication system using a plurality of orthogonal subcarriers such as OFDM or SC-FDMA preferably satisfies the following conditions.

First, the auto-correlation characteristic in the time domain for the sequence forming the SCH should be good for the detection of excellent performance on the receiving side.

Second, complexity due to synchronization detection should be low.

Third, the peak-to-average power ratio (PAPR) or cubic matrix (CM) must be low.

Fourth, if the SCH can be utilized for channel estimation, the frequency response preferably has a constant value. That is, in terms of channel estimation, a flat response in the frequency domain is known to have the best channel estimation performance.

For ease of description, reference is made based on a synchronization channel, especially S-SCH, which is considered in 3GPP LTE, but refers to other channels transmitting on a sequence basis, ie random access channel (RACH), uplink / downlink. The same concept may be applied to a DL / UL reference signal and a DL / UL control channel. Examples of the uplink / downlink control channel include an ACK / NACK channel, an ACK / NACK channel, a CQI channel, an SR channel, and the like. The channel referred to herein is not limited to a general communication channel and is a concept including a signal as in the above-described reference signal.

That is, the embodiments of the present invention described below may be applied to the case of transmitting various signal types as well as the case of transmitting a channel signal. In the following description, a binary based sequence is used. Binary sequences are advantageous in terms of complexity because they can be implemented with complex sums only in correlation operations. Of course, it is also possible to use complex-based sequences in the embodiments described below.

First, a method of generating a sequence that can use both in-phase and quadrature components of a channel as an embodiment of the present invention will be described.

According to the method of transmitting a sequence-based channel signal in the communication system of the present embodiment, the channel signal is transmitted based on a final sequence composed of two or more sequence complex sum forms.

According to this embodiment, the first sequence and the second sequence are used to generate a sequence used for transmitting a channel, for example an S-SCH signal. In the following Equation 1, an example of generating a final sequence using the first sequence and the second sequence is shown.

In Equation 1, S1 (n) represents a first sequence, S2 (n) represents a second sequence, and S (n) represents a final sequence of a combination of the first sequence and the second sequence. Here, n represents an index for the sequence element, and when the total length of the index is N, it may be any integer of 0 to N-1. As can be seen in Equation 1, the final sequence S (n) uses the first sequence S1 (n) and the second sequence S2 (n), but the first sequence S1 (n) consists of a real part and the second sequence S2 (n ) Consists of an imaginary part. Here, not only the final sequence S (n) but also the first sequence S1 (n) and the second sequence S2 (n) are similarly complex signals and may be real or imaginary signals.

Here, an additional scramble code may be applied to reduce the PAPR or CM, or to randomize the inter-cell interference. Equation 2 shows an example in which a scrambled sequence is additionally applied to the sequence generated through Equation 1 described above.

In Equation 2, S1 (n), S2 (n) and S (n) are the same as those in Equation 1 described above. E (n) represents a scrambled sequence that is additionally applied. In order to reduce the PAPR or CM or to randomize the inter-cell interference, when the scramble code is additionally applied, the same scramble code is applied to each of S1 (n) and S2 (n) as shown in Equation 2. can do. In this case, the modulation of E (n) may be scrambled with the same or different scramble sequences for each of S1 (n) and S2 (n). Unlike Equation 2, Equation 3 shows an example of scrambling each of S1 (n) and S2 (n) in a scramble sequence.

In Equation 3, S1 (n), S2 (n) and S (n) are the same as those in Equation 1 described above. In addition, E1 (n) and E2 (n) indicate a scramble sequence to be additionally applied, respectively. As described above, E1 (n) and E2 (n) may be the same or the same sequence. If E1 (n) and E2 (n) are equal to each other, the same result as in Equation 2 will be described.

In consideration of actually being transmitted, normalization may be expressed as in Equation 4 below. Hereinafter, it is assumed that the same scramble sequence is applied for convenience of description.

In Equation 4, S1 (n), S2 (n) and S (n) are the same as those in Equation 1 described above. E (n) represents a scrambled sequence that is additionally applied as in Equation 2. In particular, an example of performing normalization assumes that the power of the scrambled sequence E (n) is one.

2 is a view for explaining a method for generating a sequence according to an embodiment of the present invention.

A method of forming a final sequence by combining the first sequence S1 (n) and the second sequence S2 (n) in a complex form will be described with reference to FIG. 2. Here, the first sequence S1 (n) and the second sequence S2 (n) may both be the same kind of sequence or different kinds of sequences. In the following description, it is assumed that the same type of sequence is used. In particular, an example in which a Hadamard sequence is used as the first sequence S1 (n) and the second sequence S2 (n) will be described. As described above, it is assumed that a binary based sequence is used.

The first sequence S1 (n) having a length of N may be configured as shown in FIG. 3. That is, S1 (0), S1 (1), S1 (2), S1 (3), ..., S1 (N-4), S1 (N-3), S1 (N-2), S1 (N -1). Similarly, the second sequence S2 (n) is also S2 (0), S2 (1), S2 (2), S2 (3), ..., S2 (N-4), S2 (N-3), S2 ( N-2), may be configured as S2 (N-1).

The exemplary first sequence S1 (n) and the second sequence S2 (n) are used to construct the final sequence S (n). When the sequence generation method according to the present embodiment is applied, each element of the final sequence S (n) may be expressed as follows.

S (0) = S1 (0) + jS2 (0)

S (1) = S1 (1) + jS2 (1)

S (2) = S1 (2) + jS2 (2)

S (3) = S1 (3) + jS2 (3)

...

S (N-4) = S1 (N-4) + jS2 (N-4)

S (N-3) = S1 (N-3) + jS2 (N-3)

S (N-2) = S1 (N-2) + jS2 (N-2)

S (N-1) = S1 (N-1) + jS2 (N-1)

For the sake of understanding, assume that sequence length N = 64 and S1 (n) and S2 (n) use 64-length Hadamard sequences, respectively. And, as described above, E (n) can be selectively applied to perform scrambling of the generated final sequence, and one Golay sequence is used as E (n) when E (n) is applied. Assume to use. The amount of information that can be transmitted through each Hadamard sequence will be 64 for S1 (n) and 64 for S2 (n).

As described above, it is also possible to use a sequence based on the same or similar sequence generation method as the above-described sequence generation method. For example, when each sequence of S1 (n) and S2 (n) is a complex-based sequence, the difference between the real part of S1 (n) and the imaginary part of S2 (n) consists of the real part of the final sequence, and S1 The sum of the imaginary part of (n) and the real part of S2 (n) may consist of the imaginary part of the final sequence. That is, assuming that S1 (n) = a (n) + jb (n) and S2 (n) = c (n) + jd (n), the final sequence S (n) can be expressed as follows.

S (n) = S1 (n) + j S2 (n) = a (n) + jb (n) + j (c (n) + jd (n) = (a (n) -d (n)) + j (b (n) + c (n))

As described above, if the sequence is a binary sequence, the final sequence according to the present embodiment inserts one sequence set, that is, the first sequence into the real part of the transmitted signal as shown in Equation 1, It can be expressed by inserting another sequence set into the sequence, that is, the second sequence. As described above, when a channel signal is transmitted by using a real part and an imaginary part, respectively, a quadrature phase shift keying (QPSK) method is used, which is a method of transmitting a channel signal by dividing it into an in-phase component and an orthogonal component. The signal can be sent in a similar way to the result.

When a coherent detection method that can know or estimate the value of the channel and can be detected using the channel value is used, the combination that can be generated, that is, the total amount of information that can be transmitted, will be at most 64 * 64 = 4096. At this time, the information index of S1 (n) is 0 to 63, the information index of S2 (n) is 0 to 63, and the total information index that the final sequence S (n) can have is 0 to 4095.

If the value of the channel cannot be obtained and the non-coherent detection method is used, the combination that can be generated, that is, the total amount of information that can be transmitted will be at most ₆₄ C ₂ = 2016. Here, ₆₄ C ₂ represents an operation for the number of cases where _two of 64 are selected but any one is larger. That is, assuming that the second selection index selects a larger combination than the first selection index, for example, (0, 1), (0, 2), (0, 3), (61, 62), Combinations such as (61, 63), (62, 63) may be selected.

In this case, the amount of correlation required will be enough to perform 64 correlations, which is much smaller than the total amount of information that can be transmitted. At this time, the information index of S1 (n) is 0 to 63, the information index of S2 (n) is 0 to 63, and the total information index that the final sequence S (n) can have is 0 to 2015.

When the signal to be transmitted is represented by Equation 5, it may be expressed as Equation 5 below.

In Equation 5, S1 (n) represents a first sequence, S2 (n) represents a second sequence, and S (n) represents a final sequence of a combination of the first sequence and the second sequence, and E ( n) indicates an additionally applied scramble sequence. The transmission signal shown in Equation 5 is displayed in the frequency domain. In the case where the signal shown in Equation 5 is transmitted, the signal received at the receiving end may be represented by Equation 6 as shown in Equation 6 below.

In Equation 6, T (n) represents a transmission signal and may be expressed as shown in Equation 5, for example. H (n) represents a channel value and may be formed as a complex value. In addition, N (n) represents general noise of a channel and may be AWGN (Additive White Gaussian Noise).

When the receiving end receives a signal, for example, a signal as shown in Equation 6, the receiving signal may be detected by performing a correlation operation. Equation 7 below shows an example of a correlation calculation method that can be performed on a received signal.

은 k번째 인덱스의 원래 시퀀스를 의미한다.Equation 7 shows a correlation operation on R (n) shown in Equation 6, for example. E (n) represents a scramble sequence to be applied when a signal to which the scramble sequence is applied is transmitted at the transmitting end.

Is the original sequence of the kth index.

Here, C (k) represents a correlation output, that is, a correlation value, for a sequence corresponding to the k-th index of the sequence, and thus has a reciprocal relationship with a cost function. In the present embodiment, performing the operation of Equation 7 with respect to the one k value is defined as performing one correlation. That is, according to the present embodiment, it can be seen that the received signal can be detected by performing correlation on the original sequence index, that is, as much as the original sequence number, without performing the correlation operation as much as the total amount of information possible.

The final information can be detected through a soft value combing method for the two possible combinations. For example, using the result function value C (3) for the sequence index 3 of S1 and the result function value C (5) for the sequence index 5 of S2, the final result function can be made as shown in Equation 8 below. have.

Hereinafter, a transmission / reception operation will be described when a channel signal is transmitted using a final sequence generated by the above-described sequence combination.

For ease of explanation, it is assumed that a non-coherent detection scheme is used to generate a combination, that is, the total amount of information that can be transmitted can carry information of up to ₆₄ C ₂ = 2016. In addition, in the following description, it is assumed that information of ₂₇ C ₂ = 351, that is, only sequence, is used among the total amount of information available in 2016. As described above, an example of index allocation in case of transmitting 351 information is shown in Table 1 below.

S1 (n) index information S2 (n) index information S (n) index information 0 One 0 0 2 One 0 3 2 0 4 3

23 25 346 23 26 347 24 25 348 24 26 349 25 26 350

The transmitting end may select and transmit one of 351 pieces of information. Indexes 0 to 350 for 351 pieces of information may be represented as shown in Table 1. Here, assuming that the S2 (n) index selects a combination larger than the S1 (n) index, only 0 to 25 of the total 0 to 62 are sufficient, and S2 (n) is used. 1 ~ 26 out of 1 ~ 63 is enough. That is, since the S2 (n) sequence index selects only the combination larger than the S1 (n) sequence index, the final sequence is formed by combining S1 (n) for the 0-25 index and S2 (n) for the 1-26 index. In this case, a total of 351 sequences to be used can be generated.

In this case, the operation at the receiving end may be represented as in Equation 7. Here, since it has a range of k = 0 to 26, the received signal can be detected by 27 correlation operations. After calculating the result function for k from 0 to 26 and calculating and comparing the final result function for the combination shown in Table 1, the final information can be detected. In addition, as shown in Equation 8, the final result function value may be generated through a soft value combining method.

3 is a view for explaining an example of using a sequence combining method.

In the case of using the above-described two-stage sequence, a sequence combining method can be used to transmit a lot of information while overcoming the huge amount of computation required. The sequence combining method combines two or more sequences and transmits them. When applying this method to map to a specific physical channel, two things can be considered.

The first is a localized structure and the second is an interleaved structure. Here, the continuous structure is a structure shown in (a) of FIG. 3 to connect two or more sequences. That is, each sequence is sequentially mapped to a physical channel. And the cross structure is a structure shown in (b) of Figure 3 is to use two or more sequences so that each element intermixed with each other. In other words, the elements of each sequence are mapped to the physical channels alternately.

4 is a view for explaining an example of the 10ms radio frame structure proposed in 3GPP LTE.

As described above, in order to communicate with a base station, a terminal first performs synchronization with a base station on a synchronization channel (hereinafter referred to as "SCH") and performs cell search. Such an SCH may have a hierarchical structure, and thus divided into a primary synchronization channel (hereinafter referred to as "P-SCH", 40 and 42) and an auxiliary synchronization channel (hereinafter referred to as "S-SCH", 41 and 43). Can be.

Referring to FIG. 4, the P-SCH and the S-SCH are transmitted twice in one frame in the 10ms radio frame structure proposed in 3GPP LTE. The method shown in FIG. 5 may be used by extending the sequence combining method described with reference to FIG. 3 for the purpose of adding one bit to a frame boundary as a secondary synchronization code (SSC) of 3GPP LTE.

FIG. 5 is a diagram for explaining an exemplary sequence combining method for SSC (Secondary Synchronization Code) of 3GPP LTE.

FIG. 5 is an extension of the sequence combining method described with reference to FIG. 3, and FIG. 5A is an extension of a localized structure described with reference to FIG. 3A, and FIG. It is an extension of the interleaved structure described in 3 (a).

In other words, frame boundaries may be distinguished as SSC (Secondary Synchronization Code) composed of two combination types shown in FIG. S1 where Si is combined into a continuous structure that precedes Sj can be used as the first code, and S2 where Sj is combined into a continuous structure that precedes Si can be used as the second code by changing the order of Si and Sj. In addition, in the case of (b) of FIG. 5, S1 in which Si is combined into an intersecting structure preceded by Sj is used as the first code, and S2 in which Sj is combined into an intersecting structure preceded by Si by changing the order of Si and Sj. It can be used as the second code.

The final sequence mapping to the final channel can be configured to have the characteristics as described above to transmit the channel signal. In addition, the same or similar effects can be expected by classifying and mapping components in the channel signal mapping as described below. Hereinafter, a method of transmitting a sequence-based channel signal by mapping one or more sequences to a channel will be described.

6 is a diagram for describing a method of mapping an S-SCH signal using two or more SSCs.

6A and 6B show an example of using two sequences of length N / 2 to transmit a channel signal corresponding to a sequence of length N. The sequence used at this time is called SSC1 and SSC2, respectively.

FIG. 6A illustrates a channel mapping method corresponding to the continuous structure described with reference to FIGS. 3A and / or 5A. Referring to (a) of FIG. 6, it can be seen that N / 2 length SSC1 is continuously mapped to the channel, and then N / 2 length SSC2 is continuously mapped to the channel on the frequency axis. In particular, it can be seen that only one component, for example, the in-phase component is mapped without distinguishing the channel component. This mapping method is hereinafter referred to as a conventional localized mapping scheme.

FIG. 6B illustrates a channel mapping method corresponding to the cross-sectional structure described with reference to FIGS. 3B and / or 5B. Referring to FIG. 6 (b), it can be seen that SSC1 having an length of N / 2 and SSC2 having an length of N / 2 are mapped to channels in the frequency axis. In this case as well, it can be confirmed that only one component, for example, an in-phase component, is mapped without distinguishing the channel component. This mapping method is referred to as a conventional interleaved mapping scheme hereinafter.

It will be apparent that the combination order of SSC1 and SSC2 may be changed in the example shown in each of FIGS. 6A and 6B. In addition, the final sequence that can be generated according to an embodiment of the present invention disclosed in the description related to FIGS. 2 and 2 may be used as SSC1 and SSC2, respectively. In other words, it is also obvious that the final sequence generated by combining two or more sequences is applied to the SSC1 and SSC2 code sets of the continuous structure and the cross structure shown in FIGS. 6A and 6B. Means. Since the above transmission scheme cannot optimize PAPR or CM at the transmitting end, scrambling may be performed.

Among the proposed sequences, a sequence showing low computation amount and optimal PAPR is a Golay sequence modulated by Hadamard sequence and may have a structure as shown in FIG. 1. Here, the Golay sequence is used as a scrambling sequence, and the Hadamard sequence is used as an orthogonal sequence.

Even in the sequence showing the optimal PAPR, there is a limitation that the PAPR cannot be optimized in the structure shown in FIG. In particular, when inserting a sequence in the frequency domain in an OFDM system, when applying a sequence-modulated Golay sequence to the sequence combining method as shown in FIG. 3, since the enough information is already transmitted by the combination of two Hadamard sequences, the Golay sequence It is desirable to use as little as possible. That is, the Golay sequence is preferably used only for the purpose of reducing PAPR. Of course, it can also be used to transmit information using other Golay sequences.

In this way, it is possible to transmit a lot of information while reducing the correlation operation of the receiving end. For example, if N = 64, a combination of two sequences of length 32 can be mapped as shown in FIG. 6, and if the sequence is assumed to be a Hadamard sequence, a total of 32 * 32 = 1024 pieces of information can be transmitted. Alternatively, in selecting two information combinations, there are ₃₂ C ₂ = 240 branches for selecting the two branches without overlapping each other. In this case, it is sufficient that 32 + 32 = 64 correlation operations are performed.

7 is a diagram illustrating a method of mapping an S-SCH signal using two or more SSCs according to an embodiment of the present invention.

7 (a) and 7 (b) show an example of using two sequences of length N / 2 to transmit a channel signal corresponding to a sequence of length N. The sequence used at this time is called SSC1 and SSC2, respectively.

FIG. 7A illustrates a channel mapping method corresponding to the continuous structure described with reference to FIGS. 3A and / or 5A. Referring to FIG. 7A, it can be seen that N / 2 length SSC1 is continuously mapped to the channel, and then N / 2 length SSC2 is continuously mapped to the channel on the frequency axis. Furthermore, referring to FIG. 7A, it can be seen that the SSC1 having an N / 2 length is continuously mapped to the channel, and sequentially mapped to the in-phase component and the orthogonal component.

In other words, if S1 (0) of SSC1 is mapped to the in-phase component, then S1 (1) is mapped to the orthogonal component. Then S1 (2) is mapped back to the in-phase component. In this way, N / 2 length SSC1 can be mapped to the channel continuously. Similarly, SSC2 having an N / 2 length may be sequentially mapped to a channel following SSC1, but may be sequentially mapped to an in-phase component and an orthogonal component.

FIG. 7B illustrates a channel mapping method corresponding to the cross-sectional structure described with reference to FIGS. 3B and / or 5B. Referring to (b) of FIG. 7, it can be seen that SSC1 having an N / 2 length and SSC2 having an N / 2 length are mapped to the channel in the frequency axis. Referring to (b) of FIG. 7, in this case as well, the N / 2 length SSC1 and the N / 2 length SSC2 are mapped to the channel alternately, but it can be confirmed that they are sequentially mapped to the in-phase component and the orthogonal component.

In other words, if S1 (0) of SSC1 is mapped to the in-phase component, then S2 (0) of SSC2 is mapped to the orthogonal component. Then, S1 (1) of SSC1 is again mapped to the in-phase component. Also, S2 (1) of SSC2 is then mapped to an orthogonal component. In this way, the N / 2 length SSC1 and the N / 2 length SSC2 are alternately mapped to the channel, but sequentially mapped to the in-phase and quadrature components.

Furthermore, in FIGS. 7A and 7B, a sequence is divided into an in-phase component and an orthogonal component and mapped to a channel, but whether the same sequence or another sequence is mapped to the in-phase component and the orthogonal component crosswise is a sequence mapped to the orthogonal component In the case of, it may be described as mapping by applying a phase rotation of π / 2.

The mapping method shown in FIG. 7A is referred to as a rotational localized mapping scheme, and the mapping method shown in FIG. 7B is referred to as a rotational interleaved mapping scheme. .

In the example shown in each of FIGS. 7A and 7B, it will be apparent that the combination order of SSC1 and SSC2 may be changed as described above. In addition, the final sequence that can be generated according to an embodiment of the present invention disclosed in the description related to FIGS. 2 and 2 may be used as SSC1 and SSC2, respectively. In other words, it is also obvious that the final sequence generated by combining two or more sequences is applied to each of the SSC1 and SSC2 code sets of the continuous structure and the cross structure shown in FIGS. 7A and 7B. Means.

8 is a diagram illustrating a method of mapping an S-SCH signal using two or more SSCs according to an embodiment of the present invention.

8A and 8B show an example of using two sequences of length N / 2 to transmit a channel signal corresponding to a sequence of length N. The sequence used at this time is called SSC1 and SSC2, respectively.

FIG. 8A illustrates a channel mapping method corresponding to the continuous structure described with reference to FIGS. 3A and / or 5A. Referring to FIG. 8A, it can be seen that N / 2 length SSC1 is continuously mapped to the channel, and then N / 2 length SSC2 is continuously mapped to the channel on the frequency axis. Furthermore, referring to FIG. 7 (a), it can be seen that N / 2 length SSC1 is continuously mapped to a channel, particularly an in-phase component. In this way, N / 2 length SSC1 can be mapped to the channel continuously. In addition, SSC2 having an N / 2 length is continuously mapped to the channel after SSC1, but unlike SSC1, it is mapped to an orthogonal component.

FIG. 8B illustrates a channel mapping method corresponding to the cross-sectional structure described with reference to FIGS. 3B and / or 5B. Referring to (b) of FIG. 8, it can be seen that SSC1 having an N / 2 length and SSC2 having an N / 2 length are mapped to the channel in the frequency axis. Referring to (b) of FIG. 8, in this case as well, N / 2-length SSC1 and N / 2-length SSC2 are mapped to the channel alternately, but S1 (0) to S1 (m) and SSC2 of SSC1 are mapped. S2 (0) to S1 (m) and S2 (m) are mapped to in-phase components and the remaining SSC1's S1 (m + 1) to S1 (N-1) and SSC2's S2 (m + 1) to S1 (N It can be seen that up to -1) and S2 (N-1) are mapped to orthogonal components.

It will be apparent that the combination order of SSC1 and SSC2 may be changed in the example shown in each of FIGS. 8A and 8B. In addition, the final sequence that can be generated according to an embodiment of the present invention disclosed in the description related to FIGS. 2 and 2 may be used as SSC1 and SSC2, respectively. In other words, it is also obvious that the final sequence generated by combining two or more sequences is applied to the SSC1 and SSC2 code sets of the continuous structure and the cross structure shown in FIGS. 8A and 8B. Means.

Furthermore, in FIGS. 7A and 7B, and FIGS. 8A and 8B, a sequence is divided into in-phase components and orthogonal components and mapped to a channel, and the same sequence or another sequence intersects in-phase components and orthogonal components. As an example, an example of mapping the first part of the sequence to the in-phase component and the second part to the orthogonal component is shown. However, the rule of mapping into in-phase components and orthogonal components can be variously applied.

Also, as another embodiment of the present invention, when applying the mapping method described with reference to FIGS. 7 and 8, two or more sequences may be used as in FIGS. 7 and 8, but one sequence may be used. In other words, some elements of one sequence may be mapped and transmitted as in-phase components of the channel, and the remaining elements of the sequence may be transmitted by mapping to orthogonal components of the channel.

For example, applying the embodiment of FIG. 7 using one sequence S (n), S (0) maps to the in-phase component of the channel, S (1) maps to the orthogonal component of the channel, and S (2) Maps back into frostbite composition. In this way, up to S (N-1) can be mapped to the in-phase and quadrature components of the channel. That is, even index elements of the sequence S (n) may be mapped to in-phase components and odd index elements of the sequence S (n) may be mapped to orthogonal components. Of course, the opposite embodiment of mapping the odd index elements of the sequence S (n) to the in-phase component and the even index elements of the sequence S (n) to the orthogonal component is also possible.

Similarly, applying the embodiment of FIG. 8 using one sequence S (n), S (0) to S (N / 2-1) are mapped to in-phase components of the channel, and the remaining S (N / 2) to S ( N-1) may be mapped to orthogonal components of a channel. Similarly, the opposite embodiment of mapping S (0) to S (N / 2-1) to the orthogonal component of the channel and mapping the remaining S (N / 2) to S (N-1) to the in-phase component of the channel is possible. Of course.

In each of the above-described embodiments, each element constituting the sequence may be real or imaginary and may have a complex value.

The channel mapping method described above has been described with reference to a synchronization channel, especially S-SCH, which is considered in 3GPP LTE. As described above, other channels for transmitting the embodiments disclosed in this document based on a sequence, that is, a random access channel (RACH), an uplink / downlink reference signal (DL), Of course, the same concept can be applied to an uplink / downlink control channel (DL / UL control channel).

In addition, since the channels typically exist to provide the same function to other types of systems, the channels can be equally applied to other systems such as IEEE 802.16e / m. However, it is natural that a name for a channel providing the same function in another system may be different from that of 3GPP LTE described above. For example, in the IEEE802.16 series, the SCH may be referred to as 'preamble', the RACH as ranging, and the DL / UL reference signal as 'UL / UL pilot'.

However, when applying to other channels it is desirable to apply in consideration of the characteristics of each channel. For example, if the DL RS is mapped at six subcarrier intervals, the RS may be mapped in consideration of such channel mapping characteristics of the DL RS.

를 전송하였을 경우, 수신단에서 수신되는 신호는 다음 수학식 9과 같다.Hereinafter, an example in which the present invention is applied to DL / UL reference signal transmission will be described in more detail. Reference signal according to the present invention at the transmitting end

When the signal is transmitted, the signal received at the receiver is expressed by the following equation (9).

은 수신신호,

는 채널,

는 잡음 신호 즉, AWGN을 의미한다. 그리고, k는 시퀀스 인덱스를 나타낸다.here,

Is the received signal,

Is the channel,

Denotes a noise signal, that is, AWGN. K represents a sequence index.

는 다음 수학식 10와 같이 나타낼 수 있다. Applying LS (Least Square) method as a method of channel estimation, the estimated channel

May be expressed as in Equation 10 below.

The estimated channel may be used for channel compensation when demodulating a signal modulated by a modulation method such as BPSK, QPSK, M-ary QAM, etc. in another data part. Equation 11 below shows an example of a method for demodulating a signal through the channel estimation result of Equation 10.

는 복조 되는 수신 데이터 신호를 나타내고,

는 송신 신호,

는 채널 신호,

는 수신 데이터에 대한 잡음 신호,

는 추정된 채널 신호를 나타낸다.In equation (11)

Denotes the demodulated received data signal,

Transmit signal,

The channel signal,

Is the noise signal for the received data,

Denotes the estimated channel signal.

In general, since the reference signal is arranged in consideration of coherent time / frequency, a channel experienced by the data may be compensated with a channel estimated from the reference signal.

In addition, an example when the embodiment of the present invention is applied to a UL preamble such as RACH (ranging) or the like will be described. The RACH preamble according to the present embodiment is transmitted from the UE and is typically used for UL synchronization, scheduling request, for example, bandwidth request, time / frequency maintenance, and the like. The base station may detect a preamble transmitted to the RACH through a correlation operation to perform a scheduling request, for example, bandwidth request and time / frequency maintenance.

The RACH preamble described above includes access opportunity information of the UE and may be transmitted using a sequence. This opportunity information relates to the number of sequences available as the RACH preamble. The RACH preamble may be transmitted using the sequence generated according to the above-described embodiment of the present invention, and the number of sequences may be increased, thereby extending the opportunity of the terminal.

When a sequence generated according to an embodiment of the present invention is applied to DL / UL ACK / NACK transmission, the number of sequences may be used as information of ACK / NACK.

In addition, when the CQI is applied to the transmission of a sequence generated according to an embodiment of the present invention, the sequence may be used to transmit the CQI value. That is, a sequence generated according to an embodiment of the present invention can be used as CQI information.

When the sequence generated according to the embodiment of the present invention is applied to the control channel, the control information may be configured using the sequence generated according to the embodiment of the present invention.

In addition, when the sequence generated according to an embodiment of the present invention is applied to a general traffic channel, the data of the traffic channel may be configured using the sequence generated according to the embodiment of the present invention.

In addition, when the sequence according to the present invention is applied to the above-described synchronization channel or general traffic channels or various channel signal transmissions, at least two or more channels are multiplexed and generated according to an embodiment of the present invention. In order to distinguish each channel having a plurality of sequences to be present, it may be used for channel classification. In addition, such a sequence may be used as a code for identifying each terminal when multiplexed by CDM (code division multiplexing) between terminals.

In addition to the above examples, in general, when a sequence is applied in a communication system, a sequence generated according to an embodiment of the present invention may be widely used.

Hereinafter, an example of a preferred sequence that can be applied to the above-described embodiments will be described. However, this is only an embodiment and the type of the sequence is not limited to a specific sequence in applying the embodiments of the present invention. In the following, the sequences that can be used as the above-described SSC are described.

Among the various binary sequences, the Hadamard orthogonal sequence has a feature of reducing complexity at the receiving end by using a fast Hadamard transform (FHT). However, when scrambling is performed using the Hadamard sequence, a method for reducing PAPR or CM is required. This is because the columns of the Hadamard sequence result in very high PAPR by themselves. Alternatively, the Golay sequence can be used as a scramble code. In particular, a Golay sequence modulated with a Hadamard sequence can satisfy an appropriate PAPR within 3 dB without creating a pulse shape for Hadamard columns when applied over the entire bandwidth with one code.

Another example of a binary sequence may be an m-sequence or an PN sequence. In this case, it is also apparent that FHT can be used for m-sequence detection by applying an ordering / re-ordering matrix to the m-sequence, thereby reducing complexity at the receiving end. Methods of using FHT for m-sequence detection are described in Document <M. Cohn and A. Lempel, "on Fast M-Sequence Transforms", IEEE Transactions on Information Theory, pp135-137, January 1977. In addition, it is obvious that other types of binary sequences, for example, computer search sequences, may be used.

9 shows PDF graphs of PAPR and CM, respectively, when a Golay sequence modulated with a 64-length Hadamard sequence is applied with one code.

Referring to FIG. 9, it can be seen that a Golay sequence modulated with an uncombined pure Hadamard sequence can obtain an appropriate PAPR and a CM of 2.9732 dB or less without generating a pulse shape of 3 dB or less. That is, when the Golay sequence modulated by the Hadamard sequence is used as the SSC, an advantageous effect may be expected in terms of complexity and PAPR / CM of the transceiver. In addition, it is natural that the method described with reference to FIGS. 6 to 8 may be used as a method of mapping the channel using the SSC.

10 to 14 show the results of applying the simulation to the embodiments described above with reference to FIGS. 6 and 7. The effects of the above-described embodiments will be described in more detail through simulation results.

Table 2 shows the simulation parameters.

parameter Set Carrier frequency 2 GHz Sampling frequency 1.92 MHz FFT size 128 Number of subcarriers used 64 CP type Short CP Number of hypersus in S-SCH 680 PSC 64-length ZC SSC Two 32-length Hadamard modulated Golay sequences Timing capture Ideal acquisition Residual Frequency Offset During SSC Detection 0, 0.5, 1.0, 1.5, 2.0 ppm Channel estimation Real estimation Channel model 6-ray TU speed 30 km / h

10 to 14 are graphs showing error detection rates for the case of using the general continuous mapping method, the general cross mapping method, the rotation continuous mapping method, and the rotation cross mapping method described with reference to FIGS. 6 and 7.

In particular, FIG. 10 is a graph illustrating error detection rates for each of the four channel mapping structures described above when the residual frequency offset is 0.0 ppm. FIG. 11 is a graph illustrating an error detection rate for each of the four channel mapping structures described above when the residual frequency offset is 0.5 ppm. 12 is a graph illustrating error detection rates for each of the four channel mapping structures described above when the residual frequency offset is 1.0 ppm. FIG. 13 is a graph illustrating an error detection rate for each of the four channel mapping structures described above when the residual frequency offset is 1.5 ppm. 14 is a graph illustrating an error detection rate for each of the channel mapping structures shown in FIGS. 6 and 7 when the residual frequency offset is 2.0 ppm.

Referring to the graphs of FIGS. 10 to 14, it can be seen that the crossover mapping method has a superior effect than the continuous mapping method in terms of frequency diversity gain. In addition, when the residual frequency offset is relatively small, for example, when the residual frequency offset is smaller than 1.0 ppm, the general mapping method and the rotation mapping method show similar performances, but when the residual frequency offset has a relatively large residual frequency offset, for example, When the frequency offset is greater than or equal to 1.0 ppm, it can be seen that the rotation mapping method has a better effect than the general mapping method. This is a very advantageous effect considering that the larger the residual frequency offset, the higher the probability of becoming the worst case.

The interference due to the residual frequency offset from the neighboring subcarriers may be obtained by mapping the SSCs mapped to the neighboring subcarriers to different constellation domains by using the rotation mapping method as described with reference to FIG. 7. . Such an advantageous effect can be obtained by mapping to different constellation domains, such as in-phase components and quadrature components, without additional burden and without increasing complexity.

15 to 18 illustrate a Golay modulated by a Hadamard sequence when using the general cross mapping method, the general continuous mapping method, the rotation cross mapping method, and the rotation continuous mapping method described with reference to FIGS. 6 and 7, respectively. A graph showing the PAPR and CM characteristics for the case of using the sequence as the SSC.

It can be seen from FIG. 15 to FIG. 18 that all of the above four mapping methods show almost the same PAPR and CM characteristics. In other words, when using the continuous mapping method and the cross mapping method, both PAPR and CM characteristics are almost the same. In addition, when the general mapping method and the rotation mapping method are used, both PAPR and CM characteristics are almost the same. Therefore, in the case of using the Golay sequence modulated by the Hadamard sequence as the SSC, the PAPR and the CM characteristics are all the same even when the above four mapping methods are applied.

As another embodiment of the present invention, a sequence may be generated by differently including real and imaginary parts for each cell. For example, a specific cell may carry a sequence only on a real part and transmit it, and another cell may carry a sequence only on an imaginary part. Alternatively, the channel signal may be transmitted by applying different in-phase component and orthogonal component mapping rules for each cell. For example, in one cell, the sequence may be mapped and transmitted only to the in-phase component of the channel, and in another cell, the sequence may be mapped and transmitted only to the orthogonal component of the channel. As such, by using a different sequence generation method or channel mapping method for each cell, the amount of interference between cells may be reduced, or the diversity effect in constellation mapping may be obtained.

When applying an embodiment using a sequence consisting of a real part and an imaginary part, or an embodiment that maps a sequence into an in-phase component and an orthogonal component when mapping a sequence to a channel, a continuous structure or a cross structure is simply used as a general sequence combining method. It is the same in terms of computational quantity compared to the case, but it can be confirmed that more information can be transmitted.

In addition, since all subcarriers can be used, it shows better performance in terms of resource usage. In addition, better performance is expected in terms of interference average, frequency diversity, and long length sequence.

Furthermore, if scrambling is performed by the Golay sequence over the entire sequence consisting of the real part and the imaginary part generated by one embodiment of the present invention, the PAPR may be further optimized.

In addition, using embodiments of the present invention, it will be possible to obtain the effects of not only sufficient interference averaging, frequency diversity (in the case of OFDM) but also spreading gain which can be originally obtained.

The detailed description of the preferred embodiments of the invention disclosed as described above is provided to enable any person skilled in the art to make and practice the invention. Although the above has been described with reference to preferred embodiments of the present invention, those skilled in the art will be able to variously modify and change the present invention without departing from the spirit and scope of the invention as set forth in the claims below. You will know. Although the above-described embodiments have described a frequency hopping scheme that may be applied when transmitting an uplink data packet, a method similar to or similar to the transmission method described in the present specification may also be used for transmitting other downlink data packets. It is obvious that it can be used.

In other words, it is to be understood that this patent is not to be limited by the embodiments shown herein but is to be accorded the broadest scope consistent with the principles and features disclosed herein.

1 is a diagram for explaining an example of a two-stage sequence generation method.

2 is a view for explaining a method for generating a sequence as an embodiment of the present invention.

3 is a view for explaining an example of using a sequence combining method.

4 is a view for explaining an example of the 10ms radio frame structure proposed in 3GPP LTE.

FIG. 5 is a diagram for explaining an exemplary sequence combining method for SSC (Secondary Synchronization Code) of 3GPP LTE. FIG.

FIG. 6 illustrates a method of mapping an S-SCH signal using two or more sequences. FIG.

FIG. 7 illustrates a method of mapping an S-SCH signal using two or more sequences according to an embodiment of the present invention. FIG.

8 is a diagram for explaining a method of mapping an S-SCH signal using two or more sequences according to an embodiment of the present invention.

9 is a PDF graph of PAPR and CM, respectively, when a Golay sequence modulated with a 64-length Hadamard sequence is applied with one code.

10 to 14 are graphs of the results of applying simulation to the embodiments described above with reference to FIGS. 6 and 7.

15 to 18 illustrate a Golay sequence modulated with a Hadamard sequence when using the general cross mapping method, the general continuous mapping method, the rotation cross mapping method, and the rotation continuous mapping method described with reference to FIGS. 6 and 7, respectively. Graph showing PAPR and CM characteristics for the case of using as SSC.

Claims (20)

In a method for transmitting a signal based on a sequence in a communication system, Selecting one or more sequences; And Transmitting the signal by mapping the selected one or more sequences to one or more of an in-phase component and a quadrature component of a channel; Signal transmission method comprising a. The method of claim 1, Wherein some element of each of the one or more sequences is mapped to the in-phase component and the remaining elements of the sequence are mapped to the orthogonal component. The method of claim 1, One of the one or more sequences is mapped to the in-phase component, and the other of the one or more sequences is mapped to the orthogonal component. The method of claim 1, At least one of the selected sequence is configured by summing a first sequence and a second sequence multiplied by an imaginary unit (j), wherein the imaginary unit (j) is a number that is squared to -1. .). The method of claim 4, wherein At least one of the selected sequence is configured to multiply a third sequence and a fourth sequence by each of the first sequence and the second sequence. The method of claim 4, wherein And the first sequence and the second sequence are one of a homogeneous sequence and a heterogeneous sequence with each other. The method according to any one of claims 1 to 3, And the selected one or more sequences are mapped according to a sequence combining method when mapping the channels. The method of claim 7, wherein The sequence combining method is a method of mapping a sequence different from one sequence to the channel on a subcarrier axis, respectively. The method of claim 7, wherein And the sequence combining method is a method of mapping elements of one sequence and another sequence to the channel alternately with each other on a subcarrier axis. In the method for generating a sequence, Selecting a first sequence and a second sequence; And Generating a sequence by adding the first sequence and the second sequence, wherein the second sequence is multiplied by an imaginary unit j. And a imaginary unit (j) is a number that is squared to -1. The method of claim 10, The sequence may include one of a form in which a third sequence and a fourth sequence are multiplied by each of the first and second sequences, and a form in which a third sequence is multiplied by a complex sum of the first and second sequences. A sequence generation method. The method of claim 10 or 11, And each sequence element of at least one of the first, second and third sequences is a complex signal comprising at least one of real and imaginary parts. The method of claim 12, At least one of the first sequence, second sequence and third sequence consists of one of a scrambled sequence and an orthogonal sequence. The method of claim 10, And the first sequence and the second sequence are one of a homologous sequence and a heterologous sequence. In the method for transmitting a sequence-based channel signal in a mobile communication system, Selecting a sequence; And Transmitting a signal using both an in-phase (I) channel and a quadrature (Q) channel of the channel using the selected sequence. The method of claim 15, And the sequence uses two or more different sequences, and the real part and the imaginary part of the sequence each consist of different sequences. In a method for transmitting a signal in a communication system including a plurality of cells, Using one or more of a different sequence generation method and a sequence-based channel signal transmission method for each of the plurality of cells, The sequence generation method is characterized by generating a sequence by configuring two or more sequences in a real part and an imaginary part, The sequence-based channel signal transmission method is characterized in that for transmitting by mapping one or more sequences divided into in-phase components and orthogonal components of the channel and transmitted. The method of claim 17, Wherein each element of the sequence is a complex signal configured to include at least one of a real part and an imaginary part. In the method for transmitting a sequence-based signal, Selecting a sequence formed by summing a first sequence and a second sequence multiplied by an imaginary unit j; And Transmitting a signal using the selected sequence Signal transmission method comprising a. The method of claim 19, And the signal comprises at least one of a synchronization channel (SCH), a random access channel (RACH), a control channel (CCH), and a reference signal.

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