KR20010072845A - Method for transmitting information and suitable system therefor - Google Patents

Abstract

The present invention relates to a method for information transmission and a system particularly suited for digital transmission. At least one information signal consists of a reference frequency channel, at least one information frequency channel is generated, and thus the reference frequency channel and the information frequency channel each form a discrete state to generate a bit pattern. This allows the signal to be transmitted, for example, over a distance of several kilometers in water. Appropriate evaluation systems are also disclosed.

Description

Methods of transmitting information and systems performing the same {METHOD FOR TRANSMITTING INFORMATION AND SUITABLE SYSTEM THEREFOR}

In many technical fields, waves are used for transmission transmissions. It is, for example, electromagnetic waves or acoustic waves which propagate freely in a particular conductor or in a given transmission medium and pass from the transmitter or transmission unit to the receiver or receiver unit in this manner. If both units are tuned to a suitable frequency range or frequency provided for example for information transmission, the connection is established. Information can be transmitted in the connection in a number of ways.

To accomplish this, the initial information, which may be provided in a suitable manner such as speech, text, a series of numbers, music, image data, or other forms of data, may be converted or radiated from the transmitter to the receiver medium in the form of a wave signal. Is encoded. The receiver receives the signal, converts it back to the original signal, i.e. decodes it, and generates information corresponding to the initial information.

Depending on the type of information encoded in the wave, there is a difference between analog and digital information transmission.

In the case of analog information transmission, the transmitted value is converted into a continuous spectrum of phases of the physical state. This typically occurs in the form of amplitude, frequency and / or phase modulation of the carrier. This makes it possible to transmit vast amounts of information at a given time.

In the case of digital information transmission, on the contrary, there are limitations on specific discrete states. However, in terms of transmission speed, if electromagnetic waves are used, there is no limit until now because the frequency of the carrier is very high, and different digital states can be realized in a very short time.

In transmission media such as water, the transmission of information by electromagnetic waves is possible in a limited range since it has a small range. Therefore, there is a possibility that it can sometimes propagate at a very long distance in an environment using sound waves for information transmission. Sound waves can be modulated in the manner described above. However, sound waves are physical pressure waves that are efficient at transmittable information rates apart from the substantially lower frequencies and are different from general radio waves. For example, this propagation speed is highly dependent on the specific ambient conditions.

The big problem that can arise in the transmission of sound information can be simply illustrated by the transmission of voice signals under water. In the case of propagation in sonic space emanating from the transmitter, some waves may be banned or bent from the surface of the water and / or from the body of the water, depending on depth from various objects, particles, and even from the hierarchical heterogeneity in the water. Can be. Many other components of the sound wave will arrive at a receiver that has a different amplitude and phase relationship depending on the run length, the angular relationship and the acoustic properties of the constrained surface or medium involved. Depending on the result of the interference, the actual signal at the receiving point may suddenly be amplified, attenuated, distorted, or even entirely eliminated. Reception may also be distorted by being referred to as reverberation.

To illustrate this problem in more detail, the simple situation in which a very short signal of a specific frequency referred to as CWP (continuous wave pulse) is transmitted will be considered first. In this situation, the receiver can acquire the entire group of temporarily displaced individual pulses of different intensities in addition to the individual signals. This is referred to as the "channel response". In this case it is possible for the individual pulses to be distinguished on the receiving side, for example most suitable pulses are selected as "actual signals" (and thus other pulses can be referred to as "interference signals"), and long wave package transmission Separation of the nature of the poem is no longer effective since the receiver generally receives only the aggregate signal which may have the same frequency as the initial signal. However, interference signals and actual signals with different amplitude and phase positions are overlaid by unexpected variations in amplitude and phase positions. The above effects may make the evaluation of the signal different or even impossible in certain circumstances and are referred to as "symbol interaction". If the transmitter and receiver move in conjunction with each other, additional problems may arise in the form of frequency shifts as a result of the Doppler effect.

Many problems can make underwater communication very different by ultrasonic waves between divers and / or underwater vehicles and by remote control of underwater equipment. In particular, analog information transmission can be used very limitedly. However, this is the frequency used for speech transmission, and its use demonstrates that humans can identify well-known words and sense relationships even in reception problems for very large noise interference. By proper implementation and agreement in a limited vocabulary, the identification rate may be somewhat improved. However, this process is not suitable for transmitting computer data or other information by physical means, for example. Therefore, there is a need for suitable digital processing in the field of sound information transmission.

Current digital systems, in particular digital systems for underwater use, are based on the continuous transmission of voice signals of constant height located in rather narrow frequency bands. One application transmission is performed synchronously at high energy in the wide frequency band to achieve a greater likelihood range and also to exclude information loss due to the acoustic blind frequency range. Regardless of whether the transmission occurs in a narrow or wide frequency band, only serial "click" encoding allows for a limited data transfer rate, which allows for different transfers of large volumes of data, such as image transfers from underwater cameras. It also makes it impossible. In addition to the relatively large energy losses, this also means "acoustic pollution", and relatively "strict" systems have significant problems with the Doppler effect.

Apart from the distortion and loss caused by transmission techniques, significant differences exist when processing information contained in complex received signals in such a way that various types of interference can be screened out or eliminated, and the signals used to encode the information The parameter may be reconfigured at the receiving end. In the data transmission sector, there is no processing that can solve the above problem in a suitable and optimal manner.

The present invention relates to an information transmission method and a system suitable for information transmission.

1 illustrates the structure of an information signal that can be used in a method and system following an application consisting of a reference frequency signal and three information frequency channels.

2A shows the information signal of FIG. 1 subject to amplitude modulation.

2B shows a sequence of pulsed information signals.

3 shows a schematic diagram for encoding of an item of information.

4 shows the encoding of FIG. 3 including a parallel FGM.

5 shows signal analysis at the moment ti of the previous and next interference component by proportional FGM associated with three information frequency channels in harmony with each other.

Figure 6 illustrates the basic law of using signal analysis for an interference signal according to Figure 5 using a reference frequency signal and four information frequency channels.

FIG. 7 shows a schematic diagram using a stepped frequency shift that includes additional changes to the information frequency channel within a time pulse, such that half of the first pulse forms an additional horizontal reference for the RPDM.

8A shows a schematic diagram of encoding with only two frequency stages.

8B illustrates the principle of penal encoding of an information frequency channel.

9A and 9B show two different phase gradients generated by pPGM.

10 shows the different phase gradients that can be produced by nPGM (top) and pPGM (bottom).

11 shows the basic structure of the transmitter unit of the system according to the present application.

12 shows another basic structure of a transmitter unit including amplitude modulation of a system according to the present application.

Fig. 13 shows the basic structure of the transmitter unit of the system according to the present application according to the first embodiment.

Fig. 14 shows another basic structure of the transmitter unit of the system according to the present application according to the second embodiment.

FIG. 15 shows signal analysis at moment ti of before and after interference components by parallel FGM by reference to three information frequency channels that are in harmony with each other.

16 shows several diagrams illustrating optimal frequency spacing in different applications.

17 illustrates various embodiments of a sequence of processes that follow the present application for signal processing.

18 shows an example of a temporary change in the frequency component of a pVMT received signal, which includes one reference component and three information components under a near ideal transmission state (minimum intersymbol interaction).

19 shows the received signal according to FIG. 18 after transmitting the first information carrying the signal component at an intermediate frequency.

20 shows an example of the result of changing the channel response, where the intensities of the various spectral components of a given received component represent a substantially temporary variation.

FIG. 21 shows an example previously shown in FIG. 20 after passing through the sharp filter stage.

22 schematically illustrates a sequence of a basic embodiment of a process following an application in which a channel tuting procedure has been executed.

Figure 23 shows a very important processing step including different embodiments of the procedure for signal processing.

Fig. 24 shows the basic structure of the system according to the application for signal processing of the third embodiment.

25 shows the basic structure of a system following an application for channel tuning.

It is an object of the present invention to provide a suitable system and method for the transmission of information that enables high data rates over a large range.

Another object is to provide a method and system for the transmission of data that is associated with the cause of the referenced interference and can adapt to different transmission conditions.

In particular, it is an object of the present invention to provide a suitable system for signal processing that can be isolated and analyzed as far as possible from multiple channel responses with the maximal possible elimination of intersymbol interactions and a high degree of selectivity. Includes minimum transmission loss.

Another object is to provide a method and system for signal processing that can guarantee the best complete compensation for the Doppler effect in the same environment.

Another object is to obtain the best quality of signal processing, if available, to create a full state in this range, even in complex transmission conditions and when communicating with them underwater and for substantial increases in transmission rates. It is.

This object is solved by a technical procedure by the features of claim 1 and by a technical device by the features of claim 31.

Depending on the application, at least two signal components, at least one reference component (BK) transmitted in the reference frequency channel and at least one information component (IK) transmitted in the information frequency channel or (I1; I2; ...; IN An information signal consisting of) is generated, so that several frequency channels and components may each be used. By using it at the same time, more information units can be transmitted for time units. Discrete states can also be used for information components and information frequency channels that form a bit pattern in addition to the reference frequency channel and the reference component. As a substantial difference from previous radio technologies, no high frequency carrier waves are used in the case of the processing according to the present invention, and the low frequency waves are modulated. An information signal developed for information transmission is generated, which provides a wave comprising an overlay of at least one information frequency channel in addition to the reference frequency channel.

In the simplest case, to provide a bit pattern, the tones of a frequency or information frequency channel can be switched on and off, so that the presence and absence of the associated signal frequency component is binary information (on / off), i. It is evaluated as 0. In this way, bits can be transmitted for each of the information channels. The signal component produces a bit pattern and the information can be encoded in any desired manner.

When the simplest case described above relates to all parameters of the related information signal, it is possible to change so that different signal parameters in the on state can be identified in different digital states.

Another advantageous embodiment relates to the dependent claims.

According to claim 2, a temporary sequence of bit patterns is generated in a very simple manner.

Claim 3 comprises an advantageous basic variant, wherein the frequency channel forms a harmonic train.

If according to claim 4 a reference frequency channel is formed as a fundamental tone or fundamental wave, at least one of the information frequency channels is formed as a harmonic tone or harmonic wave for the fundamental tone or all information frequency channels are harmonic to the fundamental tone. If formed as a tone, the individual frequency and tone or signal components form a harmonic series and resonance system. A feature of the system according to the invention is that the basic tones can be transmitted permanently during the transmission of information with the lowest frequency having a large range and thus form a permanent bridge between the transmitter unit and the receiver unit in a speaking manner. The reference frequency channel designated as the base tone does not serve in this case for the actual transmission of information, but as a constant reference for the tuning of other frequency channels, if appropriate, will be proved later and for the determination of the relevant phase position, It will also be demonstrated for energy providers in the case of using nonlinear effects to increase the range of the entire frequency system. In this regard, it should be noted that instead of low tones, the desired tone of any other predetermined frequency spectrum will be used as the reference tone or base tone if more favorable in a particular environment.

The information frequency channel always determines that it has limited separation from the reference frequency channel, thereby forming all other active information frequency channels as base tones so that the known separation and proportional factors can be identified at the time of which the known receiver unit is known. It only needs to be side-by-side, and it is constantly tuned in a usable way. The above tuning process can be automated until the system can be transmitted without additional major effort on the widest different transmission state. The self-adaptive tuning of the information channel and the automatic identification of the base tones in some of the receiving units will be abolished, especially if the problems caused by conventional processing due to the Doppler effect will be abolished when harmonic frequency channel systems are used. Or a great advantage for communicating with it.

If, according to claim 5, the frequency of the reference frequency channel changes temporarily during transmission, it is not only by the receiver but also by the receiver in compensation for the frequency displacement (Doppler effect, etc.) where a constant readjustment basically occurs according to the above basis. Can be run from This also allows for a constant time change of the frequency spectrum generated in part of the transmitter unit without damaging the link to the receiver.

One or more frequency gradients may be provided if a time change in the frequency of the reference frequency channel is carried out stepwise or continuously according to claim 6. This method is referred to below as the frequency gradient method (FGM). In this way, for example, the result that the reflected or interfering signal is removed can be achieved. Variations of the reference or information signal based on the FGM are also referred to as VMT (variable multichannel transmission) hereinafter.

If the change in the component always affects each other proportionally, pFGM or pVMT is taken as the starting point, whereas in the case of variations of the component with parallel effect, paFGM or paVMT is taken as the starting point.

The use of FGM substantially makes it easier to achieve sharp and more reliable signals than in the case of conventional techniques, especially fixed frequency channels. In this case, since the operating frequency of the information frequency channel changes constantly, all signal components in the receiver unit along different transmission paths at all points given in time have different frequencies. Due to the above frequency difference, the actual information frequency channel is separated from any interference component that can be provided. That is, the inter-symbol interaction can be largely eliminated. If not, it will be reconstructed by the receiver according to the result of a clearer image of the information signal emitted by the transmitter unit.

In the case of FGM, the frequency of the reference frequency channel and the information frequency channel at a given proportionality can also be changed almost desirably, and the method and system according to the invention will be very flexible. Due to the arbitrarily induced frequency drift, mutual overlap of the various transmission systems can be avoided and undesirable eavesdropping becomes more difficult.

If other signal parameters were derived to generate the bit pattern in addition to the frequency of the information frequency channel and the reference frequency channel, the encoding is more complicated in the same way and thus the information rate is increased. If the information signal is amplitude modulated according to claim 7, the individual information frequency channels change at the oscillation node of amplitude derived for modulation over the time determined without interference interference known as "glitching" derived from the information signal. Can be.

If the bit pattern is generated in a given time pulse according to claim 8, it can be decoded by the receiver in a simple manner which increases the transmission precision.

If the beep pattern changes in a time pulse according to claim 9, the first part is used to identify which information frequency channel is used primarily for information transmission and to identify the use of the remainder for the generation of the bit pattern itself. It is possible to use. Also in this case, the first part provides another criterion with the help that the parameters of the signal component transmitted in the second pulse section can be determined with very high precision in addition to the reference frequency channel. In this way, the reliability of the transmission can be increased.

Advantageous embodiments according to claim 10 support the possibility of adapting to different transmission environments and user requirements.

For the measurement disclosed in claim 11, the transmission rate can be increased.

As a result of the high reception quality that can be achieved, in particular due to the use of FGM, the combination with switching on and off of individual signal components has already been disclosed or instead information can be encoded at a more detailed variation of a particular signal parameter or parameter combination. Can be. In addition to the frequency in the received signal, the amplitude and phase angle of the signal components have a finer reference to the natively generated signal, in particular all parameters can be integrated into the encoding. This can be done, for example, by a step-by-step change.

A substantial advantage of the process in this situation involves the fact that internal signal interference can be used for encoding. By virtue of the above relationship, a situation can be achieved in which the bit pattern or symbol can already be identified based on one or more received pulses without requiring additional reference to an external reference value.

Thus, for example, the phase angle can be determined in the form of a current relation of time pulses given between individual information components and BK. The above encoding method is simply designated as the relative phase angle method, RPWM (RPAM). In this way, the previous history no longer works, and external time loses importance for signal evaluation. Instead, the relative system internal time is given, for example it can be read out based on the cycle time at a specific moment in the BK, in each case following the current frequency. The relative phase angle can be determined, for example, in a simple manner in which all signal components, i.e., the information frequency channel and the reference frequency channel, are first normalized in one constant time as an evaluation method. But this is only to explain the principle. Since a large range of projection and transmission procedures are known from signal processing, they can be derived to determine relative phase angles. The user thus has a wide range for practical implementation. In the process according to the invention, depending on the result of the FGM and in particular the result of the pFGM, the range of interference effects can be eliminated, so that the relative phase angle can be determined with high precision, which means fine discretization, ie more digital It can be used to classify states and thus increase in information rate.

For example, in other fluctuating appendages, the information is not directly encoded in the phase angles of the individual components with respect to BK or GT, which is referred to as the vertical signal-interference criterion, but with the components of the last relative phase angle previously calculated and The difference between is referred to as the horizontal signal-interference criterion. The method is simply designated as RPDM, relative phase difference method. In the case of RPDM, in each case the first pulse of the adjacent transmission sequence operates only as a horizontal reference. Under very complicated transmission conditions, it is advantageous for RPDM to be used with the method according to claim 9. Conversely, it is sufficient to use only horizontal signal internal interference for the determination of the relative phase angle in highly desirable transmission conditions. In this case, the reference frequency channel can be used for information encoding. In the case of RPDM besides RPWM, the absence of signal components or undercuts of certain amplitude thresholds may include additional digital states.

If, according to claim 12, the number of information channels changes as a function of the transmission path, in particular a condition in which the distance between the transmitter unit and the receiver unit is reduced is obtained, and further typical high frequencies are used or other channels, e.g. Frequencies located between resonant frequencies are used, on the contrary, in very large spaces, very low frequency ranges are used. In this measurement, optimal utilization of the propagation characteristics of the wave signal is achieved, which is particularly important for the use of speech signals. In this way, a maximum bit rate and / or transmission distance can be provided which is difficult to achieve in each case, for example in an underwater environment. The above flexibility includes the principle that if a particular working range is adequately covered, then the specific transmission state can be adjusted in relation to the basic standard.

In addition to a particular state or presented criteria, the information in question may be encoded in a momentary time change, ie in a dynamic characteristic.

If the individual information frequency channels according to claim 13 are designed without overlapping into a wide band, the possibility of generating a continuous phase shift of the corresponding signal component and using it for information encoding is provided. The measurement is referred to as the phase gradient method, the PGM or the phase velocity method. The distance from the reference tone is typically associated with a characteristic curve of the mean value of that channel. The frequency of the individual information frequency channels at each time pulse during the information transmission can be shifted or slightly changed continuously within a given channel, typically a continuous, uniform or acceleration of each individual information frequency channel in relation to the reference tone or reference frequency channel. Depending on the result of the phase shift, the current reference value is less than 0.5%. The receiver unit not only recognizes whether a frequency is transmitted on that channel in a given time pulse, but also determines whether a frequency exists, and the relative phase angle and / or measurement parameters are a function of the current cycle time in the case of a reference tone or reference frequency channel. Its function is represented. Thus, in addition to the actual state or proportional value, a time change for encoding can also be used. From the above inference, a wide range of variations and combination possibilities can be used to increase the information transmission rate for large adaptation of the transmission system under the use of different conditions and for the optimization of the device and its cost.

For the simple handling and processing of the information signal, after reception the reference component is separated from the minimum value of one information component according to claim 16.

18. The process of claim 17, wherein the processes in the pair of signal components each carrying information allow for the compensation of the Doppler effect to each suitable or reference component. Depending on the results attached, this treatment step can also help prepare for the frequency stabilization treatment. In the case of paFGM, this step can lead directly to a stable, ie constant intermediate frequency configuration.

Another embodiment according to claim 18 guarantees the transmission of signal components at a constant intermediate frequency (Z1; Z2; ...; ZN + X), which may undergo different processing. The above advantages include the fact that a constant intermediate frequency (Z1; Z2; ...; ZN + X) can be located in the frequency window that is optimal for the next filter stage according to claim 20 and at the same time avoid the use of a particular sharp filter. Include facts that allow.

When using pFGM or pVMT, use of a heterodyne frequency that produces a constant intermediate frequency only by multiplexing of the signal received in the current time pulse by the received signal of the previous pulse as an alternative to the procedure according to claims 16 or 18 The possibility is maintained without and without prior separation of signal components. Variations in signal processing according to claim 19 are provided as a reference with the use of differential phase encoding.

The object of another embodiment according to claim 20 is isolated from the frequency stable spectrum of the various channel responses, and the signal optimal signal portion for each signal component minimizes the influence of interference from other signal portions in this state for filtering. The post procedure also includes the possibility that signal components in the sequence may be separated from each other if not implemented or completed according to claim 16.

For this purpose, in the simplest case, a specific filter can be used. In particular in each case components which do not require filtering, i.e. components which are not used for evaluation at the moment, are allowed. As a result, clear and detailed representatives are required for each of the information-containing signal components, which are based on the fact that the signal parameters (eg amplitude and / or phase position) used for encoding the information can be reconstructed in the best way. It also only represents the reference principle.

Of course, more complex methods can be used from known multifaceted repertoires of signal processing, but also provide them with the parameters involved in addition to the identification of signal components.

In another embodiment according to claim 21, the situation arrives at the fact that no error occurs during signal evaluation due to the processing procedure.

In another embodiment according to claim 22, for the current transmission environment, signal components and channel responses can be identified based on which signal parameters can be determined optimally, i.e. in the best way. As a result, the best signal component is present. That is, there is the highest value of energy at which the best possible quality of signal evaluation can be achieved. In order to filter the desired components as accurately as possible and to suppress possible sideband interference effects on other channel responses and optimum effects, the best possible filter settings can be determined by channel tuning. The latter contributes in particular to the extended reception radius and the increase in information rate. If a more reliable received signal can be evaluated, more possibilities are provided for using different gradients or even for different combinations of parameter changes for information encoding.

Ongoing updating of the filter settings and on-going identification of the most preferred receiving components can be achieved according to claim 23 even under varying transmission environments. The benefit in processing therefore lies in the fact that the interruption of the actual information transmission is not required for channel tuning.

According to claim 27, the above advantages are achieved when Doppler compensation is optimal.

The method according to claim 28 is used as a reference for processing received signals with heavy Doppler burdens, where each signal component is represented by only one channel value.

Other embodiments of the invention are described in the other dependent claims.

The invention is described in detail below with reference to the drawings.

Fig. 1 demonstrates how the information signal IS is composed of the reference frequency channel BK formed as the reference component, which is formed from the three information frequency channels I1, I2, I3 formed as the information component and the reference component formed as the basic tone GT. The information frequency channels shown in Fig. 1 are harmonics HK1, HK2, HK3 for the basic tone GT which form the information signal by superposition. It can be seen from the figure that each information frequency channel can be provided depending on the presence or absence of a binary digital portion of information equal to 1 or 0 (see also FIG. 2B).

The amplitude modulation in FIG. 2A shows the information signal IS of FIG. 1 to ensure steady and flowing transmission at the beginning and end of the pulse when the information signal is changed due to a temporary change in the information frequency channel.

The above change is shown, for example, in FIG. 2B, and the shape of the information signal changes from pulse to pulse, and thus in region I, the superposition of the base tone and the first and third harmonics (GT + HK2 + HK3). The configured information signal IS is provided. It constantly transmits to the base tone GT because there are no second and third harmonics in the next pulse (section II), and shows the changed information signal due to the overlap of the base tone and the first harmonic in the next pulse. The information signal corresponds to another encoded bit pattern (see section III). In this way it is possible to transmit one bit per time pulse in the respective information channel. It is derived from the one bit pattern above for each time pulse, and the information can be encoded in any desired manner. It generally depends on the number of available information channels and the function of the encoding system used or the number of other symbols to be encoded.

The criteria can be formed by the fact that direct compatibility is achieved by using several different channels of electronic data processing using 2,4,8,12,16 and more information channels.

In Fig. 3, for example, a method is shown in which the word "dolfilcom" is transmitted in a generally known ASCII code using an information channel. The frequency system for forming the information signal comprises four harmonic information frequency channels I1, I2, I3 and I4 as harmonics formed in the reference frequency channel used as the base tone GT and the channel temporarily changed by the proportional FGM. . The encoding is only operated by switching on and off of the harmonics. The horizontal lines in this case always show pulses of the same length. For each pulse, there is a spatial bit pattern designed as a symbol. In each case, the two symbols generate characters from each other in ASCII code. The letter "Dolphincom" is shown. However, other preferred codes may also be used for the encoding of the transmitted information, which allows for maximum user space for the strategy of own programming and makes the system compatible with almost all EDP systems. As shown in Fig. 3, the reference frequency channels change continuously, so that the frequencies of the four information frequency channels I1, I2, I3 and I4 are replaced proportionally. In contrast, FIG. 4 shows how the word “DolphinCom” can be transmitted using four information channels in an ASCII code, so that FIG. 4 changes the reference frequency channel continuously. However, the information frequency channel is first placed in harmony with the reference frequency, for example, and is always replaced in parallel with the change in the reference frequency channel.

5 illustrates how substantially sharp and more reliable signal analysis can be performed if the reference frequency channel changes continuously in terms of FGM. In the example shown in FIG. 5, three information frequency channels are selected by the embodiment based on FIG. 3, where the leading and trailing frequencies arrive at the receiver as interfering signals in addition to adding the actual signal frequency, respectively. Thus, each time shift is chosen equal to all three information channels. In order to clarify the underlying principle, the pulse display is omitted. The vertical dashed line (starting from ti) clearly indicates that all information frequencies received at a given time ti are different. However, due to the above frequency change, the actual signal frequency can be separated from the interference frequency, and the symbol-to-symbol interaction can be very largely eliminated if it is not complete. It is important that the amplitude and phase position of the received and "purified" signal components at the connection have a clear reference for the reference frequency channel. When using FGM, specific frequency filters can be used to separate the actual signal frequency from the individual interference frequencies. From Fig. 5, as the spacing of the signal frequencies from the interference frequencies becomes larger, the gradient df / dt of the frequency change becomes more inclined, i.e., the individual frequency ratio becomes larger. Since all information frequency channels in the system shown in FIG. 5 are always changed proportionally with respect to each other, a more inclined gradient is derived for the higher information frequency channel, thus better separation of the current signal frequency from the interference frequency. Is possible.

6 shows a schematic diagram of a system in which the above functions and effects in each case have four information frequency channels with two adjacent interference frequencies and one reference frequency channel. Dotted lines shown in Figure 6 represent the characteristics of commonly used filters. The constant window width of the filter for high information frequencies achieves better increased separation sharpness. In comparison with conventional processes, a noticeably better resolution is achieved overall. For processes that follow the application, it is a particularly high information frequency channel and is always strongly attenuated in the transmission stretch, resulting in a receiver with the lowest energy that can be released from noise. From the above process, an inclined frequency gradient can be selected for better separation in the case of an interference frequency which is located very densely at the actual signal frequency. That is, the drift rate of the frequency is increased when the flat gradient is sufficient compared to the large spacing. For the above adaptation a ready range of frequency shift patterns can be used or an efficient adaptation process of the gradient to the frequency change can be carried out. The latter is easily possible if the connection is used in both directions. That is, the transmitter unit can receive and the receiver unit can transmit. In this way, for example, analysis of the channel response behavior can be carried out and the pattern training can be carried out or the corresponding gradient can be varied between the transmitter unit and the receiver unit when the optimum gradient is set in each case for frequency displacement. However, if the interference value is very small, the gradient in the limited case in the appropriate fixed transmission state will be zero.

In the above connection, for pulse frequencies that change in proportion to the frequency level of the reference frequency channel, the possibility is principally included to maximize the transmission rate, which is the total to be analyzed for the individual components that contain only a particular oscillation time. This is because it requires a signal as.

Figures 7 and 8a, b show another possibility of causing a stepwise change in the reference frequency channel. This possibility is an interesting alternative to FGM if the transient change between the signal frequency and the interference frequency is large enough, for example in the range of several milliseconds. In this case, if all channels are replaced at the same time in a jump from pulse to pulse or at the same time in pulses that are high or small in several pulse steps but remain constant within the steps, efficient separation between signal frequency and interference frequency Can be achieved. In this case, it is advantageous to run as far as possible the frequency shift in such a way that the internal signal ratio is defined uniformly at all stages. This is easily accomplished by proportional or parallel staged changes. The above alternative is generally designated as frequency jump method or frequency step method FSM. 7,8a, b clearly shows how penetrating encoding of individual information frequency channels occurs by further relative phase encoding. To achieve this, and to increase reliability, a reference signal is transmitted to all information frequency channels at the beginning of each pulse, followed by the second half of the pulse with a properly encoded signal. 7,8a, in each case a distinction may appear between the five states, which are four digital stages with a signal (0) and an RPDM. Thus, a pulse having an information signal composed of possible combinations of 53 = 125 in three information frequency channels HK and reference frequency channels BK that can be used for encoding is derived.

8B shows the law of penal encoding of an information frequency channel. The point representing D4 in the reference characteristic D1 is the signal component, the amplitude of which exceeds the threshold Ao, four different phase angles F or four angle ranges can be digitally identified by RPWN or RPDM, and the threshold State D5, which is the amplitude of the signal component less than Ao.

Another method for encoding information is for example a phase gradient method or a phase velocity method. This is shown briefly in PGMs and is shown in FIGS. 9A, 9B and 10. 9A and 9B show what is referred to as the proportional phase velocity method (pPGM), and FIG. 10 further shows the relationship with the non-proportional phase-gradient method (nPGM).

The super coordinate principle of the PGM can be easily explained based on the following initial configuration.

A given starting point is a system in which the information frequency channels form a harmonic sequence, ie the frequency channels are executed only by proportional FGM. Any desired information frequency channel may be selected, but the frequency is transmitted at a given pulse interval, slightly upstream compared to the corresponding “reference frequency” (typically less than 0.5% of the reference value), not exactly as the harmonic of the GT. Or it is tuned downwards (see FIG. 10, top row). Basically, the frequency shift is carried out in this case, but at the receiving end is very small based only on frequency analysis, it is difficult to identify it as modulation, and consequently it is also not possible to interpret it as a digital state value. The frequency lies continuously in the sharp range of the corresponding analysis filter. As the GT is overlapped somewhat higher or lower than the reference value, the image shown in Fig. 9A or 9B arrives, and the relative phase angle increases or decreases continuously. The phase of the frequency of the information frequency channel precedes or remains behind GT. In that pulse, a phase gradient is created, the direction of which is already identified by the eye and at the same time can be determined without difficulty. In the evaluation of the phase gradient with respect to the time of the GT at a particular moment, a constant increase in the present case is derived. The prerequisite for the linear characteristic is that the initial characteristic is maintained in case of continuous frequency change of the entire frequency system, but can be easily changed at a given time. In other words, the relative detuning of the frequencies of the information frequency channels does not change with respect to GT. The performance of these conditions is clearly done by the destination pPGM, where a small 'p' represents 'proportional'. Considering the period, in the case of pPGM, a constant right or left rotation results in an information frequency phase relative to the phase of the reference frequency channel, respectively.

The above implementation can be used very advantageously for information encoding, because in signal analysis, the side of rotation, ie the direction of the phase gradient, can be determined more easily than the amount of phase shift, for example. In mathematical terms, this means that only the signal of the first choice of relative phase shift between the information frequency signal and the frequency of the GT should be determined. That is, it must be determined whether the relative phase velocity is greater or less than zero (see above in FIG. 10).

The above process can be applied to each of the time pulses for each information channel. If used in combination with simple switching on and off, the following is derived for each information channel at a given time pulse with respect to GT in four different discrete states. That is, 1. no signal, 2. a signal with a positive phase gradient, 3. a signal with a negative phase gradient, 4. a signal without a phase gradient, and thus can be implemented without a fourth state, if appropriate, which is 4 This is because the heavy encoding actually includes triple phase gradient encoding, and because one of the digital values is associated with a single speed value (zero), it cannot be reliably executed as a binary under certain circumstances. This problem follows a particular reception quality since all gradients at the transmit end can be generated with high accuracy as a rule. In theory, in any case, it is possible in the first example to double the information rate in each channel with respect to simple switching on and off, and in the second it can be increased by the third.

As an alternative to this, a large number of information frequency channels can also be saved, in which case the frequency spectrum is narrowed overall, and similarly there are several advantages. In this case, the transducer does not need to be wide-band in design, especially when the transducers are used in series, saving individual or several elements. This has the advantage of reducing the cost of the equipment, for example. On the other hand, for invariant device configurations, the large variability and adaptability of the derived system would be an advantage. For example, there is an option to increase the information rate by shortening the pulse time as a result of leaving low frequencies while suppressing high frequencies results in large transmission ranges. There is ample reason for the full range of efforts for possible cardinality, and also the information density in the information channel increases.

The pPGM can use different incremental encodings in the linear phase gradient in addition to the direction, which can be generated by detuning for different degrees of frequency of the information frequency channel, and thus of the discretization that can be achieved in certain cases. Depending on the degree, the combination and encoding probability are derived.

In combination with FGM a positive or negative phase gradient can be achieved by changing the frequency of the information frequency channel, which can be achieved by changing the frequency of the information frequency channel which is not carried out exactly in proportion to the change of the base tone (Fig. See below 10).

To identify it from the pPGM, the above variable is designated as nPGM, with 'n' indicating 'not proportional'. The nPGM is implemented such that, for example, the frequency of a particular information frequency channel is changed at a given pulse interval so that it is slightly faster or slower than provided by the fundamental variable of the proportional FGM. The variables of the PGM are all used in the optimum harmonic frequency series with the proportional FGM.

The basic principle of an optional method for the generation of phase gradients involves modifying the FGM proportionally to the extent that it can produce a small additional frequency gradient, typically linear, for each signal component even within a pulse. Next, different characteristics are obtained by distinguishing from pPGM in an overlay having GT instead of linear phase drift. That is, the direction and shape of the quadratic curve, which typically corresponds to the acceleration angular motion, follows the position of the start and end values of the individual frequency changes in relation to the reference value curve (see FIG. 10). In the case of nPGM, up to six configurations can be identified as a function of the cycle time of the GT, based on the symbols of the first and second derivatives of the associated phase angles. If two variables are adopted, a total of eight different symbol combinations are derived for the PGM.

However, other important properties of the nPGM can use the intersection of the reference value curve at the phase angle of the start or end value, or the mean of the RPWM, in addition to the symbol.

11 shows the basic structure of a transmitter unit for encoding information. The basic principle characterizes an information unit, which allows the information to be encoded at the encoder 3. The encoder encodes the information derived by the information unit into the encoding required for the frequency channel consisting of the reference frequency channel and the information frequency channel, and encodes the information frequency channel in the form of a medium for generating the reference frequency channel and at least one generator 5. Accordingly it derives the encoded information which is activated by the control module 7. The wave component is produced by a generator with a given amplitude, frequency and phase and passes through a mixer 9 activated by the control module 7.

According to the above embodiment, the information signal generated in the mixer is processed, if necessary, for the power amplifier 11 which processes the information signal in a converter or converter cascade and which is adapted to the transmission medium.

According to this embodiment a generator is provided for each frequency channel.

The embodiment shown in FIG. 12 of a preferred transmitter unit is shown in which amplitude modulation is performed on an information signal. To this end, the information signal is divided into individual components with respect to the reference frequency channel and before the information channel is led to the mixer, the signal is led to a modulator for each frequency channel, for example under the control and operation of the control module.

13 shows an embodiment of a receiver unit of a system according to the present application. The converter cascade adapted according to the converter or transmission medium receives the input information signal shown as the acoustic signal in FIG. 13 and induces it into the amplifier 23. Behind the amplifier is a filter 25 for the separation and analysis of the individual frequency channels, in particular for the filtering of the reference frequency channel. In the case of a low pass filter, the signal of the filter is directed to a reference frequency detector 27 which determines the reference frequency and the received strength. The above data is transmitted to the control module 29 of the receiving unit. In parallel, the information signal is selected before entering the low pass filter 25 and directed to a filter 31 which is controllable for the individual information frequency channels. The output signal of the filter is analyzed at the controllable threshold switch 33 and directed to a decoder which decodes the original information.

14 shows another embodiment, for example, showing a phase detector for a phase difference method or a proportional or non-proportional phase-rate method. For the analysis of the phase components, the phase detector 32 is arranged between the controllable filter 31 and the controllable threshold switch 33 and is arranged for reference according to the number of information frequency channels to be analyzed, thus determining the phase. For this purpose, the reference frequency is adopted as the reference in the elementary tone detector.

With respect to the preferred signal processing apparatus, further details are provided below on the basis of Figures 15 to 24 of different embodiments for signal processing.

The procedures that follow the application can be implemented in different ways and include two main basic functions that can be combined or applied individually as appropriate. The basic function can be designated as full Doppler compensation abbreviated as vDK and "channel purge" abbreviated as KR. These basic principles will be explained in each of the first examples before considering the possibilities for different technical and procedural variations and combinations.

1. Troubleshooting Doppler

To illustrate the basic principles of the vDK, a simple example is chosen from the first example. The lowest frequency channel here supplies the frequency and reference components of the information channel from the harmonic series. In other words, a complete numerical relationship with respect to the reference frequency is shown. If a change in frequency is made at the transmitter, it is by pVMT. At the receiver, all signal components are separated from each other in the first stage, for example by cascade of a band-pass filter (BPF). For simplicity, in the first example, it is assumed that the ideal transmission state is maintained, so that each component contains only the channel response, and all components can be transmitted and received at the same intensity. The above preferred state can be generated, for example, by propagation of electromagnetic waves in the air. The above example will be used first to illustrate how full Doppler compensation can be performed by a suitable process.

Doppler problems sometimes result in relative shifts between the transmitter and the receiver, for example because the speed of relative movement is not known precisely, which sometimes results in unpredictable frequency shifts. This also means that the phase position of the information signal can no longer be accurately determined, which means a significant limitation in all forms of information transmission using phase encoding. The above problem can be somewhat reduced by differential phase encoding, which is not a phase angle but a change from pulse to pulse, but is not basically solved. However, nearly 100 percent Doppler compensation can be achieved if the individual information components are processed in a suitable way along with the reference components. One advantageous solution involves a Doppler compensated pair by pair abbreviated with pDA, which can be implemented in different ways. One simple possibility is illustrated in detail in the following example.

For all other instances, the processing of the first information component is expressed in herr per time pulse, its frequency is f _ik and each velocity ω _ik is the corresponding value f _b and ω _b of the reference component. Twice. It is assumed that the received signal is provided in digital form, and the signal components send b and send ik coming from the transmitter have the following form.

Where N is the total number of scans made at a given pulse interval, n is the current number of scans at any given moment, ts is the length of time that scanning is performed, nts is discrete time, E is energy, and ωik is the starting phase Where ωinf is the angle of the information component used for encoding and the factor k represents the gradient of the frequency shift actively generated in the proportional VMT.

In general k may be any suitable time function, and may be positive or negative or even zero. The latter means that the use of constant transmission frequencies is a consideration in certain cases.

Since the phase position of the reference frequency at the transmitter does not change and no longer plays a role, the value in equation (1) is set to zero.

As a result of using Doppler, signal components are received and empf b and empf ik are distinguished from those transmitted by additional elements.

Where D is the Doppler coefficient, which includes the ratio of the relative speed between the transmitter and the receiver (positive signal in mutual approach and negative signal as distance increases) and the speed of the signal processed in the transmission medium.

Based on the underlined elements of the equation, the use of Doppler for the two signal components is closely dependent on the proportional factor and also represents the ratio of the corresponding transmission frequency. In the present example, the above proportional factor is equal to two.

Since the proportional factor is known, the exact amount of phase shift caused by the Doppler effect in the actual interval is no longer effective. In particular, if the reference component is in each case transformed in such a way as to obtain the same frequency characteristic as the information signal to be analyzed, then exactly the same Doppler shift is derived therefrom.

In the present example, such Doppler-error reference RF may be generated from the reference component by way of multiplexing itself. According to the multiplexing rule, it is derived as follows.

Filter out unnecessary sidebands After scanning with, we finally obtain the reference signal RF 'and differ in relation to the phase of the information component indicated in equation (S).

The fact that the phase angle of the information component can be determined allows the reference signal to be used to a certain degree as a signal-internal clock.

In a similar manner, it is possible for the criteria necessary in each case to develop from the reference signal for all other information components included in the received signal. The only condition is that multiplexing occurs multiple times and applies when filtering is needed. In general, the information components can be transformed in the same way and, for example, prove to be useful unlike the example selected here, and the frequency of the information components is located lower than the reference component or is not supported in their overall numerical relationship. . In the latter case, the same procedure can be applied such that one side of each pair is formed from reference and information components as often as necessary until the information is harmonized respectively. However, for each multiplex, the number of frequency components contained in the individual spectrum is multiplied by the product, and the result must be located in the channel so that as few steps as possible are required for Fairbypair Doppler compensation.

In general, one should carefully select all applications for phase-encoded signals with respect to the selection of the appropriate procedure for fair-by-pair Doppler compensation during the manipulation of information components that do not cause information loss due to ambiguous phase position, for example. .

Based on the examples given, the possibility of a method for determining the phase position of individual information components in a simple manner after the above-described signal processing will be described. To this end, for example, a breakdown of the corresponding information component can be executed in the quadrature function of the reference signal Rf '[n], which is described below.

In the above example, since the reference Rf '[n] has already been provided in the form of cosine, it can be written as follows.

RfC [n] = Rf '[n]

The sinus square component RfS [n] can be obtained, for example, by formation of the corresponding mean of amplitude and the first derivative of RfC [n].

Currently, the projection of the information component is recorded in the reference cosine square component.

Where N1 is the start and N2 is the end of the individual pulse.

In terms of the fact that the function value is oscillated around zero value in the second singer, the positive and negative portions are totally reserved. Thus the element generally goes to zero value and can therefore be ignored without significant error.

Thus, for the projection of the information component received as the reference sine square component, the following is derived.

Then, CQ and SQ are regarded as x and y points, respectively, in the right angle coordinate system. The connecting line between the point and the origin and the horizontal axis includes a phase angle sort Θ. This can easily be determined with a suitable algorithm. Exemplary representative forms are as follows.

The phase of the received information component appears as the difference between the start phase and the encoding phase of the transmitted wave. That is, in each of the pulses, it is invariant with time. To complete, the phase difference between the preceding pulse and the current pulse can be used for encoding. If the phase is designated by the index i or i + 1 respectively, then for differential phase encoding is calculated as follows.

Inferring, it is possible to determine the phase position of another information component for each time pulse with a high degree of accuracy. This in turn provides the user with fine discretization of the phase angle and hence increase in information rate. The above method related to phase angle determination is generally referred to later as CS projection.

The vDK in particular forms the basis for the process according to claim 28. Fig. 23 is an overview of the most important elements of the flow chart of the vDK. This may be applied in a manner similar to that of the other embodiments described above.

2. Channel Purification (KR)

KR includes the identification of the best channel response with separation for signal technology and simultaneous minimization of intersymbol interactions. Next, you can include partial Doppler compensation, which can already be extended to a series of applications.

The Doppler effect can no longer actually work, but it can be assumed that reception can be compromised by superposition of several channel responses. The transmission state frequently communicates acoustically with or between slow moving or stationary objects under water. Each signal component is represented by a full spectral channel response (see schematic diagrams in FIGS. 5 and 17A). Processing along with the application should ensure that symbol-to-symbol interaction is minimal.

In the results of the VMT, different channel responses arrive at receivers with different frequencies, but in practice it is not possible to filter the most desirable channel responses from the connected spectrum, and at the first stage of each component, most of them are very close to each other. This is because the frequency is not fixed (see FIG. 18). It is also difficult for the transmitted bandpass filter to be adjusted precisely enough. Initially it was assumed that the corresponding spectra of the reference and information components could be separated from one another (see FIGS. 17B and 17C).

After multiplexing of the reference component by each information component (FIG. 17D), two spectra are obtained at each intermediate frequency, which are different values and operate at different speeds (FIG. 17E). For example, there is the possibility of filtering each of the lower frequency bands by a lowpass filter for subsequent processing. For example, because sufficient computing capacity can be used, if the second sideband does not cause interference, it can also move. That is, the filter stage can be removed.

In the next processing step, the minimum value of the other frequency band is multiplexed by the auxiliary frequency generated in the system (Fig. 17F), and the characteristic is selected in such a way that a part of the second intermediate frequency is set according to the multiplexing result. That is, the frequency associated with it will not undergo any other temporary change (FIG. 17G).

The characteristics of each individual auxiliary frequency (H1; H2; ... HN) may vary depending on the tuning or transmission channel (see below for channel training) whose behavior is consistent or determined between the transmitter and receiver for the signal structure used to transmit the information. It is derived from one of the tunings determined in the sampling configuration and is executed at the beginning of the information transfer.

19 shows that the stage can also separate only the reference component from the information component in the first instance. By selecting the appropriate heterodyne frequency, the frequency of the information component can in each case be provided for processing to stabilize (currently the first). The first advantage of the procedure is that by means of the heterodyne frequency the desired portion of the appropriate frequency is always located in a limited window so that it can be optimally filtered by a fixed filter such as a lowpass filter (FIG. 17H).

20 shows that since several different channel responses are represented as substantially different at different times, for example, one cannot make any reliable frequency according to multiple channel responses based on the appropriate intermediate frequency of the phase position. It is closely related to the implementation.

The second filter stage is thus inserted in the processing of the ongoing channel training procedure (see description below), and the best possible separation sharpness was set for each component for the strongest channel response as a whole. The dashed line in FIG. 17H shows that the outside of the filter can be set very steeply. As a result, the influence of other channel responses can be minimized in the best way (FIG. 17I).

FIG. 21 shows that it is very closely related to the actual implementation that, as with the variation of FIG. 20 in the result of sharp filtering processes from multiple channel responses, a certain selection can be made and the influence of other parts can be suppressed. The overall process described in the above connection can be specified as partial Doppler compensation and channel refinement.

Parameter determination

The signal components are refined to the maximum possible extent of the interference channel effects thus processed and subject to detailed parameter analysis. In this environment, in addition to the phase of the signal portion carrying information, the amplitude can be determined with the maximum possible precision and reproducibility. Different amplitude values can be differentiated, for example, in the same way as threshold switches. If C-S projection is performed to determine the phase angle, the necessary reference oscillation can be artificially generated if appropriate. The latter is not technically a problem because the system recognizes the setting of the last (sharp) filter stage and hence the frequency of the signal portion carrying the information. However, depending on the type of encoding used, it is possible for the user to choose the best from a wide repertoire of known algorithms.

In the form described above, KR can be used for reference with pVWT (see FIG. 5). However, it can be adapted without any problem with paVMT (see FIG. 15). In the case of paVMT, multiplexing of the reference and information components directly results in a steady intermediate frequency, and if appropriate, multiplexing with an auxiliary frequency becomes superfluoresced. This intermediate step must meet the above objectives in order to replace the frequencies associated with a particular filter window, which in each case can be easily carried out by multiplexing by a constant auxiliary frequency. However, this is for the above description.

KR is therefore suitable for all types of VMT where the gradient where the frequency change is actively generated is not zero. In order to identify the above mentioned parameters and the next correction, they will be designated KR1. The above-described embodiment of the process according to the application forms the basis of claim 18. The most important element of this basic variant is described again overall in FIG.

The above-described modification of KR can be changed, for example, in such a way that the reference and information components are not first multiplexed by each other. In this case, the construction of a suitable intermediate frequency is generated directly in one step by the multiplexing of the individual signal components having a suitable auxiliary frequency. The above procedure provides the advantage that the spectrum of the appropriate intermediate frequency does not have more elements than the receiving component. In each case (channel refinement), after filtering the best channel response for each component, information is always present along with the criteria by the analogy described by vDK or to achieve partial Doppler compensation with the cosine and sine components of the refined reference signal. Has the possibility of processing the signal part carrying the. For reference, the frequency adaptation can be carried out after the conclusion of the last filter stage or during the multiplexing to the appropriate auxiliary frequency by multiplexing the appropriate and constant auxiliary frequency if necessary. In the second instance, the reference component only needs to pass through the filter.

Advantageous embodiments are derived by the modifications described in the preceding claims. A roughly simplified sequence scheme is designated as KR2 in the entire representation (FIG. 23).

However, if the Doppler effect does not do anything, the reference components are directed left together or used as additional information components. In this case only KR2 is useful. Parameter determination should be carried out in an analog manner for the procedure described for KR1.

For the sake of completeness, a criterion for an optional solution should be made at the start, but it does not appear vivid and, for example, a moderate intermediate frequency step in the framework of pVMT is also transferred only by the multiplexing of the signal received in a sequential pulse. Can be achieved without separation. The step similarly includes partial Doppler compensation. The feature of this case is that since the spectrum of the appropriate intermediate frequency of the associated channel is located in separate windows according to the frequency stroke, they are located in close proximity to each other in large numbers. Due to this transmission, a very complex signal structure is obtained. In particular, if very large numbers of information channels are used, care must be taken to avoid possible overlap of the vector products. Cascade sharp filters can be used to separate the channel response.

Finally, a description of the filter system is made, along with the criteria that show the basic principles of the procedure. Indeed, it can be appreciated that more complex methods of signal processing and signal analysis are used, with the potential including operational stages described in similar or different forms. In any case, the principle is the same.

The perfect answer

The basic principles of the technical procedure for full Doppler compensation and different variations of channel refinement have been described separately (including some Doppler compensation), and instances of the application will now be considered, in which case the reception may be by multiple channel responses or Hindered by strong Doppler effect. Combinations of the above interference elements, for example, are difficult to communicate with or between objects moving under water.

For this situation, possible solutions include, for example, combining both vDK and KR2.

Separation of the reference and information components is first described by the vDK, then Doppler compensation executes the pair-by-pair. This is possible as long as at least one of the signal components considered in the pair, or both, if appropriate, are transmitted in a suitable manner, which is a characteristic in which the characteristics have exactly the same frequency cycles and therefore equally heavy Doppler burdens. Optionally, sidebands that are not needed are each filtered and the remaining reference signal is filtered again.

Both components are each multiplexed by multiplexing, typically with the same auxiliary frequency (with the same gradient as the relevant component, but replaced approximately simultaneously), thus transmitted at the appropriate intermediate frequency and in each case being passed to the next filter stage for purification. Subordinate For this purpose, the sharp filter can be adjusted for each component, if appropriate. In an ideal situation, the relevant filter settings may be considered in the fine tuning of the referenced auxiliary frequency.

As a result, a signal refined by the highest inter-symbol interaction, i.e., a signal for reference in addition to the information component, is respectively obtained. After the above "purification" (including threshold analysis, if available), parameter determination is carried out, for example in accordance with the procedure described for vDK or KR2, and pairs of individual information components on the basis of the included criteria. Full Doppler compensation is achieved by the bipair procedure.

Embodiments of the processing according to the above-described application form the basis for advantageous embodiments of the processing according to claim 8. In FIG. 23 this was designated Komp.1.

Another possible solution includes a suitable combination of vDK and KR1 (simplified representation of the sequence plan of Komp1.2 in FIG. 23).

In this case, after separation of the information component and the reference, fairby pair Doppler compensation is performed next. Thereafter, one of the two components is replaced in parallel by an appropriate amount and is made by multiplexing by the auxiliary frequency generated in the system, but in this case it is constant. Both partner components are then multiplexed in turn. Thus, the processing stage shown in Fig. 17G, i.e., the planning of the appropriate intermediate frequency, is reached. Processing then continues with parameter determination following two filter stages and KR1.

The second complete solution involves the fact that the effect of frequency substitution caused by the movement by the projection of the information component on the same Doppler basis is completely eliminated. However, this results in the criterion being "used." But this is no longer necessary. The main advantage of the process lies in the fact that only one constant auxiliary frequency in the system needs to be generated in order to ensure that the desired sidebands of the appropriate intermediate frequencies are correctly positioned in the optimal frequency window for filtering. In most preferred cases, the same frequency as one frequency can be used for all component pairs. In principle, the possibility of using said auxiliary frequency arises from "purification" as a reference for phase analysis. However, since the actual effect is created to adjust the sharp filter for each signal component (in this case, the corresponding combination of individual information and reference components is already combined), the filter settings are known in the system and if phase If necessary for analysis (see KR1), accurate matching criteria in the system (including sine and cosine square components) are possible without the problem of artificially generating the criteria.

Channel training and channel tuning

The channel training technique already described several times first ensures that the signal structure best adapts to the transmission state in each case based on the appropriate test signal, and also ensures that the receiver can always perform component separation as needed. If the previous state is realized, channel tuning is carried out, which is absolutely understood to include variations involving all other channel refinement processes in addition to the process according to claim 1. For this purpose, the choices that can be used are used to transmit a rather long signal without encoding, but already have the features provided for signal transmission. In this case, when the user determines whether all frequency channels will be used at the same time or when channel tuning is to be performed based on the test signal, each in turn includes a reference component and one or more information component (s). Each procedure must, of course, coincide with variations in the selected signal processing procedure. The test signal operates through all the processing stages provided at the relevant strain leading to the formation of a suitable intermediate frequency. At this level, analysis is provided for the assessment of the energy density distribution in a given frequency spectrum (or components, respectively, mixed from individual information and reference components). For this analysis, FFT can be used. Based on the evaluation results, the best appropriate channel response (typically the maximum energy) is each selected and the best possible settings of the "sharp" filter are performed and stored. Once the relevant settings for all components have been determined, the actual information transfer can begin. The filter setting is maintained until the next channel tuning.

Especially in the case of acoustic data transmission under water, the transmission status is often not temporarily stable. In this case, one possibility is to repeat at least channel tuning at appropriate time intervals. That is, update the Sharp filter's settings on a certain basis.

The use of long encoded signals for channel tuning provides efficient statistical reliability, but also means that information transfer is simply interrupted in average time. Such interruption can be avoided. One optional advantage is provided to understand the process according to claim 23. In this situation, on the basis of the received progress signal, while the data transmission is performed in conjunction with or as part of a signal processing procedure, the reception result of several pulses is appropriately integrated for calculation. The above alternative solution basically imposes significant requirements on the evaluation system.

Determination of relative speed between transmitter and receiver

Instructions may be derived from the received signal that may aid in the current change in distance between the transmitter and receiver. Signal processing following the above-described procedure aims at reconstructing (transmission) parameters (particularly phase angles) for each signal component in the best manner. To achieve this the components are aimed at being treated with each other in such a way that the Doppler part is removed. This is treated as an interference value. The Doppler portion above contains information items in the form of Doppler coefficient D = v / c (see FIGS. 4 and 5) that are not critical for actual data transmission but can provide an indication of the relative speed v between the transmitter and receiver at a particular moment. Include. Doppler coefficients may be determined by suitable signal processing methods. The speed c of the signal propagation can be schematically known or measured in the frame of the channel sampling, and v can be determined or estimated with relatively high precision.

As an example one possible solution may be outlined.

To this end, any desired receiving component (uncoded reference component) can be derived. If necessary, this can in turn be derived separately along KR2 for the channel response. Since the signal structure used by the transmitter is known to the receiver and the phase position can be determined according to one of the preceding procedures, it is possible to generate an amplitude-standardized reference signal within the system. It can compare the reception component related to frequency characteristics and phase position besides the Doppler portion, which is not actually known. After projection of the receiving component into the sine and cosine components of the reference and filter LPF, the pure Doppler portions are obtained in a simple form of sine and cosine oscillation, each having the same amplitude. The arctan function applies a declination Dωnt _s . Since D omega n _s is known, division D is derived, D is multiplied by c and the final low v is obtained (see Doppler arrangement of FIG. 23 for a schematic sequence layout).

It would be advantageous for many applications if the above advantageous additional information could be obtained without further measurement effort.

Recognition of the Doppler portion will also contribute to the improvement of the actual signal processing. Therefore, the auxiliary frequencies generated in the system within the frame of the KR can be more accurately tuned to the structure of each individual receiving component, reducing the unwanted Doppler effect in actual signal analysis in a better and simpler manner. If it can be used by the integration of the measurements and by repeated applications, at least a temporary processing optimization can be achieved in addition to improving the evaluation results, which reduces the inevitable rapid data growth due to an increase in the Doppler resistance. The intermediate filter can be removed, and the sequence as a whole can be faster. At the heart of the process, all the pluralism is the benefit of online assessment. Even if Doppler evaluation requires additional effort, it can be saved in its entirety, because the core routine of signal processing can be managed with less hardware and software capacity if appropriate.

In addition, if the information on the current Doppler shift is provided in the form already prepared by the external measuring system, the above-mentioned improvement and the simplification of the process according to the present invention can be implemented in a simple manner.

In Fig. 24, the basic structure of the signal processing unit is shown. The basic principle characterizes a filter unit, which is composed of two filter elements BPF1 and BPF2, which can be connected and controlled in parallel and divides the received signal into reference and information components.

The two signal parts are first led to a converter unit comprising converter 1 and converter 2 along the medium for frequency change. Doppler compensation here generates payby pairs before the two parts are refined by multiplier 1 for transmission to the appropriate intermediate frequency by the heterodyne frequency carried by the generator or by the appropriate auxiliary frequency.

For the medium for the superposition of interference elements, the embodiment consists of a filter LPF1 and a first instance of a second filter, if appropriate, in this case connected downstream of the multiplier and the filter eliminates unnecessary sidebands. . Next, with the sharp filter BPF3 connected in series, the reading of a signal part occurs optimally, respectively. Parametric analysis is then passed to the medium for the parameter analysis module in this embodiment. If necessary, the parameter analysis module can be supplemented by a generator for a reference signal connected to BPF3.

The signal parameter for encoding is output at the end of the processing unit for each information component.

25 illustrates a basic arrangement for channel tuning that can be used to advantage in the same environment. By difference from FIG. 24, the signal components of the above embodiment are guided along the LPF2 to form a module for analysis of the frequency spectrum and a unit designated as 3 is directed to the medium for tuning to form an evaluation. This result is driven to the control module and starts to set the optimum filter for each BPF3.

The possibilities or applications and systems of the process according to the invention are described in detail below.

As another option, in the above process, it is possible to use without any problem for other frequency channels due to the reduction of the distance between the transmitter and the receiver. It can lie between the original or even higher frequency channels or replace the entire spectrum in the direction of the higher frequencies. In this situation, it is possible to use the weakening of the interference effect also with the decrease in the transmission distance. To achieve this, the transmitter and receiver need to be designed to understand a wide frequency spectrum and be equipped with the capacity to convert the encoder. In some of the receivers, the recognition with the new input frequency can be carried out automatically or a change to the new mode of operation can be informed to the receiver by the transmitter in a suitable manner (e.g. the last information package). The individual tone channels should be far enough apart from each other so that they can easily distinguish the transmission state from the receiver. On the contrary, due to the increase in distance, it is necessary to shift the shift of the entire spectrum with an increase in the distance between the channels by the proportion of omitting or dropping low frequency or upper channel surrenders or even intermediate stages.

The previous selection of frequency bands aims to achieve a complete batch of energy, preferably a full number multiply (harmonic) of the tones or tones whose frequencies are resonant or lower in the fundamental variation of the process.

By using the harmonic frequency series, the possibility of using the nonlinear effects of the propagation of speech is provided, as is the signal transmission obtained at significant distances. Sound waves are vertical waves, and sections with high and low densities are optional. However, since the speed of sound waves depends on the density of the medium, the dense parts spread faster. Since the flank of the original sinus oscillation becomes progressively asymmetric, that is, the sinus oscillation will be further transformed into, for example, tooth oscillation. In physical terms, this means that energy is transferred to the harmonic. In water, the above effect can be recognized after passing several kilometers. If more than one harmonic is transmitted in the base tone, each receives additional energy in deep tones due to the harmonic relationship due to nonlinear effects. As a result, they are attenuated very quickly and remain long beyond the level of fundamental noise, thus achieving a large range of use. Since the range of the system as a whole is determined in the first instance by the highest frequency band respectively, a large transmission radius is achieved overall. For this purpose the base tones must be permanent and all other tones must be transmitted in high energy. Due to the high variability of the system, other characteristics of the transmission path can also be used. For example, as a result of the layer imbalance of water, specific transmission channels with their oscillation characteristics are formed. Depending on the characteristic eigenvalues involved, different modes can be easily stimulated, and as a result can be relatively low but carry very far in compensation. In principle, the possibility appendages of the frequency bands of the transmission system are tuned in this mode. In addition to this, the transmitter and receiver should be understood to each other in a suitable manner.

If the relative speed between the transmitter and receiver is very low, the Doppler effect can be neglected and a uniform frequency change for the entire system can be implemented as a choice for the previously referenced proportional FGM. In this case, the "melody" represented by a particular "offset curve" or image item is in each case determined or specified after analysis of the particular transmission state. And all frequency channels are added to it (see FIG. 4). This method is expressed as a parallel FGM. The feature of the method is based on the fact that the same gradient is always derived for all frequency channels, ie the same drift rate as a result in an ideal state. Optimal separation of the actual signal of the interference component can be achieved over the entire spectrum. The modified method in this way also has the advantage that the frequency spectrum is increased at the reference frequency and is not spread. Due to the more bundling, the top tone does not easily cause the risk of sliding into a frequency range with a very small propagation radius and is thus cut out. The upper frequency range can be used efficiently and is faster in terms of information transmission. Parallel FGMs are more easily achieved because transducers can often operate in a limited frequency band and the use of the corresponding converter cascade is not always possible.

In general, in the case of a parallel FGM, the receiver will be informed in an appropriate manner as to how it can be tuned to individual frequency channels in relation to the GT (base tone). In principle, the switchover between proportional FGM and parallel FGM does not have any problem as it involves only a change between multiplication and addition for frequency tuning of the information frequency channel.

In the case of phase jumps that cause problems in pulse transmission, the pulse related amplitude modulation described above can be used. Another method of minimizing the impact of interference involves providing a tone in two consecutive pulses in the information channel. The same effect can also be achieved by multiplexing, for example alternating operation of even and odd information channels. As with many other parameters, the frequency-related speed characteristics of individual transmission channels can be determined by specific sampling or in the course of intercommunication, and must be taken into account when generating signals.

The reference frequency channel can be used as an additional information channel if necessary and if a particular transmission state allows it.

Claims (47)

In the method for transmitting information, Generate at least one information signal IS consisting of a reference component BK and at least one information component I1; I2; ..., IN; Said reference component (BK) and said information component (I1; I2; ...; IN) in each case form a discrete state for providing a bit pattern. 2. A method according to claim 1, wherein said at least one reference component and said at least one information component continuously change frequency with respect to time during information transmission. 3. A method according to claim 1 or 2, wherein the frequency interval can be constant over time or change over time. 4. A method according to any one of claims 1 to 3, wherein the frequency of the at least one component increases continuously at transmission intervals. 5. A method according to any one of claims 1 to 4, wherein the frequency of the at least one component decreases continuously in the transmission interval. 6. The method of claim 5, wherein the gradient of the frequency change is adjusted by a position function of the interference frequency for the individual frequencies of the components to minimize inter-symbol interactions to prevent mutual overlap of the various transmission systems. Way. 7. A method according to any one of the preceding claims, wherein the initial frequency of the component varies at every transmission interval. 8. A method according to any one of the preceding claims, wherein the range in which the frequency varies, i.e. the frequency bands for two or more components, overlap. 9. A method according to claim 8, wherein at least one component of the component, in particular the minimum reference component (BK), is arranged in a separate frequency band. 10. A method according to any one of the preceding claims, wherein the bit pattern is determined by a change in frequency, amplitude and / or phase angle of the dynamic phase characteristic in a given time clock. 11. The method of any of claims 1 to 10, wherein the bit pattern changes within a time clock. 12. A method according to any one of the preceding claims, wherein the number of information elements (I1; I2; ...; IN) varies as a function of the transmission path. The method according to any one of claims 1 to 12, wherein the reference component (BK) is used as an additional information component (IN + 1). The method according to any one of claims 1 to 13, wherein the reference component (BK) and the minimum information component (I1; I2; ...; IN) are formed as acoustic waves or electromagnetic waves. 15. The method according to any one of claims 1 to 14, wherein in order to process the information signal after reception, the reference component (BK) is separated from the minimum information component (I1; I2; ...; IN). How to feature. The method according to any one of claims 1 to 15, wherein the reference component (BK) and the information component (I1; I2; ...; IN) are processed in pairs. 17. The apparatus according to any one of claims 1 to 16, wherein the information component and the reference component, or the reference component and the information component processed in pairs, have an auxiliary frequency (H1; H2; ...; HN + X). Multiplied by and transmitted to a standing intermediate frequency (Z'1; Z'2; ...; 2'N + X). 18. The method according to claim 16 or 17, wherein in relation to the proportional change in the frequency channel, the standing intermediate frequency is formed by pair processing, in particular by multiplying a signal received with a preceding pulse and a current time pulse. Way. 16. The method of claim 1, wherein the execution time difference of the multipath portion included in the received signal is individually as a function of the rise of the frequency gradient used in the transmitted signal after the transmission to the standing intermediate frequency is expressed in the form of a frequency difference. Used as; From the spectrums of the standing intermediate frequencies Z'1; Z'2; ...; 2'N + X, an optimum signal component is respectively selected based on the filter arrangement and / or the relevant information parameter is determined by the signal. Characterized in that it is determined from the components. 20. The method of any one of claims 18 to 19, wherein channel tuning is performed at specific time intervals. 21. The method according to any one of claims 17 to 20, wherein during the transmission of information, the identification of the best receiving component and / or the update of the filter settings is performed based on an appropriate analysis of the spectrum of the standing intermediate frequencies, the result of which is Continuous channel tuning without interference of actual information transmission. 22. The method of any one of claims 17 to 21, wherein the transmission induced Doppler frequency shift is determined internally of the system, taking into account the generation of an auxiliary frequency. 23. A method according to any one of claims 17 to 22, wherein in each case said treatments are performed in pairs based on internally generated components with appropriate frequency characteristics. The method according to any one of claims 17 to 23, wherein a) The reference component BK is transmitted to the converted reference component BK ', and the at least one information component I1; I2; ... IN is converted to the converted information component I1'; I2 '; ...; IN '); b) the signal parameter related to the information encoding is based on the projection of the transformed information component I1 '; I2'; ...; IN 'to the sine and cosine components of the transformed reference component BK'. It is determined by the method. 25. The method of claim 24, wherein the reference component is transformed by converting the information component to be processed in each case into a Doppler equal reference component (RF) such that the product of the two components generates a frequency stable signal. Way. The method of claim 24, a) the transformed information components I1 '; I2'; ...; IN 'are multiplied to generate a first value CQ; b) the transformed information component (I1 '; I2'; ...; IN ') is multiplied by a reference component (RF) derived in time to generate a second value (SQ); c) a correlation is formed between said first value and said second value to obtain a final value that is invariant with respect to time, which is only affected by an information parameter invariant with time. 27. An information transmission system designed to carry out the method according to claims 17 to 26 and further comprising a transmitter and a receiver, wherein an information signal (IS) is transmitted between the transmitter and the receiver. The transmitter processes the reference component (BK) and at least one information component (I1; I2; ...; IN) to continuously change frequency with time and to provide a bit pattern; The receiver comprises means for obtaining an information signal IS consisting of at least one information component I1; I2; ... IN; and one reference component BK, wherein the at least one component A system characterized by continuously changing frequency with respect to time. 28. The method of any of claims 17 to 27, wherein the transmitter is At least one generator for providing said reference component (BK) and said at least one information component; A first control module connected to said generator for determining a frequency response; An encoder or modulator connected to the control module for converting the information by signaling means; The generator and a mixer underneath the encoder or modulator. 29. The apparatus of claim 28, wherein the receiver comprises at least one input, one processing unit and at least one output, the processing unit separating and converting the signal components and transmitting them at a standing intermediate frequency, intermediate Means for separating or suppressing portions and means for parameter analysis. 30. The multiplier according to any one of claims 28 to 29, wherein said separating or converting means comprises at least one multiplier for multiplying a minimum information component (I1; I2; ...; IN) and the reference component (BK) in pairs. Wherein the multiplication forms a spectrum of standing intermediate frequencies, and the means for suppressing the interference portion comprises at least one filter unit, wherein the filter unit filters the desired signal portion for the parameter analysis for parameter analysis. System for delivery to. The separating means comprises a filter unit having a control module connected to the top of the multiplier and including at least one filter element connected in parallel, wherein the at least one component is initially separated from other signal parts. System. 32. The apparatus according to claim 31, wherein said separating and converting means comprises: an additional multiplier for transmitting said signal component within a predetermined range of a standing intermediate frequency by a frequency invariant intermediate stage, in addition to a multiplier for processing BK and IK in pairs; System comprising a unit with a module for providing a. 33. The apparatus of claim 32, wherein said separating and converting means comprises at least one multiplier and at least one module, said module providing an auxiliary frequency called in the form of one or more generators or memory units, said separating and converting means Means that the reference and information components are transmitted separately from each other within a predetermined standing intermediate frequency range, and at least one filter unit is connected to a lower end of the separating and converting means, and means for suppressing interference portions is connected. And the filter unit is configured such that the desired signal portion is each filtered from the individual spectra of the standing intermediate frequency and removes the interference portion to provide to the bottom means for parameter analysis. 34. The system of any one of claims 32 to 33, wherein said frequency converting means further comprises at least one transducer for Doppler compensation. 35. The system of claim 34, wherein said middle portion suppression means further comprises a controllable filter. 36. A method according to any one of claims 34 to 35, wherein said parameter analyzing means comprises at least one pair of at least one reference oscillation and one information carrier signal component provided internally by the generator or a memory or a reference component. A system comprising a multiplier of and further comprising an analysis module. 37. The apparatus according to claim 36, further comprising a module connected to a tuning means connected to a lower end of said frequency converting means and to an upper end of said parameter analyzing means, a module for frequency spectrum analysis and a module for suppressing an interference portion. System characterized in that. 38. A Doppler analysis according to any one of claims 31 to 37 connected to at least one of said auxiliary frequency generators and / or to an evaluation module for determining the rate of change in distance between said transmitter and said receiver. The system further comprises a module. A system configured as part of an information transmission system according to claim 38. 40. A system configured as part of an information transmission system according to any of claims 38-39. 41. The system of any of claims 38-40, wherein the frequency converting means further comprises at least one transducer for Doppler compensation. 42. The system according to any one of claims 38 to 41, wherein the means for overlapping the interference portions comprises a filter unit having at least one control module. 43. The system according to any one of claims 38 to 42, wherein the means for superposition of the interference portions comprises further filtering controllable, each of which is connected to the bottom of the means for frequency conversion. 44. The system of any one of claims 38 to 43, wherein the means for parameter analysis comprises at least one multiplexer and an analysis module. 45. The system of any of claims 38 to 44, wherein the means for parameter analysis further comprises a generator for generating a reference signal, the generator being connected to a control module of the last filter stage. 46. A method according to any one of claims 38 to 45, wherein the additional counting means is connected above the means for parameter analysis, and the module for the analysis of the frequency spectrum and the evaluation unit are connected to the connection module of the filter unit at the interference part. System characterized in that the. 47. The method according to any one of claims 38 to 46, wherein the further counting means is for Doppler analysis and is provided to at least one generator of an evaluation module and / or auxiliary frequency for the speed change of the distance between the transmitter unit and the receiver unit. The system of being connected.