KR20010047052A - Coherent type demodulation device of base transceiver station in interim standard-95 system - Google Patents

Abstract

PURPOSE: A synchronous demodulator within a base station in IS-95 system is provided to improve a system performance by 3dB compared with an asynchronous demodulator and to remove reasons degrading a performance of a base station by implementing synchronous demodulators as many as the number of subscribers within the base station. CONSTITUTION: A synchronous demodulator within a base station in IS-95 system consist of a number of synchronous demodulating units(1000). A number of synchronous demodulating units(1000) each receives RF receiving signal via antenna, performs a synchronous demodulating operating, generates Walsh Code, and then outputs the corresponding Walsh Code signal to a control station. The synchronous demodulating unit(1000) consist of a Base-Band sampling part(1100), quadrature phase Base-Band sampling part(1200), channel estimating part(1300), phase distortion recovering part(1400) and final Walsh Code generating part(1500). The phase Base-Band sampling part(1100) and quadrature phase Base-Band sampling part(1200) consists of a multiplier(1110,1210) and low pass filter(1120,1220), respectively. The channel estimating part consists of the first multiplier, a number of the first correlator, the second multiplier, a number of the second correlator, a maximum correlation value selecting part and a channel parameter estimating part. The final Walsh Code generating part(1500) consists of the first multiplier, a number of the first correlator, the second multiplier, a number of the second correlator, a number of adder and a final Walsh Code selecting part.

Description

Synchronous demodulator in base station in IS-95 system {COHERENT TYPE DEMODULATION DEVICE OF BASE TRANSCEIVER STATION IN INTERIM STANDARD-95 SYSTEM}

The present invention relates to an in-base station synchronous demodulator in an IS-95 (Interim Standard-95; IS-95) system, and more particularly, to implement as many synchronous demodulators as the number of subscribers in a base station. The present invention relates to an in-base station synchronous demodulation device in an IS-95 system that improves processing performance during a demodulator and at the same time improves the performance of the base station.

As is well known, the terminals in the conventional IS-95 system did not transmit the pilot channel to the base station due to power consumption or the like. Therefore, the operator was forced to install and use as many asynchronous demodulators as the number of subscribers in the base station in the IS-95 system. This is because the demodulation operation can be performed without the pilot channel transmitted from the terminal.

Therefore, the asynchronous demodulator mounted in the base station in the conventional IS-95 system has a problem in that the performance of about 3 dB is lower than that of the synchronous demodulator which performs the synchronous demodulation operation, thereby degrading the performance of the base station system.

Accordingly, an object of the present invention is to provide a synchronous demodulation device in a base station in an IS-95 system for realizing a synchronous demodulator by the number of subscribers in the base station. There is.

In order to achieve the above object, the intra-base station synchronous demodulator in the IS-95 system of the present invention receives an RF received signal r (t) through an antenna and performs a synchronous demodulation operation to perform a final Walsh code. After generating, the corresponding Walsh code signal ( It is characterized in that it consists of a plurality of synchronous demodulation unit as many as the number of subscribers (K) respectively outputting a) to the control station.

On the other hand, in order to achieve the above object, the intra-base station synchronous demodulation device in the IS-95 system of the present invention, by receiving the RF reception signal r (t) through the antenna and at the same time performs the first synchronous demodulation After generating the first Walsh code, the corresponding first Walsh code signal ( A plurality of primary synchronous demodulation units corresponding to the number of subscribers (K) respectively outputting a); A reception signal delay unit receiving an RF reception signal r (t) through an antenna and delaying by "T _b " and then outputting an RF reception signal r (tT _b ) corresponding thereto; A number of primary Walsh code signals each output from one primary synchronous demodulation unit ( ) Generates an interference signal corresponding to a plurality of subscribers (K), and then receives an RF received signal r (tT _b ) delayed by "T _b " from the received signal delay unit and the RF signal. After removing each interference signal corresponding to a plurality of K subscribers from the received signal r (tT _b ), the corresponding number of K received RF signals r ′ ₁ (tT _b ),... an interference cancellation circuit unit for outputting r ' _K (tT _b )); a plurality (K) RF reception signals r' ₁ (tT _b ), ..., r ' _K (tT _b ) output from the interference cancellation circuit unit); After receiving the RF reception signal (r ' _i (tT _b )) corresponding to the order of the second to perform the second synchronous demodulation operation to generate the second final Walsh code, the corresponding second final Walsh code signal ( ) Is composed of a plurality of secondary synchronous demodulation units as many as the number of subscribers (K) respectively outputting to the control station.

1 is a functional block diagram showing the configuration of an intra-base station synchronous demodulation device in an IS-95 system according to an embodiment of the present invention;

FIG. 2 is a functional block diagram showing a configuration of a channel estimating unit respectively mounted in a number (K) synchronous demodulation units in the in-base station synchronous demodulation device in the IS-95 system according to FIG. 1;

FIG. 3 is a functional block diagram illustrating a configuration of Walsh code generators respectively mounted in a plurality of (K) synchronous demodulation units in an in-base station synchronous demodulation device according to FIG. 1;

4 is a functional block diagram showing the configuration of an intra-base station synchronous demodulation device in an IS-95 system according to this embodiment of the present invention;

FIG. 5 is a functional block diagram showing a configuration of a channel estimating unit mounted in a plurality of (K) primary synchronous demodulation units in the in-base station synchronous demodulator in the IS-95 system according to FIG. 4; FIG.

FIG. 6 is a functional block diagram showing a configuration of a primary Walsh code generator respectively mounted in a primary synchronous demodulation unit in an in-base station synchronous demodulator in the IS-95 system according to FIG. 4; FIG.

FIG. 7 is a functional block diagram showing a configuration of an interference signal canceling circuit unit in an in-base station synchronous demodulation device in an IS-95 system according to FIG. 4;

FIG. 8 is a functional block diagram illustrating a configuration of a second final Walsh code generation unit mounted in a secondary synchronous demodulation unit in the in-base station synchronous demodulator in the IS-95 system of FIG. 4.

<Explanation of symbols for the main parts of the drawings>

1000: synchronous demodulation unit 1100: in-phase baseband extraction unit

1110 multiplier 1120 lowpass filter

1200: quadrature baseband extractor 1210: multiplier

1220: low pass filter 1300: channel estimator

1310: first multiplier 1320: first correlator

1330: second multiplier 1340: second correlator

1350: maximum correlation value selector 1360: channel parameter estimator

1400: phase distortion recovery unit 1500: final Walsh code generation unit

1510: first multiplier 1520: first correlator

1530: second multiplier 1540: second correlator

1550: Adder 1560: Final Walsh Code Selection

2100: 1st synchronous demodulation unit 2110: In-phase baseband extractor

2111 multiplier 2112 lowpass filter

2120: quadrature baseband extractor 2121: multiplier

2122: low pass filter 2130: channel estimator

2131: first multiplier 2132: first correlator

2133: second multiplier 2134: second correlator

2135: maximum correlation value selector 2136: channel parameter estimation unit

2140: phase distortion recovery unit 2150: first Walsh code generation unit

2151: First Multiplier 2152: First Correlator

2153: second multiplier 2154: second correlator

2155: adder 2156: first Walsh code selection unit

2200: reception signal delay unit 2300: interference signal cancellation circuit

2310 multiplier 2320 spreader

2330: adder 2340: subtractor

2400: 2nd synchronous demodulation unit 2410: In-phase baseband extractor

2411: Multiplier 2412: Lowpass Filter

2420: quadrature baseband extractor 2421: multiplier

2422: low pass filter 2430: phase distortion recovery unit

2440: second final Walsh code generator 2441: first multiplier

2442: first correlator 2443: second multiplier

2444: second correlator 2445: adder

2446: second final Walsh code selector

Hereinafter, an intra-base station synchronous demodulation device in an IS-95 system according to an embodiment of the present invention will be described in detail with reference to the accompanying drawings.

1 is a functional block diagram illustrating a configuration of an intra-base station synchronous demodulator in an IS-95 system according to an embodiment of the present invention, and FIG. 2 is an intra-base station synchronous demodulator in an IS-95 system according to FIG. 1. FIG. 3 is a functional block diagram showing a configuration of a channel estimator respectively mounted in a plurality of K synchronous demodulation units, and FIG. A functional block diagram showing a configuration of a Walsh code generator respectively mounted in the apparatus, wherein the in-base station synchronous demodulator in the IS-95 system according to an embodiment of the present invention includes a plurality of synchronous demodulation units 1000 corresponding to the number of subscribers (K). It consists of).

The plurality of K synchronous demodulation units 1000 receive RF (Radio Frequency; hereinafter referred to as RF) through an antenna and perform a synchronous demodulation operation at the same time as receiving a received signal r (t). After generating, the corresponding Walsh Code signal ( ) Are respectively output to the control station, and the in-phase baseband extractor 1100, the quadrature baseband extractor 1200, the channel estimator 1300, and the phase distortion recovery The unit 1400 and the final Walsh code generator 1500 are respectively configured.

At this time, the in-phase baseband extractor 1100 respectively installed in the plurality of K synchronous demodulation units 1000 receives an RF reception signal r (t) through an antenna and extracts only in-phase baseband components. After that, the in-phase baseband signal d _I (t) is output to the channel estimator 1300 and the phase distortion recovery unit 1400, and is a multiplier 1110 and a low pass filter. 1120).

The multiplier 1110 mounted in the in-phase baseband extractor 1100 receives an RF received signal r (t) received through an antenna and then carries a carrier frequency (cosω _c (t)). By multiplying, it lowers the RF received signal r (t) to the baseband level.

In addition, the low pass filter 1120 mounted in the in-phase baseband extractor 1100 receives an RF received signal r (t) lowered to the baseband level through the multiplier 1110 and receives a baseband component. A filtering operation is performed to extract only the bay, and then the extracted in-phase baseband signal d _I (t) is output to the channel estimator 1300 and the phase distortion recovery unit 1400.

On the other hand, the quadrature baseband extractor 1200 mounted in each of the plurality of K synchronous demodulation units 1000 receives the RF reception signal r (t) through an antenna and extracts only the quadrature baseband component. Then, the quadrature baseband signal (d _Q (t)) is output to the channel estimator 1300 and the phase distortion recovery unit 1400, and to a multiplier 1210 and a low pass filter 1220. Consists of.

The multiplier 1210 mounted in the quadrature baseband extractor 1200 receives an RF received signal r (t) received through an antenna and multiplies the carrier frequency sinω _c (t) by It serves to lower the RF received signal r (t) to the baseband level.

In addition, the low pass filter 1220 mounted in the quadrature baseband extractor 1200 receives the RF received signal r (t) lowered to the baseband level through the multiplier 1210 and receives a baseband component. A filtering operation is performed to extract the bay, and then the extracted quadrature baseband signal d _Q (t) is output to the channel estimator 1300 and the phase distortion recovery unit 1400.

Meanwhile, the channel estimator 1300 mounted in each of the K synchronization demodulation units 1000 may output the in-phase baseband signal d _I (t) output from the in-phase baseband extractor 1100. At the same time, the quadrature baseband signal d _Q (t) output from the quadrature baseband extractor 1200 is received, and the in-phase baseband signal d _I (t) and quadrature base are received. After estimating the channel parameter components α and θ from the band signal d _Q (t), the corresponding channel parameter data C _{k and t} are output to the phase distortion recovery unit 1400. The first multiplier 1310, the plurality of M first correlators 1320, the second multipliers 1330, the plurality of M second correlators 1340, and the maximum correlation value selector 1350. ) And a channel parameter estimating unit 1360.

The first multiplier 1310 mounted in the channel estimator 1300 is an in-phase baseband signal d _I (t) output from the low pass filter 1120 mounted in the in-phase baseband extractor 1100. ) Pseudo-PN (Pseudo Random pattern; referred to as PN) Code Multiply by) to get the despread in-phase baseband signal ( ) And output to the first correlator 1320.

In addition, the plurality of M first correlators 1320 mounted in the channel estimator 1300 may include a despread in-phase baseband signal outputted from the first multiplier 1310. ) Is inputted to each of the Walsh codes (W ¹ (t), ..., W ^M (t)) and correlated with the Walsh codes corresponding to their order, and the resultant in-phase correlator output signal. ( ) Are respectively output to the maximum correlation value selector 1350.

On the other hand, the second multiplier 1330 mounted in the channel estimator 1300 is a quadrature baseband signal d _Q (output from the low pass filter 1220 mounted in the quadrature baseband extractor 1200). t)) and input the in-phase PN code ( Multiply by) to get the despread quadrature baseband signal ) And outputs it to the second correlator 1340.

In addition, the plurality of M second correlators 1340 mounted in the channel estimator 1300 may include a despread quadrature baseband signal output from the second multiplier 1330. ) Are input to each of the Walsh codes (W ¹ (t), ..., W ^M (t)) and correlated with the Walsh codes corresponding to their order, respectively. ( ) Are respectively output to the maximum correlation value selector 1350.

Meanwhile, the maximum correlation value selector 1350 mounted in the channel estimator 1300 may output a plurality of in-phase correlator output signals from the plurality of first M correlators 1320. ,… , ) And at the same time a plurality of quadrature correlator output signals from the plurality of (M) second correlator (1340) ,… , ) And the previous maximum correlation value selection signal C _{k, t-1} output from the final Walsh code generation unit 1500, and the plurality of in-phase correlator output signals ( ,… , In-phase Maximum Correlator Output Signal ) Is outputted to the channel parameter estimator 1360 and the quadrature correlator output signals ( ,… , Quadrature maximum correlator output signal ) To output to the channel parameter estimator 1360.

In addition, the channel parameter estimator 1360 mounted in the channel estimator 1300 may output the in-phase maximum correlator output signal (outputted by the maximum correlation value selector 1350). ) And quadrature maximum correlator output signal ( ), Estimates the channel parameter components α, θ, and outputs the corresponding channel parameter data C _{k, t} to the phase distortion recovery unit 1400.

Meanwhile, the phase distortion recovery units 1400 respectively installed in the plurality of K synchronous demodulation units 1000 are in-phase output from the low pass filter 1120 mounted in the in-phase baseband extractor 1100. While receiving the baseband signal d _I (t), the quadrature baseband signal d _Q (t) output from the low pass filter 1220 mounted in the quadrature baseband extractor 1200 is received. The channel parameter data C _{k, t} received from the channel parameter estimator 1360 mounted in the channel estimator 1300 is received, and the channel parameter data C _{k, t} are used. After reconstructing the phase distortion of the phase baseband signal d _I (t) and the quadrature baseband signal d _Q (t), respectively, the corresponding in-phase baseband reconstruction signal d ' _I (t) and for outputting the quadrature-phase baseband signal to restore (d _'Q (t)) in the Walsh code generator 1500 And to do.

Also, the final Walsh code generator 1500 mounted in each of the plurality of K synchronous demodulation units 1000 may output the in-phase baseband recovery signal d ' _I (t) output from the phase distortion recovery unit 1400. )) And quadrature baseband reconstruction signal (d ' _Q (t)) is input to perform a synchronous demodulation operation to generate a final Walsh code, and then the final Walsh code signal ( ), The first multiplier 1510, the plurality of M first correlators 1520, the second multiplier 1530, and the plurality of M second correlators 1540. ), A plurality of M adders 1550 and a final Walsh code selector 1560.

The first multiplier 1510 mounted in the final Walsh code generator 1500 receives an in-phase baseband reconstruction signal d ' _I (t) output from the phase distortion recovery unit 1400, and then in-phase PN. code( Multiply by) to despread the in-phase baseband recovery signal ( ) And then output to the plurality of M correlators 1520.

In addition, the first correlator 1520 mounted in the final Walsh code generator 1500 may have a despread in-phase baseband reconstruction signal (outputted from the first multiplier 1510). ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then restores the in-phase correlator. Output signal ) Is output to the adder 1550 corresponding to its own order.

On the other hand, the second multiplier 1530 mounted in the final Walsh code generator 1500 receives the quadrature baseband reconstruction signal d ' _Q (t) output from the phase distortion recovery unit 1400 and is orthogonal. Phase PN Code Multiply by) to despread the quadrature baseband reconstruction ) And then output to the plurality (M) second correlators 1540.

In addition, the plurality of M correlators 1540 mounted in the final Walsh code generator 1500 may receive the despread quadrature baseband reconstruction signal (output from the second multiplier 1530). ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then restores the quadrature correlator. Output signal ) Is output to the adder 1550 corresponding to its own order.

Meanwhile, the plurality of M adders 1550 mounted in the final Walsh code generator 1500 may output the in-phase correlator restoration output signal outputted from the plurality of M first correlators 1520. ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M second correlators 1540 at the same time as receiving an in-phase correlator restoration output signal corresponding to its own order ,… , And receives the quadrature correlator reconstruction output signals corresponding to their order, respectively, and performs an addition operation to output Walsh code symbol determination variables to the final Walsh code selector 1560.

Also, the final Walsh code selection unit 1560 mounted in the final Walsh code generation unit 1500 includes a plurality of Walsh code symbol determination variables S ₁ (t), ... from the plurality of M adders 1550. , S _M (t)), the final Walsh code is selected using a plurality of Walsh code symbol determination variables (S ₁ (t), ..., S _M (t)) and then the final Walsh code signal ( ) Is output to the control station 1, and the previous maximum correlation value selection signal C _{k, t-1} is output to the maximum correlation value selection unit 1350 mounted in the channel estimating unit 1300. do.

Next, an operation process of the intra-base station synchronous demodulation device in the IS-95 system having the above configuration will be described with reference to FIGS. 1, 2, and 3.

First, the following description is an operation process for the IS-95 reverse link from the terminal to the base station.

First, the multiplier 1110 of the in-phase baseband extractor 1100 respectively mounted in the plurality of K synchronous demodulation units 1000 receives an RF received signal r (t) received through an antenna. After multiplying by the carrier frequency (cosω _c (t)), the RF received signal (r (t)) is lowered to the baseband level. Then, the low pass filter 1120 mounted in the in-phase baseband extractor 1100 receives the RF received signal r (t) lowered to the baseband level through the multiplier 1110 and receives a baseband component. The filtering operation is performed to extract the bay, and then the in-phase baseband signal d _I (t) expressed as Equation 1 is transmitted to the channel estimator 1300 and the phase distortion recovery unit 1400. Output

In Equation 1, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Meanwhile, the multiplier 1210 of the quadrature baseband extractor 1200 mounted in each of the plurality of K synchronous demodulation units 1000 receives an RF received signal r (t) received through an antenna. By multiplying by the carrier frequency sinω _c (t), the RF received signal r (t) is lowered to the baseband level. Then, the low pass filter 1220 mounted in the quadrature baseband extractor 1200 receives the RF received signal r (t) lowered to the baseband level through the multiplier 1210 and receives a baseband component. The filtering operation is performed to extract only the quadrature baseband signal d _Q (t), which is represented by Equation 2, to the channel estimator 1300 and the phase distortion recovery unit 1400. Output

In Equation 2, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Then, the first multiplier 1310 of the channel estimator 1300 mounted in the plurality of K synchronous demodulation units 1000, respectively, has a low pass filter 1120 mounted in the in-phase baseband extractor 1100. In-phase baseband signal (d _I (t)) output from ), The despread in-phase baseband signal represented by Equation 3 ) Is output to the first correlator 1320.

In Equation 3, d _I (t) denotes an in-phase baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Then, the plurality of M first correlators 1320 mounted in the channel estimator 1300 are despread in-phase baseband signals output from the first multiplier 1310. ) Are respectively inputted from a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)) and correlated with the Walsh codes corresponding to their order, and then expressed as shown in Equation 4 below. In-phase correlator output signal ) Are respectively output to the maximum correlation value selector 1350.

,

(However, m = 1, 2, ...., M)

In Equation 4, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission.

On the other hand, the second multiplier 1330 of the channel estimator 1300 mounted in the plurality of K synchronous demodulation units 1000 is a low pass filter 1220 mounted in the quadrature baseband extractor 1200. ) Receives the quadrature baseband signal (d _Q (t)) output from ), The despread quadrature baseband signal represented by Equation 5 ) Is generated and output to the second correlator 1340.

In Equation 5, d _q (t) denotes a quadrature baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Then, the plurality of M second correlators 1340 mounted in the channel estimator 1300 may receive the despread quadrature baseband signal output from the second multiplier 1330. ) Are inputted to each of the Walsh codes (W ¹ (t), ..., W ^M (t)) and correlated with the Walsh codes corresponding to their turn numbers, and then expressed as shown in Equation 6 below. Quadrature Correlator Output Signal ) Are respectively output to the maximum correlation value selector 1350.

,

(However, m = 1, 2, ...., M)

In Equation 6, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread quadrature baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes a magnetic interference component due to quadrature spread PN code of Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission.

Subsequently, the maximum correlation value selector 1350 mounted in the channel estimator 1300 may output a plurality of in-phase correlator output signals from the plurality of first M correlators 1320. ,… , ) And at the same time a plurality of quadrature correlator output signals from the plurality of (M) second correlator (1340) ,… , ) And the previous maximum correlation value selection signal C _{k, t-1} output from the final Walsh code generation unit 1500, and the plurality of in-phase correlator output signals ( ,… , In-phase Maximum Correlator Output Signal ) Is output to the channel parameter estimator 1360. In addition, the maximum correlation value selector 1350 mounted in the channel estimator 1300 may output the plurality of quadrature correlator output signals ( ,… , Quadrature maximum correlator output signal ) Is output to the channel parameter estimator 1360.

Then, the channel parameter estimator 1360 mounted in the channel estimator 1300 may output the in-phase maximum correlator output signal (outputted from the maximum correlation value selector 1350). ) And quadrature maximum correlator output signal ( ), The channel parameter components α and θ are estimated, and the corresponding channel parameter data C _{k and t} are output to the phase distortion recovery unit 1400. In this case, the channel parameter data (C _{k, t} ) that is the output signal of the channel parameter estimator 1360 is expressed by Equation 7 below.

In Equation 7, β represents an oblivion constant, C _{k, t-1} represents a previous maximum correlation value selection signal, Denotes the in-phase maximum correlator output signal.

Then, the phase distortion recovery units 1400 respectively mounted in the plurality of K synchronous demodulation units 1000 are output from the low pass filter 1120 mounted in the in-phase baseband extractor 1100. The quadrature baseband signal d _Q (t) output from the low pass filter 1220 mounted in the quadrature baseband extractor 1200 while receiving a phase baseband signal d _I (t). And receive channel parameter data (C _{k, t} ) output from the channel parameter estimator (1360) mounted in the channel estimator (1300), and use the channel parameter data (C _{k, t} ). After reconstructing the phase distortions of the in-phase baseband signal d _I (t) and the quadrature baseband signal d _Q (t), respectively, an in-phase baseband reconstruction signal expressed by Equation 8 below is shown. (d _'I (t)) and to recover the quadrature baseband is expressed as [equation 9] The number (d _'Q (t)) and outputs the Walsh code generator 1500.

In Equation 8, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

In Equation 9, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Meanwhile, the first multiplier 1510 of the final Walsh code generator 1500 mounted in each of the plurality of K synchronous demodulation units 1000 restores the in-phase baseband output from the phase distortion recovery unit 1400. receiving the signal (d _'I (t)) in-phase PN code ( ), The despread in-phase baseband reconstruction signal represented by Equation 10 ) Is output to the plurality of M first correlators 1520, respectively.

In Equation 10, d ' _I (t) denotes an in-phase baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, and W ^j (tT ₀ -τ ^k ) The Walsh code transmitted from the k-th terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from the terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the first correlator 1520 mounted in the final Walsh code generator 1500 receives the despread in-phase baseband reconstruction signal (outputted from the first multiplier 1510). ) Are respectively inputted, and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then, as shown in Equation 11 below. Expressed in-phase correlator restoration output signal ) Is output to the adder 1550 corresponding to its own sequence number.

,

(However, m = 1, 2, ...., M)

In Equation 11, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

In addition, the second multiplier 1530 mounted in the final Walsh code generator 1500 receives the quadrature baseband reconstruction signal d ' _Q (t) output from the phase distortion reconstruction unit 1400 and is orthogonal. Phase PN Code ( ), The despread quadrature baseband reconstruction signal is expressed by Equation (12). ) Is output to the plurality of M correlators 1540.

In Equation 12, d ' _Q (t) denotes a quadrature baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents a Walsh code transmitted from a terminal of the k-th subscriber, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T ₀ ", Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the plurality of (M) second correlators 1540 mounted in the final Walsh code generator 1500 may receive the despread quadrature baseband reconstruction signal output from the second multiplier 1530. ) Are respectively inputted and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then, as shown in Equation 13 below. Quadrature Correlator Restoration Output Signal ) Is output to the adder 1550 corresponding to its own sequence number.

,

(However, m = 1, 2, ...., M)

In Equation 13, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

Meanwhile, the plurality of M adders 1550 mounted in the final Walsh code generator 1500 may output the in-phase correlator restoration output signal outputted from the plurality of M first correlators 1520. ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M second correlators 1540 at the same time as receiving an in-phase correlator restoration output signal corresponding to its own order ,… , And receive the quadrature phase correlator restoration output signals corresponding to their own order, and perform an addition operation, and then output Walsh code symbol determination variables to the final Walsh code selector 1560.

Then, the final Walsh code selection unit 1560 mounted in the final Walsh code generation unit 1500 receives a plurality of Walsh code symbol determination variables S ₁ (t) from the plurality of M adders 1550. , S _M (t)), the final Walsh code is selected using a plurality of Walsh code symbol determination variables (S ₁ (t), ..., S _M (t)) and then the final Walsh code signal ( ) Is output to the control station 1.

On the other hand, in the following with reference to the accompanying drawings for the intra-base station synchronous demodulation device in the IS-95 system according to this embodiment of the present invention will be described in detail.

FIG. 5 is a functional block diagram showing the configuration of the intra-base station synchronous demodulation device in the IS-95 system according to this embodiment of the present invention, and FIG. 6 is the intra-base station synchronous demodulation device in the IS-95 system according to FIG. FIG. 7 is a functional block diagram illustrating a configuration of a channel estimator respectively installed in a plurality of K primary demodulation units, and FIG. 7 is a diagram illustrating a plurality of (K) 1 units in an in-base station synchronous demodulator according to FIG. 5. Fig. 8 is a functional block diagram showing the configuration of the primary Walsh code generation units respectively mounted in the synchronous demodulation unit, and Fig. 8 is a function showing the configuration of the interference signal canceling circuit unit in the synchronous demodulation device in the base station in the IS-95 system according to Fig. 5. 9 is a second final Walsh code generator respectively mounted in a plurality of (K) secondary synchronous demodulation units in the in-base station synchronous demodulator in the IS-95 system according to FIG. 5. As a functional block diagram showing the configuration, the intra-base station synchronous demodulation device in the IS-95 system according to the present embodiment includes a plurality of (K) primary synchronous demodulation units 2100, a reception signal delay unit 2200, The interference elimination circuit unit 2300 and a plurality of (K) secondary synchronous demodulation units 2400.

The plurality of K primary synchronous demodulation units 2100 receive an RF reception signal r (t) through an antenna and simultaneously perform a first synchronous demodulation operation to generate a first Walsh code. Corresponding primary Walshcode signal ( ) Are output to the interference canceling circuit 2300, respectively, and an in-phase baseband extractor 2110, a quadrature baseband extractor 2120, a channel estimator 2130, and a phase distortion recovery unit 2140. ) And a primary Walsh code generator 2150, respectively.

At this time, the in-phase baseband extractor 2110 respectively mounted in the plurality of K primary synchronous demodulation units 2100 receives the RF reception signal r (t) through an antenna and in-phase baseband component. After extracting only, the in-phase baseband signal d _I (t) is output to the channel estimator 2130 and the phase distortion recovery unit 2140, and the multiplier 2111 and the low pass filter 2112 are extracted. Consists of

The multiplier 2111 of the in-phase baseband extractor 2110 mounted in each of the plurality of K primary synchronous demodulation units 2100 receives an RF reception signal r (t) received through an antenna. After multiplying by the carrier frequency (cosω _c (t)), it serves to lower the RF received signal (r (t)) to the baseband level.

In addition, the low pass filter 2112 mounted in the in-phase baseband extractor 2110 receives an RF received signal r (t) lowered to the baseband level through the multiplier 2111 and receives a baseband component. A filtering operation is performed to extract only the bay, and then outputs the in-phase baseband signal d _I (t) to the channel estimator 2130 and the phase distortion recovery unit 2140.

On the other hand, the quadrature baseband extractor 2120 mounted in each of the plurality of K primary synchronous demodulation units 2100 receives an RF reception signal r (t) through an antenna and quadrature baseband components. After extracting only the quadrature baseband signal (d _Q (t)) and outputs to the channel estimator 2130 and the phase distortion recovery unit 2140, the multiplier 2121 and the low pass filter 2122 It consists of).

The multiplier 2121 of the quadrature baseband extractor 2120 mounted in each of the plurality of K primary synchronous demodulation units 2100 receives an RF received signal r (t) received through an antenna. After multiplying by the carrier frequency (sinω _c (t)), it serves to lower the RF received signal (r (t)) to the baseband level.

In addition, the low pass filter 2122 mounted in the quadrature baseband extractor 2120 receives an RF received signal r (t) lowered to the baseband level through the multiplier 2121 and receives a baseband component. The filtering operation is performed to extract the bay, and then the quadrature baseband signal d _Q (t) is output to the channel estimator 2130 and the phase distortion recovery unit 2140.

Meanwhile, the channel estimator 2130 mounted in the plurality of K primary synchronous demodulation units 2100, respectively, is an in-phase baseband signal d _I (t) output from the in-phase baseband extractor 2110. ) Receives the quadrature baseband signal (d _Q (t)) from the quadrature baseband extractor 2120 at the same time, the in-phase baseband signal (d _I (t)) and the quadrature base After estimating the channel parameter components α and θ from the band signal d _Q (t), the channel parameter data C _{k and t} are output to the phase distortion recovery unit 2140. And a first multiplier 2131, a first correlator 2132, a second multiplier 2133, a second correlator 2134, a maximum correlation value selector 2135, and a channel parameter estimator 2136.

The first multiplier 2131 of the channel estimator 2130 mounted in the plurality of K primary synchronous demodulation units 2100 may output an in-phase baseband signal output from the in-phase baseband extractor 2110. d _I (t)) and take an in-phase PN code ( Multiply by) to get the despread in-phase baseband signal ( ) And output to the first correlator 2132.

In addition, the plurality of M first correlators 2132 mounted in the channel estimator 2130 are despread in-phase baseband signals output from the first multiplier 2131. ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then outputs the in-phase correlator signal( ) Are respectively output to the maximum correlation value selector 2135.

Meanwhile, the second multiplier 2133 mounted in the channel estimator 2130 receives the quadrature baseband signal d _Q (t) output from the quadrature baseband extractor 2120, thereby in-phase PN. code( Multiply by) to get the despread quadrature baseband signal ) And output to the second correlator 2134.

In addition, the plurality of M second correlators 2134 mounted in the channel estimator 2130 are despread quadrature baseband signals output from the second multiplier 2133. ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator output signals ( ) Are respectively output to the maximum correlation value selector 2135.

Meanwhile, the maximum correlation value selector 2135 mounted in the channel estimator 2130 may output a plurality of in-phase correlator output signals from the plurality of first M correlators 2132. ,… , ) And a plurality of quadrature correlator output signals from the plurality of M correlators 2134 ,… , ) And the previous maximum correlation value selection signal (C _{k, t-1} ) output from the first Walsh code generator 2150, the plurality of in-phase correlator output signals ( ,… , In-phase Maximum Correlator Output Signal ) Is outputted to the channel parameter estimator 2136 and the multiple quadrature correlator output signals ( ,… , Quadrature maximum correlator output signal ) And outputs to the channel parameter estimator 2136.

In addition, the channel parameter estimator 2136 mounted in the channel estimator 2130 may output an in-phase maximum correlator output signal outputted from the maximum correlation value selector 2135. ) And quadrature maximum correlator output signal ( ), And after estimating the channel parameter components (α, θ), the channel parameter data (C _{k, t} ) corresponding to the phase distortion recovery unit (2140), the interference canceller (2300) and the majority (K) It outputs to the secondary synchronous demodulation unit corresponding to its own sequence among the two secondary synchronous demodulation units 2400.

On the other hand, the phase distortion recovery units 2140 mounted in the plurality of K primary synchronous demodulation units 2100, respectively, are in-phase baseband signals d _I (output from the in-phase baseband extractor 2110). t)) and the quadrature baseband signal (d _Q (t)) output from the quadrature baseband extractor 2120 and received from the channel estimator 2130. C _{k, t} ), and the phase of the in-phase baseband signal d _I (t) and the quadrature baseband signal d _Q (t) using the channel parameter data C _{k, t} . After reconstructing the respective distortions, the primary Walsh code generator 2150 transmits corresponding in-phase baseband reconstruction signals d ' _I (t) and quadrature-phase baseband reconstruction signals d' _Q (t). It plays a role as output.

In addition, the primary Walsh code generators 2150 mounted in the plurality of K primary synchronous demodulation units 2100, respectively, have an in-phase baseband recovery signal d 'outputted from the phase distortion recovery unit 2140. After receiving _I (t)) and quadrature baseband recovery signal d ' _Q (t), the first synchronous demodulation operation is performed to generate a first Walsh code, and then the first Walsh code signal ( ) Is outputted to the interference canceling circuit unit 2300, and includes a first multiplier 2151, a plurality of M first correlators 2152, a second multiplier 2153, and a plurality of M second correlators. 2154, a plurality of M adders 2155, and a primary Walsh code selector 2156 are provided.

The first multiplier 2151 of the first Walsh code generator 2150 mounted in the plurality of K primary synchronous demodulation units 2100 respectively outputs the in-phase baseband output from the phase distortion recovery unit 2140. receiving a restore signal (d _'I (t)) in-phase PN code ( Multiply by) to despread the in-phase baseband recovery signal ( ) And output to the first correlator 2152.

In addition, the plurality of M first correlators 2152 mounted in the first Walsh code generator 2150 may receive the despread in-phase baseband reconstruction signal outputted from the first multiplier 2151. ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then restores the in-phase correlator. Output signal ) Are output to the adder 2155 corresponding to their own turn numbers, respectively.

Meanwhile, the second multiplier 2153 mounted in the first Walsh code generator 2150 receives the quadrature baseband reconstruction signal d ' _Q (t) output from the phase distortion recovery unit 2140. Quadrature PN Code ( Multiply by) to despread the quadrature baseband reconstruction ) And output to the second correlator 2154.

In addition, the plurality of M second correlators 2154 mounted in the first Walsh code generator 2150 may receive a despread quadrature baseband reconstruction signal output from the second multiplier 2153. ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then restores the quadrature correlator. Output signal ) Is output to the adder 2155 respectively corresponding to its own order.

On the other hand, the plurality of M adders 2155 mounted in the first Walsh code generator 2150 may include a plurality of in-phase correlator recovery output signals output from the plurality of first M correlators 2152. ,… , A plurality of quadrature correlator reconstruction output signals outputted from the plurality of M second correlators 2154 at the same time as receiving the in-phase correlator reconstruction output signals corresponding to their own order ,… , And receives the quadrature phase correlator restoration output signals corresponding to their own order, and performs an addition operation, and then outputs the first Walsh code symbol determination variable to the first Walsh code selector 2156.

In addition, the primary Walsh code selector 2156 mounted in the primary Walsh code generator 2150 may include a plurality of primary Walsh code symbol determination variables S ₁ (from the plurality of M adders 2155). t),…, S _M (t)), and selects the first Walsh code using a plurality of first Walsh code symbol determination variables (S ₁ (t),…, S _M (t)). Primary Walsh Code Signal ( ) Is output to the interference signal cancellation circuit 2300, and the previous maximum correlation value selection signal C _{k, t-1} is output to the maximum correlation value selection unit 2135 mounted in the channel estimating unit 2130. It plays a role.

Meanwhile, the reception signal delay unit 2200 receives the RF reception signal r (t) through an antenna and delays it by "T _b ", and then receives the corresponding RF reception signal r (tT _b ). It serves to output to the interference signal removing circuit unit 2300.

In addition, the interference signal canceling circuit 2300 may include a plurality of primary Walsh code signals respectively output from the plurality of K primary demodulation units 2100. ) Generates an interference signal corresponding to a plurality of subscribers (K), and then inputs an RF received signal r (tT _b ) delayed by “T _b ” from the received signal delay unit 2200. Upon reception, each interference signal corresponding to multiple (K) subscribers is removed from the RF received signal r (tT _b ), and then the corresponding multiple (K) RF received signals r ' ₁ ( tT _b ), ..., r ' _K (tT _b )) is output to the second synchronous demodulation unit 2400, a multiplier (K) multiplier (2310), a multiplicity (K) spreader (2320) And a plurality of K adders 2330 and a plurality of K subtractors 2340.

The plurality of K multipliers 2310 mounted in the interference signal canceling circuit unit 2300 may include a first Walsh code generation unit corresponding to a sequence number of the plurality of K primary Walsh code generators 2150. Primary Walsh code signal (2150) ) And the channel parameter data (C _{k, t} ) output from the channel estimator 2130 corresponding to its order among the channel estimators 2130 mounted in the plurality of K primary demodulation units 2100. By multiplying and multiplying each input simultaneously, it generates a phase-distorted signal and outputs the spreader 2320 corresponding to its own order.

In addition, a plurality of K spreaders 2320 mounted in the interference signal canceling circuit unit 2300 are phase-distorted signals from a multiplier 2310 corresponding to their order among the plurality of K multipliers 2310. Each input, the in-phase PN code ( ) And quadrature PN codes ( ) The product haejum to, after the reproduction terminal transmit signal (s' _i (tT _b)), respectively, and serves to output both in the number (K) of the adder 2330.

On the other hand, the plurality of K adders 2330 mounted in the interference signal elimination circuit unit 2300 transmit the plurality of K terminals transmitted signals s' ₁ (tT) reproduced by the plurality of K spreaders 2320. _b ), ..., s ' _K (tT _b )) is input and performs the addition operation in the state of excluding the terminal transmission signal s' _i (tT _b ) corresponding to its own sequence, and then corresponding Each of the interference signals is generated and then output to the subtractor 2340 corresponding to its own order.

In addition, the plurality of K subtractors 2340 mounted in the interference signal canceling circuit unit 2300 simultaneously receive the RF reception signal r (tT _b ) output from the reception signal delay unit 2200. After receiving the interference signal output from the adder 2330 corresponding to its own number among the plurality of K adders 2330, and removing the interference signals from the RF received signal r (tT _b ), respectively, It outputs a corresponding RF received signal (r ' _i (tT _b )) to each of the plurality of (K) secondary synchronous demodulation unit (400).

On the other hand, the plurality of secondary synchronous demodulation unit 2400 as many as the number of subscribers (K) is a plurality of (K) RF received signals r ' ₁ (tT _b ), ..., which is output from the interference canceling circuit unit 2300, r ' _K (tT _b )) receives the RF received signal r _i (tT _b ) corresponding to the sequence number and performs the second synchronous demodulation operation to generate the second final Walsh code, and then the corresponding 2 Second final Walsh code signal ( ) Are output to the control station 1, respectively, and the in-phase baseband extractor 2410, the quadrature baseband extractor 2420, the phase distortion recovery unit 2430, and the second final Walsh code generator 2440, respectively.

In this case, the in-phase baseband extractor 2410 mounted in the plurality of K secondary synchronous demodulation units 2400 may be one of the plurality of K subtractors 2340 mounted in the interference canceling circuit 2300. receiving the output from the subtractor 2340, corresponding to a sequence RF signals (r _'i (tT _b)) the input after receiving extracting only the in-phase baseband component, and "T _b" delayed in-phase base band signal by (d _It outputs _I (tT _b )) to the phase distortion recovery unit 2430, and is composed of a multiplier 2411 and a low pass filter 2412.

The multiplier 2411 of the in-phase baseband extractor 2410 mounted in the plurality of K secondary synchronous demodulation units 2400 includes a plurality of K subtractors 2340 mounted in the interference cancellation circuit 2300. ) Receives the RF reception signal r ' _i (tT _b ) from the subtractor 2340 corresponding to its turn number, and multiplies the carrier frequency cosω _c (t) by the RF reception signal r'. _It lowers _i (tT _b )) to baseband level.

Further, the low-pass filter 2412 mounted in the in-phase base band extracting section 2410 receives the RF received signal (r _'i (tT _b)) binary down to a baseband level through the multiplier 2411 The filtering operation is performed to extract only the baseband components, and then outputs the in-phase baseband signal d _I (tT _b ) delayed by “T _b ” to the phase distortion recovery unit 2430.

Meanwhile, the quadrature baseband extractor 2420 mounted in the plurality of K secondary synchronous demodulation units 2400 may be one of the plurality of K subtractors 2340 mounted in the interference cancellation circuit 2300. after the extracted received by the subtractor 2340, corresponding to a sequence number input the RF received signal (r _'i (tT _b)) only the quadrature-phase baseband component, and "T _b" delayed quadrature baseband signal by the (d _Q ( tT _b )) is output to the phase distortion recovery unit 2430, and is composed of a multiplier 2421 and a low pass filter 2422.

The multiplier 2421 of the quadrature baseband extractor 2420 mounted in the plurality of K secondary synchronous demodulation units 2400 is a plurality of K subtractors 2340 mounted in the interference cancellation circuit 2300. ) Receives the RF reception signal r ' _i (tT _b ) output from the subtractor 2340 corresponding to its own sequence number and multiplies by the carrier frequency sinω _c (t), thereby receiving the RF reception signal ( r ' _i (tT _b )) to lower the baseband level.

Further, the low-pass filter 2422 mounted in the quadrature base band extracting section 2420 receives the RF received signal (r _'i (tT _b)) binary down to a baseband level through the multiplier 2421 The filtering operation is performed to extract only the baseband components, and then the quadrature baseband signal d _Q (tT _b ) delayed by "T _b " is output to the phase distortion recovery unit 2430.

On the other hand, the phase distortion recovery unit 2430 mounted in the plurality of K secondary synchronous demodulation units 2400 is in-phase baseband delayed by "T _b " output from the in-phase baseband extractor 2410. At the same time as receiving a signal d _I (tT _b ), the quadrature baseband signal d _Q (tT _b ) delayed by “T _b ” output from the quadrature baseband extractor 2420 is received. receiving the said channel estimation unit 2130, a channel parameter data (C _{k, t)} output from the mounting in the first synchronous demodulator unit 2100, by using the channel parameter data (C _{k, t)} the "T _b "by the delayed in-phase baseband signal (d _I (tT _b)), and" T _b "after restoring the phase distortion of by delayed quadrature-phase baseband signal (d _Q (tT _b)), respectively, the corresponding" T _b "by the delayed in-phase baseband signal to restore _{(d 'I (tT b)} ) and" delayed by T _b "quadrature base van A restoration signal (d _'Q (tT _b)) serves to output to the second end Walsh code generator 2440.

In addition, the second final Walsh code generator 2440 mounted in the plurality of K secondary synchronous demodulation units 2400 has an in-phase base delayed by "T _b " output from the phase distortion recovery unit 2430. After receiving the band reconstruction signal d ' _I (tT _b ) and the quadrature baseband reconstruction signal d' _Q (tT _b ) delayed by "T _b ", the second final Walsh is performed by performing a second synchronous demodulation operation. Code, and then the second final Walshcode signal ( ), The first multiplier 2441, the first correlator 2442, the second multiplier 2443, the second correlator 2444, and the plurality of M adders 2445. ) And the second final Walsh code selector 2446.

The first multiplier 2441 of the second final Walsh code generator 2440 mounted in the plurality of K secondary synchronous demodulation units 2400 outputs the "T _b " output from the phase distortion recovery unit 2430. In-phase PN code (received in-phase baseband recovery signal d ' _I (tT _b )) Multiply by) to despread the in-phase baseband recovery signal ( ) And output to the first correlator 2442.

In addition, the plurality of M first correlators 2442 mounted in the second final Walsh code generator 2440 are despread in-phase baseband reconstruction signals outputted from the first multiplier 2441 ( ), Each of which is correlated with the Walsh code corresponding to its own sequence among the plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then restores the in-phase correlator. Output signal ) Are output to the adder 2445 corresponding to their own turn numbers, respectively.

On the other hand, the second multiplier 2443 mounted in the second final Walsh code generator 2440 receives the quadrature baseband reconstruction signal d ' _Q (tT _b ) output from the phase distortion recovery unit 2430. Quadrature PN code Multiply by) to despread the quadrature baseband reconstruction ) And then output to the plurality (M) second correlator (2444).

In addition, the plurality of M second correlators 2444 mounted in the second final Walsh code generator 2440 may receive the despread quadrature baseband reconstruction signal output from the second multiplier 2443. ) Are input to each of the Walsh codes (W ¹ (t), ..., W ^M (t)) and correlated with the Walsh codes corresponding to their order, respectively. signal( ) Are output to the adder 2445 corresponding to their own turn numbers, respectively.

Meanwhile, the plurality of M adders 2445 mounted in the second final Walsh code generator 2440 may include a plurality of in-phase correlator restoration output signals output from the plurality of first M correlators 2442. ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M second correlators 2444 at the same time as receiving an in-phase correlator restoration output signal corresponding to its own order ,… , Receive the quadrature phase correlator restoration output signal corresponding to its own sequence, and perform the addition operation and output the second final Walsh code symbol determination variable to the second final Walsh code selector 2446, respectively. do.

Also, the second final Walsh code selector 2446 mounted in the second final Walsh code generator 2440 may include a plurality of second final Walsh code symbol determination variables from the plurality of M adders 2445. using an S ₁ (t), ..., receives the S _M (t)), a plurality of second end-Walsh code symbol is determined variable (S ₁ (t), ..., S _M (t)) the second end Walsh After selecting the code, the second final Walsh code signal ( ) Is output to the control station (2).

Next, an operation process of the intra-base station synchronous demodulation device in the IS-95 system according to the present embodiment having the above-described configuration will be described with reference to FIGS. 5, 6, 7, 8, and 9. Let's do it.

First, the following description is an operation process for the IS-95 reverse link from the terminal to the base station.

Initially, the multiplier 2111 of the in-phase baseband extractor 2110 mounted in the plurality of K primary synchronous demodulation units 2100 respectively receives an RF received signal r (t) received through an antenna. After receiving the signal by multiplying the carrier frequency (cosω _c (t)), the RF received signal (r (t)) is lowered to the baseband level.

Then, the low pass filter 2112 mounted in the in-phase baseband extractor 2110 receives an RF received signal r (t) lowered to the baseband level through the multiplier 2111 and receives a baseband component. A filtering operation is performed to extract only the channel, and then the in-phase baseband signal d _I (t) expressed by Equation 14 is obtained by the channel estimator 2130 and the phase distortion recovery unit 2140. Will output

In Equation 14, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Meanwhile, the multiplier 2121 of the quadrature baseband extractor 2120 mounted in the plurality of K primary synchronous demodulation units 2100 respectively receives the RF received signal r (t) received through the antenna. After receiving the signal by multiplying the carrier frequency (sinω _c (t)), the RF received signal (r (t)) is lowered to the baseband level.

Then, the low pass filter 2122 mounted in the quadrature baseband extractor 2120 receives an RF received signal r (t) lowered to the baseband level through the multiplier 2121 and receives a baseband component. The filtering operation is performed to extract only the quadrature signal, and then the quadrature baseband signal d _Q (t) represented by Equation 15 is transmitted to the channel estimator 2130 and the phase distortion recovery unit 2140. Output

In Equation 15, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

At this time, the first multiplier 2131 of the channel estimator 2130 mounted in the plurality of K primary demodulation units 2100 is in-phase baseband output from the in-phase baseband extractor 2110. signal in-phase PN code receives the _(I d (t)) ( ), The despread in-phase baseband signal represented by Equation 16 ) Is output to the first correlator 2132.

In Equation 16, d _I (t) denotes an in-phase baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Then, the plurality of M first correlators 2132 mounted in the channel estimator 2130 are despread in-phase baseband signals output from the first multiplier 2131. ) Are respectively inputted, and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and are represented by Equation 17 below. In-phase correlator output signal ) Are respectively output to the maximum correlation value selector 2135.

,

(However, m = 1, 2, ...., M)

In Equation 17, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission.

Meanwhile, the second multiplier 2133 mounted in the channel estimator 2130 receives the quadrature baseband signal d _Q (t) output from the quadrature baseband extractor 2120, thereby in-phase PN. code( ), The despread quadrature baseband signal represented by Equation 18 ) Is output to the second correlator 2134.

In Equation 18, d _q (t) denotes a quadrature baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Then, the plurality of M second correlators 2134 mounted in the channel estimator 2130 are despread quadrature baseband signals output from the second multiplier 2133. ) Are respectively inputted, and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then, as shown in Equation 19 below. Quadrature Correlator Output Signal ) Are respectively output to the maximum correlation value selector 2135.

,

(However, m = 1, 2, ...., M)

In Equation 19, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread quadrature baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes a magnetic interference component due to quadrature spread PN code of Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission.

Subsequently, the maximum correlation value selector 2135 mounted in the channel estimator 2130 receives a plurality of in-phase correlator output signals from the plurality of first M correlators 2132. ,… , ) And a plurality of quadrature correlator output signals from the plurality of M correlators 2134 ,… , ) And the previous maximum correlation value selection signal (C _{k, t-1} ) output from the first Walsh code generator 2150, the plurality of in-phase correlator output signals ( ,… , In-phase Maximum Correlator Output Signal ) Is outputted to the channel parameter estimator 2136 and the multiple quadrature correlator output signals ( ,… , Quadrature maximum correlator output signal ) Is output to the channel parameter estimator 2136.

Then, the channel parameter estimator 2136 mounted in the channel estimator 2130 may output the in-phase maximum correlator output signal (output from the maximum correlation value selector 2135). ) And quadrature maximum correlator output signal ( ) The input received, the channel parameter component (α, θ), and then estimating, to the channel parameter data (C _{k, t)} is expressed as [Equation 20] the phase distortion restoration unit 2140, an interference canceller ( 2300 and a plurality of K secondary synchronous demodulation units 2400 to a secondary synchronous demodulation unit 2400 corresponding to its order.

In Equation 20, β denotes a forgetting constant, C _{k, t-1} denotes a previous maximum correlation value selection signal, Denotes the in-phase maximum correlator output signal.

On the other hand, the phase distortion recovery units 2140 mounted in the plurality of K primary synchronous demodulation units 2100, respectively, are in-phase baseband signals d _I (output from the in-phase baseband extractor 2110). t)) and the quadrature baseband signal (d _Q (t)) output from the quadrature baseband extractor 2120 and received from the channel estimator 2130. C _{k, t} ), and the phase of the in-phase baseband signal d _I (t) and the quadrature baseband signal d _Q (t) using the channel parameter data C _{k, t} . After each of the distortions is restored, an in-phase baseband reconstruction signal d ' _I (t) represented by Equation 21 below and a quadrature baseband reconstruction signal d represented by Equation 22 shown below. ' _Q (t)) is output to the first Walsh code generator 2150.

In Equation 21, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

In Equation 22, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

In addition, the first multiplier 2151 of the first Walsh code generator 2150 mounted in each of the plurality of K primary synchronous demodulation units 2100 outputs the in-phase output from the phase distortion recovery unit 2140. Receives the baseband recovery signal d ' _I (t) and receives an in-phase PN code ( ), The despread in-phase baseband reconstruction signal (Equation 23) ) Is output to the first correlator 2152.

In Equation 23, d ' _I (t) denotes an in-phase baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, and W ^j (tT ₀ -τ ^k ) The Walsh code transmitted from the k-th terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from the terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the plurality of M first correlators 2152 mounted in the first Walsh code generator 2150 may receive the despread in-phase baseband reconstruction signal outputted from the first multiplier 2151. ) Are inputted and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then expressed as shown in [Equation 24]. In-phase correlator recovery output signal ) Are respectively output to the adder 2155 corresponding to its own order.

,

(However, m = 1, 2, ...., M)

In Equation 24, m denotes the number of the correlator, k denotes the kth subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

Meanwhile, the second multiplier 2153 mounted in the first Walsh code generator 2150 receives the quadrature baseband reconstruction signal d ' _Q (t) output from the phase distortion recovery unit 2140. Quadrature PN Code ( ), The despread quadrature baseband reconstruction signal ([Equation 25]) ) Is output to the second correlator 2154.

In Equation 25, d ' _Q (t) denotes a quadrature baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents a Walsh code transmitted from a terminal of the k-th subscriber, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T ₀ ", Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the plurality of M second correlators 2154 mounted in the first Walsh code generator 2150 are despread quadrature baseband reconstruction signals outputted from the second multiplier 2153. ) Are inputted and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and are expressed as in [Equation 26]. Quadrature correlator recovery output signal ) Are respectively output to the adder 2155 corresponding to their own order.

,

(However, m = 1, 2, ...., M)

In Equation 26, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

Subsequently, the plurality of M adders 2155 mounted in the first Walsh code generator 2150 may include a plurality of in-phase correlator restoration output signals output from the plurality of M first correlators 2152. ,… , A plurality of quadrature correlator reconstruction output signals outputted from the plurality of M second correlators 2154 at the same time as receiving the in-phase correlator reconstruction output signals corresponding to their own order ,… , And receive the quadrature phase correlator restoration output signals corresponding to their own order, and perform an addition operation, and then output the first Walsh code symbol determination variables to the first Walsh code selector 2156.

Then, the primary Walsh code selector 2156 mounted in the primary Walsh code generation unit 2150 receives a plurality of primary Walsh code symbol determination variables S ₁ (from the plurality of M adders 2155). t),…, S _M (t)), and selects the first Walsh code using a plurality of first Walsh code symbol determination variables (S ₁ (t),…, S _M (t)). Primary Walsh Code Signal ( ) Is output to the interference signal cancellation circuit 2300, and the previous maximum correlation value selection signal C _{k, t-1} is output to the maximum correlation value selection unit 2135 mounted in the channel estimating unit 2130. do.

Meanwhile, the reception signal delay unit 2200 receives the RF reception signal r (t) through an antenna and delays it by "T _b ", and then receives the corresponding RF reception signal r (tT _b ). Output to the interference signal removing circuit unit 2300.

Then, the plurality of K multipliers 2310 mounted in the interference signal canceling circuit unit 2300 generate the first Walsh code corresponding to their own order among the plurality of K primary Walsh code generators 2150. The primary Walsh code signal output from the unit 2150 ( ) And the channel parameter data (C _{k, t} ) output from the channel estimator 2130 corresponding to its order among the channel estimators 2130 mounted in the plurality of K primary demodulation units 2100. Are multiplied by the input at the same time, and generates a phase-distorted signal, respectively, and outputs to the spreader 2320 corresponding to its turn.

Subsequently, a plurality of K spreaders 2320 mounted in the interference canceling circuit unit 2300 are phase-distorted from a multiplier 2310 corresponding to their order among the plurality of K multipliers 2310. Each input, the in-phase PN code ( ) And quadrature PN codes ( ) By multiplying the terminal transmission signal s' _i (tT _b ), which is represented by Equation 27, and outputting them to the plurality of K adders 2330.

(Where i = 1,…, K)

In Equation 27, P denotes a transmission power and W ^j (tT _b ) denotes a Walsh code of the j th subscriber station delayed by "T _b ". Represents an in-phase PN code, Denotes a quadrature PN code delayed by "T ₀ ", and W ^j (tT _b -T ₀ ) denotes the Walsh code of the j-th subscriber station delayed by-(T _b + T ₀ ).

In addition, the plurality of K adders 2330 mounted in the interference signal canceling circuit 2300 may transmit the plurality of K terminal signals transmitted from the plurality of K spreaders 2320 s' ₁ (tT). _b ), ..., s ' _K (tT _b )) is input and performs the addition operation in the state of excluding the terminal transmission signal s' _i (tT _b ) corresponding to its own sequence, and then corresponding Each of the interference signals is generated and output to the subtractor 2340 corresponding to the sequence number.

Then, the plurality of K subtractors 2340 mounted in the interference signal canceling circuit 2300 receive the RF received signal r (tT _b ) output from the received signal delay unit 2200 and simultaneously After receiving the interference signal output from the adder 2330 corresponding to its own number among the plurality of K adders 2330, and removing the interference signals from the RF received signal r (tT _b ), respectively, It outputs a corresponding RF received signal (r ' _i (tT _b )) to each of the plurality of (K) secondary synchronous demodulation unit (400).

Subsequently, the multiplier 2411 of the in-phase baseband extractor 2410 mounted in the plurality of K secondary synchronous demodulation units 2400 includes a plurality of K subtractors mounted in the interference cancellation circuit 2300. After receiving the RF reception signal r ' _i (tT _b ) from the subtractor 2340 corresponding to its own number in 2340, the multiplier multiplies the carrier frequency cosω _c (t) by the RF reception signal ( Lower r ' _i (tT _b )) to the baseband level.

Then, the low-pass filter 2412 mounted in the in-phase base band extracting section 2410 receives the RF received signal (r _'i (tT _b)) binary down to a baseband level through the multiplier 2411 The phase distortion recovery unit 2430 performs a filtering operation to extract only the baseband components, and then applies the in-phase baseband signal d _I (tT _b ) delayed by “T _b ” expressed by Equation 28. )

(Where i = 1,…, K)

In Equation 28, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Represents an in-phase PN code, Represents the distorted phase component of the channel, W ^j (tT _b -T ₀ -τ ⁱ ) represents the Walsh code transmitted from the terminal delayed by "T ₀ + T _b ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

On the other hand, the multiplier 2421 of the quadrature baseband extractor 2420 mounted in the plurality of K secondary synchronous demodulation units 2400 is a plurality of K subtractors mounted in the interference cancellation circuit 2300. The RF reception signal r ' _i (tT _b ) output from the subtractor 2340 corresponding to the order of the number 2340 is received and multiplied by the carrier frequency sinω _c (t), thereby receiving the RF. the signals _{(r 'i (tT b)} ) and lower in the baseband level.

Then, the low-pass filter 2422 mounted in the quadrature base band extracting section 2420 receives the RF received signal (r _'i (tT _b)) binary down to a baseband level through the multiplier 2421 A filtering operation is performed to extract only baseband components, and then the quadrature baseband signal d _Q (tT _b ) delayed by “T _b ” expressed by Equation 29 below is used as the phase distortion recovery unit. 2430).

(Where i = 1,…, K)

In Equation 29, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Represents an in-phase PN code, Represents the distorted phase component of the channel, W ^j (tT _b -T ₀ -τ ⁱ ) represents the Walsh code transmitted from the terminal delayed by "T ₀ + T _b ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise.

Subsequently, the phase distortion recovery unit 2430 mounted in the plurality of K secondary synchronous demodulation units 2400 is in-phase baseband delayed by "T _b " output from the in-phase baseband extractor 2410. At the same time as receiving a signal d _I (tT _b ), the quadrature baseband signal d _Q (tT _b ) delayed by “T _b ” output from the quadrature baseband extractor 2420 is received. receiving the said channel estimation unit 2130, a channel parameter data (C _{k, t)} output from the mounting in the first synchronous demodulator unit 2100, by using the channel parameter data (C _{k, t)} the "t _b "by the delayed in-phase baseband signal (d _I (tT _b)), and" T _b "by delayed quadrature-phase base band signal, to then restore the phase distortion of the (d _Q (tT _b)) each of the formula 30], and "T _b" by the delayed in-phase baseband signal to restore _{(d 'I (tT b)} ) and to be expressed by equation 31; The "T _b" by delayed quadrature-phase baseband signal to restore (d _'Q (tT _b)) is represented as outputs to the second end Walsh code generator 2440.

(Where i = 1,…, K)

In Equation 30, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted by the terminal delayed by "T _B + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

(Where i = 1,…, K)

In Equation 31, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, and W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

In addition, the first multiplier 2441 of the second final Walsh code generator 2440 mounted in the plurality of K second synchronous demodulation units 2400 may output “T” output from the phase distortion recovery unit 2430. _In -phase PN code (d ' _I (tT _b )) received by delayed by _b " ), The despread in-phase baseband reconstruction signal represented by Equation (32) ) Is generated and output to the first correlator 2442.

In Equation 32, d ' _I (tT _b ) denotes an in-phase baseband reconstruction signal delayed by "T _b ", τ ^k denotes a tracking component of a k-th subscriber channel, and P denotes a transmission power. k denotes the k-th subscriber, α ^k denotes the distorted magnitude component of the k-th subscriber channel, and W ^j (tT _b -τ ^k ) denotes the Walsh code transmitted by the k-th subscriber station delayed by "T _b ". W ^j (tT _b -T ₀ -τ ^k ) represents the Walsh code transmitted from the k-th terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, and W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the plurality of M first correlators 2442 mounted in the second final Walsh code generator 2440 are despread in-phase baseband reconstruction signals outputted from the first multiplier 2441. ) Are respectively inputted and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then, as shown in Equation 33 below. Expressed in-phase correlator restoration output signal ) Are respectively output to the adder 2445 corresponding to its own sequence number.

,

(However, m = 1, 2, ...., M)

In Equation 33, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (tT _b -τ ^k ) represents the Walsh code transmitted from the k-th subscriber station delayed by "T _b ", Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

In addition, the second multiplier 2443 mounted in the second final Walsh code generator 2440 receives the quadrature baseband reconstruction signal d ' _Q (tT _b ) output from the phase distortion recovery unit 2430. Quadrature PN code ), The despread quadrature baseband reconstruction signal (Equation 34) ) Is outputted to the plurality of M second correlators 2444.

In Equation 34, d ' _Q (tT _b ) denotes a quadrature baseband reconstruction signal delayed by "T _b ", τ ^k denotes a tracking component of a k-th subscriber channel, and P denotes a transmission power. k denotes the k-th subscriber, α ^k denotes the distorted magnitude component of the k-th subscriber channel, and W ^j (tT _b -τ ^k ) denotes the Walsh transmitted from the terminal of the k-th subscriber delayed by "T _b ". Code, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, and W ^j (tT _b -T ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T _b + T ₀ ". , Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise.

Then, the plurality of M second correlators 2444 mounted in the second final Walsh code generator 2440 are despread quadrature baseband reconstruction signals output from the second multiplier 2443. ) Are respectively inputted and correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then, as shown in Equation 35 below. Quadrature Correlator Restoration Output Signal ) Are respectively output to the adder 2445 corresponding to its own sequence number.

,

(However, m = 1, 2, ...., M)

In Equation 35, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT _b -T ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T _b + T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.

Meanwhile, the plurality of M adders 2445 mounted in the second final Walsh code generator 2440 may include a plurality of in-phase correlator restoration output signals output from the plurality of first M correlators 2442. ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M second correlators 2444 at the same time as receiving an in-phase correlator restoration output signal corresponding to its own order ,… , The quadrature phase correlator restoration output signal corresponding to its own sequence is input, and after the addition operation is performed, the second final Walsh code symbol determination variable is output to the second final Walsh code selector 2446.

Then, the second final Walsh code selector 2446 mounted in the second final Walsh code generation unit 2440 may include a plurality of second final Walsh code symbol determination variables from the plurality of M adders 2445. using an S ₁ (t), ..., receives the S _M (t)), a plurality of second end-Walsh code symbol is determined variable (S ₁ (t), ..., S _M (t)) the second end Walsh After selecting the code, the second final Walsh code signal ( ) Is output to the control station 2.

As described above, the intra-base station synchronous demodulator in the IS-95 system according to the present invention implements the synchronous demodulator as many as the number of subscribers in the base station, thereby improving the system performance by 3 dB compared to the asynchronous demodulator during demodulation of the received signal. In addition to this, there is an excellent effect of eliminating the base station deterioration factor.

Claims (52)

After receiving the RF signal r (t) through the antenna and performing a synchronous demodulation operation to generate a final Walsh code, the corresponding Walsh code signal ( And a plurality of synchronous demodulation units corresponding to the number of subscribers (K), each of which is output to the control station. The method of claim 1, The plurality of K synchronous demodulation units receive an RF reception signal r (t) through an antenna, extract only in-phase baseband components, and then output the in-phase baseband signal d _I (t). An in-phase baseband extractor; A quadrature baseband extractor which receives the RF reception signal r (t) through the antenna and extracts only the quadrature baseband component and then outputs the quadrature baseband signal d _Q (t); The in-phase baseband extractor receives an in-phase baseband signal d _I (t) and at the same time receives a quadrature baseband signal d _Q (t) in the quadrature baseband extractor. After estimating the channel parameter components (α, θ) from the in-phase baseband signal (d _I (t)) and the quadrature baseband signal (d _Q (t)), the corresponding channel parameter data (C _{k, t)} A channel estimator for outputting; The in-phase baseband extractor receives an in-phase baseband signal d _I (t) and at the same time receives a quadrature baseband signal d _Q (t) in the quadrature baseband extractor. receiving the channel parameter data (C _{k, t)} from the estimation, the channel parameter data (C _{k, t)} to the in-phase baseband signal (d _I (t)) and quadrature-phase baseband signal using a (d After reconstructing the phase distortion of _Q (t), respectively, the phase for outputting the corresponding in-phase baseband reconstruction signal d ' _I (t) and the quadrature baseband reconstruction signal d' _Q (t) A distortion recovery unit; The phase distortion recovery unit receives the in-phase baseband recovery signal d ' _I (t) and the quadrature baseband recovery signal d' _Q (t) and performs a synchronous demodulation operation to generate a final Walsh code. And then the final Walsh code signal ( And a final Walsh code generation unit for outputting the control unit) to the control station. The method of claim 2, The in-phase baseband extractor receives an RF reception signal r (t) received through an antenna and multiplies the carrier frequency cosω _c (t) by the RF reception signal r (t). A multiplier for lowering to a baseband level; The RF receiver receives the RF signal r (t) lowered to the baseband level through the multiplier and performs a filtering operation to extract only the baseband components. Then, the in-phase baseband signal d _I (t) is decoded. And a low pass filter output to the channel estimator and the phase distortion recovery unit. The method of claim 3, wherein In the IS-95 system, an in-phase baseband signal d _I (t), which is an output signal of a low-pass filter mounted in the in-phase baseband extractor, is represented by Equation 1 below. Synchronous demodulation device in base station. [Equation 1] In Equation 1, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 2, The quadrature baseband extractor receives an RF reception signal r (t) received through an antenna and multiplies the carrier frequency sinω _c (t) by the RF reception signal r (t). A multiplier for lowering to a baseband level; The RF receiver receives the RF signal r (t) lowered to the baseband level through the multiplier and performs a filtering operation to extract only the baseband components. The quadrature baseband signal d _q (t) is then decoded. And a low pass filter output to the channel estimator and the phase distortion recovery unit. The method of claim 5, In the IS-95 system, the quadrature baseband signal d _Q (t), which is an output signal of the low pass filter mounted in the quadrature baseband extracting unit, is represented by Equation 2 below. Synchronous demodulation device in base station. [Equation 2] In Equation 2, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 2, The channel estimator is configured to receive an in-phase baseband signal d _I (t) from the in-phase baseband extractor and obtain an in-phase PN code ( Multiply by) to get the despread in-phase baseband signal ( A first multiplier for generating and outputting; In-phase baseband signal despread by the first multiplier ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the in-phase correlator output signal ( A plurality of first correlators (M) each outputting a); The quadrature baseband extractor receives a quadrature baseband signal (d _Q (t)) to obtain an in-phase PN code ( Multiply by) to get the despread quadrature baseband signal A second multiplier for generating and outputting; Quadrature baseband signal despread by the second multiplier ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator output signals ( A plurality of (M) second correlators each of which outputs a); A plurality of in-phase correlator output signals from the plurality of first M correlators ,… , ) And a plurality of quadrature correlator output signals from the plurality of M correlators ,… , ) And the previous Walsh code generation unit receive the previous maximum correlation value selection signal (C _{k, t-1} ), the plurality of in-phase correlator output signal ( ,… , In-phase Maximum Correlator Output Signal At the same time select and output the multiple quadrature correlator ,… , Quadrature maximum correlator output signal A maximum correlation value selector which selects and outputs; In-phase maximum correlator output signal ( ) And quadrature maximum correlator output signal ( IS-95, comprising: a channel parameter estimator for estimating channel parameter components?,?, And outputting corresponding channel parameter data C _{k, t} to the phase distortion recovery unit; In-base synchronous demodulation device in a system. The method of claim 7, wherein A despread in-phase baseband signal which is an output signal of a first multiplier mounted in the channel estimator ( ) Is an intra-base station synchronous demodulator in the IS-95 system, characterized by the following Equation (3). [Equation 3] In Equation 3, d _I (t) denotes an in-phase baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 7, wherein In-phase correlator output signal (output signal of the first correlator mounted in the channel estimator) ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (4). [Equation 4] , In Equation 4, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission. The method of claim 7, wherein A despread quadrature baseband signal that is an output signal of a second multiplier mounted in the channel estimator ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (5). [Equation 5] In Equation 5, d _q (t) denotes a quadrature baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 7, wherein Quadrature correlator output signal (output signal of the second correlator mounted in the channel estimator) ) Is an intra-base station synchronous demodulator in the IS-95 system, characterized by the following Equation (6). [Equation 6] , (However, m = 1, 2, ...., M) In Equation 6, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread quadrature baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes a magnetic interference component due to quadrature spread PN code of Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission. The method of claim 7, wherein The channel parameter data (C _{k, t} ), which are output signals of the channel parameter estimator mounted in the channel estimator _, are expressed as shown in Equation 7 below. [Equation 7] In Equation 7, β represents an oblivion constant, C _{k, t-1} represents a previous maximum correlation value selection signal, Denotes the in-phase maximum correlator output signal. The method of claim 2, The in-phase baseband reconstruction signal d ' _I (t), which is an output signal of the phase distortion reconstruction unit, is expressed by Equation 8 below. [Equation 8] In Equation 8, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 2, The quadrature baseband reconstruction signal (d ' _Q (t)), which is an output signal of the phase distortion reconstruction unit, is expressed by Equation (9) below. [Equation 9] In Equation 9, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 2, The final Walsh code generation unit receives an in-phase baseband reconstruction signal d ' _I (t) from the phase-distortion recovery unit and receives an in-phase PN code ( Multiply by) to despread the in-phase baseband recovery signal ( A first multiplier for generating and outputting; In-phase baseband reconstruction signal despread by the first multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the in-phase correlator restoration output signal ( A plurality of first correlators (M) each outputting a); The phase distortion recovery unit receives a quadrature baseband reconstruction signal d ' _Q (t) and uses a quadrature PN code ( Multiply by) to despread the quadrature baseband reconstruction A second multiplier for generating and outputting; Quadrature baseband reconstruction signal despread by the second multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator restoration output signal ( A plurality of (M) second correlators each of which outputs a); A plurality of in-phase correlator recovery output signals outputted from the plurality of first M correlators ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M correlators while receiving the in-phase correlator restoration output signals corresponding to the ,… , A plurality of M adders for receiving the quadrature correlator reconstruction output signals corresponding to their turn, and performing an addition operation and outputting Walsh code symbol determination variables, respectively; The number (M) a plurality of the Walsh code symbol is determined from the adders variable _{(S 1 (t), ...} , S M (t)) the input received, a plurality of the Walsh code symbol is determined variable (S ₁ (t), ... After selecting the final Walsh code using S _M (t), the final Walsh code signal ( And a final Walsh code selector for outputting the previous maximum correlation value selection signal (C _{k, t-1} ) to the maximum correlation value selector. . The method of claim 15, A despread in-phase baseband reconstruction signal, which is an output signal of a first multiplier mounted in the final Walsh code generator, ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (10). [Equation 10] In Equation 10, d ' _I (t) denotes an in-phase baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, and W ^j (tT ₀ -τ ^k ) The Walsh code transmitted from the k-th terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from the terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 15, In-phase correlator restoring output signal which is an output signal of the first correlator mounted in the final Walsh code generation unit ( ) Is an intra-base station synchronous demodulation device according to Equation (11). [Equation 11] , (However, m = 1, 2, ...., M) In Equation 11, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission. The method of claim 15, A despread quadrature baseband reconstruction signal, which is an output signal of a second multiplier mounted in the final Walsh code generator, ) Is an intra-base station synchronous demodulator in the IS-95 system, characterized by the following Equation (12). [Equation 12] In Equation 12, d ' _Q (t) denotes a quadrature baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents a Walsh code transmitted from a terminal of the k-th subscriber, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T ₀ ", Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 15, Quadrature phase correlator recovery output signal which is an output signal of the second correlator mounted in the final Walsh code generation unit ( ) Is an intra-base station synchronous demodulation device according to Equation (13). [Equation 13] , (However, m = 1, 2, ...., M) In Equation 13, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission. Simultaneously with the reception of the RF reception signal r (t) through the antenna, the first synchronous demodulation operation is performed to generate a first Walsh code, and then a corresponding first Walsh code signal ( A plurality of primary synchronous demodulation units corresponding to the number of subscribers (K) respectively outputting a); A reception signal delay unit receiving an RF reception signal r (t) through the antenna and delaying the signal by "T _b ", and then outputting a corresponding RF reception signal r (tT _b ); A plurality of first Walsh code signals respectively output from the plurality of K primary demodulation units ( ) Generates an interference signal corresponding to a plurality of subscribers (K), and then receives an RF received signal r (tT _b ) delayed by "T _b " from the received signal delay unit. After removing each of the interference signals corresponding to the multiple (K) subscribers from the RF received signal (r (tT _b )), the corresponding multiple (K) RF received signals r ' ₁ (tT _b ), An interference cancellation circuit unit for outputting r, _K (tT _b )); The interference cancellation multiple output in circuit (K) number of RF received signal _{(r '1 (tT b)} , ..., r' K (tT b)) from the RF received signal (r _'i (tT corresponding to their sequence number _b )) is input to perform a second synchronous demodulation operation to generate a second final Walsh code, and then a corresponding second final Walsh code signal ( And a plurality of secondary synchronous demodulation units corresponding to the number of subscribers (K), each of which outputs C) to the control station. The method of claim 20, The K primary demodulation demodulation units receive an RF reception signal r (t) through an antenna, extract only in-phase baseband components, and then in-phase baseband signal d _I (t). An in-phase baseband extractor for outputting a; A quadrature baseband extractor which receives the RF reception signal r (t) through the antenna and extracts only the quadrature baseband component and then outputs the quadrature baseband signal d _Q (t); The in-phase baseband extractor receives an in-phase baseband signal d _I (t) and at the same time receives a quadrature baseband signal d _Q (t) in the quadrature baseband extractor. After estimating the channel parameter components (α, θ) from the in-phase baseband signal (d _I (t)) and the quadrature baseband signal (d _Q (t)), the corresponding channel parameter data (C _{k, t)} A channel estimator for outputting; The in-phase baseband extractor receives an in-phase baseband signal d _I (t) and at the same time receives a quadrature baseband signal d _Q (t) in the quadrature baseband extractor. receiving the channel parameter data (C _{k, t)} from the estimation, the channel parameter data (C _{k, t)} to the in-phase baseband signal (d _I (t)) and quadrature-phase baseband signal using a (d After reconstructing the phase distortion of _Q (t), respectively, the phase for outputting the corresponding in-phase baseband reconstruction signal d ' _I (t) and the quadrature baseband reconstruction signal d' _Q (t) A distortion recovery unit; After receiving the in-phase baseband reconstruction signal d ' _I (t) and the quadrature baseband reconstruction signal d' _Q (t) from the phase distortion reconstruction unit, the first-order Walsh is performed by performing a first order synchronous demodulation operation. Code, and then the first Walsh code signal ( And a first Walsh code generator for outputting the interference signal to the interference cancellation circuit. The method of claim 21, The in-phase baseband extractor receives an RF reception signal r (t) received through an antenna and multiplies the carrier frequency cosω _c (t) by the RF reception signal r (t). A multiplier for lowering to a baseband level; The RF receiver receives the RF signal r (t) lowered to the baseband level through the multiplier and performs a filtering operation to extract only the baseband components. Then, the in-phase baseband signal d _I (t) is decoded. And a low pass filter output to the channel estimator and the phase distortion recovery unit. The method of claim 22, In the IS-95 system, an in-phase baseband signal d _I (t), which is an output signal of a low-pass filter mounted in the in-phase baseband extractor, is expressed by Equation 14 below. Synchronous demodulation device in base station. [Equation 14] In Equation 14, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 21, The quadrature baseband extractor receives an RF reception signal r (t) received through an antenna and multiplies the carrier frequency sinω _c (t) by the RF reception signal r (t). A multiplier for lowering to a baseband level; The RF receiver receives the RF signal r (t) lowered to the baseband level through the multiplier and performs a filtering operation to extract only the baseband components. The quadrature baseband signal d _q (t) is then decoded. And a low pass filter output to the channel estimator and the phase distortion recovery unit. The method of claim 24, In the IS-95 system, the quadrature baseband signal d _Q (t), which is an output signal of the low pass filter mounted in the quadrature baseband extracting unit, is represented by Equation 15 below. Synchronous demodulation device in base station. [Equation 15] In Equation 15, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 21, The channel estimator, The in-phase baseband extractor receives an in-phase baseband signal d _I (t) and in-phase PN code ( Multiply by) to get the despread in-phase baseband signal ( A first multiplier for generating and outputting; In-phase baseband signal despread by the first multiplier ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the in-phase correlator output signal ( A plurality of first correlators (M) each outputting a); The quadrature baseband extractor receives a quadrature baseband signal (d _Q (t)) to obtain an in-phase PN code ( Multiply by) to get the despread quadrature baseband signal A second multiplier for generating and outputting; Quadrature baseband signal despread by the second multiplier ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator output signals ( A plurality of (M) second correlators each of which outputs a); A plurality of in-phase correlator output signals from the plurality of first M correlators ,… , ) And a plurality of quadrature correlator output signals from the plurality of M correlators ,… , ), The first Walsh code generator receives the previous maximum correlation value selection signal (C _{k, t-1} ), and outputs a plurality of in-phase correlator output signals ( ,… , In-phase Maximum Correlator Output Signal At the same time select and output the multiple quadrature correlator ,… , Quadrature maximum correlator output signal A maximum correlation value selector which selects and outputs; In-phase maximum correlator output signal ( ) And quadrature maximum correlator output signal ( ), The channel parameter components (α, θ) are estimated, and the corresponding channel parameter data (C _{k, t} ) are subjected to the phase distortion recovery unit, the interference canceller, and the plurality of (K) second order synchronous demodulation units. And a channel parameter estimator for outputting to a second synchronous demodulation unit corresponding to its own sequence among the synchronous demodulators in the IS-95 system. The method of claim 26, A despread in-phase baseband signal which is an output signal of a first multiplier mounted in the channel estimator ( ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (16). [Equation 16] In Equation 16, d _I (t) denotes an in-phase baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 26, In-phase correlator output signal (output signal of the first correlator mounted in the channel estimator) ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (17). [Equation 17] , (However, m = 1, 2, ...., M) In Equation 17, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission. The method of claim 26, A despread quadrature baseband signal that is an output signal of a second multiplier mounted in the channel estimator ) Is an intra-base station synchronous demodulation device according to Equation (18). Equation 18 In Equation 18, d _q (t) denotes a quadrature baseband signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. , α ^k represents the distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes a distorted phase component of a k-th subscriber channel, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted from a k-th terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, Denotes the distorted phase component of the k-th subscriber channel, K denotes the total number of subscribers, α ⁱ denotes the distorted magnitude component of the subscriber channel, and W ^j (t-τ ⁱ ) denotes the Walsh code transmitted from the terminal. Indicates, Represents an in-phase PN code, Denotes the distorted phase component of the channel, W ^j (tT ₀ -τ ⁱ ) denotes the Walsh code transmitted by the terminal delayed by "T ₀ ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. The method of claim 26, Quadrature correlator output signal (output signal of the second correlator mounted in the channel estimator) ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (19). [Equation 19] , (However, m = 1, 2, ...., M) In Equation 19, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread quadrature baseband signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. , W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the distorted phase component of the k-th subscriber channel, Denotes a magnetic interference component due to quadrature spread PN code of Q channel, Denotes the interference component by multiple users, Denotes noise on the radio, E _w denotes Walsh component energy, and j denotes a Walsh code number at the time of transmission. The method of claim 26, The channel parameter data (C _{k, t} ), which are output signals of the channel parameter estimator mounted in the channel estimator _, are expressed as shown in Equation 20 below. [Equation 20] In Equation 20, β denotes a forgetting constant, C _{k, t-1} denotes a previous maximum correlation value selection signal, Denotes the in-phase maximum correlator output signal. The method of claim 21, In-base synchronous demodulation device in the IS-95 system, characterized in that the in-phase baseband recovery signal (d ' _I (t)) that is the output signal of the phase distortion recovery unit is expressed by Equation 21 below. [Equation 21] In Equation 21, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 21, An orthogonal phase baseband recovery signal (d ' _Q (t)), which is an output signal of the phase distortion recovery unit, is expressed by Equation 22 below. [Equation 22] In Equation 22, K denotes the total number of subscribers, P denotes transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from a terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 21, The first Walsh code generator, The phase distortion recovery unit receives an in-phase baseband recovery signal d ' _I (t) and outputs an in-phase PN code ( Multiply by) to despread the in-phase baseband recovery signal ( A first multiplier for generating and outputting; In-phase baseband reconstruction signal despread by the first multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the in-phase correlator restoration output signal ( A plurality of first correlators (M) each outputting a); The phase distortion recovery unit receives a quadrature baseband reconstruction signal d ' _Q (t) and uses a quadrature PN code ( Multiply by) to despread the quadrature baseband reconstruction A second multiplier for generating and outputting; Quadrature baseband reconstruction signal despread by the second multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator restoration output signal ( A plurality of (M) second correlators each of which outputs a); A plurality of in-phase correlator recovery output signals outputted from the plurality of first M correlators ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M correlators while receiving the in-phase correlator restoration output signals corresponding to the ,… , A plurality of adders for receiving quadrature phase correlator reconstruction output signals corresponding to their order, respectively, and performing an addition operation and outputting first Walsh code symbol determination variables, respectively; A plurality of primary Walsh code symbol determination variables S ₁ (t), ..., S _M (t) are input from the plurality of M adders, and a plurality of primary Walsh code symbol determination variables S ₁ ( t),…, S _M (t)) to select the first Walsh code and then the first Walsh code signal ( And a first Walsh code selector for outputting the previous maximum correlation value selection signal (C _{k, t-1} ) to the maximum correlation value selector. Device. The method of claim 34, A despread in-phase baseband reconstruction signal, which is an output signal of a first multiplier mounted in the first Walsh code generator, ) Is an intra-base station synchronous demodulator in the IS-95 system, characterized by the following Equation (23). [Equation 23] In Equation 23, d ' _I (t) denotes an in-phase baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, and W ^j (tT ₀ -τ ^k ) The Walsh code transmitted from the k-th terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (t-τ ⁱ ) is a Walsh code transmitted from the terminal. Indicates Denotes an in-phase PN code, and W ^j (tT ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 34, In-phase correlator restoring output signal, which is an output signal of the first correlator mounted in the first Walsh code generator, ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following Equation (24). [Equation 24] , (However, m = 1, 2, ...., M) In Equation 24, m denotes the number of the correlator, k denotes the kth subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (t-τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber, Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission. The method of claim 34, A despread quadrature baseband reconstruction signal, which is an output signal of a second multiplier mounted in the first Walsh code generator, ) Is an intra-base station synchronous demodulator in the IS-95 system, characterized by the following Equation (25). [Equation 25] In Equation 25, d ' _Q (t) denotes a quadrature baseband reconstruction signal, τ ^k denotes a tracking component of a k-th subscriber channel, P denotes a transmission power, and k denotes a k-th subscriber. Α ^k represents a distorted magnitude component of the k-th subscriber channel, W ^j (t-τ ^k ) represents a Walsh code transmitted from a terminal of the k-th subscriber, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, W ^j (tT ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T ₀ ", Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 34, Quadrature phase correlator restoration output signal which is an output signal of the second correlator mounted in the first Walsh code generation unit ( ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (26). [Equation 26] , (However, m = 1, 2, ...., M) In Equation 26, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission. The method of claim 20, The interference canceling circuit unit may include a primary Walsh code signal output from a primary Walsh code generator corresponding to a sequence number of the plurality of K primary Walsh code generators. ) And the channel parameter data (C _{k, t} ) output from the channel estimator corresponding to its own order among the channel estimators mounted in the plurality of K primary demodulation demodulation units, respectively, and are multiplied at the same time. A multiplier (K) multipliers for generating and outputting a phase-distorted signal, respectively; Receive a phase-distorted signal from a multiplier corresponding to its own sequence among the plurality of K multipliers, respectively, and in-phase PN code ( ) And quadrature PN codes ( ) Of the product as haejum terminal transmission signal (s' _i (tT _b)), a number (K to output after each play) and a spreader; A terminal transmission signal corresponding to its own sequence is received by receiving all of the plurality of K transmission signals s ' ₁ (tT _b ), ..., s' _K (tT _b ) reproduced by the plurality of K spreaders. _{(s' i (tT b)} ) is performing the addition operation in which the exception condition, and generate the corresponding signal to interference since each output after a number (K) of the adders; The RF signal received from the RF signal r (tT _b ) and the interference signal from the adder corresponding to the sequence number of the K adders at the same time, the RF received signal r ( after removing an interference signal from tT _b)), respectively, the corresponding RF received signal (r _'i (on the IS-95 system, characterized in that configured the tT _b)) of a plurality (K) of the subtractor for each output Synchronous demodulation device in base station. The method of claim 39, The interference cancellation circuitry a plurality (K) The output signal of terminal transmission signal _{(s' i (tT b)} ) of the two spreader mounted in to is in IS-95 systems, characterized in that, it expressed as [Equation 27] Synchronous demodulation device in base station. [Equation 27] (Where i = 1,…, K) In Equation 27, P denotes a transmission power and W ^j (tT _b ) denotes a Walsh code of the j th subscriber station delayed by "T _b ". Represents an in-phase PN code, Denotes a quadrature PN code delayed by "T ₀ ", and W ^j (tT _b -T ₀ ) denotes the Walsh code of the j-th subscriber station delayed by-(T _b + T ₀ ). The method of claim 20, The number (K) of the second synchronous demodulator unit, receiving the plurality (K) RF received signal _{(r 'i (tT b)} ) from the subtractor corresponding to their sequence numbers of the two subtractors mounted within the interference cancellation circuit An in-phase baseband extractor for extracting only an in-phase baseband component and outputting an in-phase baseband signal d _I (tT _b ) delayed by the "T _B "; After receiving the RF reception signal r ' _i (tT _b ) from a subtractor corresponding to its own sequence among the plurality of K subtractors mounted in the interference cancellation circuit, only the quadrature baseband component is extracted, and the " T _b A quadrature baseband extractor for outputting a quadrature baseband signal d _Q (tT _b ) delayed by? The quadrature baseband signal is delayed by "T _b " at the same time as receiving the in-phase baseband signal d _I (tT _b ) delayed by "T _b " from the in-phase baseband extractor. Receives the signal d _Q (tT _b ) and receives the channel parameter data C _{k, t} from the channel estimator mounted in the first synchronous demodulation unit, and receives the channel parameter data C _{k, t} . It was used to restore the phase distortion of the "T _b" by the delayed in-phase baseband signal (d _I (tT _b)), and "T _b" by delayed quadrature-phase baseband signal (d _Q (tT _b)), respectively , the corresponding outputs "T _b" by the delayed in-phase base-band reconstructed signal _{(d 'I (tT b)} ) , and "T _b" by delayed quadrature-phase base-band reconstructed signal _{(d' Q (tT b)} ) equivalents A phase distortion recovery unit; The phase on the distortion restorer "T _b" by restoring the delayed in-phase baseband signal _{(d 'I (tT b)} ) , and "T _b" by restoring the delayed quadrature-phase baseband signal _{(d' Q (tT b)} ) After receiving the input, the second synchronous demodulation operation is performed to generate the second final Walsh code, and then the second final Walsh code signal ( And a second final Walsh code generation unit for outputting the control unit) to the control station. 42. The method of claim 41 wherein The in-phase baseband extraction unit receives an RF reception signal r ' _i (tT _b ) from a subtractor corresponding to its own sequence among the plurality of K subtractors mounted in the interference cancellation circuit unit, and then carries a carrier frequency (cosω). _c (t)) and as a product haejum, the RF received signal _{(r 'i (tT b)} ) for lowering a multiplier to a baseband level; Receiving the RF received signal _{(r 'i (tT b)} ) binary down to a baseband level through the multiplier performs the filtering operation in order to extract only the baseband component, and after that "T _b" delayed by the in-phase baseband And a low pass filter for outputting a signal d _I (tT _b ) to the phase distortion recovery unit. The method of claim 42, The in-phase baseband signal d _I (tT _b ) delayed by "T _b ", which is an output signal of the low-pass filter mounted in the in-phase baseband extractor, is expressed by Equation 28 below. In-base station synchronous demodulation device in the IS-95 system. [Equation 28] (Where i = 1,…, K) In Equation 28, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Represents an in-phase PN code, Represents the distorted phase component of the channel, W ^j (tT _b -T ₀ -τ ⁱ ) represents the Walsh code transmitted from the terminal delayed by "T ₀ + T _b ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. 42. The method of claim 41 wherein After receiving the input to the quadrature baseband extracting unit, RF received signal _{(r 'i (tT b)} ) from the subtractor corresponding to their sequence number of a plurality (K) of the subtractor mounted within the interference cancellation circuit carrier frequencies (sinω _c (t)) and as a product haejum, the RF received signal _{(r 'i (tT b)} ) for lowering a multiplier to a baseband level; Receiving the RF received signal _{(r 'i (tT b)} ) binary down to a baseband level through the multiplier performs the filtering operation in order to extract only the baseband component, and after that "T _b" delayed by the quadrature baseband And a low pass filter for outputting a signal (d _q (tT _b )) to the phase distortion recovery unit. The method of claim 44, The quadrature baseband signal (d _q (tT _b )) delayed by "T _b ", which is an output signal of the low pass filter mounted in the quadrature baseband extracting unit, is expressed by Equation 29 below. In-base station synchronous demodulation device in the IS-95 system. [Equation 29] (Where i = 1,…, K) In Equation 29, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Represents an in-phase PN code, Represents the distorted phase component of the channel, W ^j (tT _b -T ₀ -τ ⁱ ) represents the Walsh code transmitted from the terminal delayed by "T ₀ + T _b ", Denotes a quadrature PN code delayed by "T ₀ ", Represents the distorted phase component of the channel, Indicates noise. 42. The method of claim 41 wherein In the IS-95 system, the in-phase baseband reconstruction signal d ' _I (tT _b ) delayed by "T _b ", which is an output signal of the phase distortion reconstruction unit, is expressed by Equation 30 below. Synchronous demodulation device in base station. Equation 30 (Where i = 1,…, K) In Equation 30, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted by the terminal delayed by "T _B + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. 42. The method of claim 41 wherein In the IS-95 system, the quadrature baseband reconstruction signal d ' _Q (tT _b ) delayed by "T _b ", which is an output signal of the phase distortion reconstruction unit, is expressed by Equation 31 below. Synchronous demodulation device in base station. Equation 31 (Where i = 1,…, K) In Equation 31, K denotes the total number of subscribers, P denotes a transmission power, α ⁱ denotes a distorted magnitude component of a channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, and W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. 42. The method of claim 41 wherein The second final Walsh code generation unit receives an in-phase baseband reconstruction signal d ' _I (tT _b ) delayed by "T _b " from the phase distortion reconstruction unit, and in-phase PN code ( Multiply by) to despread the in-phase baseband recovery signal ( A first multiplier for generating and outputting; In-phase baseband reconstruction signal despread by the first multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the in-phase correlator restoration output signal ( A plurality of first correlators (M) each outputting a); The phase distortion recovery unit receives a quadrature baseband reconstruction signal d ' _Q (tT _b ) and a quadrature PN code ( Multiply by) to despread the quadrature baseband reconstruction A second multiplier for generating and outputting; Quadrature baseband reconstruction signal despread by the second multiplier ( ) Are correlated with Walsh codes corresponding to their order among a plurality of Walsh codes (W ¹ (t), ..., W ^M (t)), and then the quadrature correlator restoration output signal ( A plurality of (M) second correlators each of which outputs a); A plurality of in-phase correlator recovery output signals outputted from the plurality of first M correlators ,… , A plurality of quadrature correlator restoration output signals outputted from the plurality of M correlators while receiving the in-phase correlator restoration output signals corresponding to the ,… , A plurality of adders for receiving quadrature phase correlator reconstructed output signals corresponding to their turn, and performing an addition operation and outputting second final Walsh code symbol determination variables, respectively; A plurality of second final Walsh code symbol determination variables S ₁ (t), ..., S _M (t) are inputted from the plurality of M adders, and a plurality of second final Walsh code symbol determination variables S ₁ (t), ..., S _M (t)) to select the second final Walsh code and then the second final Walsh code signal ( And a second final Walsh code selector for outputting the control unit to the control station. The method of claim 48, A despread in-phase baseband reconstruction signal, which is an output signal of a first multiplier mounted in the second final Walsh code generator, ) Is an intra-base station synchronous demodulation device according to Equation (32). Equation 32 In Equation 32, d ' _I (tT _b ) denotes an in-phase baseband reconstruction signal delayed by "T _b ", τ ^k denotes a tracking component of a k-th subscriber channel, and P denotes a transmission power. k denotes the k-th subscriber, α ^k denotes the distorted magnitude component of the k-th subscriber channel, and W ^j (tT _b -τ ^k ) denotes the Walsh code transmitted by the k-th subscriber station delayed by "T _b ". W ^j (tT _b -T ₀ -τ ^k ) represents the Walsh code transmitted from the k-th terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ " corresponding to the k-th terminal, Denotes an in-phase PN code corresponding to the k-th terminal, K denotes the total number of subscribers, α ⁱ denotes a distorted size component of the subscriber channel, and W ^j (tT _b -τ ⁱ ) equals "T _b ". Represents a Walsh code sent by a delayed terminal. Denotes an in-phase PN code, and W ^j (tT _b -T ₀ -τ ⁱ ) denotes a Walsh code transmitted from a terminal delayed by "T _b + T ₀ ", Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 48, In-phase correlator restoring output signal, which is an output signal of the first correlator mounted in the second final Walsh code generator, ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (33). [Equation 33] , (However, m = 1, 2, ...., M) In Equation 33, m represents the number of the correlator, k represents the k-th subscriber, T _w represents the periodic component of the Walsh code, τ represents the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (t-τ ^k ) denotes the m th Walsh code, P denotes the transmit power, and α ^k denotes the distorted magnitude component of the k-th subscriber channel. W ^j (tT _b -τ ^k ) represents the Walsh code transmitted from the k-th subscriber station delayed by "T _b ", Denotes the magnetic interference component due to the in-phase spreading PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission. The method of claim 48, A despread quadrature baseband reconstruction signal, which is an output signal of a second multiplier mounted in the second final Walsh code generator, ) Is a base station synchronous demodulation device in the IS-95 system, characterized in that as shown in [Equation 34]. [Equation 34] In Equation 34, d ' _Q (tT _b ) denotes a quadrature baseband reconstruction signal delayed by "T _b ", τ ^k denotes a tracking component of a k-th subscriber channel, and P denotes a transmission power. k denotes the k-th subscriber, α ^k denotes the distorted magnitude component of the k-th subscriber channel, and W ^j (tT _b -τ ^k ) denotes the Walsh transmitted from the terminal of the k-th subscriber delayed by "T _b ". Code, Represents the in-phase PN code of the k-th subscriber, Denotes a quadrature PN code delayed by "T ₀ " of the k-th subscriber, and W ^j (tT _b -T ₀ -τ ^k ) denotes a Walsh code transmitted by the k-th terminal delayed by "T _b + T ₀ ". , Represents the in-phase PN code, Represents a quadrature PN code delayed by "T ₀ ", Indicates noise. The method of claim 48, Quadrature phase correlator restoration output signal which is an output signal of the second correlator mounted in the second final Walsh code generation unit ( ) Is an intra-base station synchronous demodulation device in the IS-95 system, characterized by the following equation (35). [Equation 35] , (However, m = 1, 2, ...., M) In Equation 35, m denotes the number of the correlator, k denotes the k-th subscriber, T _w denotes the periodic component of the Walsh code, τ denotes the tracking component of the subscriber channel, Denotes the despread in-phase baseband reconstruction signal, W ^m (tT ₀ -τ ^k ) denotes the m th Walsh code delayed by "T ₀ ", P denotes the transmit power and α ^k denotes the k-th subscriber Represents the distorted magnitude component of the channel, W ^j (tT _b -T ₀ -τ ^k ) represents the Walsh code transmitted from the terminal of the k-th subscriber delayed by "T _b + T ₀ ", Denotes the magnetic interference component due to the quadrature spread PN code of the Q channel, Denotes the interference component by multiple users, Represents wireless noise, E _w represents Walsh component energy, and j represents Walsh code number at the time of transmission.