KR20000011044A - Distributed network control of a dimmable fluorescent lighting system - Google Patents

Abstract

PURPOSE: A dimmable fluorescent lighting systems is to provide greater flexibility, improved ergonomic function, energy savings over systems lacking such control, a lower cost of installation, to be installed profitably in retrofit situations, as well as new construction, to calibrate easily. CONSTITUTION: A fluorescent lighting system comprises a distributed network (138) of lighting controls and control power sources. A plurality of controls (84) share a proportional-response control line (58) with a default value, wherein the control requesting the largest deviation from the default value prevails. Certain controls (124) may additionally share a polling line (126), in which the controls must agree on a value, before it can be requested on the proportional-response control line. Interactions between controls on the network provide for a method to control the total illumination on a scene, including both artificial (94) and natural (96) light, down to the light level where only natural light (96) is present. Unidirectional control nodes (86) allow a first network to exert control on a second network, without affecting the control levels in the first network. Thereby, hierarchical network control can be established. In addition, the method provides for network power to energize the control network (63), derived either from the lighting ballasts (52) or from external network-compliant power sources (192) strategically located in the network. A self-energizing contactor (80) switches power to the lighting system (56).

Description

Dimmable Fluorescent Lighting System

It has been found that higher efficiency can be obtained by lamps using gas discharge than incandescent filaments. As such, fluorescent lamps have been dominant in commercial lighting applications for more than 50 years. However, while dimming control provides a large proportion for incandescent lamp installation, such control provides only a small percentage for positioning by fluorescent lamps. The lack of dimmable fluorescence lighting systems is energy savings and consequent environmental savings, since lighting is a large percentage of total energy use in various commercial situations, and the additional dimming control of additional lighting systems contributes to many energy savings benefits. It represents the loss of an important opportunity to gain everyone.

One reason for this low rate of dimmable fluorescent lighting system is the lack of good quality controls at a reasonable cost. Dimmable lighting systems that are widely available today include The Mark XII and Lutron control protocols. Widely applicable to the lighting industry, Mark XII dimmable ballasts respond to 0-10 dB signals. While this is one of the most widely used in current use, the system generally lasts only a single manual, light sensor or occupancy control, the most beneficial control involving the use of many control tasks of the same kind.

Another system available from Lutron includes a central control box to which many controls and ballasts must be connected. This control box allows a high degree of fluidity in the control of other fixtures. In general, however, installation is expensive because the control must be connected to an expensive central control box even if each fixture is located far away.

Currently available dimmable fluorescent lighting systems are typically expensive to install and allow only a limited range of controllable parts, except for the Lutron system. However, it is the use of an adaptive control configuration arrangement that provides an energy savings mode as well as additional benefits with respect to ergonomic response.

In addition, convenient lighting control is difficult to measure during installation and duration. For example, photosensor sensitivity should generally be in the absence of external illumination. This is usually limited to measurement every evening, which leads to higher labor costs.

In addition, the treatment process is typically repetitive, requires manual adjustment and must be performed when the light sensor is located in a suitable place. Therefore, this requires a lot of rise and fall in one step while a lot of time is increased by manual approach to the optical sensor. Adjustment of the light sensor can take as long as exactly 30 minutes, and the cost of difficult labor generally reduces the financial reward for installing the light sensor. As such, the unwieldy measurement process is a substantial obstacle to the widespread acceptance of many lighting controls.

In addition, very complex lighting controls such as light sensors, occupancy sensors and infrared manual remote controls require an external power source for their operation. Frequently, the power supply involves the installation of a conduit to bring the wires associated with the line for control and a diminishing transformer that supplies power for individual control.

The cost of these installations is frequently expensive from an equipment renewal standpoint and is of great importance in comparison to the possible energy savings expected with the use of the control. In addition, the need for an external power source has a restraining effect on the use of multiple controls that can affect lighting in one place because each control requires its own low voltage source.

Therefore, the only controls that provide the largest single energy savings are typically installed at each location, although the benefits of increasing energy savings and the ergonomic environment result in the installation of additional controls.

The present invention relates to a dimmable fluorescent lighting system in which a plurality of controls interact to control the illumination level.

1 is a block diagram of a local control network,

2 is a block diagram in which a local control network is connected to a shared proportional response control line;

3 is a block diagram illustrating a shared proportional response control system with polling of control devices in an additional polling response environment in FIG. 2;

FIG. 4 is a block diagram illustrating a polling wire control system showing internal components of the controllers polling in FIG. 3;

5 is a block diagram illustrating the combination of components in a single control device;

6 is a block diagram of a dynamic lighting stabilizer,

7 is a schematic diagram of an optical sensor with two loop response speed operations without a dynamic lighting stabilizer;

8 is a schematic diagram of a dynamic lighting stabilizer with double loop speed and automatic measurement in FIG. 6, FIG.

9A is a schematic diagram of a dynamic lighting stabilizer with dual loop speed and automatic measurements performed by means other than that of FIG. 8, FIG.

9b is a schematic diagram of a dynamic full effect lighting stabilizer with double loop speed and automatic measurement,

10A is a schematic diagram of a travel sensor allowing remote operation measurement,

10B is a schematic diagram illustrating the output stage of the occupancy sensor of FIG. 10;

11 is a block diagram showing an illumination network with a single level of control;

12 is a block diagram showing an illumination network having three levels of control;

13A to 13H are schematic diagrams showing embodiments of solids of the direction signal device;

14 is a schematic diagram of a single controller motherboard,

15 is an exploded plan view schematically showing the physical design of the single control device shown in FIG. 5;

FIG. 16 is a schematic cross-sectional view of the single control device of FIG. 15 along line 16-16 shown in FIG. 15;

FIG. 17 is a block diagram showing a lighting network similar to FIG. 12 in which compliant power supplies are powering the network; FIG.

18A is a block diagram of a dimmable ballast that goes through a line-isolated control interface;

18b is a block diagram of a lighting fixture having a ballast capable of dimming, where the line-isolated control interface is not an absolutely necessary component as a dimmable ballast;

19 is a schematic diagram of an electronic ballast designed to provide power for gas discharge lamps while at the same time providing line isolation, low voltage power for external use;

20 is a schematic diagram of an alternative embodiment of an electronic ballast that includes the use of additional magnetic components that are not used to power a lamp;

21 is a schematic diagram of another embodiment of an electronic ballast that includes the use of an additional oscillation circuit as well as additional magnetic components not used to power a lamp;

22 is a schematic representation of an embodiment of an electronic ballast that further includes the use of additional capacitive components,

23 is a circuit diagram of a line-isolated control and power interface;

24 is a schematic diagram of a compliant, current-limiting power supply for use as a distributed power source in a lighting control network;

25 is a schematic diagram of a self-powered connector for powering a circuit;

FIG. 26A is a flowchart illustrating a method for measuring the optical sensor of FIG. 8;

FIG. 26B is a flow chart illustrating a method for measurement of the light sensor of FIG. 9A and the light sensor of FIG. 9B.

SUMMARY OF THE INVENTION The present invention has been made in view of the above-mentioned problems of the prior art, and an object thereof is to control a fluorescent lighting system in view of the defects of a fluorescent lighting system which can be controlled at present. To provide a lighting system.

It is also an object of the present invention to provide a dimmable fluorescent lighting system that can be advantageously installed from the standpoint of equipment update as well as a new structure and is easy to measure.

Another object of the present invention is to provide a dimmable fluorescent lighting system that can improve the operation of ergonomics and at the same time overcome such control deprivation systems and save energy.

In addition, another object of the present invention is to provide a dimmable fluorescent lighting system that can be installed at a lower cost and can provide occupants with direct control of the fluorescent lighting systems lighting in their workspace.

In order to achieve the foregoing or other objects and in accordance with the purpose of the present invention, as embodied and broadly described therein, the present invention refers to a system for controlling lighting in one place using multiple lighting controls connected to a network. do.

Multiple lighting controls will be selected from a set comprising occupancy controls, light controls, computer controls, and remote control receivers, usually many of these controls will be accommodated. The controls are coupled to at least one lighting modulator, wherein the lighting modulator can provide varying amounts of power to at least one gas discharge to illuminate a location by electrically coupling the controls with the lighting modulator. . With the wire a control signal will be shared between the controls and the modulators, the control signal having one default value at which point each control changes its level in a single direction from the default value.

The control signal is fixed at the level of illumination control to be at the level farthest from the default value. The lighting modulator then changes the power source to a gas discharge lamp coupled to it in response to the values of the control signal. The system is made up of at least one regulated power supply with tracking, whereby at least one control is coupled through the power line by flowing a regulated DC voltage to power the controls coupled to the power line.

An infrared control receiver is connected to at least one of the controls via a separate infrared control receiver signal wire, which passes a signal from the infrared transmitter to at least one of the controls, the signal being converted to mode conversion signals and remote illumination. It will contain all of the level requirements. In addition, the electrically conductive polling wire is connected to at least two occupancy sensors. When at least one occupancy sensor is coupled to a polling wire that is detecting people in the area, the polling wire signal value indicates the presence of people in the area from an inactive value indicating the absence of people in that area under monitoring. Switch to the active value.

The polling signal activation value causes all occupancy sensors connected to the polling wire to attempt to modulate the signal to the control wire to an illumination level suitable for the occupied space. The device is connected to at least one power source to an AC line voltage that powers at least one of the lighting modulators. A self-contained line connector is used to switch the AC line power to at least one of the modulators, wherein the energy used to control the connector is temporarily stored from a line-related AC source in an energy storage device associated with ground, When the connector is in the switched state it is emitted through the optical insulator.

The insulator triggers an electrical switch to power a relay coil using a source of line-related AC voltage used to power the lighting modulator.

In addition, the present invention is directed to additional devices and methods, and the best mode for carrying out the present invention through these additional devices and methods is described next.

The present invention includes a network of lighting controls that interact with each other to control a dimmable fluorescent lighting system. In order to make the network work properly, one method is described with ballasts that can control each other and control to determine the interaction of the controls. In addition, for maximum control adaptability, a method for hierarchical control configuration is depicted. In addition, the methods are depicted with controls for obtaining power for action, and many new control methods resulting from the interaction become possible. The new and available methods are subsequently described in detail in the best mode for carrying out the invention.

Hereinafter, various control methods that can be represented by the lighting control network will be described. In general, lighting systems have four types of control types, and the ways in which the control types operate in the present invention are given in the following sections.

First, manual control allows direct electrical connection to the user, for example by a wall dimmer or infrared remote control. In some cases, the user attempts to adjust the illuminance level as much as possible, from the manual illuminance to the very dark illuminance (the minimum artificial illuminance is given by the ballast).

Manual control in the control network of the present invention may include user input, infrared remote control, voice recognition, telephone input, and any other method of local computer control.

Secondly, light control means that the light sensor detects the amount of light that has penetrated from underneath the sensor, typically located on the ceiling, within the working area. If the working area receives light directly or indirectly from a window or skylight, the light from the operating area can consist of both natural and artificial light. The goal of the light sensor is to be controlled by artificial light and lighting systems. It generally reduces the use of the corresponding energy generated and to some extent ensures that natural light provides adequate illumination.

This method of reducing energy consumption is often called "daylight harvesting". The process of harvesting sunlight requires sensitive measurement of the photo-sensor. The goal of the measurement is to adjust the operating point of the light sensor.

Typically, the light sensor adjusts itself so that the amount of artificial light is reduced as soon as the maximum artificial lighting is exceeded. To set this measurement point, the measurement is usually performed at night when the light sensor can only observe the appearance of artificial light. The method has many important disadvantages, including time consuming and expensive measurements.

The most important limitation, however, is that the system is inherently set to provide only one predetermined amount of light, usually very artificial lighting brightness. The current method of invention utilizes the cooperation of an optical sensor, either direct manual or infrared remote manual control. Instead of the previous technology in a single set of illumination maintained by the system, the current method is to provide this level of user control.

Thus, when working at a computer terminal, a user may require a lower light level that combines more artificial and natural light while working at a desk. This mode of lighting control depends on how much network capability of the present invention allows manual input control up to the optical sensor. This way of overall lighting control is called "dynamic lighting stabilization".

Third, occupancy control refers to the presence of moving objects in the area. It also detects the appearance through infrared and sonar. Occupancy detectors are often referred to as movement (movement) detectors because they are usually detected through human movement detection.

The purpose of such sensors in lighting systems is to reduce lighting levels and energy use when the illuminated area is not occupied. Until recently, occupancy detectors have only changed the controlled light when movement is detected. However, frequently converting fluorescent lamps (lighting and turning off) by using occupancy sensors seriously reduces lamp life and financial savings. By placing occupancy sensors in a network that includes controllable ballasts and new control logic, the current method of invention provides a more appropriate ergonomic response.

The dual timing method is used slowly for dim lights while recovering a lot of lights quickly. If a person appears but no motion is detected or if no motion is detected by the detection element, darkening is performed slowly, and the person may deliberately announce the appearance to the system. And placing itself in relative darkness can hinder the light.

However, the occupant is then detected when the illumination level becomes dark due to the operation of the occupancy sensor. And the illuminance quickly returns to its original level.

For example, this prevents a large delay between entering an unoccupied room and the time the higher light levels are restored. There are many additional limitations with respect to occupancy sensors, the prior art. In some lighting scenarios, for example, it is difficult for an occupancy sensor to find motion in the whole area of light it controls. Therefore, it would be useful to use cooperative multiple occupancy sensors for long or "L" shaped porches to feel occupied anywhere in the bath, large work area, and within that area.

The current invention describes the logic required for a network comprising multiple occupancy sensors.

In a functional overview, logic requires that all occupancy sensors agree that the area under surveillance is to be occupied before the light darkens. If a person was detected by only one occupancy sensor, that other sensor could not arbitrarily dim the light without consent from another connected sensor. Another collaborative approach allows for telemetry from occupied sensors from the present invention, including interaction with manual control, whether direct or infrared remote. Supervised occupancy sensors require the user to set a physical jumper, dipswitch, or potentiometer within the occupancy sensor to set the level of sensitivity.

Because this requires physical interaction with the occupancy sensor, and because the occupancy sensor must work with the user from the sensor at some distance, the effort in setting up the control is forceful and numb.

In many occupancy sensors, some choice of sensitivity is provided. Or, many separate climbs and descents on the ladder are required to select the appropriate sensitivity.

The present inventive method by facilitating remote command input into the occupancy sensor allows a new method of occupancy sensor control. Using the command input via the infrared remote control, when the occupancy sensor is activated, the user is responsible for which between the office door (the occupancy sensor is not activated) at which the occupant enters the door and the person walking outside of it momentarily. It can show the commanded movements to allow for sensitive discrimination of and to be within the limits of the required occupancy sensor range.

The same logic described herein for this measurement will be appropriate whether occupancy is detected using sound waves or using an infrared detector. The method of the present invention, for the cooperation between the occupancy sensors and for the distant measurement of the occupancy the sensor will operate with the use of radio frequency or other recognition tags, the circumstances in which the occupant is found by the recipient in the room. Wear a short dog tag.

Fourth, the energy management system control can be as small as part of the office local lighting control network. Or they may be as big as the whole building. For the purpose of illustrating the invention, a local network is the same ballast in which all of the control in that network is described further later. Hierarchical networks, multiple and complex, are considered cooperative networks to coordinate what they have control and the aggregation of their ballasts.

One form of control over local networks is a type of computer or programmable microcontroller arranged to manage energy for the purpose of providing financial return through energy savings.

This control is frequently called an energy management system (EMS). And can work as a room, in a building, or in a building-wide floor. One drawback of many commercially available energy management systems is that EMS removes local control from its users. Energy savings can come at the cost of poor ergonomics, worker satisfaction and productivity.

In the method of the present invention, the energy management system can be handed over to smaller networks that illuminate various lights within the “caps” or even overturned energy boundaries when needed by individual workers or groups of workers.

User input could be through the mouse, either directly through computer interaction, such as a keyboard, a scripted phone interaction with a computer connected to a telephone system, or in other ways.

The computer either interacts directly with the network or through a powerline transmission protocol using encoded frequency information.

The previous discussion showed some of the controls that may participate in a local control network. Soon the following discussion shows how this control might interact within a local network. While there are many specialized methods of control discussed later, the most widely used protocol is that of a shared proportional response system.

1 is a block diagram of a local control network. And, affects all of them in that way by their associated control over fixtures in that local control network.

Although not shown in this figure, the shared control signal is carried through control line 58 having electrical connections to both the ballast and the control or other connections within this network, including electrical groups and control power connections.

The majority of fluorescent lamps 50 are powered by the majority of dark 52 ballasts. Each ballast 52 includes one line-insulated control interface 54 that transmits a shared control signal from the control line 58 to the dark ballast 52.

Fluorescent lamp 50, dark ballast 52 and line-insulated control interface 54 are all located in the majority of fluorescent lighting fixtures 56 represented by enclosed dot boxes. The method of the present invention is to provide a scheme wherein sensors requiring whereby lowest illumination levels among a plurality of sensors providing proportional response control are prevalent.

Consider for example. Darkening manual control 60 with lead light and on / off, local computer control in which occupancy sensor 62, far infrared receiver 59, and 63 are actively responding to the user and the environment at the same time. Consider an exchange office.

The infrared remote receiver detects signals from passive remote transmitters operated by room occupancy or other local infrared transmitters and optical sensors 64, which can be automatic or occupied sensors 62, and the first photosensor supervision line 65. Command to the infrared control 61, one occupancy sensor supervision line 67 and the infrared control supervision line 69, which measures or adjusts the general operation of each control.

The following table tracks the scenario described below. And the combined passive and infrared passive remote control signals are referred to collectively as manual. Using the manual dimmer 60 or infrared control 61 when the user enters the office in the morning he will set the illumination level to a complete illumination level, for example a comfort level of up to 90%.

The change in illumination level is caused by fluorescent lamp 50. The fluorescent lamp receives an approximate power level from the dark ballasts 52 which in turn receives the local network illumination level from the control interface 54. After the occupancy sensor 62 detects the appearance of the user and the environment, the external illumination does not meet enough illumination, which is the level of illumination. And the light output will be set to 90%.

In general, if the exterior lighting increases (when the sun shines on a window), there may be enough surrounding lighting to meet some of the user's needs. If the lighting sensor 64 determines that it now requires only 50% artificial light output to maintain the 90% previous demand of the user's artificial maximum illumination, the lighting system is reduced to that 50% level. Will be.

If the user leaves room, occupancy sensor 62 will find unoccupied and commanded light with reduced output to some level, which in this case is expected to be 10%.

The reduction in ignition will gradually become. So if the occupancy sensor 62 fails to identify the currently attending user, this gives the user time to make its presence known up to the sensor 62. When the user returns, the system quickly readjusts itself to deliver more dim 60, and the light set by the light sensor 64.

The second optical sensor supervisory line 71 connects the infrared control 61 to the light sensor 64 exchanges 134 through the infrared control method.

The second light sensor supervision line 71 adjusts the signal to the total illumination level required by the user for dynamic lighting stabilization. Dynamic lighting stabilization is detected up to the infrared remote control receiver 59 and transmitted to the infrared control 61.

That is, the user sets the overall amount of light desired in the area of control. And artificial and natural light.

The optical sensor 64 is directly connected to the infrared passive remote receiver 59 via the first optical sensor supervision line 65. The light sensor supervision line 65 transfers the request from the lighting installer or the administrator to automatically check the light sensor 64 to the user.

In the absence of dynamic lighting stabilization, commands are given by the infrared remote receiver 59 and transferred to infrared control where 61 by 69 control supervision of the infrared wires secures 69 to the wire. There, they wire 58 to the switch 134 in the second position without interaction with the photosensor 64 while being retained and transferred directly to the control.

In FIG. 1, a shared proportional response control signal is transmitted along control wire 58 which in its preferred implementation carries a low voltage DC voltage signal between the control and ballast 52.

The manner in which separate controls adjust the control signal established on control line 58 is described in the following section.

2 is a block diagram of a local control network coupled with a shared proportional response control line. Each plurality of lighting converters 88 includes a stop resistor with 90 connected to a source of voltage 92. Well, it was marked by Ｖ +.

If no controller 84 in any environment is active in adjusting the likelihood of the wire 58, then the stop resistor 90 in this case enables the voltage to remain at its negligible value at Ｖ + of the voltage source 92. .

When this voltage potential is at its negligence value, any of the controllers 84 of multiple output environments of artificial light, 94 are adjusted by a light adjuster for full illumination, its folded and drained diodes 86 If control is taken by lowering the likelihood of the negative pole of, the likelihood of the signal wire 58 is also lowered to the likelihood of the positive pole of the controller pull-down diode 86.

If controller 84 in any other environment reduces its collapsing diode 86 cathode potential over that of the first controller, the likelihood of electrically conducting wires 58 is lowered beyond the influence of the first controller. Lose.

Control of the likelihood of the wires 58 of electrically conducting is transferred to the controller 84 of the environment with the lowest internal potential. And it is the famous device, unlike the folded diode, which allows the 86 to electrically conduct the wire 58 of conduction, unidirectional control over the signal.

A device that allows such unidirectional control may be called and described as a "unidirectional signal device". Well, it's an electronic circuit that acts like a device of unidirectional cues, a unidirectional current door and a current going tool.

Each light regulator 88 is prepared in advance, producing a very light amount of 94 artificial light, in the following way to the control signal and wire 58 of the signal. When the control signal is at its negligence value, the amount of light emitting at 94 is maximum. The amount of illumination from light with 94 reduces, in a sense, the amount of reduction determined by the benefit factor set in the light adjuster 88 described later. And as the control that the signal changes, it forms the neglect.

The polarity in the device and the components, the possibilities, or other control transfer treaties that envision the spirit of this invention. And it's a lot of substitution that's understood The control signal, which could be adjusted by which on the control line, can be converted into cipher text in the frequency modulation of the alternating flow. Some of the methods proposed herein can be employed together to implement multiple methods of control at the same time.

The essence of the present invention's education was related to a shared proportional response control line. And it is. And in the shared control line 84 signals all controllers attempting to set control, and therefore the amount of light from light adjuster 88 as a result of this simple logic igniting ergonomic environmental accuracy calculations. It is a considerable value to naturally adjust the level of lighting in a system with multiples to control the resulting devices.

The "understanding" of the network is decentralized, since it is independent logic control over the network by each sensor, this is the amount required to design the network as the connectivity of the network requires the amount of labor and wires. It means that it can be changed very much while reducing the impact.

The 58 connecting the control single dose also had to be a control wire that does not carry power for the control in its preferred implementation. And he is noted. The control power wire 66 carrier powers the control.

As shown in the figure, all of the controls can share the same control power wire 66.

For example, if wires of signals carrying signals and power were employed, the signals could be carried by frequency modulation with the power supplied by the DC component.

The exception to the shared-proportional response control logic described is what happens when multiple occupancy sensors are scrutinizing an area. For example, long holes may have en occupancy sensors at both ends. While each has a field of view that overlaps the sequence, either can thus cover the whole area. And the hole can only be considered empty when both occupancy sensors are very representative. And that proper control requires that machine-to vote.

If only one occupant sensor finds an empty hole, one may find that it lowers the illumination described above according to the shared proportional response control logic since the person in the hall may only find it by the other occupancy sensor. I didn't want to.

In this case, the method allows the occupancy sensor going to the "voting" one to determine if they all agree that the area is empty under audit; it is only an occupancy sensor that should be registered in the directory.

The example given is here except for one that deviates from several multiple-sensors scenarios that benefit from voting signals.

Degree. Figure 3 is a block diagram representing a shared proportional response control system while voting with polling-responsive controllers in the environment. A subset of the controllers in the environment are poll-responsiＶe to the voting signal shared by them. The polling wire 124 that communicates in such a way that the poll-responsiＶe controller 124 to which 126 attends only acts as an element in the system in response to a stimulus affecting only one or several of the poll-responsiＶe controllers 124. Poll-responsiＶe controller 124 when it is connected to all of the poll-responsiＶe controllers 124, prohibiting control of the control signal wire 58 and pulling down and agreeing that all poll-responsiＶe controllers are highly arranged. Agrees the possibility of control signal wire 58 to pull-down. By the way, it is the wire that votes 126 to prevent all connected poll-responsiＶe controllers 124 from pulling down.

When everything is connected, Poll-responsiＶe controller 124 agrees to pull down the possibility of a control signal wire 58 making the polling wire system. And allows the possibility to be lowered. When this possibility is lowered, the light adjuster 88 all attached to that control signal modulates the light output of the attached light 58 and thus telegrams 94 its voting media in this case, that sharing The separation from the proportional response control wire is shown 58, but it could be a separate signal sharing the same control signal wire 58. Although it will increase the cost and complexity of the sensor, which is part of the voting network, such sharing of network control wires will reduce the cost and complexity of setting up the network. Such as, could include other means of communication. The control power wire 66 carrie powers the plurality of controls.

As shown in the figure, one of the environment's poll-responsiＶe controllers 124 shares control power line 66. And it only powers the controller that 124 is connected to, while poll-responsiＶe controller 124 in another environment has an external power source of 125.

One of the two that rely on sharing that choice, powering method, part of the nature of that distance and configuration of its control, control connection, line power, and availability of access to other considerations. This is a block diagram representing a wire control system that votes.

Resistors R1C and R2C are examples of several stops that can maintain the potential of the control signal wire at 58 at a voltage source of 92+. Two polling responding controllers 124 are shown when it is not affected by any controller. For illustrative purposes, each controller 124 shown is a motion detector.

In each controller, 124 is a folded D1C that allows only one controller at a time to affect the possibility of its control signal wires.

Each motion detector 124 includes a motion detection traversal 128 whose design is well known in prior art. This circuit 128 could include detectors of the sound detector's infrared or other effective sensing technologies that are infrared and negative. In each, the traversal is an integrated traversal U1C, which represents the output stage of the motion detection traversal 128 and is arranged by which of the collectors of the transistor Q1C is pulled down the base of the transistor Q3Cis. Some transistors Q3C are PNP emitter followers. And affect the possibility at the cathode of the diode D1C.

Voting wire 126 provides a connection between the collectors of transistor Q1C in each poll-responsiＶe controller where 124 in the poll wires 126. If the movement is found by any integrated circuit U1C, the collector of any transistor Q1C will do it for each. And highly forces some collectors to another poll-responsiＶe controller 124 farther than the possibilities of those other collectors that are very connected. And wire 126 to the connection provided by the poll.

This prevents any connected poll-responsiＶe controller 124 from lowering the likelihood of the control signal wire 58. When agreeing that all connected poll-responsiＶe controllers 124 have no movement, can do the possibility of control wire signal 58. Affected. Such voting machine will be special use within a plurality of motion / occupancy detectors in operation.

The present invention teaches the use of multiple controls within a local lighting system network to improve energy savings and provide a convenient and productive environment. To achieve the greatest benefit of the present invention, 2: 3 controls will be installed in a room or work space. Often, the optimal location for light, occupancy, and manual dimming controls only end up in a certain work area. Because of this advantage, the occupancy control can be easily monitored by humans, and the light control can adjust the light that bounces over a certain work surface while the receiver for the remote control dimmer can be close to the invading people.

The same arrangement of multiple controls in a single location allows the near integration of the controls to be a single accommodation while sharing electronic and physical components. As it is based on the coordination of multiple controls, the embodiment of the present invention includes a common control unit incorporating self-weight control means. As can be seen, the present invention not only simplifies installation and reduces costs, but also provides new interactions between different control means.

A single control device in which multiple controls are combined in the single receptacle is then referred to. However, the physical arrangement in which the controls are combined into a single receptacle is simply convenient, and the invention furthermore works if the controls are located in separate receptacles.

5 is a block diagram illustrating components and connections within a single control unit 138 coupled to multiple controls. The internal control bus 142 is affected by the output of the light sensor 64, occupancy / movement sensor 62, and infrared control 61. As shown below, the internal control bus 142 acts as a shared proportional response control line. Moreover, the single controller 138 includes an infrared remote receiver 59 that receives the controls from the user that the command enters via an infrared transmitter or other infrared transmitting means (not shown).

Each of these controls is coupled to the internal control bus 142, which acts as a shared proportional response control line that permits the control requiring the lowest control response to take advantage. To maintain the shared proportional response control line, each control attached to the internal control bus 142 will be mounted to the internal control bus 142 via an external unidirectional signaling means. The control values present in the internal control bus 142 are transmitted to the lighting modulators coupled to the single control unit 138 via the connector J7.

The single controller 138 is manufactured to be installed in the single controller 138 housing from one to three of the controls. When the movement sensor 62, the light sensor 64, and the infrared control 61 are all installed in the single control device 138, the single control device 138 is configured as shown in FIG. . In general, the infrared remote receiver 59 is located in a suitable place to receive commands from an external transmitter that signals the controls inherent within the single controller 138.

The infrared control mode switch 134 controls the operation of the infrared control 61 and the light sensor 64. When the infrared control mode switch 134 is in the 'DN' position such that the infrared control 61 is directly coupled to the control bus 142, the infrared control 61 is the infrared remote receiver 59 It works very similarly to a manual dimmer that maintains a dimming signal from a far-infrared transmitter. When simply operated with a manual dimmer, the infrared control 61 directly adjusts a control signal to the internal control bus 142.

However, when the infrared control mode switch 134 is in the 'UP' position which directly connects the infrared control 61 to the optical sensor 64, the infrared control 61 is the optical sensor 64. ) To the position that controls the light output. In this way, the user does not adjust the amount of light output by one artificial light source, but rather adjusts the total amount of natural and artificial light within the area detected by the light sensor 64. As mentioned before, the method of lighting control is called dynamic lighting stabilization.

Note that the alternate arrangement and packaging of the controls has a similar behavior. For example, the infrared remote receiver 59 and infrared control 61 will be physically and electrically integrated. In addition, the infrared control mode switch 134 is absent while preferentially acting (direct dimming or dynamic lighting stabilization) for the permanently fixed infrared control 61 by wire connection design.

The inner-controller control wire 165 is connected to the connectors J1, J2, J3 together with the other lighting controls, and the connector J7 is connected with the other controllers or ballasts. The inner-controller control cable 165 provides a path for control signal communication between the single controllers and other lighting controllers, somewhat later described ballasts.

6 is a block diagram of a dynamic lighting stabilizer. Artificial light 94 as well as light converter 96 responsive to the input light from natural light 95 generate a signal at its output. The lighting transducer 96 is a component that responds to variations in light energy having converted electrical characteristics. Such transducers will include any photosensitive means coupled with a photodiode, photoresist, or circuitry that converts or amplifies the output signal to an analog signal of the illumination stimulus.

The dual-rate control amplifier 98 compares the signal output by the transducer 96 with the reference voltage 100, and polarity proportional to the difference between the illumination transducer 96 signal and the internal reference voltage 100 (error). Produces an output signal with an over slew rate magnitude. The dual-speed term is adjusted to two distinct values in which the proportional constant that relates the dual-speed amplifier 98 defined above to the 'error', for example, affects for a given error. Explains about the facts.

The proportional constant will be alternately adjusted to multiple values or stored continuously. The voltage reference 100 signal is completely governed by a signal that is communicated to the external illumination stable signal wire 136, which is a signal line of lower impedance such that the output impedance of the voltage reference 100 completely controls it. High enough to allow an external control signal from 136).

The external illumination stability control signal is emitted from the infrared control 61 and transmitted to the optical sensor 64 through the infrared control mode switch 134 at the 'UP' position. From then on it is transmitted to the error amplifier 98 via an external illumination stability signal wire 136. Therefore, the user adjusts the adjustment point for the error amplifier 98 via infrared remote control. When the infrared control mode switch 134 is in the 'DN' position, no external signal is received via the signal wire 136 and the internal voltage reference 100 is single adjusted for the photosensor 64. Set points

In addition, the illumination stabilization signal does not need to be transmitted from the infrared control 61, and the signals alternately carry out computer control or voltage control signals of lower impedance than the voltage reference 100 in the signal wire 136. Other means for determining will be delivered from the manual dimmer arrangement. In addition, the physical proximity of the optical sensor 64 and the infrared control 61 within the single control device 138 facilitates communication of the control signal via the signal wire 136 and other arrangements of the optical sensor. 64 and the infrared control 61 make it possible to move away from each other.

The output of the double-speed error amplifier 98 is inspected by a window comparator 102 that determines whether the error amplifier output is within a given linear range. The output of the window comparator 102 activates a starter indicator LED D2K to indicate whether the signal is within the detection range of the window comparator for the purpose of manually storing the optical sensor illumination response. Once control loop saturation initials for the photosensor are determined, it is desirable to indicate the state of the control loop. This is done by observing the light output response of the system in response to the movement of the control set point.

In the present invention, the error start indicator is displayed when the system exceeds the minimum or maximum loop saturation start, or both. In general, the indicator will be an illumination source that can be seen from the outside of the control enclosure so that a technician who adjusts the error beginning while the control is in a computational state can detect the beginning. There are many different ways in which lighting can be presented at the beginning. However, representing the illumination source in the preferred mode is to illuminate the light between the minimum and maximum error signals, which will be cut when the loop is saturated.

Switch S1E represents the slew rate of the error amplifier 98 for a given input error signal, both a cyclically increasing electrical switch as well as a passive switch. When using a manual switch, the increased slew rate of the amplifier is provided to assist in functional checks and circuit adjustments with respect to what is found during normal operation. During normal operation, the slew rate slows the rapid change in radiated light and the sudden change in artificial light which is convenient for the user. However, during the adjustment of the saturation start for the optical sensor, the slow slew rate increases the time required during the measurement.

Therefore, a fast slew rate is advantageous during manual adjustment. In some form, the system acts as simple light control only by the window comparator without the electrical actuation or dynamic illumination input of the switch S1E. In this simple form, the switch S1E becomes much more advantageous to operate through electrical operation during the initial energy supply period when the fast slew rate is easy for short term system stability.

In addition, the switch with dynamic lighting stability is electrically adjustable. The window comparator 102, which is connected to the output of the double-speed error amplifier 98, transmits when the output of the error amplifier 98 is out of a predetermined range or via a signal wire 136. It is designed to be detected when it is being driven from one limit to another faster than a predetermined rate indicating a high rate change of the external control voltage or a high rate change of the illumination level striking the illumination converter 96.

If one of these situations occurs, the window comparator 102 closes the switch S1E, which increases the loop speed. The window comparator 102 is designed such that the switch S1E remains closed for a period of time after the error amplifier 98 comes out of saturation or stops the slew in a short period of time. This allows the amplifier 98 to quickly return to adjustment after generating a saturation termination or after a significant change in the external input control voltage.

The electrical control of the slew rate of the double-speed error amplifier 98 via the switch S1E allows for changes made by the user in lighting stability to ensure that the system affecting the lighting 94 is registered immediately. The change initiated by such a user quickly changes the external input control voltage through the wire 136 which affects the closing of the switch S1E. Moreover, electrical control of the switch S1E allows the system to quickly re-establish equilibrium in the event of equilibrium being interrupted.

The system is often far from equilibrium when the light 94 is turned on because the light modulator 88 has to be adjusted to provide full illumination from the light 94 at the start. Another purpose for this adjustment is for the user to get instant feedback in which the lighting responds to the command and the lighting system is free of defects. However, systems that adjust quickly and allow the user to adjust the desired lighting level are more ergonomically pleasing. In this case, a quick readjustment is provided by the electrical regulation of the switch S1E with the illumination detected by rapidly changing the system during the start-up of the system. The result of a quick balance can be provided by implying an alternative in the switch S1E that includes various combinations of both digital and analog circuits.

The condition must be adjusted so that the slew rate of the double-speed error amplifier 98 does not change continuously during the normal operation of the lighting system while the electrical closure of the switch S1E is being performed. If the lighting system varies by more than 5% below 500 Hz, the electrical closure limit of the switch S1E provides a satisfactory adjustment to the observer. The switch S1E should normally open within 1 second of the closing operation under the conditions described above. Of course, other adjustments will be satisfied in other offices or work environments.

It should be noted that the system is a closed feedback loop in which the double-speed error amplifier 98 generates a control signal that acts on the illumination modulator 88 which affects the incident illumination hitting the illumination transducer 96. The signal is input to the error amplifier 98 to complete the loop. The feedback loop is operative to adjust the overall incident illumination to the scene sensed by the light transducer 96. The optical sensor is adjusted to provide the desired illumination level by adjusting the value of the reference voltage 100 and the amount of light that strikes the illumination transducer 96 to provide a shape to the input error amplifier 98.

The present invention allows the window comparator 102 to be adjusted to include all signals detected only by whether the loop is adjusting and correct and whether the loop is adjusting or saturated. In the above, the start indicator (LED D2K) is illuminated only during the saturation period. However, the circuit can be easily arranged such that the LED D2K illuminates only during normal adjustment periods (other indications are active). In this case, the indicator LED 104 serves a second purpose, indicating that the operating power source is present in the circuit since both the operating power indication and the normal loop adjustment provide dual adjustment.

The initial indication may be acted on by various other alarm means rather than via LED D2K, including an audible or electrical indicator. In addition, the error signal indicator not only needs the maximum and minimum reachable values of the error signal but also includes other values.

It is beneficial in any environment, such as to include multiple indicator lights, one to display the maximum reachable value, and the other to indicate to the technician the minimum attainable value that reduces the possible ambiguity provided by the light sensor. Should be. It is advantageous if the switch S1E is closed when a large change in the signal from any source is encountered, or during the return period from loop saturation, when the unit is initially energized.

7 is a schematic diagram of an optical sensor with two loop-response speeds operating without dynamic lighting stability. This method is consistent with FIG. 6 by the voltage reference line 136 terminating the voltage reference 100 while not accepting an external input.

The photodiode D1R in the combination with current / voltage converter 106 constitutes the lighting converter 96 in the case of a light / voltage converter having an output at node E5K. During normal operation, the embroidery switches S1K and S2K are open. The illumination associated with the voltage at E5K is compared with the reference voltage at node E1K seen through resistor R3K at the nonconducting input of error amplifier 97, generated by reference voltage element 100.

The output of the error amplifier 97 reacts by slewing at E5K and E1K in a speed and direction proportional to the difference in magnitude of the voltage. Capacitor C1K and resistor R1K define the slew rate of amplifier 97 for a given error input. The output of the error amplifier 97 is a current stored by the unidirectional signaling means 130 and provided to the output of the output node E4K. Closed loop operation is achieved by connecting the output node E4K to the control input of an external variable illumination source having an intensity proportional to the voltage of the output node E4K and an illumination source of the diode D1R that at least partially illuminates. The circuit is arranged such that the increase in illumination hitting the diode D1R reduces the light output from various illumination sources, outside of the bar being balanced. The resistor R4K adjusts the reference voltage by adjusting the amount of illumination and the loop that strike the diode D1R.

The capacitor C1K and resistor R1K provide slew rate control for the amplifier 97 that can be used during normal operation. If measurement or adjustment is required, the loop speed defined by the feedback component of the amplifier 97 can be modified by closing the switch S2K. As the switch S2K is closed, the resistor D2K is disposed in parallel with the resistor R1K. The reduced equivalent resistance rapidly advances the slew rate of the amplifier 97. This allows the result of adjusting the reference voltage by adjusting the resistor R4K, which has less than a delay because of the faster loop response.

The switches S1K and S2K together function as both electrical and passive switches having the function S1E in FIG. In addition, the circuit configuring the error amplifier 97, capacitor C1K, switch S1E (from the S1K and S2K switches) and resistors R1K and R2K has the function of double-speed error amplification of FIG. Combined to give.

A plurality of comparators 114, 115 according to a pair of offsets 240, 242 are inputs that form a voltage at node E1K with a positive (+) (−) offset 240, 242 voltage and at node E5K. Together, we construct a window comparator. During the normal operation period, when the switch S2K is in the open state and the voltage at the node E5K lies in a window generated by the voltage of the positive (+) (−) offset 240, 242 node E1K, The outputs of both comparators are in their initial state, if the voltage at node E5K is outside the voltage window, one of the comparators will change state. Since the outputs of comparators 114 and 115 are connected together in OR logic, 122 is triggered by an IORO gate once both are activated. The one-time 122 is designed to change state for the entire time the trigger is activated and for a positive predetermined one-time time after the trigger ends. When triggered by the OR gate 140, the electronic switch S1K closes.

This arranges the resistor R2K in parallel with the resistor R1K. The parallel coupling has a reduced equivalent resistance that rapidly advances the slew rate and loop response of the double-speed error amplifier 98. This causes large and sudden changes in the voltage value of the node (E5K or E1K) to trigger a faster response than would otherwise occur. Furthermore, the loop saturation state is to be detected as a constant difference between the voltages of each node E1K, E5K. Therefore, return from loop saturation is facilitated by the faster loop speed provided by the detection of the window comparator. Current buffer 120 activates LED D2K, which indicates the state of the current loop lie.

The unidirectional signaling means 130 comprises a circuit for detecting whether a load is present at the output. If no load is present at the output, the sense circuit exits the trigger, E6K, at the first 122 through IORO gate 140. Therefore, the loop speed is increased and the rest is increased while the load is not present at the output E4K and after the load is placed at the output E4K for a 'one time' time. This typically returns to faster adjustment when applied to a load that is the control signal for various lighting sources.

8 is a schematic diagram of a dynamic lighting stabilizer having a double loop speed that includes automatic measurements. Multiple switches S1R, S2R are shown here in mode during normal operation. Non-volatile digital voltage divider 222, photodiode D1R coupled with feedback element and current / voltage converter 106 forms an illumination converter 96 in the case of a light / voltage converter. Including other lighting conversion means is also applied. The practical guidance of the present invention requires a means for outputting an analog signal only to the light striking the transducer while at the same time varying the output signal ratio for a given illumination stimulus under the control of the measuring means.

The diverter output voltage at node E7R is related to the current generated by the value of the feedback resistor to digital divider 222 and the level of illumination striking photodiode D1R. The error amplifier 97 is the difference between the node E7R voltage seen through resistor R1R and the reference voltage 236 seen through resistor R3R at the node E1R voltage and the non-switched input. Amplify The resistor R1R and the capacitor C1R adjust the response speed and the slew rate of the amplifier 97. The output of the amplifier 97 is a current which is provided to the output node E4R and stored by the unidirectional signaling means 130 at the same time. Closed loop operation is achieved by connecting the output node E4R to the control input of an external variable illumination source with intensity responsive to the photodiode D1R at least partially illuminating the light source and the output node E4R. The circuit is arranged to reduce the illumination output from an external, variable illumination source where the increase in illumination striking the photodiode D1R is balanced.

The resistor R3R provides an impedance between the reference voltage 236 and the unconverted input of the amplifier 37, which is as if the external voltage is connected to an external control voltage input E6R. When the voltage input to E6R has a low source impedance and the switch S1R is in a normal operation state, it is as if an external voltage can ignore a voltage known through the resistor R3R.

At the same time, the error amplifier 97, the capacitor C1R, the electronic switch S2R and the resistor R1R (R2R) function as a dual speed amplifier 98.

A schematic flowchart of the process involved in the measurement is shown in FIG. 26A, which can be understood in connection with FIG. The measurement of the circuit is started by promoting the measurement mode input signal E5R. When the input signal E5R starts, the switch S1R changes state, removes the external control voltage input E6R from the non-switched input of the amplifier 97, and the non-switched input of the amplifier 97. Is replaced by the reference voltage 236 potential and the offset 234 is added. Thereafter, the input signal E5R closes the switch S2R through the IORO gate 140 and the first 122.

The resistor R2R, now parallel to the resistor R1R, increases the slew rate of the resistor 97. Together with the large voltage applied to the node E1R this adjusts the output of the amplifier 97 to the maximum control limit and ensures the maximum output signal of the output E4R and thus the maximum from the various illumination sources. Illuminance is controlled. The input signal E5R also activates the enable line of the unconverted digital voltage divider 222. Since the reference voltage 236 is related to the maximum functional voltage, the maximum illuminance applied from various illumination sources is controlled. If there are no other lighting sources and various external lighting sources are at their maximum, the light hitting the photodiode DIR is at its maximum. By doing this, the voltage of the node E7R becomes the maximum control voltage value, so that the measurement can be performed, and the external various illumination sources also reach the maximum at that time.

Referring in more detail with reference to FIG. 8, the measurement is made by a window comparator that checks the voltage at node E7R in relation to reference voltage 236. Offset 232 creates a voltage window for the comparators 114, 115. One of the comparators will be started if the node E7R voltage drops out of the window. The circuit arranges the comparator to start and adjust the nonvolatile voltage divider 222 in the direction of returning the node E7R voltage toward the center of the voltage window. This automatically adjusts the gain of the amplifier 106.

Therefore, the automatically selected feedback resistance value is stored in the non-volatile digital voltage divider 222 when the measurement mode signal input E5R is reactivated. Because the voltage divider 222 is non-volatile, the resistance value remains stored when the system is energized again, in order to avoid the need to remeasure each time the power is returned. appear. As the signal input E5R is reactivated, the first 122 remains active for a pre-adjusted time.

This reduces the time required for the circuit to return to regulation while maintaining the amplifier 98 in a faster response speed mode. The unidirectional signaling means 130 comprises a circuit for detecting whether a load is present at the output node E4R. If the load is not present at the output node E4R, the sensing circuit flows out the trigger at a time 122 through the IORO gate 140.

Therefore, the loop speed is increased and the remainder is increased for 122 times while the load is not present at the output node E4R and after the load is located at the output node E4R. This typically allows for a faster return to adjustment when applied to a load that is a control signal to various lighting sources.

9A is a schematic diagram of a dynamic automatic stabilizer with automatic measurement and double loop speeds performed by means other than that of FIG. 8. In normal operation, the electrical switch S2R and the switch S3R are opened while the electrical switch S4R coupled with the node E1R and the external control voltage input E6R is closed. Photodiode D1R, coupled with current / voltage converter 106, feedback element, and non-volatile digital voltage divider 223, is coupled to the value of feedback resistor and voltage level of photodiode D1R in voltage divider 223. In the case of a light / voltage telephone with an output voltage at the node E7R concerned, it forms an illumination converter 96.

The error amplifier 97 amplifies the difference between the node E7R voltage seen through the resistor R1R and the node E1R voltage at the unconverted input of the error amplifier 97. A reference voltage at the input node E1R is applied to the non-switched input of the amplifier 97 via a micro-controller 238, node E7R through a first analog / digital A / D, resistor R5R. It is the response of the reference voltage 228, which is processed by the analog / digital (A / D) that passes through to the node E8R and is processed internally.

The resistor (R5R) is the signal received by the external control voltage input (E6R) is the error amplifier (E8R) so as to reverse the node (E8R) voltage if the impedance of the signal is lower than the impedance provided by the resistor (R5R) At the end of the non-switching of 97, an impedance is provided between the voltage E1R and the reference voltage E8R. The microcontroller 238 continuously monitors the external control voltage input E6R on a line 136 that uses an A / D converter for the microcontroller 238. The circuit is operative to maintain the continuous total illumination detected by the light transducer 96 (the illumination plus the artificial).

The resistor R1R and the capacitor C1R adjust the response speed and the slew rate of the amplifier 97. The output of the amplifier 97 is a current which is temporarily stored by the unidirectional signaling means 130 and sent to an output node E4R. If no load is present, the sense circuit will trigger the trigger once 122 via IORO gate 140. Therefore, the loop speed is increased and the remainder is increased for 122 times while the load is not present at the output node E4R and after the load is located at the output node E4R. This typically allows for a faster return to adjustment when applied to a load that is a control signal to various lighting sources.

Optionally, the microcontroller 238 senses a change in the external control voltage input E6R at an input 136 that is larger than a predetermined beginning, and the microcontroller 138 is configured to output the error amplifier for a predetermined time. Triggering the one time 122 that increases the slew rate of 97 causes the command to flow through the output line 274 to the input of the OR gate 140. As a result, quick adjustment redundancy occurs when the system changes the automatic or manual adjusted illumination.

Closed loop operation is achieved by coupling the output E4R to the control inputs of various external lighting sources having an intensity responsive to the output node E4R voltage and an illumination source that at least partially illuminates the photosensor D1R. The circuit reduces the light output from various external lighting sources such that the increase in overall illumination coming to the photodiode D1R is balanced. The resistor (R5R) has a lower source impedance to the external control voltage input (E6R) if the external voltage is coupled to the external control voltage input (E6R) and the resistor (R5R) if the switch (S1R) is in the closed position. It provides an impedance between the non-switched input of the amplifier 97 and the repeated reference voltage of node E8R so as to reverse the voltage seen through.

The measurement is performed with or without the presence of a constant source of enclosed illumination. In external and variable illumination sources and in the absence of illumination that is not the external variable source at maximum brightness, the control voltage E4R in which the voltage of the switch 106 of the output node E7R matches the maximum brightness of the external variable illumination source. Is equal to the maximum value of. To this end, an effective measurement process is calculated by subtracting the effect of the enclosed lighting, which can be used to obtain precise measurements.

A summary flow chart of the steps involved in the measurement is shown in FIG. 26B, which is understood to be combined with FIG. 9A. The measurement of the circuit is initiated by activating the measurement mode signal input E5R. The switch S4R is opened while the signal input E5R is activated, and the external control voltage input E6R is disconnected from the node E1R. Furthermore, the signal input E5R closes the switch S3R, which switches the amplifier 97 to a voltage follower for the voltage shown at the non-switching input E1R. The IORO gate 140 The signal input E5R is triggered by the first time 122 where the resistor R2R formed in parallel with the resistor R1R is positioned and the switch S2R is closed. The signal input E5R enables the measurement procedure inherent in the microcontroller 238.

In response to the permission signal E5R, the microcontroller 238 initializes an initial program for performing automatic measurement processing. The node E8R voltage is regulated to a voltage equal to the maximum control voltage as it is known that the external variable illumination source produces the brightest illumination. For lighting purposes we assume that the maximum control voltage is 10 kW. The resistance of the nonvolatile digital divider 223 and the gain of the amplifier 106 are proportional to the binary data bus 244 when the digital divider 223 is permitted. The microcontroller 238 can use the data output bus 244 to permit the digital voltage divider 223 to be allowed by the digital voltage divider resistor providing maximum gain to the amplifier 106 and activating the enable line E9R. Adjust to the maximum binary number.

The node E8R voltage is fixed at 10 kHz. The voltage is passed by the amplifier 98 which acts as a voltage follower to the external variable illumination source, the output node E4R and to the unidirectional signal means 130 which reacts by providing the maximum illumination.

The voltage at node E7R is ignored because the amplifier 98 is switched to a voltage follower for the non-switched input. The microcontroller 238 then incrementally increases the gain of the amplifier 106 by the digital voltage divider 223 until the microcontroller 238 calculates the node E7R voltage until the microcontroller 238 becomes 6 kV. Decrease the data bus 244 which is decreasing.

At this time, the binary number appearing on the data bus 244 is sent to a memory in the microcontroller 238. The controller 238 reduces the node E8R voltage to 5 kV. The voltage is passed through to the output E4R where the external and variable illumination source brightness is reduced by 50% of the full state. The new lower low voltage at node E7R is dedigitized and stored. For the sake of explanation, we assume a value of 4 ms for node E7R.

The value is subtracted from the pre-read value of 6 ms and digitized equivalent. The result (6 μs-4 μs = 2 μs) is divided by the original 5 μs difference in the control signal representing an amplifier gain of 2/5. If the gain of the amplifier is to be measured, 1/1 will be seen in terms of gain, i.e. a 5 dB change in the amplifier is a 5 dB change in the control signal. In terms of gain of 2/5 or 5/2, they are calculated because they are multipliers required for the amplifier to obtain a gain of 1. The stored binary and new binary numbers are adjusted on the data bus 244 when the amplifier initially reached 6 kHz is mutually increased. In the digital voltage divider 223, the permission line E9R in which the nonvolatile gain information is stored is released. The system is now being measured.

When the measurement mode input E5R is released, the amplifier 98 returns to the eye error amplifier mode and normal operation excludes the first 122 still maintaining the closed state of the switch S2R. And start again. This allows the amplifier 98 to maintain a fast response speed and quickly return to loop in adjustment. The round 122 then ends and the loop slows down the operation.

9B is a schematic diagram of a dynamic light stabilizer with automatic measurement and dynamic full effect light stabilization, double loop speed. The purpose of this circuit is to maintain a constant total effect illumination (TEI), which is the sum of the time components of artificial and external lighting. This is distinguished from the dynamic lighting stabilizer described in Figures 8 and 9A, which stabilizes the sum of the exterior and perforated lighting without increasing the exterior lighting. The dynamic lighting stability may be considered a particular case in which the weighting factor of the external lighting is always equal to one in the calculation of the TEI. For this discussion, we consider natural lighting (although other sources of lighting, such as high intensity discharges and area lighting can be applied), the usefulness of TEI differs from the characteristics of the spectrum of the artificial and negative vision and Lambert. Extract. Therefore, compensation for the change in natural light by the amount of artificial light that depends on the location and source of natural and artificial light as well as the environment in which the light is illuminated will provide an effective change in the light perceived by the user.

In order to adjust the TEI output of the dynamic lighting stabilizer, the amount of artificial and natural lighting components must always be known. The following discussion assumes proper measurement of the means by having the node E7R voltage equal to the maximum output value at which the external light modulator responds under control output E4R. The measurement process is discussed below. The artificial lighting is calculated as an element of the output control voltage E4R extracted from the D / A output 270 of the microcontroller 239. Therefore, the information can directly access the microcontroller 239. The total amount of illumination is made available from the output of the illumination transducer 96 which samples a certain area directly under control, the information being fed into the microcontroller 239 by the node E7R. From these two values, the amount of natural light is calculated by subtracting. Thereby, if T is total illumination, N is natural lighting and A is artificial lighting. By the above definition, T = A + N and thus N = T-A.

The total effect illumination (TEI) is to be calculated by the microcontroller 239 through the formula TE1 = A + XN. Here, X will generally be larger, but is a weighting factor that is greater or less than this. In the following discussion, it is believed that X is a constant, although the guidance of the present invention is that X will be a variable function of the total illumination T or external control voltage input E6R. The microcontroller arch is involved in a closed loop feedback system where the output control voltage E4R is varied such that the difference between the external control voltage input E4R and the calculated TEI is minimized.

The rate of change of the output 270 from the microcontroller 239 through the unidirectional signaling means 130 to the illumination modulator coupled to the output E4R may vary based on the value of the input 272. Can be adjusted by an internal time constant. In the first state, the time constant provides a smooth and gradual change in artificial illumination in normal operation. In the second state, the time constant is determined after the desired illumination interruption in which the TEI is registered with the external control voltage input E6R. Provides quick restable of illumination to be returned. Such a collapse is input to the microcontroller 239 through the OR gate 140 and line 272 which occur under at least three following situations. In the first case, it is beneficial for the system to recover adjustments as soon as possible for the predetermined period of time stored in the microcontroller 239 and at the end of the measurement. In the second case, the unidirectional signaling means 130 comprises a circuit for detecting whether a load is present at the output node E4R. If a load is not present at the output, the sense circuit flows a signal through the IORO gate 140 to the microcontroller 239 by line 272. The loop speed is increased and the others are increased while the load is not present at the output node E4R and for a predetermined period of time stored in the microcontroller 239 after the load is located at the output node E4R. In the fourth case, the microcontroller 239 continuously monitors the change in the external control voltage input E6R. If the input change exceeds a predetermined beginning indicating that the lighting network by automatic or manual means causes the desired lighting input to change, fast restable of the system is performed.

The measurement is performed with or without the presence of a source of invariant enclosed illumination in a manner similar to the dynamic lighting stabilizer of FIG. 9A. The following notions pertain to both FIGS. 9B and 26B.

The measurement of the circuit is made by activating the measurement mode signal input E5R. Signal input E5R via the IORO gate 140 by line 272 changes the interval time constant in the microcontroller 239 to permit re-stable fast lighting as described above. The signal input E5R permits the inherent measurement order to the microcontroller 239.

In response to the permission signal E5R, the microcontroller 239 initializes an initial program for performing an automatic measurement process. The output voltage on line 270 is adjusted to a voltage equal to the maximum control voltage that tells the external variable illumination source to respond when it produces the brightest illumination. For illumination, suppose we assume that the maximum control voltage is equal to 10 kW, the resistance of the nonvolatile digital voltage divider 223 and the gain of the amplifier 106 are the data bus 244 when the digital voltage divider 223 is permitted. It is proportional to the binary number of. The microcontroller 239 adjusts the data output bus 244 such that the digital voltage divider resistor permits the digital voltage divider by activating the permit line E9R while providing maximum gain for the amplifier 106.

The voltage at the control output line 270 is fixed at 10 kW, and the output node E4R reacts by providing maximum illumination. Then, the microcontroller 239 continuously reduces the data bus 244 which gradually decreases the gain of the amplifier 106 by the digital divider 223, and the microcontroller 239 Calculate the node (E7R) voltage up to 6Ｖ.

At this time, the binary number appearing in the data bus 244 is sent to the memory in the micro control unit 239, the control unit 239 reduces the voltage to the output line 270 to 5 kW. The voltage is again passed through the output E4R, where the external and variable illumination source brightness is reduced by 50% of full state. The new lower node (E7R) voltage is digitized, for the sake of explanation, we install a 4 Ｖ value at the node (E7R). The value is subtracted from the pre-read digitized equivalent of 6 ms. The result (6Ｖ-4Ｖ = 2Ｖ) is divided by the original 5 원시 difference in the control signal resulting in an amplifier gain of 2/5. If the amplifier gain is measured, the gain perspective should be 1/1, i.e., the 5 ms conversion in the amplifier is preferably for a 5 ms change in the control signal, a mutual gain perspective of 2/5 or 5/2 is a gain of 1. Because of the multiplier required for the amplifier to obtain

When the first 6 kHz amplifier is increased by one another, the binary and new binary numbers are adjusted to the data bus 244. The permission line E9R storing the nonvolatile gain information in the digital voltage divider 223 is released. Currently, the system is being measured and the values of the result inputs E6R, E7R of the measurements in the absence of uncontrolled or natural lighting are nearly equal. When the measurement mode input E5R is cleared, the internal time number of the microcontroller is recovered after a predetermined time stored in the microcontroller 239, and the feedback loop slowly returns the operation speed.

In the absence of an external control voltage input E6R, the resistor R3R receives the microcontroller 239 in the input line 136 of the reference voltage 228. The reference voltage 228 is made equal to the maximum control voltage that indicates that the external lighting modulator responds.

What has been described above described the coordination of infrared remote control with an optical sensor providing a new mode of interaction called illumination stabilization. In addition, new uses include the use of external signals most conveniently from the far infrared to the initial measurement of the optical sensor. The following description extends to the cooperative mode of the sensor, including between the occupancy sensor and the infrared remote.

In the above, the measurement of the occupancy sensor is difficult because the presence of a person affects the measurement because the person performing the measurement cannot be physically located close to the occupancy sensor. The infrared remote control provides a means for communicating with an occupancy sensor that is effective for measurement. 10A is a schematic diagram of a travel sensor that permits remotely operated measurements including both manual and magnetic measurement modes. The signal from the element 210 that senses movement is amplified by the first amplifier 212. The gain of the first amplifier 212 is governed by a nonvolatile digital voltage divider 225 and disposed as a feedback element for the first amplifier 212, the output of the first amplifier 212 being the second It is further amplified by amplifier 214 and applied to one input of comparator 216. Normally in the detection mode, the comparator 216 passes through the trigger input of the timing circuit 218. The timing circuit 218 provides an output for a predetermined length of time after being triggered by the output of the comparator 216. The output of the timer 218 passes through the input of the output terminal 220 and the output node E8C. In this case, the output node E8C does not have a match found between all the occupancy sensors connected to the polling signal input E11C and the polling signal E such that the output terminal 220 does not come down to the output node E8C. Under the control of E11C), the output stage 220 includes a temporary storage of current and calculates the adjustment of the bath and level when it is determined that the occupancy sensor is not occupying the room, as well as the adjustment of the time of lower or rising illumination. It includes many other features. The internal components constituting the output stage are described in more detail below.

Upon receiving a measurement command from all of the plurality of measurement command inputs E10C, E12C, E13C, and E16C, the measurement cycle is initiated. During that time IORO gate 230 is activated at the output of node E15C. This permits adjustment of the nonvolatile digital potentiometer 225 and prevents the timer 218 from operating and draining the output. At the energized position again, as shown at the output of the comparator 216, the electrical switch S1C is tied to the UP / DOWN input of the digital voltage divider 225. The voltage divider 225 is allowed and the circuit moves the digital voltage divider 222 in the direction required for the output E14C to increase the gain of the amplifier 212 if the comparator 216 is not started. Arranged to adjust. Conversely, if comparator 216 is started, the circuit is arranged to further lower the gain of amplifier 212.

If the measurement command input E10C (automatic measurement until release) is activated, the given stimulus is applied to the movement sensor 210. The circuit will continue to adjust the gain of the amplifier 212 in the correct direction until the output of the comparator changes state. The change state of comparator 216 indicates that a measurement is made. The circuit then reverses the gain adjustment made in the comparator 216 across the beginning again. Therefore, the circuit will continue shaking with the measuring point until the measuring input E10C is released. Since the angular decrease and increase of the digital voltage divider 222 is small and the gain change of the amplifier 212 is small, the system causes the state of the comparator 216 to be measured at the moment of release of the measurement command.

If the measurement command input E12C (time adjusted measurement) is activated, timer 224 is triggered. The output of the timer 224 allows the digital voltage divider 225 through an IORO gate 230. At this time, the measurement command input E12C is released and the measurement is exceeded by the timer 224 output while terminating the measurement cycle and timer 224.

When the measurement command input E13C (automatic measurement until the beginning is reached) is activated, the flip-flop 226 is IsetO. The flip flop 226 output allows the digital voltage divider 225 through the IORO gate 230. Once the process has occurred the command line input E13C will be released and the measurement mode continues by the flip-flop 226 output until the comparator 216 output changes state. The circuit is arranged such that the state of the comparator output E14C changes in the direction IresetO flip-flop 226 at which the measurement cycle ends.

Manual adjustment is made by activating the manual measurement command input (E16C). Activation of input E16C allows digital voltage divider 225 and suppresses timer 218 via IORO gate 230. At the same time, the E16C switches the switch S1C. This disconnects the comparator output E14C from the Iup / downO input of the voltage divider 225 and connects the Iup / downO input of the voltage divider to the manual adjustment input E9C. While E16C is active, the potentiometer is adjusted in the direction indicated by the manual input (E9C) state.

Various measurement commands described above are allowed within the same specification as shown in FIG. 10A. Or only a few commands may be used in one embodiment. The control of commands via inputs E9C, E16C, E10C, E13C, E12C is generally controlled through the use of input means separate from the occupancy sensor. Since the means are physically far from the occupancy sensor, the user will initiate a measurement from a distance that is not in proximity to the occupancy sensor, involved in the measurement or moving outside of the doorway.

As noted above, conventional occupancy sensors respond by turning on and off the lighting, where the preferred mode of light control is largely unsuitable for use in a network where the brightness of the individual light is rather than on / off of the light. do. The method of the current invention can use an occupancy sensor to change the illumination level from the individual illumination. This provides two basic benefits. First, the fluorescent lamp life is greatly reduced by frequently turning on / off. Lamp life is greatly extended by using brightness modulating lamps which provide the energy advantage of occupancy sensing. Second, people do not have to enter and adjust a dark room, such as a bathroom, which is good for triggering an occupancy sensor. In such cases, the occupant feels uncomfortable and fearful or hurts himself. This problem is particularly exacerbated by the on / off cycle, where the lamp ignition takes a perceptible time to accompany the occupancy sensor. The method of the present invention is intended when the occupancy sensor determines that the room is not occupied so that the person entering the room has enough lighting to see the surroundings before the occupancy sensor triggers, before the rooms still have significant energy saving benefits. The low light level will light it up.

The method of the present invention provides a different rate of change of illumination when the illumination is going up or down by the occupancy sensor. For this difference in timing, if the occupancy sensor incorrectly reduces the light level and determines that the room is not occupied, it gives the occupant an ergonomic and safe advantage. Slowly decreasing the lighting allows the occupant sensor to know the presence of a person by deliberate movement before the occupant significantly reduces the lighting level. On the other hand, if the light enters a room already reduced by the occupancy sensor, a quick return of the higher light level is essential for the occupant's safety and comfort.

FIG. 10B is a schematic diagram illustrating the output terminal 220 of the occupancy sensor of FIG. 10A. Three separate functions are shown, including the ability to adjust the dimming level to provide a separate speed to raise or lower the output signal to perform polling between the occupancy sensors in the manner described above. Lose. The circuit depicting this feature has some similarities to FIG. However, the differences between the other embodiments will become apparent because of the additional functionality described above.

The absence of an active polling signal at the input signal E17C and at the input E17C to a sufficiently low voltage (reactivated) output terminal 220 at the capacitor C11C and the reverse bias diode D11C in the detection circuit. The set of potentials is made sufficient by the voltage divider R13C through R12C). The force potential stored in the capacitor C11C is temporarily stored by the unidirectional signal means 130 and passed to the output node E8C. Therefore, by adjusting the value of voltage divider R13C, output node E8C can be adjusted to a desired voltage level. Thus, the dimming level detected by the occupancy sensor is adjusted when determining that the sensor is not occupied in a certain area. Within the guidance of the method of this expression, voltage divider R13C is replaced by a fixed voltage divider or by electrical means to provide a desired fixed or variable voltage.

When the occupancy sensor determines that the inspection area is occupied, the input E17C is activated and rises to a voltage at least equal to the highest control voltage at which the illumination system responds. The diode D11C is a forward bias in which a voltage almost appears at the top of the resistor R11C through the forward diode D12C, and is a polling signal at the polling signal input E11C. The impedance of resistor R11C is made sufficiently lower than resistor R12C so that capacitor C11C fills a voltage approximately equal to the cathode of diode D12C regardless of the regulation of resistor R13C.

The force potential in the capacitor C11C is temporarily stored by the unidirectional signal means 130 and passed to the output E8C. The value of resistor R11C is less than 1 second by fast time constant (typically filling a different value) so that capacitor C11C has little delay between the cooperative voltage change at the output E8C and activation of the input E17C. Is between 0 Ω and all values combined to give When input E17C is released, reverse bias diodes D11C and D12C and capacitor C11C are regulated by resistor R13C through resistor R12C having a much higher impedance than resistor R11C mentioned above. To the set voltage value. The discharge rate of the capacitor C11C and the charge cooperation rate of the output node E8C are much longer than the charge rate provided when the input E17C is activated. The charge rate of the capacitor C11C is governed by the value of the resistor R11C, and the discharge rate of the capacitor C11C is governed by the value of the resistor R12C. The values of resistors R11C and R12C are predetermined and fixed at the same time, and are adjusted either electrically or manually during the adjustment of the output terminal 220 of the occupancy sensor.

When multiple output stages 220 are connected together to polling signal input E11C, activation of all inputs E17C from multiple output stages 220 raises the polling signal input E11C voltage in all output stages. Since the impedance ratios of the resistors R11C and R12C in all the output terminals 220 described above, all the capacitors C11C of the output terminal 220 is almost charged to the value of the node E11C. The output E8C of all output stages 220 is supplied to the capacitor C11C from the rest of the one or more occupancy sensors 62 even if released if the input E17C determines that certain areas are unoccupied under the sensitivity of the sensors. Will be the voltage. In common with the polling signal input E11C, the input E17C from all occupancy sensors must be released before the capacitor C11C is discharged to the regulated voltage by the resistor R13C.

Other forms of combination of control means (infrared far and light sensors) or similar forms of interaction of control means (polling of occupancy sensors) represent a powerful way of controlling a local network. Next we show how these methods are extended to include interaction control in large, hierarchical networks.

The shared proportional response control system described above operates under equivalent control in a general environment. In the example given in FIG. 1, all are operating within one local latching network, such as a manual dimmer 60, an illumination sensor 64, an occupancy sensor 62, an infrared remote 61, and a local computer control 63. . However, consider a workspace for two people who had a set of light fixtures near a window that provided external lighting. Such installations near the window are treated as photoresist control. While other parts of the room away from the windows and outside lighting are not available. Consider that the entire space corresponds to a centered occupancy sensor. Finally, consider that the total space was immediately controlled by the Building Energy Management System (EMS), which controlled the lighting of the entire plane. This scenario involves three levels of control that used to be irregular in the desired lighting system. We are building an EMS system that controls the entire plane at the top level. At the next level, control of the room area using the occupancy sensor, finally, control of some space, only part of the installation responds to the photosensitive device. While those away from the window need respond to the top two levels of control, it would be useful if the installation near the window responds to all three levels of control. While facilities in different designs on the same plane respond only to higher-level controls, in addition to local controls where local controls may reside in different spaces, conventional lighting systems generally do not handle multiple controls within the same level. While several levels are unknown, those levels require special circuitry and connections. In other respects, a shared proportional response control system will be described below, which explicitly handles multiple levels of control. Each control is connected to the other controls by one of the two points. One point connects for control at the same level or above. On the other hand, the other point connects to control at the lower level connection. A special "lower leＶel" connector blocks the control signals from below, allowing connection to other remaining points for combined control of objects while preventing them from affecting the control signals within a higher level. If other connected controls are within the same level, this represents "supervision control" from the level above it to the current level. This allows for hierarchical control to be established simply from the network connection rather than from special hardware.

In FIG. 5, control at the same or above control level is transmitted on the control bus 144 to the internal control bus 142 via the unidirectional signaling means 130 in a single control. It prevents the voltage in the internal control bus 142 from affecting the internal bus 144. The internal control bus 142 is potentially affected by four managements.-Pass-through internal control voltage, travel sensor 62, light sensing means 64, and connected via unidirectional signaling means 130; Infrared control 61. The internal control bus operates as a shared proportional response control line. Thus, the control requesting the lowest control signal on the internal control bus 142 takes advantage of the pull-down diode 86 and the unidirectional signaling means 130.

Because of the unidirectional signaling means 130, a single control given is controlled at the same or above level than affecting the control over a given control and at a lower level connected to the connector J7.

At the same time, a single control has no influence on the control connected to the connectors J1, J2, J3. This satisfies the requirements of hierarchical control. Complex hierarchical controls within the network can be organized using the same controls or simply establish a link of controls.

11 is a block diagram depicting a lighting network with a single level of control. The single control 138 includes an optical sensor 64, an infrared control 61, an occupancy sensor 62, an infrared remote receiver 59 and a unidirectional signal sud 130. As indicated by the rounded rectangle surrounding "P", "I", "O", and "R", and pointing down, pointing down. Since there is only one level of control each, there is no equivalent control connected to the supervisor or input / pass-through connectors (J1, J2, J3). It is represented by a rectangle within the upper quadrant of the single controller 138.

Four power generating dimmable ballasts 146 are connected to the output jack J7. Since there is only one level of control, any control under the control of one control is connected to the output connector J7 of the single controller 138. Stabilizer 146 responds to any of the three controls within a single control 138. Since there is no equivalent control operating at or above the level of the supervisor or the single control 138, the unidirectional signaling means 130 has no influence in this control environment.

Network cable 166 connects the allasts 146 to a single control 138. This cable contains numerous wires. It includes at least a control signal wire and a return. On top of that, the cable 166 may include a wire that carries a DC power supply with a stable resistor and a polling wire for the occupancy sensor that is polling. In this block diagram, single-control 138 is shown with those internal connections that connect to the control. Wire power, return and polling connections are not shown. Power supplied to the ballast resistor 146 is transmitted to the single control 138 via the network cable 166.

12 is a block diagram depicting an illumination network with three levels of control. In this figure, a number of single controls are depicted. Each showing three input connectors and one output connector. The names for the condensers J1, J2, J3, J7 are topologically consistent from beginning to end of the block diagram. Follow those depicted in FIGS. 5 and 11. Internal controls are assigned to characters in a rounded rectangle. The letter "R" referring to the infrared remote receiver 59, the letter "O" referring to the occupancy sensor 62, the letter "I" referring to the infrared control 61, and the light sensing means 64 The letter "P", inverted triangle, refers to the unidirectional signaling means 130. As in FIG. 11, single controls are depicted with only those internal connections involved in the control during power up. Return and polling connections are not shown.

Network computer control 148 is the highest level of control. It does not have a network input, but only a single output connector 164. The lighting network is divided into two higher level regions. Labeled Zone1 and Zone2. Each with a stable resistor is controlled by a single control. Zone 1 single controller 150 and Zone 2 single controller 152. each. Output from computer control 148 is transmitted via network cable 166 in the input / pass-through connector of Zone 1 single controller 150. The single controller 150 is in rotation connected via an input / pass-through connector J3 to the Zone 2 single controller 152 input connector J1 through the continuity of the network cable 166.

Voltage regulation by computer controller 148 is transmitted to the respective control bus via unidirectional signaling means of single controller 150, 152. This higher level supervisory control voltage establishes a maximum control voltage on the control buses of both Zone 1 single controller 150 and Zone 2 single controller 152. And via the single controllers, note that the choice of connectors J1, J2, J3 for the network connection for the entire network is at will. Thus, all three jacks are in the same environment within a single control. It should be noted that the control voltage at the input connectors of the single controller 150, 152 is solely under the control of the computer controller 148. The single controllers 150, 152 themselves are not able to exert an influence over the voltage in each input control bus.

In this technique, Zone 1 single controller 150 includes only infrared control while it supports an infrared remote receiver. This may mean, for example, that the band-shaped lights control over different areas of a room or the lights control over multiple rooms. The network cable 166 turns out from the single controller 150 and connects both Zone 1 as well as Zone 2 single controller 156 to a pair of stabilizers 146. Thus, it can be seen that both control signals within the network cable 166 can transfer lighting control to other controllers. However, the same signal exerts control beyond the stable resistor output. Zone 1, Zone 2 single controller 156 is connected to the Zone 1, Zone 2 single controller 154 via an input resistor. Because in this third level of control all input connectors in a single controller 154, 156 are in parallel. The single control receiver is the control voltage of the output control bus of the single controller 150. It is set by the lower level control voltage radiating from the infrared control of the single controller 150 and the computer control 148. Thus, in this third, the low level of the single controller 154, 156 responds to the higher level controller 150, 148.

It is noteworthy that many single controls 150, 152, 154, 156, 158, 160, 162 have different supplements of internal control. For example, the single controller 154 has three controls while the single controller 156 has only one control. The single controllers do not have the same control. However, each of these single controls nevertheless retains the remaining characters. Including infrared passive remote input, internal control bus, and input communications via a unidirectional signal buffer. This commonality within the interface supporting the lighting network makes for simple design, installation, maintenance and operation.

In addition, the supervisory single controller 150 and the single controllers 154, 156 are random in the input / pass-through connectors J1, J2, J3. The system has a single controller 150 output connector J7 connected to an input / pass-through connector J2 of a single controller 154 and the input / pass-through of the single controller 154. The connector J1 works equally if it is connected to the input / pass-through connector J3 of the single controller 156.

Each lowest single control affects the artificial lighting thrust within a given area where it will be illuminated by the ballast 146 under control. For this purpose, we mention the single controllers with the zone number design for each single controller. The Zone 2 single controller 152 comprises three single controllers-Zone 2, Zone 1 single controller 158, Zone 2, Zone 2 single controller 160, and Zone2, Zone 3 single controller 162. Supervise). In this example, the single controllers are daisy chained as the Zone1 Zone 1 and Zone 2 single controllers 154 and 156. The single controllers are connected in a star form with multiple connections as a single controller 160. The ability to use both a dach chain and a star-shaped arrangement is widely permitted for connectivity between single controls that make the necessary cable yard during installation. Single controls are configured to have more than three input connectors as described herein. And it is permitted to have wide fluidity in installation. In addition, certain 'star connectors' are permitted to have a star connection between multiple single controllers on the input connector.

The single controllers 154, 156, 158, 160, 162, all of which have three levels, are connected to dimmable lighting ballasts made via a single controller output connector J7. The single controllers affecting a given ballast 146 are connected to the output connector J7 to the circuit cable 166 connected to the ballast and the output connector J7 of the other single controller to the same input / pass over the single controller. It can be determined by following the network cable 166 from the -through connectors J1, J2, J3. By using this logic, one is that the ballast connected to the output connector J7 on the single controller 158 is not controlled by any other controller, but by the computer controller 148 and the Zone 2 single controller 152, Dominated by a local single controller 158.

The structure of the hierarchical network using the method according to the invention uses a unidirectional signaling device 130. These mechanisms 130 may prevent lower level lighting control from affecting the functionality of the higher level control, or may affect ballasts that do not have hierarchical control directly from the controller.

13A-13G are a series of simplified schematic diagrams illustrating another body of a unidirectional signaling device. All of these instruments act as analog DC signal heaters, although other unidirectional signal instruments are applicable to analog DC signal controllers. In most cases, the unidirectional signaling mechanisms of FIGS. 13A-13G can be substituted for one another in light of the differences in the embodiments summarized below.

Page 13

13A is a schematic diagram of a diode operating as a unidirectional current switch. The unidirectional switching method using the diode 86 is widely used in the description relating to Figs. 3, 4, and 5 in which the diode 86 is used as an example because of its simplicity. The advantage of diode devices is that they are not very expensive and take up little space in complex circuit designs. However, a drawback of the silicon diode is that a connection voltage drop of 0.7 kΩ occurs. In Scotting diodes can be used instead as long as they can take full advantage of the normal diode, but they exhibit lower voltage drops.

Since the diode represents a simple and practical unidirectional current switch, the mechanism below provides further advantages as a current buffer. Because of their buffering capacity, these mechanisms can provide additional fan-out for commutation control signals, thus providing improved operation in large networks.

FIG. 13B shows two examples of the use of a transistor operating as a unidirectional current buffer. PNP transistors 252 and NPN transistors 254 at both ends have input signals to the base, output signals from the emitters, collectors are grounded or connected to a power source, and are operated on the polarity of the instrument and the polarity of the signal. This depends. Therefore, the PNP transistor 252 and the NPN transistor 254 are used in the form of a classic emitter follower, and in the application of PNP or NPN, depends on the direction of the load. The advantage of using such a transistor as a current buffer is the current gain, which can control a relatively large output with a small input. This is extraordinarily convenient in large networks. However, transistors have the disadvantage of voltage offset, which is likely to occur from input to output due to the forward junction across the base emitter junction, thus affecting the control signal being buffered.

Figure 13C is a schematic diagram showing two examples of the use of a MOSFET operating as a unidirectional current buffer. The n-channel MOSFET 256 and the p-channel MOSFET 258 have a gate as input, a source as an output, and a drain connected to ground or a power source as shown, and thus the polarity of the instrument and the polarity of the signal. Depends. Therefore, the MOSFET 256 and the MOSFET 258 are assembled in the form of a classic source follower. The advantage of using a MOSFET as a current buffer is that it can achieve near limit current from input to output. In addition, the MOSFETs 256 and 258 show extremely high input impedance. However, due to the inherent starting voltage required for the channel flow, a voltage drop occurs between the gate and the source. In addition, there is generally a big difference in starting voltage device for the same kind of apparatus. The latter two elements described above make MOSFETs less beneficial for use as current buffers in low voltage networks or when the limits cited above control to a lesser or unacceptable extent.

FIG. 13D is a schematic illustration of a diode 86 providing unidirectionality and an op-amp 260 arranged as a voltage follower. The advantage of this voltage buffer is its very high voltage acquisition and very high input impedance.

In addition, the offset voltage caused by the diode 86 is compensated by the high loop gain and feedback voltage at the non-switched input of the OP-AMP 260. However, the output will remain one diode voltage drop higher than the OP-AMP when under control, in saturation, in a control network equipped with the current buffer.

13E is a schematic diagram illustrating an OP-AMP 260 with a classical low voltage follower arranged with an output current boost transistor 252. This configuration shows a higher current capacity than one typical OP-AMP that exhibits very high input impedance as well as very high output current capacity. Transistor base emitter junctions are compensated by the feedback loop and high loop gain. However, in this configuration, the sub voltage is offset by the limit range of control and the base emitter voltage drop.

13F is a schematic diagram illustrating OP-AMP 262 with an integrated NPN open-transistor output structure arranged with a classical voltage follower. The advantage of this configuration is again its very high current gain and very high input impedance. The open collector output structure of the NPN transistor integration in the amplifier 262 provides an output voltage of nearly 0 kV limited by the integrated transistor saturation voltage. However, the structure generally has a less scattering capacity than the structure using an external, discrete transistor.

13G is a schematic diagram illustrating OP-AMP 260 coupled to an external NPN transistor output. The input switching and non-switching termination of the OP-AMP 260 is accurate for the classic voltage follower that includes the signal polarity inversion characteristic of the transistor 254 connected in a common emitter configuration. Therefore, the transition and non-switch symbols shown in the inset phrase are accurate to the classical voltage followers when the circuit considers its entirety. This embodiment provides the same advantages as the arrangement shown in FIG. 13F. However, additionally typically use discrete NPN transistors connected to the output of the op-amp 260, which have a higher spread than the general purpose, commercially available OP-AMP, while providing higher run current capacity.

The single control unit 138 supplies network power to the control means as described below, polls the network hierarchical arrangement and poll-response environmental controls, and employs multiple control coordination using shared proportional response control lines. It is a convenient means for constructing a lighting control network which is permitted. In addition, the single controller 138 is easily installed hierarchically. By careful design, the single controller can be produced at low cost. This chapter describes the design for the single control unit 138 with many of the beneficial features specified above.

14 is a schematic of an exemplary single controller motherboard 168. The motherboard is a central circuit that provides connections for residential controls as well as external controls. In addition, the motherboard 168 provides local voltage regulation and signal current for external signal inputs that affect the local output.

The connectors J1, J2, J3 are input / pass-through connectors wired in parallel. A plurality of connectors J4, J5, J6 are connected to the motherboard 168 having an optical sensor 64, an infrared control 61 and a movement sensor 62. The connector J8 is provided directly from the manual dimmer to a single controller. Finally, the connector J7 output provides an output control voltage for controlling a single controller and lighting modulators at a lower level of control. Multiple connectors wired in parallel with connector J8 provide additional fluidity to the interconnection network by some degree of wire connection. The connectors J1, J2, J3 are generally connected to ballasts, lighting controllers, and other single controllers via network cables 166, as shown in Figures 11 and 12.

Throughout the drawings, pins 1 to 4 of all connectors are parallel. An external low voltage DC providing voltage to all controls is built into pin 1. Pin 2 is the power return. Pin 3 is a signal that allows pass-through dimming from controls above the hierarchical or vertical same control. Pin 4 is a pass-through polling wire specifically for shared proportional response control logic for using multiple occupancy sensors.

Voltage regulator 176 receives the unregulated power supply from all connector pins 1 and transmits the voltage regulated by a single controller low voltage regulator 176 to all residential modules on pin 5 of the other mating connector. Pin 2 of the connector is power return.

Pin 7 is an output control bus while simultaneously transmitting control signals from all resident modules and a unidirectional current buffer that alternately receives inputs from all connector pins 3.

The infrared control mode switch 134 is used to determine whether the output directly affects the internal control bus 142 or whether a signal is sent to the optical sensor 64 to participate in lighting stability. Adjust the function. The switch 134 alternately connects J5 pin 7 to the output control bus or J4 pin 8 to the dynamic lighting stable input of light control. When the switch 134 is in the electronic position, the light control module or the remote control module may override the internal control bus 142. When the switch 134 is in the latter position, the control signal from the remote control is sent to the light control on an illumination stabilization basis and removed from the output bus. Light control uses this input as an internal illumination level reference set point that allows remote control to adjust the adjustment point within the light control.

During the dynamic lighting settling, the Dashne reference voltage using the output from the infrared remote receiver to the set to adjust the reference voltage will be controlled by the use of a manual dimmer. Connector J8 provides a direct connection to the passive dimmer and its signal line above connector J8, line 7, may replace the remote control voltage signal.

The connectors J1, J2, J3 and pin 4 over the output connector J7 are pass-through connectors for the polling wires when polling logic control is desired for multiple occupancy sensors. Embroidery switches S2F and S3F provide for separating local movement control from the polling impact of other controls. When the switch S2F is closed, the movement sensor with a polling wire connected to the output connector J7 participates in polling with the movement sensor on the local controller. In case the switch S3F is also closed, the mobile controls connected to the input / pass-through connectors J1, J2, J3 participate in polling with the mobile sensor on the local controller. When both switches S2F and S3F are closed, the movement sensors connected to the input connector J7 participate in polling with the movement control devices connected to the input / pass-through connectors J1, J2, J3.

In all cases, the output control signal will be affected by the movement sensor if it is currently located in the local single controller.

A power indicator (LED D1F) in series with the current limiting resistor (R1F) provides a local indication of where the power is present.

The unidirectional signaling means 130 is of the type described in FIG. 13B through FIG. 13G to provide current amplification from pin 3 (input control bus 144) of the connector to pin 7 (internal control bus 142) of the connector. Is a unidirectional current buffer. The signals arriving at pin 3 are not imposed by the actual control of the ballast and other controls imposed on the system on pin 7.

At night, on weekends or at different times, external, widely manufactured EMS controls on a single control unit can adjust the maximum level a critical area of a building can achieve. However, during these times there are others, office workers and managers needed to work in the area of the building. Widely manufactured ENS control allows maximum illumination to be fixed at low levels. It is often useful to have a widely manufactured EMS control that has a way of disconnecting the local lighting control from higher control in the hierarchy.

Pin 9 on the manual control connector J8 and the remote control connector J5 receives the reversed command. When the signal arrives at pin 9, the disconnect timer 196, which opens the electrical network disconnect switch 194, is activated. The timer 196 allows local reversal to include EMS control from limited duration such that proper network control is re-established within a reasonable time that typically exists between 10 and 120 minutes.

The timer 196 and the switch 194 are located on the motherboard such that these components can be shared by both manual control input and original control.

15 is a schematic top view of the physical design of a typical single controller, an infrared remote receiver and an infrared control board in combination with three boards, from the motherboard 168 to the optical sensor board 184, the mobile sensor board 186. There are a number of balances 170 of 182, 184, and 186. The electrical components of each control are the photodiodes D1A on the optical sensor board 184, the manual switch S2K, and on the infrared board 182. The photodiode D1H is shown. While the infrared passive remote receiver 59 and infrared control 61 are shown on both occupying boards 182 and separated by line 183, these components are located on other boards without changing their functionality. In addition, control arrangements on other boards shown on separate boards may be located in place of the motherboard 168.

Additionally, the balanced state 170 physically couples the motherboard 168 to the control boards 182, 184, and 186. Electrical coupling is made via a plurality of male connectors J4, J5, J6 located on the motherboard 168 to a plurality of female connectors 174 located on the individual control boards 182, 184, 186.

At the center of the motherboard 168 are the input / pass-through connectors J1, J2, J3, the manual input connector J8 and the output connector J7. Additional input / pass-through or output connectors are located on the motherboard 168. In addition, the power indicator LLED D1F is located at the center above the motherboard 168,

FIG. 16 is a schematic cross-sectional view of a single control device according to lines 16-16 of FIG. 15, wherein the single control housing 178 is an electrical component as well as a means for mounting the single control device to a wall or ceiling (not shown). The outer shell (shell) made of plastic, including. The top surface of the single controller is open to allow not only electrical connection with a single lighting system network but also to maintain the electrical components of the single controller. The lower surface of the single control device is generally continuous. However, sensors from the interior of the single controller to ambient sensing, as well as adjustments and switches that allow the user to adjust the operation of a single controller without removing a single controller element or removing the single controller from the location of the installation. It has a number of orifices that allow it.

In the cross-sectional area, the orifices of the outer housing 172 are photodiode (s) from the optical sensor board 184 and the infrared receiving board 182 so that they protrude relatively into the space under a single control that is viewed downward in the working area. D1A, D1H). In addition, the switch S2K pops out of the lower space of the single controller housing 172 which permits its adjustment without inhibiting or dithering other single controls.

The infrared board 182, the optical sensor board 184, and the moving sensor board (not shown) are mounted on the single controller motherboard 168 together with the balance state 170. In addition, each control board is electrically connected to the motherboard 168. The infrared control 61 and the connector J7 on the motherboard 168 are connected to the connector 174 on the infrared board 182. Multiple connections between the motherboard 168 and the control boards 182, 184, 186 allow four boards to eliminate interaction from the single controller housing 178.

The motherboard 168 normally prevents the motherboard 168 from being separated from the housing 172 and expands around the entire housing 172 and at the same time stabilizes the expansion 180 to stabilize the multiple points. It is stably at the housing bulge 178 protruding from it.

When the stable expansion 180 is under pressure, it is coupled to the external fluidity of the single controller housing 172 as much as possible, such that the motherboard 168 can be removed from the housing 172.

When the single control device is installed, the output connector J7 bounces upwards from the motherboard 168 which permits a network coupling made from the motherboard 168 in the ceiling or other structure in which the single control device is mounted. Comes out. The connector J7 is conveniently connected to a telephone to permit the coupling to be easily created or removed.

The infrared board (unknown) 182, the optical sensor board 184 and its motion sensor board have a standoff 170 and are attached to a single controller motherboard 168. In addition, each control board is electrically connected to the motherboard 168. For control 61 of infrared, connector J5 to motherboard 168 is connected to connector 174 to board 182 of infrared. Many of the connections between the motherboard 168 and its control boards 182, 184 and 186 enable the four boards to be removed from the single controller housing 178 intact. The motherboard 168 normally rests on the housing ridge 178, which extends around the entire housing 172 and is secured in various ways by the securing extensions 180, with the securing extensions 180 extending out of the housing, prevents attachment from housing 172.

When the securing extensions 180 are pressed, the single controller housing 172 will bend outwards, causing the motherboard 168 to fall off the housing 172. When a single controller is installed, the output connector J7 will pop up upwards on the motherboard 168, allowing network connections to be made from either the motherboard 168 in the ceiling or other structure on which a single controller is mounted. This connector J7 is easily a telephone connector, which makes it easy for a connection to be made or removed.

As explained subsequently, the control system consists of intelligent dimmers, occupancy sensors, lighting sensors and, in some cases, intelligent, digitally addressed building power management system end-nodes, which will require low power.

Under the previous technology, this power source comes directly from its mains and is required for a separate pressure reducing transformer connected in a junction box in the wall or ceiling for each article. Beyond the obvious consumption of these transformers, there is the additional consumption of installing high voltage piping that brings power to the transformer.

The distributed network control of this invention entails the use of more sensors, perhaps two to five times more than current usage in a commercial building. Therefore, the means for powering such control are economically a complete view of the feasibility of including distributed network control of the lighting system.

The present invention teaches two different ways to power the control circuit. The first method uses a ballast to supply power for control, in which there is a line separation link of a dimmer ballast that receives darkening information from the control network and also powers the network for the operation of the control element. In general, this method of powering a network control device is desirable because it requires no more than normal installation of the ballasts and controls and the connection between them.

The block diagram in FIG. 12 illustrates the use of this particular ballast to power the network. The ballast with a given power supply is a special power generating ballast 146 of the configuration described below. Each power generating ballast 146 supplies enough power for one or more controls.

In Fig. 12, there are 18 power generating ballasts that power 13 controls and 7 infrared remote receivers. (Computer controller 148 generally does not require power from the network.) Such power is transmitted into the network through a power distribution wire contained in network cable 166.

However, it should be noted that the power source from power generation ballast 146 is generally available in the network. For example, zone 2 single controller 152 has no ballast directly connected to its input connector J1, J2, J3 or its output connector J7, only it receives power for operation from the network.

However, the use of powe-generation ballasts 146 requires the use of special ballasts with line break links to enable power supply, and in general, a limited amount of power available from each ballast to power the attached controls. There is this.

Therefore, if the number of controls exceeds the power generation capability available at power generation stabilizer 146, the network will fail to adjust properly without further assistance. Therefore, a second method is provided for certain applications, in which the use of a special ballast is inconvenient or there is not enough force available from that particular ballast.

In the second method, a particularly easy power supply is used where it is most accessible in the network. This method requires additional components besides ballast and network control and involves the installation of additional components such as additional connections to the "mains". However, once installed, this method can handle any arrangement, combination of ballast and control. In addition, the network using this method can operate in the use of various widely-commercially-a-ailable dimmable ballasts, which can compensate for the cost of additional components and installations at low cost.

17 depicts a block diagram of the use of a readily available power supply to power a network. The network shown is its topographical connection, the implementation of control, and the designation of internal components that are almost equivalent to FIG. 12. As shown in Figures 11 and 12, single controllers only depict internal connections related to their control, while no power, reture, and polling connections are shown.

In this example, the power generation ballast 146 represented in FIG. 12 is replaced by a general dimmable ballast 52 that does not supply power for its network control.

Instead, the aggregated network power sources 188 are provided in a distributed location within the network to power network control. As can be seen, this power supply 188 can be connected to the input connectors J1, J2 or J3 as represented by a single controller 154 of the output connectors J7 and Zone1 Area 2 or a single controller 150 and 152 of zone1 and zone2.

A single controller has power return pins on connectors J1, J2, J3 and J7 in parallel with the power supply. Therefore, the power supply connected to any connector on a single connector distributes power across the network. The wire carrying this power source is present in the network cable 166. The network shown has excess power capacity, since each power source 188 must generally be able to supply enough power to each of 30 to 60 control lines.

Therefore, any of the power sources shown can power the network shown, and if specifically controlled, the power sources are located within a desired distance from one other. However, despite the current draw of each control, the distance between the control and the power source becomes an important factor, and additional power may be required for remotely located controls or ballasts.

The next chapter will describe the configuration of the power generation method for network control using the method described above.

The design of the power supply for the control circuit is not completely isolated from the issues that accompany the design and the characteristics of analog control. In the first method, the control protocol characteristic is intrinsically linked to the power generation method. In the area of control electronics, the circuit to be controlled is often connected to the main and not isolated from the main.

Therefore, there may be a need to transmit control data through the voltage separation boundary between the low voltage control circuit and the mains.

This need is costly to construct, construct and install the control network that is not isolated from the high voltage mains. Such non-separable networks are burdened with safety and fire protection as enforced by local and national laws. Therefore, material and configuration requirements represent a cost reduction that can be greatly reduced if the control network is separated from the mains. There are many techniques that can be employed to provide this necessary separation. Current pioneering technologies include light or infrared transmission, magnetic coupling, radio transmission and several others.

There are as many topologies, configurations, methods of implementation and control protocols as possible within these technologies. The present invention teaches the control protocol how small an absolute magnitude the variable DC voltage is with, and which safety considerations have to be taken into account and which should be separated from the mains. A separate connection interprets this voltage through a voltage separation boundary to a controllable element (receiver) associated with the main.

If such a voltage control system is present, several disadvantages of limiting system utilization are revealed. In one version of the voltage controlled signal system, the receiver associated with the main produces a current source that separates it from the mains with voltage compliance greater than 10 volts DC. The controlling element draws on that current source. And adjust the voltage.

The resulting voltage then reacts back to the main side of the voltage separation boundary. Since the separation link generates current by itself, it may not be important that the controlling transmission stage sinks and additional control elements are also present. It will be incremented each time it is added to the system (the receiving end with its separate connection). If enough recipients are added to the system, the current sink required can be larger than that the control can handle, resulting in loss of control. If there is sufficient current capability in the control, the voltage drop caused by the magnitude of the current through what may be an important length of the control system wire with its accompanying resistance creates undesirable inaccuracies across the network. You can.

One version of the voltage control system employs the current source technique described above with a control voltage origin offset from 2 volts to zero. The system does not respond to control voltages down to 2 volts. And in doing so, it provides a minimum of 2 volts to provide power for conditioning the circuit.

Therefore, the provided control circuit draws the control line voltage using the control and the shunt mode of the circuit which are continuously powered from there. This means that if the circuit is drawn by the number of receivers in the system, provided that the circuit is provided by the number of receivers in the system, for that two volts and a smaller flow, then the receiver will appear more now then. The control that the line will be in requires a control that is designed to function properly as it draws a quiet current down by the circuit.

Another issue in these systems is that each controlled device must know exactly that the control voltage should be 2 volts. This is not easily done without sacrificing accurate internal reference at the receiver. If the level is not correctly interpreted for the two volts by the element under its control, the transmit / receive accuracy will not match. And the system will continue to suffer.

The limiting boundaries for the size of this system are:

1. The control of transmitting circuits in the system must not draw more current than can be supplied by the receiver.

2. The current sink required causes an undesirable voltage drop along the network.

3. The regulating transmitter ability to submerge enough flow to provide control

The system will also suffer from insufficient operating voltage when operated at its two remaining volts. It is an important aspect of the practically required improved system in which the size of the sink flow is made smaller, the disconnected connection. It is an additional important aspect of an improved system in which sufficient voltage and flow are made available as the resource of force on the composite regulates the circuit.

Since the control network is connected to the ballast that it regulates, the ballast is supplied with sufficient energy to power the control network. And it is convenient to power the network from the ballast.

This method of powering the network obeys both the network, the control network, if it does not need to be wired independently of power and the need to provide a separate power supply for the cost of installation. 18A is a block diagram of a ballast 146 capable of dimming power while additionally energized to energize control. And, which is designed to change its force with the gas release lamp in response to the input signal. A pair of nodes E1C and E2C are force input rows that receive power from a common force source such as an AC line voltage.

The dimmable ballast 146 includes line-insulation control controls 147. And since providing force to external control and control means 250 for the reception of control signals from that external control, it means 248 which is much more subdivided by force. Node E5C receives a power line disconnect control signal from an external control.

Node E7C provides a low voltage force for use by isolated lines of resources and external control. Node E6C represents feedback for Node E5C and Node E7C. Certain electronic components will be shared between the power supply method 248 and the control method 250 in the secure implementation taught by the present invention. On command from the control, the signal given by the control means 250. And, the variable force is provided to the lamp via feedback E4C, which is matched with the high frequency AC lamp output E3C.

Several elements, line isolation control interface 147, power method 248, and control method 250 may be seen as necessary to generate line isolation power for external control and to receive line separation signals to control the ballast.

18B is a block diagram of a high voltage enclosure (light fixture) 56 showing an alternative implementation to FIG. 18A. There, the element that the line-insulation interface controls is not present in a suitable ballast. By placing this element at the line-isolation boundary of the high voltage fixture 56, the rating of the wire connection to the line-isolation boundary of the high voltage fixture 56, The rating of the wires connecting to control node E5C, the return node E6C and the line-insulating force for control node E7C, do not need to meet the requirements of electricity generally established for wires entering high voltage fences.

Furthermore, placing this element at the line separation boundary eliminates the need to repeat the circuits each told within the ballast. Instead, one distant line-insulation with control harmonizing 55 can service multiple ballasts 53 or multiple ballasts 53 that are not in the associated fixture56.

The control had to be a ballast 53 that interacts with far line-insulation to match 55 in this implementation. But use it of separate remote interface 55 shared with other ballast 53. And he is noted. And from ballast 146 described previously is identified in ballast 53. And full line-insulation control does not match 147.

In fact, ballast 53 constitutes that portion of power supply ballast 146 that shows FIG. 18A which control does not include complete line separation to match 147. Control includes most of the functionality of the remote line-isolated interface 147 to match 55. However, some changes may be made to components and configurations to perform this function far.

There are many ways to get control force from the ballast. These various methods are discussed in the following sections, depending on the general structure employed.

FIG. 19 is a schematic diagram of a typical electronic ballast designed to provide force against a gas-loading lamp and to provide low voltage force for isolated lines and external use. The method involves the specialized use of the components of the magnet which are employed to gain control force and at the same time power the lamp. Input terminals E1C and E2C receive common AC power. The commutator 198 rectifies AC power into DC at the input of the pushing inductor L1M.

Power decomposes correction circuit 202 into factor and D1M draws the power from the power line in such a form with Boost inductor L1M and the dipole to reflect on its power line, almost resistive load. Store energy from the pushing inductor L1M that provides 204 to the DC power resources for the power oscillator. The high frequency output powers the oscillator which is connected to the inductor L2M, which the 204 sounds well. The output of the resonant inductor L2M is connected to a capacitor C2M whose value is determined to be close to the resonance with the inductor L2M. The operating frequency of the high frequency powers the oscillator 204.

The junction of inductor L2M and capacitor C2M is even more connected to high coupling capacitor C3M. The components of its high frequency output block the DC powering the oscillator 204. Then we pass a high frequency AC component to the first thing (T1M: A) of the output transformer T1M. The output transformer T1M has a plurality of secondaries T1M: B, T1M: C and T1M: D, the singular or plural of the gas representing which winds up s to emit a lamp.

The explanation given here represents the ballast of a traditional electron. And now it will be referred to as "electronic ballast lamp power circuit". Even more transformer T1M. It's the second T1M: E. And a target among the second T1M: E. The line then isolates power for external use to provide a resource of power.

Very arranged enough to provide line-insulating resources of power. And it is electrically isolated from transformer T1M and all other packages.

Diode D2M corrects the AC voltage with a second T1M: E. And store that energy in the capacitor C4M which becomes smooth. The circuit associated with the plurality of transistors Q1M and Q2M constitutes an active current limiter.

The possibility above capacitor C4M is seen through the resistor R1M on the emitter of transistor Q1M. The magnitude of the external load flow is reflected in the voltage drop through the resistor R1M. The value of resistor R1M is chosen such that the transistor Q2M base / emitter will be biased forward at its required current limit.

As a transistor with Q2M biased to one side, the transistor Q2M collector diverts the flow to the reference of transistor Q1M. And reduces the transistor Q1M conductivity. If an addition with an external load is applied, transistor Q2M is biased much more on the quiet side. And reduce the conductivity of the distant transistor Q1M. Therefore, the current drawn to exploit the external load is limited to that which advances the transistor Q2M.

The requested leＶel that D3M was not drawn by the rod. The zener diode, which defines its output voltage in the excess flow, is switched through diode D3M to have its output voltage at the required level. Different methods of current limit are well known in the art and can be used instead. The description of the control power regulation has been described here. And begins with a discussion of the use of the dipole D2M to amend the AC, the voltage being referred to as "power conditioning circuit".

The power conditioning circuit with the second T1M: E constitutes the power method 248 shown in FIG.

20 is a schematic diagram of a typical electronic ballast designed to provide power for a gas discharge lamp and to provide low voltage power for isolated lines and external use.

The method was employed to gain control accompanying the use of the power added components of magnets that are not familiar with power lamps. The electronic ballast lamp power circuit is similar to that described during FIG. 19. Even more transformer T1M. It's the second second T1M: E. And the goal of the second T1M: E, which provides power resources for external use. Thus, the second transformer T1M: E is a source of power from the excitation of the magnetic field from the magnetic field of the transformer T1M.

The arrangement of the second T1M: E does not provide enough from the force line for separation of the dielectric. Transformer T2M is designed to provide dielectric separation and E5C between the second T1M: E and the line-insulated output E7C. A pair of second packages T2M: A and T2M: E os, transformer T2M, are very arranged to provide sufficient insulation to provide isolation of the dielectric across the device. The power to condition the circuit is the same as described with respect to FIG.

FIG. 21 is a schematic diagram of a typical electronic ballast designed to provide power to a gas burden lamp and to provide low voltage power for isolated lines and external use. The method added magnet components that are not accustomed to power lamps such as additional components that vibrate as power is employed to gain control accompanying its use.

The electronic ballast lamp power circuit is similar to that described during FIG. 19. The power factorizes correction circuitry, including active circuitry where 202 requires low voltage power. As such, the power factorizes correction circuitry that includes circuitry for providing low voltage power where 202 is generally a related power line. Oscillator 208 uses some of the lower voltages at which the line whose power resolves correction circuit 202 into isolation.

The output of oscillator 208 is connected to a separate transformer winding T2M: A. Package T2M: A and T2M: B of transformer T2M are highly arranged to provide sufficient insulation to provide isolation of the dielectric across the device. The power to condition the circuit is the same as described with respect to FIG. A detailed view of this implementation will be described later.

22 provides power for the gas burden lamp and low lines for external use. A schematic diagram of a typical electronic ballast designed to provide voltage power. The method added capacitive components as power was employed to gain control that accompanies its use. The electronic ballast lamp power circuit is similar to that described during FIG. 19. It is connected to capacitor C5M that some of that energy appears at the junction of well-ringed inductor L2M and well-sounding capacitor C2M.

AC energy is stored in capacitor C4M, which is connected via capacitor C5M and is revised and smoothed by dipole D2M. The dipole D4M accumulates the charge on top of the capacitor C5M. AC reference feedback E5C will be attached to earth ground or any potential with a sufficiently low AC impedance path to enter E1C and E2C to provide a current path back to the AC line that provides energy to outputs E7C and E5C. The value of capacitor C5M is chosen such that negligible power line frequency flow will flow, as long as it has an impedance at a sufficiently high power pretreatment frequency such that the impedance of capacitor C5M is sufficiently low to provide a current path at high frequencies.

Capacitor C5M will be thought of as the line separation component of the dielectric. The rest of the power conditioning circuit is the same as described with respect to FIG.

Seemingly opposing low control flow requirements and sufficient flow for circuit power, sufficient voltage for complex circuits at any time, and also the control voltage, powering the control circuit is achieved by eliminating that requirement. Can be.

With this, the flow achieved and the flow required for control can only be reduced to the level splashed by the circuit of the separate connection. And now the separated voltage can be made available to the control circuit at any time.

If the minimum specification is deleted at those two volts, the origin of the slope for the control voltage can strike zero volts. The receiver inside it is then consulted for voltage requirements while removing it. The present invention includes a control system with the described characteristics. The new control system employs a combination of magnets that simultaneously send control information from the transmitter to the receiver in a single transformer. It then sends a substantial low voltage power from the receiver to the transmitter. Moreover, this new system requires extremely small control flows. And responds appropriately to the control signal at the origin of the zero volt slope.

The circuit functions as a specialized oscillator powered from its receiver side. The oscillator has two distinct states: the first state in which time energy is fixed multiplied by the transformer core accumulating element. However, it is the second state in which this energy is released equally through two of the transformer packs. This is equivalent to energy. And the same voltage stored in any two capacitors. And resides on the side opposite the voltage separation boundary. And indicates the control voltage as given and transmitted. The time to release this energy is variable and dependent on its control voltage as it is transmitted.

Operation is best understood by following the implementation depicted in FIG. 23, line-isolation control and power interface over the period of operation. It should be noted that this implementation partially coincides with the method for powering control using a further element that is magnet and vibrates as represented in FIG. 21.

At the heart of the circuit is the transformer T1P, which is a pedestal core transformer with all windings equal to a specified inductance. Transformer windings T1P: A & B are tightly coupled but the voltage is separated from the windings T1P: C and D.

Assuming integrated circuit U1P is applied, turn on transistor Q1P and affect Ｖcc across winding T1P: A. Transistor Q1P remains for a time controlled by transistor R1P and capacitor C1P. Due to its ratiometric calculations (similar to the industry standard LM555N manufactured by National Semiconductor), the "on" time created by the integrated circuit U1P is stable for changes in supply voltage and temperature.

The polarity of the wound T1P: D is such that the dipole D2P is the conduct and energy that now operates the integrated circuit U8P and provides the circuit with external control stored in capacitor C6P. Transformer Packing T1P: B & C The polarity is negative, the plurality of bipolar tubes D4P and D5P are not polarized. Also during this time, transistor Q4P is on.

Transistor Q4P polarization disables the controllable current mirror, integrated circuit U7P. During this time, a predictable amount of energy is stored in the core of the transformer T1P because the transformer T1P inductance is known and is the time overvoltage charged through the wound T1: A. The integrated circuit U1P is now over, and the transistor Q1P is closed. The energy stored in the core of the transformer T1P now reverses all wrapped polarities. Diodes D4P and D5P are now conducted in several capacitors C5P and C7P.

Capacitors C5P and C7P are made large enough to not charge a significant amount of voltage through them because of their individual cycles; the flow continues to flow the transformer T1P load. Integrated circuit U5P comparator feels the polarity through the dipole D5P. Integrated circuit for voltage integrated across all dipoles D51'starts for switching / cancellation where the U5P output goes low, when all energy in the transformer T1P is released, the package begins to collapse U5P sets the integrated circuit U2P NOR gate output high. Then fire the integrated circuit U1P, which begins at the next cycle.

During this part of the cycle, transistor Q4P has left. And enable the integrated circuit U7P flow mirror. The relationship between the current mirror U7P and the flow in the integrated circuit emitted by the transformer T1P is an important factor in providing control signal replication accuracy. The circuit U8P is the current buffer which clamps that voltage to the capacitor C5P at the value of the control voltage fed into the control line E2P. Now that this voltage is a sin, it has crossed the transformer winding T1: C and so it has crossed the sinuous T1: B voltage will be a sin.

Repeat the voltage found on capacitor C7 for capacitor C5P and possibly As is the goal of the circuit. This can only be achieved if the circuit has its sinuous series resistance with the same load flowing in both sides. Traversed and across the junction of the dipole to be aligned so that D4P and D5P are very close. For voltage matching, the dipole: the circuit is made from a stock of a producer. And there is no need.

The important thing is to load both sides of the circuit equally. This implies that half of the available average flow in the transformer T1P. And must flow on each leg of the circuit. Since the average sums the cycles 1/2 and the highest flow stored in the transformer T1P, the available flows each time the same transformer T1P is loaded, the value of the flow in the integrated circuit U7P undertakes lpeak / 4 by the resistor R6P. Should be.

So half of all available flow is submerged by an integrated circuit that must be submerged to succeed in clamping the U7P and its balance by the output of the integrated circuit U8P. (1/3) Capacitors C5P and C7P provide high frequency clamping effects required. The net result of that is a very accurate relationship between the voltage on the capacitor C5P and C7P.

Integrated circuit U7P is disabled for its cost at the cycle of transformer T1P by transistor Q4P. If it wasn't, the flow would not properly average lpeak / 4 over the range of voltages and subsequent charge / discharge obligations in the cycle the circuit operates. It is possible to "block" oscillators 208.

Sometimes when starting up, oscillator 208 would not stop. This is similar to the starting point we met with the Linfinity LX1562 (a PFC controller) and some other chips that believe in "end of flow" detection. This is tricked by averaging the voltage at the output of the integrated circuit U5P. The integrated circuit U5P is obliged to cycle with varying control voltages.

At low control voltages, the average output voltage is high of the average fall up to nearly 50% of cc at high control voltages. A voltage below 50% of Ｖcc indicates a stopped oscillator. Well, that's 208. Integrated circuit U3P output now goes high. By the way, it is the biasing that the integrated circuit U5P non-conversion inputs during the dipole D1P. The result is a flip of the output of the integrated circuit U5P, which fires the integrated circuit U1P and restores normal operation. Perhaps the solution of a single architecture would be a missing pulse detector with internal timing components.

Integrated circuit U4P is a high noise emptying noise. Triggers such as transistor Q1 are turned off. And the integrated circuit U5P output goes high. When the control voltage is very low, when there is a significant load reflected from transformer T1P to the load at voltage node E1P, the leaking inductance on transformer T1 will allow voltage on the bipolar D5P anode going to "ping". If not suppressed, this can generate multiple triggers from the integrated circuit U5P output. The integrated circuit U4P does not need to be externally programmable. For 1-2, all that is required.

The dipole tube D3P with resistor R5P prevents negative voltage, the control circuit outside the transformer winding T1: B from the forward biasing input by the board in the integrated circuit U5P unconverted power into the feedback above the voltage feedback E4P The low voltage is provided through the resource E1P. The voltage on capacitor C6P is currently limited by a plurality of combinations of transistors Q2P and Q3P, and integrated circuit U9P. Resistor R3P sets its current limit. The other resistor R4P presently releases the pull attached to the control. One important minor aspect of the design of the line E2P is its inherent power supply rejection while resistor R7P and capacitor C4P roughly at 10 volts provide input filtering and reverse polarity protection for integrated circuit U8P. .

Conventionally integrated inductance ratio and time circuit U1P "on". And the integrated circuit U7P flow is a collection in which Ｖcc can be changed without noticeably affecting accuracy. This is because the energy immersed by the integrated circuit U7P with the energy stored in the transformer T1 is directly proportional to both Ｖcc.

Another important aspect of the circuit is that it may be modified to emulate the input flow of its de facto current standard by reducing the value of resistor R4P until a short circuit value of about 0.5 motherboards is achieved above control line E2P. will be. The resistor where R3 may be increases such that its current limit is 0.5 mA and the voltage resource E1P may be disconnected to the control line E2P. This provides true current resources and eliminates the availability of external power supplies.

As explained above, the use of auxiliary power sources obtained from the ballast has the possible disadvantage that a circuit for generating line-insulated power must be built into the ballast. Because this suggests an important number of these ballasts, the cost of including this circuit in each ballast may be important.

The current invention instead teaches the use of one or more power modules placed across a network that provides distributed power. The use of compliant and current-limited power resources allows the east and west of these many power resources.

The present invention provides a number of advantages and benefits to the design and equipment of dimmable fluorescent lighting systems. The joint response of multiple controls that control all of the same ballasts allowed by the present invention provides the ability to tailor system response with great precision and adaptability. As noted above, the combination of the optical sensor, occupancy sensor and infrared remote receiver allows control to properly respond to a sufficient number of input stimuli normally observed in the working environment.

Local networks will be combined in hierarchical control to allow a much wider response. The use of ballast in power control circuits avoids the need to provide additional power sources and wire connections. This reduces cost costs and, more importantly, substantially reduces the cost of installing lighting systems because additional wire connections and labor are not necessarily required. This is especially important for equipment renewal, as infrared remote control is wired inside the walls without the need for remote control. Reduced installation costs in terms of equipment renewal represent a significantly greater financial reward for installing control circuitry.

In the electrical power supply area, more specifically in the switching electrical system area, it is advantageous to use a power relay or contactor rather than a mechanical switch to switch the electrical power supply to the load. It would be advantageous to use a contactor or power relay in the following cases:

1. If an electrical load is imposed on the switch rather high, perhaps the switch's excess current is present in the selected position.

2. The switch shares areas with low voltage or extraneous wiring or circuits.

3. If the switching control element is not a mechanical switch and is a low-current low-voltage circuit, the relay is located in the system in position in the flow of power than the start-up control position which is a little distance from the system and is convenient for system control. It will be more appropriate in position.

Because contactors or relays are electromagnetic devices, low voltage power sources are often used to activate them. This voltage is generated by an isolated voltage step-down converter, referenced to the local earth ground, and separated from the line voltage. The electromagnetic coil of the contactor is connected and magnetized from a low voltage power supply isolated by a switch. Thus, the switch is needed to carry only the current required to operate the contactor coil, not the load transfer.

It is clear that the source of power used in the isolation voltage drop converter is the power line for providing starting energy. It is a disadvantage to drop some magnetic current. Moreover, noise generated in the transducer layers at the power line frequency is also included. In addition, the switch must be located in the primary position relative to the voltage generated by the mains or in the secondary position relative to the current in the contactor coil.

New moans have been devised that can operate power relays or contactors with small voltages and currents independent of the source line rather than the energy source derived from the converter.

Regardless of the source of the power line, all circuits have one thing in common, regardless of their voltage and type. All types avoid using earth ground as the current carrying conductor. That is, a specific ground fault detection circuit is often used to turn off the power when ground current is detected above a certain amount.

Ground currents are not desired, but in many electrical circuits and line garden products, a small amount of current counts to earth ground frequently. This current has a negative impact on the components in some products. For example, products with circuits that produce conductor noise at high frequencies use a method of connecting capacitors to earth ground to reduce noise. While small, these elements still give some conductance to ground at the power line frequency. Small leakage currents contribute to the incomplete character of the product's insulator configuration. Higher limits on leakage current are usually controlled by local or global safety codes or warranty arguments.

New approaches to operating electromagnetic coils using relays or contactors use a small amount of leakage current to provide an acceptable operating signal. Because in the new system, the leakage current flows to earth ground, and the voltage associated with the earth ground is limited to a small and safe value. Furthermore, the energy generated by this new circuitry is converted to an indicator if it is not used to start up. This circuit is therefore a mechanism for indicating the starting state, for supplying pilot light, or for placing the switch during low light conditions.

1 used this self-magnetizing relay. Self-magnetizing relay 80 is powered on input power line 76. Based on the above and in more detail below, the self-magnetizing relay 80 has a sufficient line of on / off switch 60 connected to the magnetic magnetizing relay 80 by a pilot light and line isolation 78 to magnetize the pilot light of the dimmer. -Induces isolation power.

This pilot illumination provides for indicating the position of the dimmer 60 in low light conditions. Normally, since the local control network is powered by a dimmable ballast 52, it does not have a nominal power source. However, the self-magnetizing relay provides power for self magnetization under the on / off control of the manual dimmer 60. Once the manual dimmer 60 activates relay 80, it powers the ballasts 52 through the 82 power line.

Self-magnetizing contactors enable the closing of an AC power relay or contactor by a small leakage current accumulated between the AC power and earth ground during the half period of the line voltage. 25 is a simplified circuit of the self-powerded contactor magnetization circuit. The current to charge capacitor C1T is derived at E1T AC high. The other side is led through the resistor R1T of the return path from the capacitor to earth ground E2T.

The current is small, but is sufficient to charge C1T to diac Q1T trigger voltage during the half cycle of the AC line. When S1T is open, diac Q1T discharges C1T through the connection of diodes D1T D2T D3T D4T by the polarity of the LED in the optical insulator U1T. The current pulse of the optical insulator U1T drives the isolated triac Q2T at the output of the optical insulator U1T. This in turn triggers the triac Q2T gate, which relay K1T completes the conduction path to Ac low E3T. Resistor R2T limits the current to the gate of triac Q2T. Close the relay with triac in conduction and make power available to the external load.

The bidirectional nature of the active component provides trigeringrhk conduction for bidirectional line voltage. When S1T is closed, another conduction path is provided to discharge C1T. In this path, S1T and the D5T D6T pair by voltage polarity are lower than the voltage required by the LEDs and diode connections for conduction of the contact drop number inside the opti-insulator U1T in the voltage drop. Therefore, the opti-isolator U1T will not trigger. The discharge of diac Q1T forward biases LED1 and D5T D6T and provides an indication when S1T is closed.

The present invention provides many benefits and advantages in the design and implementation of dimmable fluorescent lighting systems.

Claims (119)

A plurality of lighting controls selected from the set comprising occupancy controls, light controls, computer controls, and remote control receivers; A housing housed therein at least two lighting controls; An illumination modulator for providing various amounts of power to the gas discharge lamp to illuminate the light in one area; A control signal having a default value shared between the controls and the modulator allows each control to change the level in a single direction from the default value while at the same time the control signal is farthest from the default value. The lighting modulator to electrically connect the controls and the lighting modulator by varying power to gas discharge lamps connected thereto in response to the value of the control signal so as to fix the level of the lighting control; A regulated power supply; An electrically conductive power line for coupling the power supply and at least one control to supply power to a control having a regulated DC voltage coupled thereto; . An infrared control receiver for receiving a signal transmitted from one infrared transmitter and simultaneously communicating a signal including mode conversion signals and remote illumination level request signals to one control via a separate wire; Connected to at least two occupancy sensors and has a polling signal value that, under monitoring, switches from an inactivation value indicating the absence of a person to an activation value indicating the presence of a person in the area, and capable of detecting a person in the area. An electrically conductive polling line connected to all occupancy sensors connected to at least one occupancy sensor and simultaneously activating the polling signal to modulate the polling signal with its control wires up to an appropriate illumination level in the occupied space; Wires connected to an AC line voltage for powering the lighting modulator; Relay coils using a source of line-related AC voltage used for powering the lighting modulator in the stored state while temporarily storing energy for control from a line-related AC source in a ground-related energy storage means. Lighting control comprising a self-conducting line connector used to switch AC line power to the modulator to release energy through an optical insulator that triggers electrical switching to energize the coil. system. A first step of providing a common electrical connection to the at least one lighting modulator and the plurality of lighting controls to the electrically conductive wires once an analog electrical control signal having a default value is determined; Adjusting an electrical control signal with the illumination controls such that all controls adjust the level in a single direction from the default value; A third step of fixing the control signal to a value at the level of the illumination control such that the level is determined at a value farthest from the default value; And a fourth process of acting on the illumination in the area by the light modulator such that the light modulator is responsive to the level of an electrical control signal. . The method of claim 2, And wherein said illumination modulator is responsive to said default control signal by calculating a maximum amount of artificial illumination. The method of claim 2, At least one of said illumination controls has a sensitive response to illumination. The method of claim 2, And at least one of said lighting controls detects movement. The method of claim 2, And at least one of the lighting controls is manually adjustable. The method of claim 2, Wherein at least one of the illumination controls receives remote signals transmitted by wireless transmission. The method of claim 7, wherein And said far-field signals are transmitted by infrared electronic energy. The method of claim 2, And at least one of the lighting controls is a digital computer. The method of claim 2, At least one of said lighting controls is connected to an electrically conductive wire via a unidirectional signaling means. The method of claim 10, And said unidirectional signal means comprises a diode. The method of claim 10, And said unidirectional signal means comprises a transistor. The method of claim 10, And said unidirectional signal means comprise a MOS FET. The method of claim 10, And said unidirectional signal means comprises an operational amplifier. The method of claim 10, And said unidirectional signal means comprises a transistor and an operational amplifier connected to its output and a collector. The method of claim 2, And said control signal is at a voltage level. The method of claim 16, And said voltage level varies between 0 and 10 volts. The method of claim 16, And wherein said default voltage is comprised of a maximum voltage. The method of claim 2, And wherein said controls are connected in a star-shaped configuration with a common electrical connection. The method of claim 2, And wherein said controls are connected in a daisy chain configuration with a common electrical connection. Illuminating a predetermined area to a desired level during the occupied space; Providing a logic to combine detection signals from each of the occupancy sensors to produce a polled signal; A third process of detecting the presence of the occupant in the predetermined area by at least one occupancy sensor; If the at least one occupancy sensor senses the presence of a person in a certain area, determining a polled signal at a value indicating a presence of the occupant in the certain area; If the polled signal is a value indicating the absence of occupants in a certain area, a predetermined area using a plurality of occupancy sensors, comprising a fifth process of adjusting the lighting within a predetermined area to a desired level during the non-occupying space. Method for controlling lighting in the room. The method of claim 21, And said shared detection signal medium consists of electrically conductive wires. The method of claim 22, And said detection signal comprises a DC voltage. The method of claim 23, And the signal indicative of the presence of a human consists of a voltage whose absolute magnitude exceeds a predetermined threshold. A plurality of lighting controls; Power input means for supplying electrical power for said lighting controls; Consisting of electrically conductive wires connected to the lighting controls by unidirectional signaling means, wherein at least one of the unidirectional signaling means is provided for each lighting control, and a shared proportional response control for adjusting the response of the lighting controls. Means; Output lighting means for connecting the shared proportional response control means to the lighting modulator; and controlling the illumination provided by the at least one gas discharge lamp that is variously powered by the at least one lighting modulator. Device for The method of claim 25, Provided by at least one gas discharge lamp that is variously powered by at least one lighting modulator, characterized in that the control signal input means for passing the input control signal in a single direction to the shared proportional response control means. Device for controlling the illumination of the light. The method of claim 26, Means for temporarily disconnecting the control signal input means from the shared proportional response control means for controlling the illumination provided by the at least one gas discharge lamp which is variously powered by at least one illumination modulator. Device. The method of claim 25, At least one gas discharge that is variously powered by at least one lighting modulator, characterized in that the power adjusting means is further configured to provide a regulated electric power to the plurality of control means and to receive power from the input means. Device for controlling the illumination provided by the lamp. The method of claim 25, The polled occupant sensors only produce a control signal suitable for the non occupied area when all occupied sensors match that a certain area is not occupied so that occupant sensors in the means poll polling occupant sensors located outside of the means. And means for polling occupancy sensors is further configured thereby to control the illumination provided by the at least one gas discharge lamp which is variously powered by the at least one illumination modulator. The method of claim 25, An apparatus for controlling illumination provided by at least one gas discharge lamp, which is variously powered by at least one illumination modulator, characterized in that a remote input means is further configured for receiving an input from an electronic energy transmitter. The method of claim 30, The device for controlling illumination provided by at least one gas discharge lamp which is variously powered by at least one illumination modulator, characterized in that the electromagnetic energy received by the remote input means is of infrared radiation. The method of claim 25, Provided by at least one gas discharge lamp, which is variously powered by at least one lighting modulator, further comprising switching means for switching the lighting control with the dynamic lighting stabilizer between the alternating control voltage inputs. Device for controlling lighting. Placing the movement sensor in a measurement mode; Calculating a movement at a predetermined distance from the movement sensor while the movement sensor is in a measurement mode; A third step of increasing the sensitivity of the movement sensor by electrical means if the detected movement is lower than a predetermined level of detection; A fourth step of reducing the sensitivity of the movement sensor by electrical means if the detected movement is higher than a predetermined level of detection; A fifth step of repeatedly increasing and decreasing the sensitivity of the movement sensor; A sixth process of storing the sensitivity of the movement sensor; And a seventh step of terminating the measurement mode. The method of claim 33, wherein The seventh process is a manual control method for adjusting the sensitivity of the movement sensor. The method of claim 33, wherein The seventh process is a time adjustment control, characterized in that for adjusting the sensitivity of the movement sensor. The method of claim 33, wherein And wherein the seventh step is generated so that the movement crosses each other from when the sensitivity is higher than the predetermined level to lower than the predetermined level. The method of claim 33, wherein Movement occurs intersecting with each other from when the sensitivity is lower than the predetermined level to higher than the predetermined level. The method of claim 33, wherein And wherein the seventh process combines a subjective step of announcing the completion of the measurement mode. The method of claim 33, wherein And said predetermined distance consists of a range and a range of distances for detecting the presence of a person during normal operation of said movement sensor. The method of claim 33, wherein And said predetermined distance is outside of a range of distances and limits of detecting a zone of a person during normal operation of said movement sensor. A first process of detecting the combined external and artificial illuminance using light sensing means; Providing a second electrical signal relating to the illuminance to an error amplifier; Supplying an electrical signal to the error amplifier for displaying a desired degree of illumination; And a fifth process of outputting a signal from an error amplifier to a shared proportional response control line affecting an illumination modulator coupled to the control line to minimize the difference between the detected illuminance and the desired illuminance. A method of lighting control in a predetermined region. 42. The method of claim 41 wherein And said error amplifier is coupled to said shared proportional response control line by said unidirectional signal means. 43. The method of claim 42. And said unidirectional signal means comprise a diode. The method of claim 42, And said unidirectional signal means comprise a transistor. The method of claim 42, And said unidirectional signaling means comprise a MOS FET. The method of claim 42, And said unidirectional signal means comprise an operational amplifier. The method of claim 42, And said unidirectional signal means comprise a transistor and an operational amplifier having a collector connected at its output. 42. The method of claim 41 wherein And the electrical signal representation of the detected illuminance and the electrical signal representation of the desired illuminance are at a DC voltage level. 42. The method of claim 41 wherein And said light sensitivity means comprises a photodiode. 42. The method of claim 41 wherein The slew rate (多 比 率) of the error amplifier is a method of lighting control in a predetermined region, characterized in that made electrically adjustable 51. The method of claim 50 wherein The slew rate of the error amplifier is formed in a short time proportionately when an electric power source is first applied to the error amplifier. 51. The method of claim 50 wherein The slew rate of the error amplifier is formed in a short period of time proportionally when the electrical signal display of the desired illumination level is changed. 51. The method of claim 50 wherein The slew rate of the error amplifier is proportionally formed in a short period when the output load of the error amplifier falls below a predetermined threshold and returns to a value above the predetermined threshold. Way. A first step of detecting the combined external and artificial illumination degree in a predetermined region using a light sensing means; A second process of determining an amount of artificial light in a predetermined area from the known control signal output to the artificial light modulator; Extracting external illumination by subtracting the artificial illumination determined from the detected combined external and artificial illumination levels; A fourth process of calculating total effect illumination by adding the determined artificial illumination to a product of the extracted external illumination and a predetermined function; A fifth step of supplying an electrical signal indication of said desired total effect illumination; And a sixth process of outputting a shared proportional response control line acting on the illumination modulators coupled to the control response line to minimize the difference between the calculated total effect illumination and the desired total effect whaudd. Lighting control method in a predetermined region. The method of claim 54, wherein The predetermined function is a lighting control method in a predetermined region, characterized in that consisting of a constant. The method of claim 55, The constant is a lighting control method in a predetermined region, characterized in that made between 1 and 3. The method of claim 54, wherein And said fourth process is performed using a digital computer. A first step of initializing a measurement order; A second process of outputting an illumination modulator and adjusting a minimum amount of artificial light in a predetermined area, the control signal indicating a maximum amount of illumination available from lamps powered by said illumination modulator; A third process of detecting the combined external and artificial lighting in a predetermined region using a light sensing means; A fourth step of converting the detected illuminance into an electrical signal using a converter having a variable gain; The converter further comprises a fifth step of determining a variable gain of the converter to output a control signal indicative of the amount of illumination available from the lamp powered by the illumination modulator, the incremented by a predetermined value; A sixth step of storing the gain determined in a nonvolatile memory; And a seventh step of returning to the operation mode. The method of claim 58, Wherein said predetermined value is comprised between 1 and 2; The method of claim 58, And wherein said third process comprises transmitting a control signal to a shared proportional response control line via a unidirectional signal means. The method of claim 58, Said first process being activated by a far-field signal carried by a calibrated infrared energy beam. A first step of initializing a measurement order; A second process of outputting an illumination modulator and adjusting an initial control signal indicating a maximum amount of illumination available from lamps powered by said illumination modulator, said minimum portion of artificial lighting in a predetermined area; A third step of determining a gain value of the optical sensor of the optical control device at the maximum amount; A fourth step of incrementally decreasing the gain value of the optical sensor until the output response of the optical sensor is substantially a predetermined initial response value; A fifth process of storing a gain value in a digital memory; Transmitting a second control signal to the illumination modulator, wherein the second control signal is indicative of a predetermined percentage of the maximum amount of illumination available from the illumination modulator; A seventh process of obtaining a second response value from the photosensor; A new gain value for the optical sensor is calculated by multiplying the stored gain value by the difference between the initial control value and the second control signal, and dividing the result by the difference between the initial response value and the second response value. 8 courses; A ninth step of storing the new gain value in a nonvolatile memory; And a tenth step of returning to the operation mode. 63. The method of claim 62, And wherein said second process comprises transmitting a control signal to a shared response proportional control line via a unidirectional signal means. 63. The method of claim 62, And wherein said first process is activated by a far-field signal carried by a calibrated infrared energy beam. Lighting modulation means for providing a gas discharge lamp with a variable amount of power supplied by a line-related AC source of power coupled to the input power; Control means for generating control signals to control the output power of the illumination modulating means; Control signal transmission means for transmitting a control signal from said control means, electrically insulated from a power source; Control signal receiving means for receiving a control signal from the control signal transmission means and simultaneously transmitting the control signal across the DC line-insulation boundary of the lighting structure; Apparatus for controlling the output of at least one gas discharge lamp in the lighting structure, characterized in that it comprises a control signal carrying means electrically coupled to the power source to convey information from the control signal receiving means to the lighting modulation means. . 66. The method of claim 65, And said control signal transmission means comprises a shared proportional response control line. 66. The method of claim 65, Power transmission means for delivering power electrically coupled to a power source to a power receiving means for delivering power across a DC line-insulation boundary of the lighting structure, and from the power source from the power receiving means to the control means. Apparatus for control of the output of at least one gas discharge lamp in a lighting structure, further comprising a power carrier for carrying an electrically lonnie-insulated power source. 66. The method of claim 65, And the structure comprises at least two lighting modulators. 66. The method of claim 65, And said illumination modulating means is comprised of a fluorescent illumination ballast (Ballast). A first process of providing a common electrical coupling of at least one lighting modulator and at least one lighting control to the initial electrically conductive wire once the initial analog electrical control signal having a default value is determined; A second process of providing a common electrical coupling of at least one other lighting control to the second electrically conductive wire once the analog electrical control signal to determine the second value is determined; A third step in which an analog electrical control signal is transmitted in a single direction from the second wire to the first wire and electrically coupled between the first wire and the second wire adjusted by the unidirectional signaling means; A fourth step in which all the controls are leveled unidirectionally from the default value to adjust an electrical signal in the first wire with lighting controls coupled to the first wire; A fifth process of adjusting an electrical signal in a second wire by means of said lighting controls coupled to said second wire; Said means being part of a set constituting said illumination controls coupled to said first wire and said unidirectional signaling means to control said control signal in said first wire so as to level at a value farthest from said default value. A sixth process of fixing to the level value of the means; The illumination modulator comprises a seventh process acting on the illumination by means of the illumination modulator in response to the level of the electrical control signal in the first wire at least one illumination modulator using a plurality of illumination controls A method for controlling illumination provided by at least one gas discharge lamp that is powered by a variety of sources. The method of claim 70, And wherein said unidirectional signaling means comprises a diode. The method for controlling illumination provided by at least one gas discharge lamp powered by at least one illumination modulator using a plurality of illumination controls. The method of claim 70, Wherein said unidirectional signaling means comprises a transistor, wherein said at least one gas discharge lamp is powered by at least one lighting modulator using a plurality of lighting controls. The method of claim 70, The unidirectional signaling means controls the illumination provided by at least one gas discharge lamp powered by a variety of power modulators using at least one lighting modulator using a plurality of lighting controls, characterized in that it comprises a MOS FET. How to. The method of claim 70, The unidirectional signaling means comprises an operational amplifier, characterized in that the method for controlling illumination provided by at least one gas discharge lamp powered by at least one illumination modulator using a plurality of illumination controls. . The method of claim 70, The at least one gas discharge lamp, the unidirectional signaling means comprising both a transistor coupled to its output and an operational amplifier, at least one gas discharge lamp powered by at least one lighting modulator using a plurality of lighting controls. A method for controlling the illumination provided by. The method of claim 70, And said first electrical control signal is comprised of a voltage. The method of controlling illumination provided by at least one gas discharge lamp supplied by a variety of power sources by at least one lighting modulator using a plurality of lighting controls. The method of claim 70, Wherein said default voltage is at a maximum voltage; and wherein said default voltage is controlled by at least one gas discharge lamp powered by at least one lighting modulator using a plurality of lighting controls. The method of claim 70, The controls coupled to the first wire and the second wire share at least one gas discharge lamp that is supplied with various powers by at least one lighting modulator using a plurality of lighting controls, characterized in that they share a common source of electrical power. A method for controlling the illumination provided by. The method of claim 70, Illumination provided by at least one gas discharge lamp powered by a variety of power supplies by at least one lighting modulator using a plurality of lighting controls, characterized in that the plurality of controls coupled to the first wire number exceed two. How to control. The method of claim 70, The at least one control coupled to the second wire comprises a digital computer, the illumination provided by the at least one gas discharge lamp powered by the at least one lighting modulator utilizing a plurality of lighting controls How to control. The method of claim 70, Said first wire being disconnectable from said second wire under human supervision, wherein said first wire is controlled by at least one gas discharge lamp powered by a variety of power supplies by at least one light modulator utilizing a plurality of lighting controls. How to. 82. The method of claim 81 wherein Said first wire being automatically recombined to said second wire after a predetermined period of time provided by at least one gas discharge lamp supplied with various powers by at least one lighting modulator utilizing a plurality of lighting controls. Method for controlling the lighting. The method of claim 70, The second wire is provided by at least one gas discharge lamp that is supplied variously by at least one lighting modulator using a plurality of lighting controls further comprising a common electrical connection to the at least one lighting modulator. Method for controlling lighting. A first process of supplying power from at least one gas discharge lamp having a variable amount of power from the ballast; A second process of passing a current through a lighting control for a lamp using a source of electrical energy radiated from the ballast at a proportional constant predetermined voltage; And a third step of adjusting the amount of power provided by the ballast to the lamp responsive to a control signal from the control. 87. The method of claim 84, The power supply carried by the electrical conductor to supply energy to the control is separated from the electrical conductor of the control signal. 87. The method of claim 84, Electrical energy that energizes the control is directly isolated from the power source to the ballast input. 87. The method of claim 84, Electrical energy that energizes the control from the ballast is limited to current at a predetermined level. 88. The method of claim 87, Wherein the current is limited to only 100 mA. 87. The method of claim 84, And an electrical energy source for energizing the control comes from a magnetic component of the ballast that simultaneously acts to provide electrical excitation for a lamp. 92. The method of claim 89, The additional magnetic component provides direct current isolation of the control signal from a power source to the ballast input. 87. The method of claim 84, A timely energy source for energizing the control is from a magnetic component that does not act to provide an electrical power source for the lamp. 87. The method of claim 84, And an electrical energy source for energizing the control is connected to a capacitor from an AC source of voltage in the ballast. 87. The method of claim 84, And the electrical energy source for energizing the control and means for providing direct current isolation of the control signal from a power source to the ballast input is of the same magnetic component. 94. The method of claim 93, Electrical energy for energizing the control and control signals share the same magnetic field in the magnetic component. 87. The method of claim 84, And said predetermined voltage is between 12 kV and 15 kV. Connecting the lighting control to the ballast of the lighting system using the first electrically conductive wires; Attaching the control to the ballast using a second electrically conductive wire; A third process of supplying electrical power through the first electrically conductive wire from the ballast to the control; And transmitting a control signal for adjusting an electrical power output of the ballast to a lighting system through the second electrically conductive wire from the control to the ballast. . 97. The method of claim 96, And the control signal and the electrical power source share the same magnetic field in the magnetic means. 97. The method of claim 97, And said self-limiting means is located in said ballast. 97. The method of claim 96, And wherein said transmitted control signal is electrically isolated from said power source at said ballast input from a power source. 97. The method of claim 96, Electrical power supplied from the ballast to the control is electrically isolated from the power source to the ballast input from the power source. 97. The method of claim 96, Electrical power supplied from the ballast to the control is supplied to a predetermined voltage. 102. The method of claim 101, wherein And said predetermined voltage is between 12 kV and 15 kV. 97. The method of claim 96, Electrical power supplied from the ballast to the control is limited to current at a predetermined value. 103. The method of claim 103, The predetermined value is only 100 kHz or less A first process of electrically connecting a plurality of lighting controls having line-insulated wire suitable for low voltage power transmission; Attaching the wire to a plurality of line-insulated power sources; And a third step of drawing the line-insulated power source required to energize the lighting controls from a wire. 105. The method of claim 105, Wherein the sources of line-isolated power supply are limited to current at a predetermined value. 107. The method of claim 106, And the current is limited to only 500 mA. 105. The method of claim 105, And at least one source of said line-insulated power source consists of a ballast. 105. The method of claim 105, And wherein said line-insulated power source is at a predetermined voltage. 112. The method of claim 109, And said predetermined voltage is between 12 kV and 15 kV. A first process of temporarily storing energy from an AC source in a ground related energy storage means; A second process of dissipating the stored energy when the connector operating device is in an unswitched state; A third process of releasing said stored energy through an optical insulator when said connector actuator is in a switched state; And a fourth process of triggering an electrical switch under the influence of the opto-isolator to energize the relay coil using a line-related AC voltage to power the relay coil. Method for energizing the connector. 112. The method of claim 111, wherein And said grounding-related energy storage means comprises a capacitor. 112. The method of claim 111, wherein And said second process comprises supplying power to said illumination emitting diode. The method of claim 111, And said third process comprises discharging a trigger means. 116. The method of claim 114, wherein And said trigger means comprises a diode AC switch (diac). 112. The method of claim 111, wherein And said electrical switch comprises electrical latching means. 117. The method of claim 116 wherein And said latching means comprises a triac. 112. The method of claim 111, wherein Wherein the current diverted from the line-related AC voltage to ground is less than or equal to a predetermined value. 119. The method of claim 118 wherein And the current converted to ground is less than 5 mA.