KR102137359B1 - Circuit for hybrid switched capacitor converter - Google Patents

Abstract

The circuits include: an inductor having a first side connected to V _IN ; A first switch having a first side connected to the second side of the inductor, and a second side not connected to the second side of the inductor; A second switch having a first side connected to V _IN ; A first capacitor having a first surface connected to a second surface of the second switch; A third switch having a first surface connected to a second surface of the first switch; A fourth switch having a first surface connected to a second surface of the third switch; A fifth switch having a first side connected to the second side of the first capacitor and to the second side of the fourth switch and having a second side coupled to the voltage source; And a second capacitor having a first surface connected to the first surface of the fourth switch and a second surface connected to the second surface of the fifth switch.

Description

Circuit for hybrid switched capacitor converter

[Cross reference to related applications] This application claims the benefit of U.S. Patent Application No. 15/695,955, filed September 5, 2017, which is hereby incorporated by reference in its entirety. .

TECHNICAL FIELD The present disclosure provides an apparatus for providing a reconfigurable Dickson Star switched capacitor voltage regulator and/or for providing a hybrid (eg, two-stage) voltage regulator. Fields, systems, and methods.

There is a strong demand to reduce the size of electronic systems. Size reduction is particularly desirable in mobile electronic devices where space is important, but it is also desirable in servers deployed in big data centers because it is important to put as many servers as possible in a fixed size real estate.

Some of the largest components in electronic systems are voltage regulators (also referred to as power regulators). Voltage regulators often include a number of bulky off-chip components, processors, memory devices (e.g. dynamic read access memory (DRAM)), radio frequency ( It is used to deliver voltages to circuits such as integrated chips including radio-frequency (RF) chips, WiFi combo chips, and power amplifiers.

To efficiently deliver power, the voltage regulator can use a "buck" topology. This regulator is referred to as a buck regulator. The buck regulator uses an inductor to transfer charge from the power source to the output load. The buck regulator can use power switches to connect/disconnect the inductor to/from different voltages (at different time points), thereby providing a weighted average output voltage of different voltages. The buck regulator can regulate the output voltage by controlling the amount of time the inductor is coupled to different voltages.

Unfortunately, the buck regulator is not very suitable for highly integrated electronic systems. The conversion efficiency of the buck regulator depends on the size of the inductor, especially when the power conversion ratio is high and the amount of current consumed by the output load is large. Existing buck regulators often use multiple off-chip inductor components because the inductor can occupy a large area and is bulky enough to integrate on-die or on-package. This strategy often requires a large area on the printed circuit board, which in turn increases the size of the electronic device. The challenge is exacerbated as mobile system-on-chips (SoCs) become more complex and more and more voltage domains need to be delivered by a voltage regulator.

Accordingly, new voltage regulator circuits are desirable.

Circuits for hybrid switched capacitor converters are provided. In some embodiments, circuits are provided, the circuits comprising: an inductor having a first side and a second side, wherein the first side is connected to the input voltage; A first switch having a first side and a second side, wherein the first side is connected to the second side of the inductor and the second side is not connected to the second side of the inductor; A second switch having a first side and a second side, wherein the first side is connected to the input voltage; A first capacitor having a first side and a second side, wherein the first side is connected to the second side of the second switch; A third switch having a first side and a second side, wherein the first side is connected to the second side of the first switch; A fourth switch having a first side and a second side, wherein the first side is connected to the second side of the third switch; A fifth switch having a first side and a second side, wherein the first side is connected to the second side of the first capacitor and to the second side of the fourth switch, wherein the second side is coupled to the voltage source; And a second capacitor having a first side and a second side, wherein the first side is connected to the first side of the fourth switch, where the second side is connected to the second side of the fifth switch.

In some of these embodiments, at least one of the first switch, second switch, third switch, fourth switch, and fifth switch is a transistor.

In some of these embodiments, at least one of the first switch, second switch, third switch, fourth switch, and fifth switch is a MOSFET.

In some of these embodiments, at least one of the first switch, the second switch, the third switch, the fourth switch, and the fifth switch is a transistor, and the first switch, second switch, third switch, fourth switch , And at least one of the fifth switch is controlled by a controller.

In some of these embodiments, when the circuit is in the first state: the first switch is closed; The second switch is opened; The third switch is opened; The fourth switch is closed; The fifth switch is opened; When the circuit is in the second state: the first switch is closed; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed.

In some of these embodiments, when the circuit is in the first state: the first switch is closed; The second switch is opened; The third switch is opened; The fourth switch is closed; The fifth switch is opened; When the circuit is in the second state: the first switch is closed; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed; When the circuit is in the third state: the first switch is opened; The second switch is closed; The third switch is opened; The fourth switch is closed; The fifth switch is opened; When the circuit is in the fourth state: the first switch is opened; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed.

In some of these embodiments, the circuits include: a sixth switch having a first side and a second side, wherein the first side is connected to the second side of the inductor; A seventh switch having a first side and a second side, wherein the first side is connected to the input voltage; A third capacitor having a first side and a second side, wherein the first side is connected to the second side of the seventh switch; An eighth switch having a first side and a second side, wherein the first side is connected to the second side of the sixth switch; A ninth switch having a first side and a second side, wherein the first side is connected to the second side of the eighth switch; A tenth switch having a first side and a second side, wherein the first side is connected to the second side of the third capacitor and to the second side of the ninth switch, wherein the second side is coupled to the voltage source. It includes more.

In some of these embodiments, the circuits include: a sixth switch having a first side and a second side, wherein the first side is connected to the second side of the inductor; A seventh switch having a first side and a second side, wherein the first side is connected to the input voltage; A third capacitor having a first side and a second side, wherein the first side is connected to the second side of the seventh switch; An eighth switch having a first side and a second side, wherein the first side is connected to the second side of the sixth switch; A ninth switch having a first side and a second side, wherein the first side is connected to the second side of the eighth switch; A tenth switch having a first side and a second side, wherein the first side is connected to the second side of the third capacitor and to the second side of the ninth switch, wherein the second side is coupled to the voltage source. Further comprising, when the circuit is in the first state: the first switch is opened; The second switch is closed; The third switch is opened; The fourth switch is closed; The fifth switch is opened; The sixth switch is opened; The seventh switch is opened; The eighth switch is closed; The ninth switch is opened; The tenth switch is closed; When the circuit is in the second state: the first switch is opened; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed; The sixth switch is opened; The seventh switch is closed; The eighth switch is opened; The ninth switch is closed; The tenth switch is opened.

In some of these embodiments, the circuits include: a sixth switch having a first side and a second side, wherein the first side is connected to the second side of the inductor; A seventh switch having a first side and a second side, wherein the first side is connected to the input voltage; A third capacitor having a first side and a second side, wherein the first side is connected to the second side of the seventh switch; An eighth switch having a first side and a second side, wherein the first side is connected to the second side of the sixth switch; A ninth switch having a first side and a second side, wherein the first side is connected to the second side of the eighth switch; A tenth switch having a first side and a second side, wherein the first side is connected to the second side of the third capacitor and to the second side of the ninth switch, wherein the second side is coupled to the voltage source. Further comprising, when the circuit is in the first state: the first switch is opened; The second switch is closed; The third switch is opened; The fourth switch is closed; The fifth switch is opened; The sixth switch is opened; The seventh switch is opened; The eighth switch is closed; The ninth switch is opened; The tenth switch is closed; When the circuit is in the second state: the first switch is opened; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed; The sixth switch is opened; The seventh switch is closed; The eighth switch is opened; The ninth switch is closed; The tenth switch is opened; When the circuit is in the third state: the first switch is closed; The second switch is opened; The third switch is opened; The fourth switch is closed; The fifth switch is opened; The sixth switch is opened; The seventh switch is opened; The eighth switch is closed; The ninth switch is opened; The tenth switch is closed; When the circuit is in the fourth state: the first switch is opened; The second switch is opened; The third switch is opened; The fourth switch is closed; The fifth switch is opened; The sixth switch is closed; The seventh switch is opened; The eighth switch is closed; The ninth switch is opened; The tenth switch is closed; When the circuit is in the fifth state: the first switch is opened; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed; The sixth switch is closed; The seventh switch is opened; The eighth switch is opened; The ninth switch is closed; The tenth switch is opened; When the circuit is in the sixth state: the first switch is closed; The second switch is opened; The third switch is closed; The fourth switch is opened; The fifth switch is closed; The sixth switch is opened; The seventh switch is opened; The eighth switch is opened; The ninth switch is closed; The tenth switch is opened.

Various objects, features, and advantages of the disclosed claims may be more fully appreciated with reference to the following detailed description of the disclosed claims when the same reference numbers are considered in connection with the following figures that identify the same elements.
1A and 1B illustrate an example of a buck regulator and its operation as known in the prior art.
2 shows an example of a 3:1 step-down Dickson Star SC regulator as known in the prior art.
3A-3C illustrate an example of the operation of a 3:1 step-down Dickson Star SC regulator as known in the prior art.
4 illustrates an example of a reconfigurable Dickson Star SC regulator that can be reconfigured to support multiple conversion ratios according to some embodiments.
5A-5C illustrate an example of the operation of the reconfigurable regulator of FIG. 4 for a 3:1 conversion ratio in accordance with some embodiments.
6A-6C illustrate an example of the operation of the reconfigurable regulator of FIG. 4 for a 2:1 conversion ratio in accordance with some embodiments.
7A-7C illustrate an example of the operation of the reconfigurable regulator of FIG. 4 for a 1:1 conversion ratio in accordance with some embodiments.
8 illustrates an example of a fixed conversion ratio 4:1 Dickson Star SC regulator in accordance with some embodiments.
9A-9C show examples of operation of a 4:1 Dickson Star SC regulator in accordance with some embodiments.
10 shows an example of a 4:1 reconfigurable Dickson Star SC regulator in accordance with some embodiments.
11A-11C illustrate an example of operation of a 4:1 reconfigurable Dickson Star SC regulator in a 4:1 conversion mode in accordance with some embodiments.
12A-12C illustrate an example of operation of a 4:1 reconfigurable Dickson Star SC regulator in a 3:1 conversion mode according to some embodiments.
13A-13C illustrate an example of the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 2:1 conversion mode according to some embodiments.
14A-14C illustrate an example of the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 1:1 conversion mode according to some embodiments.
15A and 15B illustrate an example of an N:1 reconfigurable Dickson Star SC regulator in accordance with some embodiments.
16 illustrates an example of a 4:1 reconfigurable Dickson Star SC regulator in accordance with some embodiments.
17A-17C illustrate an example of the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 4:1 conversion mode according to some embodiments.
18A-18C illustrate an example of operation of a 4:1 reconfigurable Dickson Star SC regulator in a 3:1 conversion mode according to some embodiments.
19A-19C illustrate an example of operation of a 4:1 reconfigurable Dickson Star SC regulator in a 2:1 conversion mode according to some embodiments.
20A-20C illustrate an example of the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 1:1 conversion mode in accordance with some embodiments.
21A and 21B illustrate an example of an N:1 reconfigurable Dickson Star SC regulator in accordance with some embodiments.
22-24 illustrate examples of step-up reconfigurable Dickson Star SC regulators in accordance with some embodiments.
25 illustrates an example of a two-stage voltage regulation system in which the SC regulator provides first stage voltage regulation according to some embodiments.
26A and 26B illustrate an example of the embodiment of FIG. 25 where the second stage regulator is a buck converter in accordance with some embodiments.
27 illustrates an example of a two-stage voltage regulation system in which the SC regulator provides second stage voltage regulation according to some embodiments.
28A and 28B illustrate an example of a two-stage voltage regulator in which the first stage regulator is made of an inductor according to some embodiments.
29A and 29B illustrate an example of the operation of the two-stage regulator of FIG. 28 where the SC regulator in accordance with some embodiments is a 4:1 Dixon Star switched-capacitor (SC) regulator.
30 illustrates an example of the duty-cycling of the second stage regulator and the voltage swing of V _TMP according to some embodiments.
31 illustrates an example of a two-stage voltage regulation system where the second stage regulator is a multi-phase voltage regulator in accordance with some embodiments.
FIG. 32 illustrates an example of the phase relationship between switch capacitors of FIG. 31 in accordance with some embodiments.
33 illustrates an example of a control sequence of switches that makes it possible to maintain the duty cycle of a first stage regulator in accordance with some embodiments.
34 is an example of a block diagram of a computing device including a voltage regulation system in accordance with some embodiments.
35A-35C show an example of operation of an N:1 step-down Dickson Star SC regulator in an N:1 conversion mode in accordance with some embodiments.
36A-36C illustrate an example of a hybrid converter (including an inductor and a 2:1 switch capacitor regulator) and its operation when in H21 mode, in accordance with some embodiments.
37A-37C illustrate examples of hybrid converters (including inductors and 2:1 switch capacitor regulators) and their operation when in 2:1 SC mode, in accordance with some embodiments.
38A and 38B illustrate examples of multiphase hybrid converters (including inductors and 2:1 switch capacitor regulators) and their operation when in 2:1 SC mode, according to some embodiments.
39A-39E illustrate an example of a multiphase hybrid converter (including an inductor and a 2:1 switch capacitor regulator) and its operation when in H21 mode, in accordance with some embodiments.

In the following description, in order to provide a thorough understanding of the disclosed claims, numerous specific details regarding the devices, systems, and methods of the disclosed claims, and the environment in which such devices, systems, and methods may operate, and the like. Details are presented. However, it is apparent to those skilled in the art that the disclosed claims may be practiced without these specific details, and that certain features well known in the art are not described in detail to avoid the complexity of the disclosed claims. something to do. Additionally, it will be understood that the examples provided below are for purposes of illustration, and that there are other devices, systems, and methods within the scope of the disclosed claims.

Modern electronic systems are tightly integrated as a system-on-chip (SoC) that includes multiple processing cores and heterogeneous components (eg, memory controllers, hardware accelerators) in a single chip. The popularity of SoCs combined with tighter power budgets drives the control of voltage and frequency with block-by-block granularity. Block-by-block voltage control can enable the electronic system to only raise the voltage of the core(s) that desire higher performance. The voltage control for each block may improve power and/or performance.

However, due to cost and size limitations of off-chip voltage regulators, traditional approaches of dynamic voltage and frequency scaling (DVFS) have been performed at the coarse-grain level. Moreover, traditional DVFS schemes have been limited to slow voltage/frequency scaling at microsecond timescales due to the slow speed of off-chip voltage regulators. Faster DVFS with nanosecond timescales can further save power consumed by SoCs by closely tracking SoC voltages for rapidly changing computational demands.

In view of these shortcomings of off-chip voltage regulators, there is a growing interest in building integrated voltage regulators (IVRs) that reduce board size and enable nanosecond timescale, DVFS per core. The IVR can include a variety of voltage regulators, including switching regulators and low-dropout linear regulators. IVRs that can reduce board size and enable nanosecond timescale, DVFS per core, were presented at the IEEE International Symposium on High-Performance Computer Architecture (HPCA) in February 2008 by Wonyoung Kim et al. A paper entitled "System Level Analysis of Fast, Per-Core DVFS using On-Chip Switching Regulators"; A paper entitled "Design Techniques for Fully Integrated Switched-Capacitor DC-DC Converters" published by IEEE Journal of Solid-State Circuits (JSSC) in September 2011 by Hanh-Phuc Le et al.; And a paper entitled "A Fully-Integrated 3-Level DC/DC Converter for Nanosecond-Scale DVFS" published by IEEE Young of Solid-State Circuits (JSSC) in January 2012 by Wonyoung Kim et al., Disclosed in the papers written by the inventors of the present application, each of these papers is hereby incorporated herein by reference in its entirety.

An example of a switching regulator is a buck regulator. 1A and 1B illustrate examples of a buck regulator and its operation as known in the prior art. As illustrated in FIG. 1A, the buck regulator 100 may include an inductor 108 and two switches 114 and 116. The buck regulator 100 can connect the inductor 108 to the first voltage source V _IN 104 and the second voltage source 118 through a set of power switches 114, 116. In some cases, the second voltage source 118 can be a ground voltage source. The power switches 114, 116 can be turned on and off using external controls. In some cases, power switches 114 and 116 can be controlled such that the two switches are not turned on simultaneously.

Power switches 114 and 116 may be formed from any suitable transistors in some embodiments. For example, transistors can be implemented using MOSFET transistors. More specifically, for example, in some embodiments, switch 114 may be implemented using a P-channel MOSFET transistor, and switch 116 may be implemented using an N-channel MOSFET transistor.

As illustrated in FIG. 1B, as power switches 114 and 116 are turned on and off at period T, the input of inductor V _X 102 can swing from 0 to V _IN at period T. Inductor 108 and capacitor 120 act as a low-pass filter that produces a signal at regulator output V _OUT 110 with small voltage ripple by averaging V _X 102 over time. The output voltage V _OUT 110 is the amount of time the inductor 108 is coupled to the first voltage source V _IN 104, and the inductor 108 is the second voltage source 118 (0V for illustrative purposes) Im) may be dependent on the amount of time to be coupled. For example, the buck regulator 100 can adjust the level of V _OUT 510 to V _IN D + (0V)(1-D), where D, a number from 0 to 1, V _X is coupled to V _IN It is part of the time being ringed. D is also referred to as the duty cycle of V _X 102. The current-consuming output load 106 can be any type of electronic device, including a processor, memory (DRAM, NAND flash), RF chip, WiFi combo chip, power amplifier, and the like.

The efficiency of the buck regulator 100 can be computed as follows:

은 출력 부하로 전달되는 전력을 나타내고

는 벅 레귤레이터(108)의 출력 전력을 나타낸다.

은 다음과 같이 컴퓨팅될 수 있다:

, 여기서

는 전압 레귤레이션 프로세스 동안 전력 손실들의 양을 포함한다.here

Denotes the power delivered to the output load

Denotes the output power of the buck regulator 108.

Can be computed as follows:

, here

Contains the amount of power losses during the voltage regulation process.

중 하나는, 인덕터(108)의 기생 저항에 의해 발생되는 저항성 손실

을 포함한다. 벅 레귤레이터(100)가 전류(112)를 제공함으로써 출력 부하에 전력을 전달할 때, 이상적으로, 벅 레귤레이터(100)는 그것의 출력 전력 모두를 출력 부하(106)에 제공한다. 그러나, 실제 시나리오에서, 벅 레귤레이터(100)는 인덕터(108)에서 내부적으로 그것의 출력 전력의 일부를 소산시킨다. 이상적으로, 인덕터는 제로 저항을 갖는다. 그에 따라, 인덕터(108)를 통한 전류는 어떠한 전력도 소산시키지 않을 것이다. 그러나, 실제 시나리오에서, 인덕터는, 주로 인덕터를 형성하는 재료의 저항으로 인해, 유한 저항과 연관된다. 인덕터의 이 바람직하지 않은 유한 저항이 기생 저항이라고 지칭된다. 기생 저항은 인덕터를 통한 전류가 에너지를 소산시키게 할 수 있기 때문에 기생 저항이 저항성 전력 손실을 발생시킬 수 있다. 그에 따라, 저항성 전력 손실은 벅 레귤레이터(100)의 전력 변환 효율을 감소시킬 수 있다.Major power losses associated with buck regulator 100

One is resistive loss caused by parasitic resistance of the inductor 108

It includes. When the buck regulator 100 delivers power to the output load by providing current 112, ideally, the buck regulator 100 provides all of its output power to the output load 106. However, in a real world scenario, the buck regulator 100 dissipates a portion of its output power internally at the inductor 108. Ideally, the inductor has zero resistance. Accordingly, the current through inductor 108 will not dissipate any power. However, in the actual scenario, the inductor is associated with a finite resistance, mainly due to the resistance of the material forming the inductor. This undesirable finite resistance of the inductor is referred to as parasitic resistance. Parasitic resistors can cause current through the inductor to dissipate energy, so parasitic resistors can cause resistive power losses. Accordingly, the resistive power loss can reduce the power conversion efficiency of the buck regulator 100.

로서 컴퓨팅될 수 있고, 여기서 R_L은 인덕터(108)의 기생 저항의 값이고, I_L,RMS는 인덕터(108)를 통한 전류의 평균 제곱근이다. 인덕터 전류의 피크-투-피크 리플(peak-to-peak ripple)(I_L,PP(120))을 감소시킴으로써 I_L,RMS가 감소될 수 있다. 그에 따라, 벅 레귤레이터(100)는 인덕터 전류의 피크-투-피크 리플 I_L,PP(120)를 감소시킴으로써 저항성 손실

을 감소시킬 수 있다.When the current is alternating, then the resistive power loss

Can be computed as, where R _L is the value of the parasitic resistance of the inductor 108, and I _L,RMS is the mean square root of the current through the inductor 108. I _L,RMS can be reduced by reducing the peak-to-peak ripple of the inductor current (I _L,PP 120). Accordingly, the buck regulator 100 reduces resistivity by reducing the peak-to-peak ripple I _L,PP 120 of the inductor current.

Can be reduced.

, 여기서 C는 접합부(122)에서의 기생 커패시턴스의 양이고,

는 벅 레귤레이터(100)가 스위칭하는 주파수이고, V는 접합부(122)에서의 전압 스윙이다. 이 전력 손실은 상당할 수 있는데, 이는 스위치들(114, 116)의 사이즈가 커서 그것이 기생 커패시턴스를 증가시키기 때문이고, 그리고 V_X(102)에 대한 전압 스윙이 크기 때문이다.There are two ways to reduce the peak-to-peak ripple I _L,PP 120 of the inductor current. First, the buck regulator 100 can switch to high frequency and reduce the period T of the switching regulator. However, this solution can increase the power consumed to charge and discharge the parasitic capacitance at the junction 122 between the switches 114, 116. This capacitive power loss can be significant, because the size of the switches 114, 116 can be large because it increases the parasitic capacitance, and the voltage swing for V _X 102 is large. This capacitive power loss can be computed as follows:

, Where C is the amount of parasitic capacitance at the junction 122,

Is the frequency at which the buck regulator 100 switches, and V is the voltage swing at the junction 122. This power loss can be significant, because the size of the switches 114, 116 is large because it increases the parasitic capacitance, and the voltage swing for V _X 102 is large.

Second, the buck regulator 100 can reduce the parasitic resistance R _L by using the inductor 108 having a high inductance value. However, this approach makes the inductor 108 large, which makes integration difficult.

Another example of a switching regulator is a switched capacitor (SC) regulator. The SC regulator can use one or more capacitors instead of an inductor to transfer charge from the power source to the output load. The SC regulator can provide output voltages that are a weighted average of different voltages by connecting/disconnecting one or more capacitors to/from different voltages using power switches (each different voltage connected at different times). The SC regulator can control the output voltage by changing the configuration, sequence and duty cycle that causes the capacitors to be coupled to each other. Since capacitors are easier to integrate on-die or on-package than inductors, it is easier to implement SC IVRs with smaller sizes.

One type of SC regulator is the Dickson Star SC regulator. An example of a 3:1 step-down Dixon Star SC regulator (a step-down Dixon Star SC regulator configured to divide the input voltage level by 1/3) is illustrated in FIG. 2. The Dickson Star SC regulator has several advantages compared to other SC regulator topologies. First, it uses fewer capacitors compared to other SC regulator topologies such as ladder type SC regulators. Secondly, it can use transistors with lower voltage ratings as switches compared to other SC regulator topologies, such as a series-to-parallel SC regulator. Third, it can be scaled more easily with higher input voltages compared to other SC regulator topologies such as series-parallel SC regulators.

The Dickson Star SC regulator 200 inputs the switching capacitors C1 _FLY 204 and C2 _FLY 206, and the switching capacitors C1 _FLY 204 and C2 _FLY 206, the input voltage node V _IN 202, the output A switch matrix comprising a plurality of switches 216, 218, 220, 222, 224, 226, and 228 configured to electrically couple to voltage node V _OUT 208 and ground node GND 210. It can contain. The output node V _OUT 208 is coupled to the output load I _OUT 212 and a decoupling capacitor C _OUT 214.

3A to 3C illustrate the basic operation of the Dickson Star SC regulator 200. As shown in FIG. 3C, the Dickson Star SC regulator 200 is duty cycled between state 0 (illustrated in FIG. 3A) and state 1 (illustrated in FIG. 3B) with duty cycle D over time. The value of the duty cycle (D) can be any value from 0 to 1, and preferably from 0.25 to 0.75.

When the switching capacitors C1 _FLY 204 and C2 _FLY 206 are sufficiently large, the voltages V _C1FLY and V _C2FLY across these switching capacitors, respectively, remain almost constant between state 0 and state 1. Additionally, often a large decoupling capacitor C _OUT 214 is always coupled to output V _OUT 208 to reduce noise to the output. Accordingly, the output voltage V _OUT 208 remains almost constant in state 0 and state 1. Based on these characteristics, the following voltage relationships can be derived:

State 0: V _OUT (208) + V _C1FLY = V _C2FLY

State 1: V _OUT (208) = V _C1FLY

State 1: V _OUT (208) + V _C2FLY = V _IN (202)

By removing V _C1FLY and V _C2FLY from these relationships, the following relationships can be derived:

V _OUT = (1/3) x V _IN

This shows that the alternation between state 0 and state 1 provides 3:1 step-down voltage regulation. This 3:1 step-down Dixon Star SC regulator design can be extended to an N:1 step-down Dixon Star SC regulator, where N is a number greater than 3.

35A and 35B show the topology and operation of the N:1 step-down Dickson Star SC regulator. The N:1 step-down Dixon Star SC regulator can include a capacitor matrix (also referred to as a capacitor bank). The capacitor matrix can include a first capacitor sub-matrix and a second capacitor sub-matrix. The capacitors in the first capacitor sub-matrix are called C(1, j), where the first index "1" refers to the "first" capacitor matrix, and the second index "j" to the first capacitor sub-matrix. It refers to the jth capacitor in the matrix. Likewise, capacitors in the second capacitor sub-matrix are referred to as C(2, j). 35A and 35B, the first capacitor sub-matrix includes M number of capacitors; The second capacitor sub-matrix includes K number of capacitors. M may be equal to floor(N/2), and K may be equal to floor((N-1)/2).

The N:1 step-down Dickson Star SC regulator includes multiple switch matrices. The switches in the first switch sub-matrix include the lower four switches SW1 216, SW2 218, SW3 220, and SW4 222. The switches in the second switch sub-matrix are referred to as SW(2, j), where the index "j" refers to the jth switch in the switch matrix.

35A and 35B, in the first switch sub-matrix SW1 216, SW2 218, SW3 220, SW4 222, the number of switches and connections of the switches are irrespective of the value of "N" Does not change. The second switch sub-matrix includes F number of switches, and the value F can be equal to M+K+1.

SW1 216 is connected between one terminal of GND 210 and SW2 218. The other terminal of SW2 218 is connected to one terminal of V _OUT 208 and SW3 220. SW4 222 is connected between GND 210 and other terminals of SW3 220. SW(2,1) is connected between V _OUT 208 and one terminal of C(1,1). The remaining switches in the second switch sub-matrix are connected between the capacitors in the first capacitor sub-matrix and the capacitors in the second capacitor sub-matrix. For example, SW(2, j) (where J>=2) is connected between one terminal of C(1,p) and one terminal of C(2, q), where the value p is ceiling( j/2) and the value q equals floor(j/2). The connection between SW1 216 and SW2 218 is connected to the other terminal of C(1,p), and the connection between SW3 220 and SW4 222 is connected to the other terminal of C(2,q). do.

The N:1 step-down Dickson Star SC regulator can be duty cycled between state 0 and state 1, as shown in FIGS. 35A and 35B, respectively, by turning on and off switches in the switch matrices.

35A and 35B show the operation of the N:1 step-down Dickson Star SC regulator in N:1 conversion mode. In state 0, in the first switch sub-matrix, SW1 216 and SW3 220 are turned off (i.e. open), and SW2 218 and SW4 222 are turned on (i.e. closed). In the second switch sub-matrix, all odd index switches are turned off (i.e. open), while all even index switches are turned on (i.e. closed). Subsequently, in state 1, all switch states are inverted compared to state 0.

The advantage of this switch configuration is that, regardless of how large N is, all switches have only a maximum V _OUT 208 applied across them. One drawback is that some capacitors have high voltages applied across them, which requires high voltage rated capacitors which can be bulky and expensive. In some embodiments, the voltages V _C(1,p) and V _C(2,q) across the capacitors are ((p-1) x 2+1) x V _OUT 208 and qx 2 x V Same as _OUT 208. As a result, this Dixon star configuration is useful when low voltage switches and high voltage capacitors are available.

Dixon Star SC regulators may be useful, but this design will still be limited to a single conversion ratio (the ratio between the input voltage V _IN 202 of N:1 and the output voltage V _OUT 208) and provides different conversion ratios. In order to do this, the voltages cannot be efficiently regulated.

One disadvantage of using a single conversion ratio SC regulator is the limited range of output voltages. Often, the efficiency of SC regulators can degrade at output voltages that are not a predetermined fraction of the input voltage (eg, 1/N). SC regulators are typically optimized to achieve high efficiency at a single conversion ratio. For example, when an SC regulator is coupled to a battery providing 3.3V, the SC regulator may be optimized to receive 3.3V and provide a fixed output voltage of 1.1V. In this case, the efficiency of the SC regulator is optimized to provide an output voltage of 1.1V-the efficiency of the SC regulator will decrease as the output voltage deviates from 1.1V. In other words, the SC regulator may be optimized to provide high efficiency at a conversion ratio of 3:1, and the efficiency of the SC regulator may decrease as the conversion ratio deviates from 3:1. This decline in efficiency is unfortunate because the system-on-chip (SoC) may operate at many voltage levels, and it would be desirable to use a single SC regulator to accommodate all of these voltage levels in the SoC. .

One way to support multiple conversion rates is to provide multiple regulators, each dedicated to a specific conversion rate, and enable only one of these regulators depending on which conversion rate needs to be supported. . However, this requires many redundant capacitors and switches. For example, when a 3:1 regulator is being used, all switches and capacitors for 2:1 and 1:1 regulators remain idle without being used. Redundant capacitors and switches require an area for the integrated circuit chip and add costs, both of which are undesirable.

Accordingly, it would be desirable to provide a single SC regulator that can achieve high efficiencies at multiple conversion ratios. In other words, by providing a single SC regulator that can be reconstructed for one of many conversion ratios (e.g. 1/2, 1/3, 2/3, 2/5, 3/5, 4/5) It would be desirable for a single SC regulator to accommodate one of many output voltage levels with high efficiency.

This disclosure shows a reconfigurable Dickson Star SC regulator that can support multiple conversion ratios by reconstructing between various modes. The reconfigurable Dickson Star SC regulator is designed to reduce the number of redundant capacitors by reusing capacitors and switches across multiple modes of operation (over multiple conversion ratios).

In some embodiments, the reconfigurable Dixon Star SC regulator includes a regular Dixon Star SC regulator and a mode switch matrix. The mode switch matrix includes a plurality of switches coupled to a regular Dixon Star SC regulator. Depending on the desired conversion ratio, one or more switches in the mode switch matrix may be enabled to reconstruct the arrangement of capacitors in a regular Dickson Star SC regulator. In this way, the mode switch matrix is capable of reconstructing the conversion ratio of the regular fixed conversion mode Dickson Star SC regulator.

In some embodiments, depending on the reconstructed conversion ratio of the reconfigurable Dixon Star SC regulator, the switches in the regular fixed conversion mode Dickson Star SC regulator take into account the reconstructed arrangement of capacitors (compared to its regular fixed conversion mode operation. It may be controlled differently.

In the discussions above, an N:1 reconfigurable Dixon Star SC regulator refers to a reconfigurable Dixon Star SC regulator that can be reconfigured to provide any one of the M:1 conversion ratios, where M is 1 to N Is the value.

4 illustrates an example of a reconfigurable Dickson Star SC regulator that can be reconfigured to support multiple conversion ratios according to some embodiments. 4 shows a 3:1 reconfigurable Dickson Star SC regulator 400 that can be reconstructed with one of the conversion ratios: 3:1, 2:1, 1:1. The 3:1 reconfigurable Dixon Star SC regulator 400 is a mode comprising a fixed 3:1 Dixon Star SC regulator 200 of FIG. 2 identified using box 404, and a single mode switch SW8 402. And a switch matrix 406. This additional mode switch 402 can be selectively operated to convert the fixed 3:1 Dixon Star SC regulator of FIG. 2 to a 3:1 reconfigurable Dixon Star SC regulator.

5-7 illustrate the operation of the reconfigurable regulator of FIG. 4 for conversion ratios 3:1, 2:1, 1:1, respectively, in accordance with some embodiments. 5A-5C, the mode switch SW8 402 can be simply turned off (in the "open" position) to operate the reconfigurable Dixon Star SC regulator 400 in a 3:1 conversion mode. The fixed 3:1 Dixon Star SC regulator 404 in the reconfigurable regulator 400 can be operated in the same way as in FIG. 3 (a plurality of switches to switch the regulator between state 0 and state 1). Duty cycle).

6A to 6C, the fixed 3:1 regulator 404 is duty cycled between state 0 and state 1 to operate the reconfigurable Dickson Star SC regulator 400 in a 2:1 conversion mode. Accordingly, switch SW8 402 can be turned on (ie closed) during state 0 and switch SW8 402 can be turned off (ie open) during state 1. In a sense, this 3:1 reconfigurable Dixon Star SC regulator operates in a 2:1 conversion mode, as in the traditional 2:1 SC regulator, the mode switch SW8 402 switches the switching capacitors C1 _FLY (204 ) And C2 _FLY 206 are connected together in a parallel fashion and cause them to operate collectively as a single large capacitor in state 0. For example, in a traditional 2:1 SC regulator, switching capacitors, or multiple switching capacitors connected in parallel to act as one switching capacitor, are connected between the input voltage and the output voltage in one state, while in the other state It is connected between the output voltage and ground. By switching between these two states, the output voltage is half of the input voltage. The switches of FIGS. 6A and 6B are turned on and off as shown in the figures to allow switching capacitors to behave as in a traditional 2:1 SC regulator.

7A-7C, switch SW8 402 as the regulator is duty cycled between State 0 and State 1 to operate the reconfigurable Dickson Star SC regulator 400 in a 1:1 conversion mode. Can be turned on (ie closed) during state 0 and switch SW8 402 can be turned off (ie open) during state 1. The remaining switches are turned on and off accordingly, allowing the switching capacitors to behave as in a traditional 1:1 SC regulator. For example, in a traditional 1:1 SC regulator, switching capacitors, or multiple switching capacitors connected in parallel to act as one switching capacitor, are connected between input voltage and ground in one state, while output in the other state It is connected between voltage and ground. By switching between these two states, the output voltage becomes similar to the input voltage. The switches of FIGS. 7A and 7B are turned on and off as shown in the figures to allow switching capacitors to behave as in a traditional 1:1 SC regulator.

In some embodiments, the reconfigurable Dixon Star SC regulator can be a 4:1 reconfigurable Dixon Star SC regulator. In other words, the reconfigurable Dickson Star SC regulator can be configured to provide one of the following conversion ratios: 4:1, 3:1, 2:1, 1:1. To facilitate discussion of a 4:1 reconfigurable Dixon Star SC regulator, FIG. 8 illustrates a fixed conversion ratio 4:1 Dixon Star SC regulator 800. Compared to the 3:1 Dixon Star SC regulator 200 of Figure 2, the 4:1 Dixon Star SC regulator 800 has one or more switching capacitors C3 _FLY 802 and one or more switches SW9 804.

Similar to the 3:1 Dixon Star SC regulator 200, the 4:1 regulator 800 is duty cycled between state 0 and state 1 to provide voltage regulation. 9A-9C show duty cycling of a 4:1 regulator 800 between state 0 and state 1. Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _IN (202) = V _C3FLY + V _OUT (208)

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _C3FLY = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT

V _C3FLY = 3 x V _OUT

V _OUT = (1/4) x V _IN

Accordingly, the Dixon Star SC regulator illustrated in FIG. 8 operates as a 4:1 step-down Dixon Star SC regulator.

In some embodiments, the fixed conversion mode 4:1 Dixon Star SC regulator can be augmented with a mode switch matrix to provide a 4:1 reconfigurable Dixon Star SC regulator. 10 shows a 4:1 reconfigurable Dickson Star SC regulator 1000 in accordance with some embodiments. The 4:1 reconfigurable Dixon Star SC regulator 1000 includes a fixed conversion mode 4:1 Dixon Star SC regulator and a mode switch matrix with two mode switches SW10 1002 and SW11 1004. The mode switch matrix is designed to reconstruct the arrangement of capacitors in a fixed conversion mode 4:1 Dixon Star SC regulator to enable reconstruction between 4:1, 3:1, 2:1 and 1:1 conversion ratios.

11A-11C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 4:1 conversion mode according to some embodiments. In this mode of operation, while the Dickson Star SC regulator cycles duty between State 0 and State 1, as shown in FIG. 11C, mode switches SW10 1002 and SW11 1004 are also duty cycled to convert 4:1. Providing a ratio, it behaves similarly to SW1 216 and SW2 218. For example, in state 0, the first mode switch SW10 1002 is turned off (“open”), and the second mode switch SW11 1004 is turned on (“closed”), and in state 1, the first mode Switch SW10 1002 is turned on (“closed”) and second mode switch SW11 1004 is turned off (“opened”).

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _IN (202) = V _C3FLY + V _OUT (208)

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _C3FLY = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT

V _C3FLY = 3 x V _OUT

V _OUT = (1/4) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 11A and 11B operates as a 4:1 step-down Dixon Star SC regulator.

12A-12C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 3:1 conversion mode according to some embodiments. In this mode of operation, while the regulator cycles duty between state 0 and state 1, as shown in FIG. 12C, mode switches SW10 1002 and SW11 1004 are also duty cycled to provide a 3:1 conversion ratio. do. For example, in state 0, the first mode switch SW10 1002 is turned on (“closed”), and the second mode switch SW11 1004 is turned off (“open”), and in state 1, the first mode Switch SW10 1002 is turned off ("open") and second mode switch SW11 1004 is turned on ("closed").

In some sense, the operation of this 4:1 reconfigurable Dixon Star SC regulator operating in 3:1 conversion mode is similar to that of the fixed conversion mode 3:1 Dixon Star SC regulator 200 of FIG. 2. For example, the switching capacitors C2 _FLY 206 and C3 _FLY 802 are connected together in parallel to provide a larger single capacitor, which operates together as C2 _FLY 206 in FIG. 2. As another example, the switching capacitor C1 _FLY 204 of FIGS. 12A and 12B operates as the C1 _FLY 204 of FIG. 2. Accordingly, the number of capacitors in the 4:1 reconfigurable Dixon Star SC regulator is different from the fixed conversion mode 3:1 Dixon Star SC regulator in FIG. 2, but the 4:1 reconfigurable Dixon Star SC regulator uses multiple switches. It can operate in 3:1 conversion mode through reconstruction of the capacitor arrays.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C2FLY = V _C3FLY

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _IN (202) = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT (208)

V _C3FLY = 2 x V _OUT (208)

V _OUT = (1/3) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 12A-12C operates as a 3:1 step-down Dixon Star SC regulator.

13A-13C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 2:1 conversion mode according to some embodiments. In this mode of operation, while the Dickson Star SC regulator cycles duty between state 0 and state 1, as shown in FIG. 13C, mode switches SW10 1002 and SW11 1004 are also duty cycled to convert 2:1. Provide a ratio. For example, in state 0, the first mode switch SW10 1002 is turned off (“open”) and the second mode switch SW11 1004 is turned on (“closed”), and in state 1, the first mode Switch SW10 1002 is turned on (“closed”) and second mode switch SW11 1004 is turned off (“opened”).

In a sense, this 4:1 reconfigurable Dixon Star SC regulator operates in 2:1 conversion mode, as in the traditional 2:1 SC regulator, the regulator has three switching capacitors C1 _FLY 204, C2 _FLY (206), due to the connection with the both C3 _FLY (802) in parallel and operating them in bulk as a single large capacitor. For example, in a traditional 2:1 SC regulator, switching capacitors, or multiple switching capacitors connected in parallel to act as one switching capacitor, are connected between the input voltage and the output voltage in one state, while in the other state It is connected between the output voltage and ground. By switching between these two states, the output voltage is half of the input voltage. The switches of FIGS. 13A and 13B are thus turned on and off to allow the switching capacitors to behave as in a traditional 2:1 SC regulator.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C1FLY = V _C2FLY = V _C3FLY = V _IN (202)-V _OUT (208)

State 1: V _C1FLY = V _C2FLY = V _C3FLY = V _OUT (208)

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C1FLY = V _OUT

V _C2FLY = V _OUT

V _C3FLY = V _OUT

V _OUT = (1/2) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 13A-13C operates as a 2:1 step-down Dixon Star SC regulator.

14A-14C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 1:1 conversion mode according to some embodiments. In this mode of operation, while the Dickson Star SC regulator cycles duty between state 0 and state 1, as shown in FIG. 14C, mode switches SW10 1002 and SW11 1004 are not duty cycled. For example, in both state 0 and state 1, the first mode switch SW10 1002 is turned on (“closed”) and the second mode switch SW11 1004 is turned off (“opened”).

In a sense, this 4:1 reconfigurable Dixon Star SC regulator operates in 1:1 conversion mode, as in the traditional 1:1 SC regulator, the regulator has three switching capacitors C1 _FLY 204, C2. _FLY (206), due to the connection with the both C3 _FLY (802) in parallel and operating them in bulk as a single large capacitor. For example, in a traditional 1:1 SC regulator, switching capacitors, or multiple switching capacitors connected in parallel to act as one switching capacitor, are connected between input voltage and ground in one state, while output in the other state It is connected between voltage and ground. By switching between these two states, the output voltage becomes similar to the input voltage. The switches of FIGS. 14A and 14B are turned on and off as shown in the figures to allow switching capacitors to behave as in a traditional 1:1 SC regulator.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C1FLY = V _C2FLY = V _C3FLY = V _IN (202)

State 1: V _C1FLY = V _C2FLY = V _C3FLY = V _OUT (208)

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C1FLY = V _OUT

V _C2FLY = V _OUT

V _C3FLY = V _OUT

V _OUT = V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 14A-14C operates as a 1:1 step-down Dixon Star SC regulator.

In some embodiments, the 3:1 reconfigurable Dixon Star SC regulator 400 illustrated in FIG. 4 and the 4:1 reconfigurable Dixon Star SC regulator 1000 illustrated in FIG. 10 are N:1 reconfigurable Dixon Star SC. It can be extended to a regulator, where N can be any number greater than one.

15A and 15B illustrate an N:1 reconfigurable Dickson Star SC regulator in accordance with some embodiments.

In some embodiments, the N:1 reconfigurable Dixon Star SC regulator 1500 can include a capacitor matrix (also referred to as a capacitor bank). The capacitor matrix can include a first capacitor sub-matrix and a second capacitor sub-matrix. The capacitors in the first capacitor sub-matrix are called C(1, j), where the first index "1" refers to the "first" capacitor matrix, and the second index "j" to the first capacitor sub-matrix. It refers to the jth capacitor in the matrix. Likewise, capacitors in the second capacitor sub-matrix are referred to as C(2, j). 15A and 15B, the first capacitor sub-matrix includes M number of capacitors; The second capacitor sub-matrix includes K number of capacitors. In some embodiments, M is equal to floor(N/2) and K is equal to floor((N-1)/2).

In some embodiments, the N:1 reconfigurable Dixon Star SC regulator 1500 comprises a first switch sub-matrix, a second switch sub-matrix, a third switch sub-matrix, a fourth switch sub-matrix, and a fifth Includes switch matrix.

The switches in the first switch sub-matrix are referred to as SW(1, j), where the first index "1" refers to the "first" switch matrix, and the second index "j" to the first switch sub-matrix. J-th switch in the matrix. Likewise, switches in the second switch sub-matrix are referred to as SW(2, j); The switches in the third switch sub-matrix are called SW(3, j); The switches in the fourth switch sub-matrix are called SW(4, j); The switches in the fifth switch sub-matrix are called SW(5, j).

15A and 15B, each of the first switch sub-matrix and the second switch sub-matrix includes M number of switches; Each of the third switch sub-matrix and the fourth switch sub-matrix includes K number of switches; The fifth switch sub-matrix includes L number of switches. In some embodiments, M is equal to floor(N/2); K is equal to floor((N-1)/2); L is the same as N.

In some embodiments, regulator 1500 may be duty cycled between state 0 and state 1 by turning on and off switches in the switch matrix of regulator 1500.

15A and 15B illustrate the operation of an N:1 reconfigurable Dickson Star SC regulator 1500 in an N:1 conversion mode according to some embodiments. In state 0, all switches in the first switch sub-matrix on the lower left side are turned on, while all switches in the second switch sub-matrix side are turned off. Additionally, all switches in the third switch sub-matrix are turned off, while all switches in the fourth switch sub-matrix are turned on. In the fifth switch sub-matrix, all odd index switches are off, while all even index switches are on. Subsequently, in state 1, all switch states are inverted compared to state 0. There are additional switches including SW(j,1), SW(j,2), SW(j,3), SW(j,4)-where j is greater than 1, and the capacitor topologies are shown in Figure 35 Similar to the N:1 step-down Dickson Star.

To operate the N:1 reconfigurable Dixon Star SC regulator 1500 in the (N-1):1 conversion mode, the capacitor (C(1, M)) with the highest index in the first capacitor sub-matrix and the first The capacitors C(2, K) with the highest index in the two capacitor sub-matrix can be connected together in parallel to act as a single capacitor. This "single" capacitor is a (N-1):1 fixed conversion mode Dickson Star SC regulator-capacitors C(2, K), SW(5) connected to V _IN 202 via switch SW(5,L) , L), the upper switch in the fifth switch matrix, and the two switches connected to C(2,K) SW(3, K) and SW(4, K) without N:1 fixed conversion mode Dickson Star SC The same Dixon Star SC regulator as the regulator-can act similarly to C(1, M) in.

To operate an N:1 reconfigurable Dickson Star SC regulator in (N-2):1 conversion mode, three capacitors connected to V _IN 202 through the fewest switches in the fifth switch sub-matrix are in parallel Connected together, they can act like a single capacitor. These three capacitors are, for example, one capacitor C(1, M) with the highest index in the first capacitor sub-matrix, and two capacitors with the highest indices in the second capacitor sub-matrix ( C(2, K), C(2, K-1)). These "single" capacitors are (N-2):1 fixed conversion mode Dickson Star SC regulators-C(1, M) and C(2, K), SW(5, L) and SW(5, L-1) The upper two switches in the fifth switch matrix, and the switches connected to C(1,M) and C(2,K) SW(1,M), SW(2,M), SW(3, K), N:1 fixed conversion mode without SW(4,K) Same as C(2, K-1) in Dickson Star SC regulator-same as Dickson Star SC regulator.

More generally, to operate the N:1 reconfigurable Dixon Star SC regulator in (NR):1 conversion mode, the "R+" is connected to V _IN 202 through the fewest switches in the fifth switch sub-matrix. 1" number of capacitors can be connected together in parallel to act as a single capacitor, and the remaining switches can be operated as if operating a (NR):1 fixed conversion mode Dickson Star SC regulator.

In some embodiments, another topology of the Dickson Star SC regulator may enable reconstruction between conversion modes. 16 illustrates a 4:1 reconfigurable Dickson Star SC regulator 1600 in accordance with some embodiments. The 4:1 reconfigurable Dixon Star SC regulator 1000 of FIGS. 10-14 is compared to the fixed conversion mode 4:1 Dixon Star SC regulator 800 of FIG. 8 with two additional mode switches SW10 1002 and SW11 (1004). 16 illustrates a different type of 4:1 reconfigurable Dickson Star SC regulator using two additional mode switches SW12 1602 and SW 13 1604 at different positions.

17A-17C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator operating in a 4:1 conversion mode according to some embodiments. The positions of the mode switches are slightly different, but the capacitor topology in State 0 and State 1 is the same as the regulator 1000 of FIGS. 11A and 11B. Accordingly, the relationships between the voltages across the capacitors in states 0 and 1 of FIGS. 17A and 17B are related to the voltages across the capacitors in states 0 and 1 of FIGS. 11A and 11B. same. 11A and 11B, assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, for two states: The relationships of can be derived:

State 0: V _IN (202) = V _C3FLY + V _OUT (208)

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _C3FLY = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT

V _C3FLY = 3 x V _OUT

V _OUT = (1/4) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 17A and 17B operates as a 4:1 step-down Dixon Star SC regulator.

18A-18C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator in a 3:1 conversion mode according to some embodiments. The operating principle in 3:1 conversion mode is similar to the 3:1 SC regulator illustrated in FIG. 2. Switching capacitors C1 _FLY 204 and C3 _FLY 802 are connected together in parallel to act as a single large capacitor, similar to capacitor C1 _FLY 204 in FIG. The switching capacitor C2 _FLY 206 of FIGS. 18A and 18B operates in a similar manner to C2 _FLY 206 of FIG. 2.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C2FLY = V _C3FLY

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _IN (202) = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT (208)

V _C3FLY = 2 x V _OUT (208)

V _OUT = (1/3) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 18A-18C operates as a 3:1 step-down Dixon Star SC regulator.

19A-19C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator when the 4:1 reconfigurable Dickson Star SC regulator is operating in 2:1 mode, according to some embodiments. The basic principle is similar to the 4:1 reconfigurable Dickson Star SC regulator illustrated in FIGS. 13A and 13B. Switching capacitors _{C1 FLY (204), C2 FLY} (206), C3 FLY (802) is the in Fig. 13a and 13b the capacitor C1 _FLY (204), in a parallel _{C2 FLY (206), C3 FLY} (802) It works like a single large capacitor when connected and works like a single large capacitor when connected in parallel.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C1FLY = V _C2FLY = V _C3FLY = V _IN (202)-V _OUT (208)

State 1: V _C1FLY = V _C2FLY = V _C3FLY = V _OUT (208)

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C1FLY = V _OUT

V _C2FLY = V _OUT

V _C3FLY = V _OUT

V _OUT = (1/2) x V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 19A-19C operates as a 2:1 step-down Dixon Star SC regulator.

20A-20C illustrate the operation of a 4:1 reconfigurable Dickson Star SC regulator when a 4:1 reconfigurable Dickson Star SC regulator is operating in a 1:1 mode, according to some embodiments. Switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802, the capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 in parallel in FIGS. 14A and 14B. It works like a single large capacitor when connected and works like a single large capacitor when connected in parallel.

Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _C1FLY = V _C2FLY = V _C3FLY = V _IN (202)

State 1: V _C1FLY = V _C2FLY = V _C3FLY = V _OUT (208)

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C1FLY = V _OUT

V _C2FLY = V _OUT

V _C3FLY = V _OUT

V _OUT = V _IN

Accordingly, the reconfigurable Dixon Star SC regulator illustrated in FIGS. 14A-14C operates as a 1:1 step-down Dixon Star SC regulator.

The regulators of FIGS. 10-14 and the regulators of FIGS. 16-20 use a mode switch matrix with switches located in different positions, but the final capacitor arrangements are the same. Accordingly, the reconfigurable regulator 1000 is functionally the same as the reconfigurable regulator 1600.

In some embodiments, 4:1 reconfigurable regulator 1600 can be generalized to provide an N:1 reconfigurable regulator, where N is greater than one. 21A-21C illustrate an N:1 reconfigurable Dickson Star SC regulator 2100 operating in accordance with some embodiments.

The N:1 reconfigurable Dickson Star SC regulator 2100 may also include a capacitor matrix. The capacitor matrix can include a first capacitor sub-matrix and a second capacitor sub-matrix. The capacitors in the first capacitor sub-matrix are called C(1, j), where the first index "1" refers to the "first" capacitor matrix, and the second index "j" to the first capacitor sub-matrix. It refers to the jth capacitor in the matrix. Likewise, capacitors in the second capacitor sub-matrix are referred to as C(2, j). 21A and 21B, the first capacitor sub-matrix includes M number of capacitors; The second capacitor sub-matrix includes K number of capacitors. In some embodiments, M is equal to floor(N/2) and K is equal to floor((N-1)/2).

In some embodiments, the N:1 reconfigurable Dixon Star SC regulator 2100 includes a switch matrix with a first switch sub-matrix, a second switch sub-matrix, and a third switch sub-matrix.

The switches in the first switch sub-matrix are referred to as SW(1, j), where the first index "1" refers to the "first" switch matrix, and the second index "j" to the first switch sub-matrix. J-th switch in the matrix. Similarly, switches in the second switch sub-matrix are referred to as SW(2, j), and switches in the third switch sub-matrix are referred to as SW(3, j). 21A and 21B, the first switch sub-matrix includes E number of switches; The second switch sub-matrix includes D number of switches; The third switch sub-matrix includes F number of switches. In some embodiments, E is equal to 2 x ceiling(N/2)-1; D is equal to floor(N/2); F is the same as N.

In some embodiments, a switch in the first switch sub-matrix connects two capacitors in the first capacitor sub-matrix. For example, C(1, p) and C(1, p+1) are connected via SW(1, p). Similarly, a switch in the second switch sub-matrix connects two capacitors in the second capacitor sub-matrix. For example, C(2, p) and C(2, p+1) are connected via SW(2, p). The switch in the third switch sub-matrix connects the capacitor in the first capacitor sub-matrix to the capacitor in the second capacitor sub-matrix. For example, C(1, p) and C(2, p) are connected via SW(3, 2 xp), C(1, p+1) and C(2, p) are SW(3, 2 xp + 1).

In some embodiments, the regulator 2100 can be duty cycled between state 0 and state 1 by turning on and off switches in the switch matrix of the regulator 2100, as shown in FIGS. 21A and 21B.

21A and 21B illustrate the operation of an N:1 reconfigurable Dickson Star SC regulator 2100 in an N:1 conversion mode in accordance with some embodiments. In state 0, in the third switch sub-matrix, all odd index switches are turned off (i.e. open), while all even index switches are turned on (i.e. closed). Subsequently, in state 1, all switch states in the third switch sub-matrix are inverted compared to state 0. All switches on the first switch sub-matrix and all switches on the second switch sub-matrix side are turned off on both state 0 and state 1. There are additional switches that include first and second switch matrices, but since all of these switches are turned off, the capacitor topologies are similar to the N:1 step-down Dickson star in FIG. 35.

To operate the N:1 reconfigurable Dixon Star SC regulator 2100 in the (N-1):1 conversion mode, it is connected to V _IN 202 through the fewest switches in the third switch sub-matrix (or In other words, the capacitor closest to the input terminal)-this is C(2,K) in Figures 21A and 21B-and the capacitor in the same matrix but with one lower index-this is C(2) in Figures 21A and 21B , K-1) is-can be connected together in parallel to act as a single capacitor. To keep the two capacitors connected to the "single" capacitor, SW(2, D) is always on in state 0 and state 1. This "single" capacitor is a (N-1):1 fixed conversion mode Dickson star SC regulator-the same Dickson star as the N:1 fixed conversion mode Dickson star SC regulator without C(2, K), SW(3, F) It can operate similar to C(1, M) in SC regulators. Because C(2, K) is not independent in this mode (but works with C(2, K-1)), SW(3, F-1) is turned off in both State 0 and State 1 . C(1, M) acts as an upper capacitor, SW(1, E) acts like an upper switch, and SW(3, F) is turned off in both state 0 and state 1. In summary, SW(2, D) is always on in state 0 and state 1, SW(3, F-1) and SW(3, F) are always off in state 0 and state 1, and SW(1, E) is switched on and off in state 0 and state 1, respectively.

To operate an N:1 reconfigurable Dixon Star SC regulator in (N-2):1 conversion mode, three capacitors connected to V _IN 202 through the fewest switches are connected together in parallel to act as a single capacitor can do. 21A and 21B, these three capacitors are C(2,K), C(1,M), and C(2,K-1). This "single" capacitor is (N-2):1 fixed conversion mode Dickson Star SC regulator-without C(2, K), C(1,M), SW(3, F), SW(F-1) N:1 fixed conversion mode Same as C(2, K-1) in the Dickson Star SC regulator-the same as the Dickson Star SC regulator. In order to keep three capacitors connected as a "single" capacitor, SW(2,D), SW(3, E-1) are always on in state 0 and state 1. Since C(2, K) and C(1, M) no longer exist independently, SW(3, F-1) and SW(3, F-2) turn on both State 0 and State 1 Is off. C(2, K-1) acts as an upper capacitor, SW(3, F) acts like an upper switch, and SW(1, E) is turned off in both state 0 and state 1. In summary, W(2, D) and SW(1, E-1) are always on in State 0 and State 1, SW(3, F-1), SW(3, F-2), SW(1 , E) is always off in state 0 and state 1, and SW(3, F) is switched off and on in state 0 and state 1, respectively.

More generally, to operate an N:1 reconfigurable Dixon Star SC regulator in (NR):1 conversion mode, the "R+" is connected to V _IN 202 through the fewest switches in the third switch sub-matrix. The 1" number of capacitors can be connected together in parallel to act as a single capacitor, and operate the rest of the switches like operating a (NR):1 fixed conversion mode Dickson Star SC regulator.

In some embodiments, the control module is configured to perform the following switch operations to operate the N:1 reconfigurable Dixon Star SC regulator in (N-R):1 conversion mode. The control module excludes the upper switch SW(1, E) in the first switch sub-matrix, which is directly connected to the input voltage terminal, and the upper "R" number of switches in the first and second matrices ( For example, it is configured to turn on the R switches closest to the input voltage terminal, or in other words, the R switches having the smallest number of switches between them and the input voltage terminal). The first switch in the first switch sub-matrix and the second switch in the second switch sub-matrix have the same number of switches between them and the input voltage terminal and only one of them can be included in the set of R switches. When present, then the second switch in the second switch sub-matrix will be selected. For example, when R is equal to 3, SW(2, D), SW(1, E-1), and SW(2, D-1) are selected as the "3" switches closest to the input voltage terminal. . The control module is configured to hold the R switches turned on in both State 0 and State 1 to connect the top three capacitors in parallel.

In addition, the control module excludes the upper switch SW(3, F) in the third switch sub-matrix connected to the input voltage terminal, and the upper "R" number of switches in the third switch matrix (eg For example, it is configured to turn off the R number of switches closest to the input voltage terminal, or in other words, the R number of switches having the smallest number of switches between them and the input voltage terminal). For example, when R is equal to 3, SW(3, F-1), SW(3, F-2), and SW(3, F-3) are always off in state 0 and state 1.

Further, when R is odd, the control module turns off the upper switch SW(3, F) in the third switch sub-matrix, and the upper switch SW(1, E) in the first switch sub-matrix is turned off. It is configured to operate the upper switch SW(1, E) in the first switch sub-matrix as if it is the upper switch of the three switch sub-matrix.

In some embodiments, when R is even, the control module turns off the upper switch SW (1, E) in the first switch sub-matrix, and the upper switch SW (3, in the third switch sub-matrix). It is configured to operate the upper switches SW (3, F) in the third switch sub-matrix as if F) is the upper switch of the first switch sub-matrix.

In some embodiments, the state of the upper switch is reversed compared to the uppermost switch in the third switch matrix that is not always off. For example, if R is equal to 3, because R is odd, SW(3, F) is turned off. In addition, SW(3, F-1), SW(3, F-2), and SW(3, F-3) are always off. Accordingly, the upper switches SW(1, E) are in an inverted state compared to the upper switch SW(3, F-4) in the third switch matrix which is not always off.

In some embodiments, the reconfigurable Dickson Star SC regulator can be operated as part of the voltage regulator system. The voltage regulator system can operate in multiple interleaved phases (eg, in a time-interleaved manner over a single period), and the reconfigurable Dixon Star SC regulator provides the output voltage in one of the interleaved phases. Can be used to For example, the voltage regulator system may include three reconfigurable Dixon Star SC regulators, each operating out of phase with 0 degrees, 120 degrees, and 240 degrees.

In some embodiments, the reconfigurable Dixon Star SC regulator can be used in a variety of applications including power management integrated circuits (PMICs), battery chargers, LED drivers, envelope tracking power amplifiers. have.

In some embodiments, the capacitances of the switching capacitors (e.g., C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802) are set to be proportional to the output current of the reconfigurable Dixon Star SC regulator. Can. For example, the capacitance of the switching capacitor can be in the range of 0.1nF/mA and 100nF/mA depending on the target power efficiency. The reconfigurable Dickson Star SC regulator can improve its efficiency by using larger capacitance values in some embodiments.

In some embodiments, the reconfigurable Dixon Star SC regulator can be operated in a reverse configuration (eg, the input node and the output node of the reconfigurable Dixon Star SC regulator are switched). The direction of operation of the reconfigurable Dixon Star SC regulator can be flexibly modified to accommodate various types of input voltage sources and output loads coupled to the input node and output node of the reconfigurable Dixon Star SC regulator.

In some embodiments, the reconfigurable Dickson Star SC regulator can be operated in the reverse direction to operate it as a step-up regulator. For example, the input node of the reconfigurable Dixon Star SC regulator can be coupled to a target load (e.g., chip) and the output node of the reconfigurable Dixon Star SC regulator is connected to the input voltage source (e.g., battery). Can be coupled.

22-24 illustrate step-up reconfigurable Dickson Star SC regulators 2200, 2300, and 2400, respectively, in accordance with some embodiments. The regulator 2200 is a step-up reconfigurable 1:3 Dickson Star SC regulator; The regulator 2300 is a step-up reconfigurable 1:4 Dickson Star SC regulator; The regulator 2400 is a step-up reconfigurable 1:4 Dickson Star SC regulator. It can be a step-up reconstruction of 22 to 24 Dickson star SC regulators except that is, V _IN (202) and turns V _IN (202) the location of the V _OUT (208) is lower than V _OUT (208) , Similar to the step-down regulators of FIGS. 6, 10, and 16, respectively.

In some embodiments, the reconfigurable Dickson Star SC regulator can be operated in the reverse direction to operate as a battery charger. For example, the input node of the reconfigurable Dixon Star SC regulator can be coupled to the power line of a power source, for example, a Universal Serial Bus (USB), and the output of the Reconfigurable Dixon Star SC regulator The node can be coupled to the battery such that the output voltage and output current of the reconfigurable Dickson Star SC regulator are used to charge the battery.

In some embodiments, a reconfigurable Dickson Star SC regulator can be particularly useful for charging batteries in a handheld device. Handheld devices such as smartphones provide a voltage output within the range of approximately 2.8 to 4.3V depending on whether the battery is charged or not (e.g. 4.3V when fully charged, 2.8V when fully discharged). It is possible to use a lithium ion (Li-ion) battery. Li-ion batteries in handheld devices can be charged using a universal serial bus (USB). The current version of the USB power line uses 5V higher than the voltage output of the Li-ion battery (and future versions of USB may use much higher voltages). Accordingly, the voltage from the USB power line must be stepped down before it can be used to charge a Li-ion battery. To this end, the reconfigurable Dickson Star SC regulator receives the power line voltage (and current) from the USB and provides a step-down version of the power line voltage (and current) to the Li-ion battery so that the Li-ion battery has voltage and current from the USB. It can be configured to be charged based on.

In some embodiments, the configuration identified above where the battery is charged using a USB power line can be used in reverse with USB On-The-Go (OTG), where the battery in the first device Can charge the second device by transferring power to the second device via USB. In this scenario, the battery at the first device is configured to deliver current through the USB to the battery at the second device. Although the output voltage of the battery in the first device may be lower than the USB power line voltage, the reconfigurable Dickson Star SC regulator can operate in a step-up configuration to step up the output voltage of the battery to the output voltage of the USB power line. have. In this way, the battery in the first device can charge the battery in the second device through the USB power line.

In some embodiments, an SC regulator, such as a reconfigurable Dixon Star SC regulator, can be operated in conjunction with other voltage regulators to provide two-stage voltage regulation. 25 illustrates a two-stage voltage regulation system in which the SC regulator provides first stage voltage regulation according to some embodiments. 25 includes a regulator 2502 and a second stage voltage regulator 2504. SC regulator 2502 may be any type of SC regulator, including, for example, one of the reconfigurable Dixon Star SC regulators disclosed herein. In some embodiments, the second stage voltage regulator 2504 can include one or more of a buck regulator, an SC regulator, a linear regulator, and/or any type of voltage regulators capable of providing voltage regulation. .

In some embodiments, the SC regulator 2502 provides an output voltage at which the SC regulator 2502 can provide high efficiency, followed by the output of the SC regulator 2502 using the second stage regulator 2504. It can be operated to regulate the voltage.

For example, the reconfigurable Dixon Star SC regulator 2502 is the input voltage 202, V _TMP 2506, which is the fraction of the input voltage 202 that the reconfigurable Dixon Star SC regulator 2502 can provide with high efficiency. ). For example, V _TMP 2506 can be V _IN /N, where N is the step down ratio. Thereafter, the second stage voltage regulator 2504 can receive the V _TMP 2506 and regulate it to provide it to V _OUT 208.

26A illustrates the embodiment of FIG. 25 where the second stage regulator is a buck converter 100 in accordance with some embodiments. Here, V _TMP 2506 is regulated by buck converter 100 in fine steps using multiple power switches 114, 116 and one or more inductors 108. 26B illustrates the timing diagram of signals in the regulator.

The two-stage regulator illustrated in FIGS. 25 and 26, also referred to as a hybrid regulator, is excellent for SC regulators to divide voltages over predetermined fraction values and second stage regulators such as buck regulators are fine steps. It depends on the fact that it can be good at regulating over a wide range of output voltages. For example, in a 12V-1V (12V-to-1V) step-down regulator, the reconfigurable Dickson Star SC regulator 2502 receives 12V at V _IN 202 and provides 1/6 step-down, V _TMP At 2506, 2V can be provided. Subsequently, the buck regulator 100 may provide a subsequent regulation for regulating 2V to 1V. This two-stage regulator reduces the voltage swing at the internal node Vx of the buck regulator 100 to V _TMP 2506, which can be substantially smaller than V _IN 202, so this topology is junction 122 ), it is possible to reduce the capacitive power loss in the buck regulator 100 due to parasitic capacitance.

27 illustrates a two-stage voltage regulation system in which the SC regulator provides second stage voltage regulation according to some embodiments. 27 includes a first stage voltage regulator 2702 and an SC regulator 2704. SC regulator 2704 may be any type of SC regulator, including, for example, one of the reconfigurable Dixon Star SC regulators disclosed herein. In some embodiments, the first stage voltage regulator 2702 can include one or more of a buck regulator, an SC regulator, a linear regulator, and/or any type of voltage regulators capable of providing voltage regulation. .

In FIG. 27, the first stage regulator 2702 receives the input voltage V _IN 202 and provides an output V _TMP 2706 to the SC regulator 2704. The SC regulator 2704 can subsequently step down V _TMP 2706 to the desired output voltage 208.

When the first stage regulator 2702 is a switched inductor regulator, the two-stage voltage regulation system of FIG. 27 operates the switched inductor regulator at a high switching frequency and with a small amount of current flow through the inductor to inductor resistive loss of the switched inductor regulator. Can be reduced. This approach can reduce the resistive loss of a switched inductor regulator even with a small inductor with low inductance. In addition, this topology can also reduce the capacitive loss (CV ² f loss) of the switched inductor regulator by limiting the voltage swing across the switches.

In some embodiments, the first stage regulator 2702 can include only an inductor. 28A illustrates a two-stage voltage regulator in which the first stage regulator is made of an inductor in accordance with some embodiments. 28B illustrates a timing diagram of signals in the two-stage voltage regulator of FIG. 28A in accordance with some embodiments. Here, the first stage regulator is a single inductor 2802. One terminal of the inductor 2802 is coupled to the input voltage V _IN 202, and the other terminal of the inductor 2802 is coupled to the input of the SC regulator 2704. The input voltage to SC regulator 2704 is referred to as V _TMP 2706.

In some embodiments, the input voltage V _TMP 2706 of the SC regulator 2704 is connected to one of the plates of the switching capacitor C _FLY 2804 at the SC regulator 2704. As SC regulator 2704 switches between state 0 and state 1 (see, eg, FIGS. 3A and 3B), voltage potential V _TMP 2706 on the top plate of switching capacitor C _FLY 2804 is two The voltage is switched between V ₁ and V ₂ . Based on this operation, the following relationship can be derived:

V _IN (202) = V ₁ D + V ₂ (1-D)

The values of V ₁ and V ₂ are set by the conversion ratio of V _OUT 208 and SC regulator 2704. As a result, the conversion ratio between V _IN 202 and V _OUT 208 can be finely controlled based on the conversion ratio of duty cycle D and SC regulator 2704. The advantage of the two-stage regulator of Fig. 28 is that the single-stage SC regulator 2704, which can only provide integer-ratio conversion modes, by simply adding a single inductor 2802, provides non-integer-ratio conversion modes. It can be converted into a possible two-stage regulator.

In some embodiments, the two-stage regulator may have a bypass switch SWI 2806 configured to short circuit the inductor 2802 at the first stage regulator. Bypass switch SWI 2806 causes the first stage regulator to turn off when its operation is not required.

29A and 29B are two stages of FIG. 28 where the SC regulator 2704 is a 4:1 Dixon Star Switched Capacitor (SC) regulator 800 (such as the regulator 800 of FIG. 8) according to some embodiments. Illustrates the operation of the regulator.

In some embodiments, the second stage 4:1 regulator 800 is duty cycled between state 0 and state 1 to provide voltage regulation, as also illustrated in FIGS. 9A and 9B. Assuming that the switching capacitors C1 _FLY 204, C2 _FLY 206, and C3 _FLY 802 and the decoupling capacitor C _OUT 214 are large, the following relationships can be derived for the two states:

State 0: V _TMP (2706) = V _C3FLY + V _OUT (208)

State 0: V _C2FLY = V _C1FLY + V _OUT (208)

State 1: V _OUT (208) = V _C1FLY

State 1: V _C3FLY = V _OUT (208) + V _C2FLY

Where V _C1FLY is the voltage across the first switching capacitor C1 _FLY 204, V _C2FLY is the voltage across the second switching capacitor C2 _FLY 206, and V _C3FLY is the voltage across the third switching capacitor C3 _FLY 802 to be. These relationships can be reconstructed as follows:

V _C2FLY = 2 x V _OUT

V _C3FLY = 3 x V _OUT

V _OUT = (1/4) x V _TMP

Accordingly, the second stage SC regulator operates as a 4:1 step-down regulator, and V _TMP 2706 swings from 3 x V _OUT to 4 x V _OUT in state 0 and state 1. The voltage swing of V _TMP 2706 as well as the duty cycling of the second stage regulator is illustrated in FIG. 30.

Since V _TMP 2706 swings from 3 x V _OUT to 4 x V _OUT , this voltage swing is regulated by inductor 2802 to provide the following relationship:

V _IN (202) = (3 x V _OUT )D + (4 x V _OUT )(1-D) = (4-D) x V _OUT

Where D is a value from 0 to 1, and preferably from 0.25 to 0.75. In other words, the two-stage regulator of Fig. 29 enables the following voltage relationship:

V _OUT = (1/(4-D)) V _IN

Accordingly, the voltage regulator control system can control the duty cycle D from 0 to 1 to fine tune the relationship between V _IN 202 and V _OUT 208 beyond integer conversion ratios. In a sense, the first stage regulator and the second stage regulator of Fig. 28 have the same duty cycle D.

31 illustrates a two-stage voltage regulation system in which the second stage regulator is a multiphase voltage regulator in accordance with some embodiments. The multiphase voltage regulator in the second stage regulator allows the first stage regulator and the second stage regulator to use independent duty cycles. This may be advantageous in some cases because the efficiency of the SC regulator may degrade when the duty cycle of the SC regulator deviates from 0.5. By having the first stage regulator and the second stage regulator have independent duty cycles, the second stage regulator can be operated at a high efficiency level (for example, close to a duty cycle of 0.5) regardless of the desired output voltage of the voltage regulation system. Can.

As shown in FIG. 31, in some embodiments, the second stage SC regulator has two 4:1 SC regulator modules SC_ph0 (3102) and SC_ph1 (3104 ), where SC_ph0 (3102) and SC_ph1 (3104) ) Works with their own phases. In some embodiments, the two SC regulator modules may phase out 180 degrees. The phase relationship between SC_ph0 3102 and SC_ph1 3104 according to some embodiments is illustrated in FIG. 32. In FIG. 32, two 4:1 SC regulator modules operate at a duty cycle of 0.5, thereby achieving high efficiency.

While the two 4:1 SC regulator modules operate at a duty cycle of 0.5, the duty cycle of the switched inductor regulator in the first stage regulator can be controlled independently. In particular, the switched inductor regulator switches its own duty cycle D by switching the switches SW9 804 and SW17 3126 out of phase at duty cycle D, regardless of the duty cycle of the two 4:1 SC regulator modules. Can have

For example, when modules SC_ph0 3102 and SC_ph1 3104 on both sides operate at a duty cycle of 0.5, C3 _FLY 802 and C6 _FLY 3110, as illustrated in the waveforms of FIG. The voltages V1 (3130) and V2 (3132) at the top plate of the swing from 3 x V _OUT 208 to 4 x V _OUT 208 at a duty cycle of 0.5. The voltages V1 (3130) and V2 (3132) at the top plates of C3 _FLY 802 and C6 _FLY 3110 swing from 3 x V _OUT 208 to 4 x V _OUT 208 at any given time. As shown in FIG. 32, switches SW9 804 and SW17 3126 either set V _TMP 2706 at duty cycle D to either 3 x V _OUT 208 or 4 x V _OUT 208. It can be turned on and off (in different phases) in duty cycle D to connect to one. This allows the first stage regulator to operate at duty cycle D, while the second stage regulator (including two 4:1 SC regulator modules SC_ph0 3102 and SC_ph1 3104) operates at a duty cycle of 0.5. , It improves the operation efficiency of the second stage regulator.

When the switches SW9 804 and SW17 3126 are duty cycled in the duty cycle of D, the amount of time that one particular SC module is used may depend on the duty cycle D. For example, in FIG. 32, the duty cycle D is less than 0.5. Accordingly, the first SC module 3102 is used less than 50% of the time while the second SC module 3104 is used more than 50% of the time. In the extreme case, one SC module can use 100% of the time while the other SC module uses 0% of the time. To accommodate these extreme scenarios-all other switches and capacitors in the two SC modules 3102, 3104 are sufficient to allow a single SC module to deliver the maximum required output power-just as no other SC module exists. It may need to be largely sized.

In some embodiments, switches SW9 804 and SW17 3126 are controlled to maintain the duty cycle of the first stage regulator while each switch SW9 804 and SW17 3126 is turned on for the same amount of time. Can be. In this way, the SC modules in the multiphase regulator (second stage regulator) use the same amount of time regardless of the duty cycle of the first stage regulator. This allows switches and capacitors in SC modules to be about half the size, compared to the scenario where a single SC module needs to be able to deliver the maximum required output power.

33 illustrates a control sequence of switches that cause each switch SW9 804 and SW17 3126 to turn on for the same amount of time while maintaining the duty cycle of the first stage regulator in accordance with some embodiments. In a given period, the first switch SW9 804 keeps the second switch SW17 3126 turned off while 50% of the time is turned on, and the second switch SW17 3126 turns on 50% of the time. The first switch SW9 804 is kept turned off during the period. However, the time instance at which the period begins is determined to cause the voltage V _TMP 2706 to swing between 3 x V _OUT to 4 x V _OUT at duty cycle D.

For example, when SW9 804 is turned on and SW17 is turned off, voltage V _TMP 2706 is coupled to V1 3130, when SW9 804 is turned off and SW17 is turned on, voltage V _TMP 2706 is coupled to V2 3132. Accordingly, by shifting the time instance 3302, the duty cycle D where V _TMP 2706 is at 4 x V _OUT can be controlled. For example, when time instance 3302 is shifted to the right, duty cycle D will increase proportionally; When time instance 3302 is shifted to the left, duty cycle D will decrease proportionally. One additional benefit of this configuration is that V _TMP 2706 switches to twice the frequency of the switched inductor and switched capacitor regulators. This feature may enable the use of a smaller inductor 3302 without incurring additional switching losses.

The second stage regulator has been illustrated using a reconfigurable Dickson star regulator, but other types of SC regulators can also be used in the second stage regulators of FIGS. 27-29 and 31. For example, the second stage regulator can include a ladder SC regulator, a reconfigurable ladder SC regulator, a series-parallel SC regulator, a reconfigurable series-parallel regulator, and/or any other types of SC regulators.

In some embodiments, a two-stage regulator can be used in a variety of applications including power management integrated circuits (PMICs), battery chargers, LED drivers, envelope tracking power amplifiers.

In some embodiments, the capacitance of the switched capacitor regulator can be set to be proportional to the output current of the two-stage regulator. For example, the capacitance of a switched capacitor regulator can be in the range of 0.1nF/mA and 100nF/mA depending on the target power efficiency. A two-stage regulator can improve its efficiency by using larger capacitance values.

In some embodiments, the two-stage regulator can be operated in the reverse direction to operate as a step-up regulator. For example, the input node of a two-stage regulator can be coupled to a target load (e.g., a chip) and the output node of a two-stage regulator can be coupled to an input voltage source (e.g., a battery). have.

In some embodiments, the two-stage regulator can be operated in the reverse direction to operate as a battery charger. For example, the input node of a two-stage regulator can be coupled to a power source (eg, a power line of a universal serial bus (USB)) and the output node of a two-stage regulator can be coupled to a battery. .

Various embodiments of the disclosed two-stage regulator can be used as a battery charger in a battery operated device. For example, the output node of a two-stage regulator can be coupled to a battery, so that the output voltage and output current of a two-stage regulator are used to charge the battery.

A two-stage regulator can be particularly useful for charging batteries in handheld devices. Handheld devices such as smartphones provide a voltage output within the range of approximately 2.8 to 4.3V depending on whether the battery is charged or not (e.g. 4.3V when fully charged, 2.8V when fully discharged). It is possible to use a lithium ion (Li-ion) battery. Li-ion batteries in handheld devices can be charged using a universal serial bus (USB). The current version of the USB power line uses 5V higher than the voltage output of the Li-ion battery (and future versions of USB may use much higher voltages). Accordingly, the voltage from the USB power line must be stepped down before it can be used to charge a Li-ion battery. To this end, a two-stage regulator receives the power line voltage and current from the USB and provides a step-down version of the power line voltage and current to the Li-ion battery so that the Li-ion battery can be charged based on the voltage and current from the USB. Can be configured.

In some embodiments, the above-identified configuration in which the battery is charged using a USB power line can be used inversely with USB on the go (OTG), where the battery in the first device is powered by USB. The second device can be charged by transferring it to the two devices. In this scenario, the battery at the first device is configured to deliver current through the USB to the battery at the second device. Although the output voltage of the battery in the first device may be lower than the USB power line voltage, the two-stage regulator can operate in a step-up configuration to step up the output voltage of the battery to the output voltage of the USB power line. In this way, the battery in the first device can charge the battery in the second device through the USB power line.

34 is a block diagram of a computing device including a voltage regulation system in accordance with some embodiments. Computing device 3400 includes processor 3402, memory 3404, one or more interfaces 3406, accelerator 3408, and voltage regulator system 3410. Computing device 3400 may include additional modules, fewer modules, or any other suitable combination of modules that perform any suitable operation or combination of operations.

In some embodiments, the accelerator 3408 can be implemented in hardware using an application specific integrated circuit (ASIC). The accelerator 3408 can be part of a system on a chip (SOC). In other embodiments, the accelerator 3408 is a logic circuit, a programmable logic array (PLA), a digital signal processor (DSP), a field programmable gate array (FPGA), or any other integrated circuit can be implemented in hardware. In some cases, the accelerator 3408 can be packaged in the same package as other integrated circuits.

In some embodiments, voltage regulator system 3410 may be configured to provide a supply voltage to one or more of processor 3402, memory 3404, and/or accelerator 3408. The voltage regulator system 3410 may include one or more voltage regulator (VR) modules 3412-1 ... 3412-N. In some embodiments, the one or more VR modules 3412-1 ... 3412-N may be a reconfigurable Dickson Star SC regulator, as disclosed, for example, in FIGS. 4, 10, and 16. have. In some embodiments, the one or more VR modules 3412-1 ... 3412-N may be a two-stage regulator, as disclosed, for example, in FIGS. 27-29, 31. The one or more VR modules 3412-1 ... 3412-N may operate in multiple interleaved phases.

In some embodiments, the voltage regulator system 3410 may include a switch control module configured to control the switch configuration in one or more VR modules 3412-1 ... 3412-N. For example, when the switch control module receives a command to operate a 3:1 reconfigurable Dixon Star SC regulator, as shown in FIGS. 5A-5C, in 3:1 conversion mode, the switch control module It can be configured to control the switches 216, 218, 220, 222, 224, 226, and 228 and the mode switch SW8 402 to operate the reconfigurable Dixon Star SC regulator in 3:1 conversion mode. As another example, when the switch control module receives a command to operate a 3:1 reconfigurable Dixon Star SC regulator, as shown in FIGS. 6A-6C, in 2:1 conversion mode, the switch control module It can be configured to control the switches 216, 218, 220, 222, 224, 226, and 228 and the mode switch SW8 402 to operate the reconfigurable Dixon Star SC regulator in a 2:1 conversion mode. In some embodiments, the switch control module can be synthesized using hardware programming languages. Hardware programming languages can include Verilog, VHDL, Bluespec, or any other suitable hardware programming language. In other embodiments, the switch control module can be designed manually and can be manually laid out on a chip.

Computing device 3400 may communicate with other computing devices (not shown) through interface 3406. The interface 3406 can be implemented in hardware to transmit and receive signals in various media such as optical, copper, and wireless, and in a number of different protocols, some of which may be non-transitory.

In some embodiments, computing device 3400 may include user equipment. The user equipment can communicate with one or more wireless access networks and wired communication networks. The user equipment can be a cellular phone with telephony capabilities. The user equipment may also be a smart phone that provides services such as word processing, web browsing, gaming, e-book capabilities, operating system, and full keyboard. The user equipment can also be a tablet computer that provides network access and most of the services provided by a smart phone. User equipment includes Symbian OS, iPhone OS, RIM's Blackberry, Windows Mobile, Linux, Linux, HP WebOS, Tizen, and Android. Operating system, or any other suitable operating system. The screen may be a touch screen used to input data to the mobile device, in which case the screen may be used instead of a full keyboard. User equipment may also maintain global positioning coordinates, profile information, or other location information. The user equipment may also be a wearable electronic device.

Computing device 3400 may also include any platforms capable of computations and communication. Non-limiting examples are televisions (TVs), video projectors, set-top boxes or set-top units, digital video recorders (DVR), computers, netbooks, laptops, and any other audio/s with computational capabilities. Includes visual equipment. Computing device 3400 may be comprised of one or more processors that process instructions and execute software that may be stored in memory. The processor also interfaces to communicate with memory and other devices. The processor can be any applicable processor, such as a system on a chip that combines a CPU, application processor, and flash memory. Computing device 3400 may also provide various user interfaces such as a keyboard, touch screen, trackball, touch pad, and/or mouse. Computing device 3400 may also include speakers and display device in some embodiments. Computing device 3400 may also include a biomedical electronic device.

36A-36C, a hybrid converter 3600 incorporating a 2:1 SC regulator and an inductor is shown, according to some embodiments. As illustrated in FIG. 36A, converter 3600 may include inductor 3602, capacitors 3604 and 3606, and switches 3608, 3610, 3612, 3614, and 3616. Also shown in FIG. 36A, a load 3618 illustrated as a current can be coupled to the output of converter 3600.

The inductor 3602 can be any suitable inductor formed using any suitable technique and having any suitable size in some embodiments. For example, in some embodiments, inductor 3602 may be a separate inductor formed from a winding having a size of 2 x 1.2 mm in some embodiments.

Capacitors 3604 and 3606 may be any suitable capacitors formed using any suitable technology or techniques and having any suitable size or sizes in some embodiments. For example, in some embodiments, these capacitors (and all other capacitors described herein) are on-chip capacitors, such as metal-on-metal (MoM) ) Capacitors, metal-insulator-metal (MiM) capacitors, MOSFET capacitors (capacitors that use the gate oxide capacitance of the MOSFET), Multi-Layer Ceramic Capacitors ( MLCC), tantalum capacitors, aluminum electrolytic capacitors, or individual capacitors implemented on a chip or circuit board, such as film capacitors, or any other suitable capacitors. As another example, capacitors 3604 and 3606, in some embodiments, may have sizes of 2 x 1.2 mm and 1.6 x 1 mm, respectively.

The switches 3608, 3610, 3612, 3614, and 3616 can be any suitable switches formed using any suitable technique in some embodiments. For example, in some embodiments, switches may be formed from transistors, such as MOSFET transistors. More specifically, for example, in some embodiments, some of the switches can be implemented using a P-channel MOSFET transistor, and other switches of the switches can be implemented using N-channel MOSFET transistors. have. In some embodiments, transistors can be sized to maximize efficiency. For example, larger transistors add switching losses, while smaller transistors add conduction losses. Accordingly, in some embodiments, sizes may be selected according to a specific application to maximize efficiency.

The load 3618 can be any suitable load. For example, in some embodiments, load 3618 may be a battery for a mobile device.

Converter 3600 includes two operational "modes": 2:1 SC mode using 2:1 switched capacitor (SC) portion 3620; And a hybrid 2:1 (H21) mode using inductor 1602 and switch 3610 with a 2:1 SC portion. This converter uses a controller (not shown) to connect to a wall adapter (or other power supply) and by adjusting the output of the wall adapter (or other power supply) providing the input voltage (V _IN ) using a controller. Very high efficiencies can be achieved in 2:1 SC mode (where the converter's input voltage (V _IN ) and output voltage (V _OUT ) maintain a 2:1 ratio). However, there are legacy wall adapters (and other power supplies) that cannot continuously adjust the output voltage to maintain a 2:1 ratio. For example, many wall adapters have a fixed 5V output. Since the output of the converter 3600 may also be directly connected to a battery that may have a voltage of 3V to 4.5V, the converter's input to output voltage ratio, when connected to 5V V _IN , rather than the desired 2:1, 5 :3 (or ~1.66:1) to 5:4.5 (or ~1.11:1). To resolve the mismatch, the converter can operate in H21 mode, which can support any ratio of 1:1 to 2:1 in some embodiments.

2: 1 using the SC mode and the H21 mode, hybrid converter adapter is its continuously adjusts the output voltage to 2 connected to the V _IN: when to maintain 1 V _IN for V _OUT ratio (standalone 2:01 High efficiency can be maintained in 2:1 SC mode (similar to SC charger) and higher efficiency can be achieved than buck charger when ~2:1 V _IN to V _OUT ratio cannot be maintained by going to H21 mode . Compared to using a 2:1 SC charger and an independent buck charger in parallel, the hybrid converter also reduces solution size and cost by reusing multiple switches in 2:1 SC mode and H21 mode.

36A and 36B illustrate a hybrid converter 3600 when in H21 mode and in state 0 and state 1 respectively. 36C illustrates how V _X 102 changes as the converter changes between state 0 and state 1. By adjusting the duty cycle (how much time is spent in State 0 to State 1), the hybrid converter can adjust the input voltage to output voltage ratio. The following equation sets the duty cycle (D) of the regulator based on the required input and output voltages:

D = T ₀ / (T ₀ +T ₁ )

(Average of V _X (102)) = V _IN (this is because the average voltage for the two nodes V _IN and V _X of the inductor needs to be the same at steady state)

(Average of V _X (102)) = 2*V _OUT *D + V _OUT *(1-D) (based on Figure 36b)

2*V_OUT*D + V_OUT*(1-D) = V_IN

2*V _OUT *D + V _OUT *(1-D) = V _IN

V_OUT*D + V_OUT = V_IN

V _OUT *D + V _OUT = V _IN

V_OUT(1+D) = V_IN

V _OUT (1+D) = V _IN

D = V_IN/V_OUT - 1

D = V _IN /V _OUT -1

37A-37C illustrate the hybrid converter 3600 when in 2:1 SC mode and in state 0 (FIG. 37A) and state 1 (FIG. 37B). As shown in these figures, the inductor is not used because the switch 3610 is open in both state 0 and state 1 when in 2:1 SC mode.

When the hybrid converter 3600 is operating in the H21 mode (as shown in Figs. 36A to 36C), the duty cycles of both the SC portion of the hybrid regulator and the inductor portion of the regulator need to be the same. The problem with this setup is that the SC portion may be most efficient, for example, at 50% duty cycle, but it will be forced to operate at, for example, 10% duty cycle due to the required input voltage to output voltage ratio. It may be.

To overcome this, in some embodiments, the duty cycle of the SC portion and the inductor can be accomplished independently using a two-phase hybrid converter 3800 as illustrated in FIGS. 38A and 38B and FIGS. 39A-39E. have. For example, in some embodiments, the inductor duty cycle can be set according to the required input and output voltage values (according to the equations above), while the SC partial duty cycle (often 50% duty cycle) is the maximum It can be set to achieve efficiency.

38A and 38B and similar components of converter 3800 of FIGS. 39A-39E may be the same as the similar components described in connection with FIGS. 36A and 36B above in some embodiments.

38A and 38B illustrate a two-phase hybrid converter 3800 when configured to operate in a 2:1 SC mode. As shown, in this mode, the switches 310 and 320 are: state 0, SC_ph0; State 0, SC_ph1; State 1, SC_ph0; And because it is open in state 1, SC_ph1, the inductor is not used. Thus, in this mode, the converter 3800 operates as a two-phase 2:1 SC regulator. That is, the switches are opened and closed in four state and phase combinations shown in FIGS. 38A and 38B. In some embodiments, states may have any suitable duty cycle, such as 50%. The switches in the phase 1 portion of the converter 3800 may switch at any suitable point in relation to the switches in the phase 0 portion of the converter 3800 in some embodiments. For example, switches in the phase 1 portion of the converter 3800 may be switched out of phase by 180 degrees from switches in the phase 0 portion of the converter 3800 in some embodiments.

39A-39E illustrate the hybrid converter 3800 when configured to operate in H21 mode. 39A-39D, the switches SW1 310 and SW6 320 are inductor switches, while the switches SW2 312, SW3 314, SW4 316, SW5 318, SW7 322 , SW8 324, SW9 326, and SW10 328 are SC switches. During operation of converter 3800 in H21 mode, both sides of the inductor switches and SC switches have two different states, which are repeated between these two states. The two states of the inductor switches are referred to herein as L_state0 and L_state1, and the two states of SC switches are referred to herein as SC_state0 and SC_state1. For example, the following can be a switch configuration for each of these four states:

L_state0: SW1 on, SW6 off

L_state1: SW1 off, SW6 on

SC_state0: (SW4, SW8, SW10) on, (SW3, SW5, SW9) off

SC_state1: (SW4, SW8, SW10) off, (SW3, SW5, SW9) on

SW2 and SW7 are always off. How much time is spent in L_state0 vs. L_state1 determines the inductor duty cycle. How much is consumed in SC_state0 vs. SC_state1 determines the SC duty cycle. In some embodiments, the inductor switches can be repeated between L_state0 and L_state1 in one duty cycle, and the SC switches can be repeated between SC_state0 and SC_state1 in different duty cycles.

39E shows a timing diagram that allows the hybrid converter 3800 to repeat between states 0 to 3 in some embodiments. Each of these states works as follows:

State 0: L_state0, SC_state0

State 1: L_state1, SC_state0

State 2: L_state1, SC_state1

State 3: L_state0, SC_state1

In this particular example as shown in Figure 39E, the duty cycle of the SC portion is fixed at 50%, but this can be any suitable value, and the duty cycle of the inductor switches is D. The inductor switches can adjust D independently of the duty cycle of the SC portion by adjusting the time spent in each of the states 0 to 3. If the efficiency of the SC portion is maximized at 50% duty cycle, the SC duty cycle can be fixed at 50%, while the inductor duty cycle D can be adjusted to support various input to output voltage ratios.

In some cases, certain switches can be removed to reduce the area allocated to transistors instead of limited operating modes. For example, if the converter only works on H21 and it is okay to disable the 2:1 SC mode, the switch 3608 in FIG. 36A and SW2 312 and SW7 322 in FIGS. 39A-39D will be removed. Can.

The switches of FIGS. 36A, 36B, 37A, 37B, 38A, 38B, and 39A-39D can be controlled by any suitable controller. For example, when these switches are implemented as MOSFETs, these switches can be controlled by a controller that applies an appropriate voltage to the gates of the MOSFETs such that an open or closed connection is provided between the sources and drains of the MOSFETs. have. The controller can be any suitable device or circuit. For example, the controller can be a hardware processor that executes software loaded from memory to a hardware processor. As another example, the controller can be dedicated logic circuits, field programmable gate arrays, and/or any other suitable device or circuit for providing suitable control signals.

It should be understood that the disclosed claims are not limited to the arrangements of components presented in the following description or illustrated in the drawings, and to the details of the configuration, whose application is not limited. The disclosed claims are capable of other embodiments and of being practiced and carried out in various ways. Also, it should be understood that the phraseology and terminology employed herein is for the purpose of description and should not be regarded as limiting.

As such, those skilled in the art can readily use the concepts upon which the present disclosure is based, as a basis for the design of other structures, devices, systems, and methods for performing various purposes of the disclosed claims. You will recognize that it may be. Accordingly, it is important that the claims be considered to include such equivalent arrangements, as long as they do not depart from the spirit and scope of the disclosed claims.

Although the disclosed claims have been described and illustrated in the exemplary embodiments described above, the present disclosure has been made by way of example only, and numerous changes in the details of implementation of the disclosed claims are limited only by the following claims, It is understood that it may be made without departing from the spirit and scope of the disclosed claims.

Claims (9)

As a circuit,
An inductor having a first surface and a second surface, wherein the first surface is connected to an input voltage;
A first switch having a first side and a second side, the first side being connected to the second side of the inductor;
A second switch having a first surface and a second surface, wherein the first surface is connected to the input voltage;
A first capacitor having a first surface and a second surface, wherein the first surface is connected to the second surface of the second switch;
A third switch having a first surface and a second surface, wherein the first surface is connected to the second surface of the first switch;
A fourth switch having a first surface and a second surface, the first surface being connected to the second surface of the third switch;
A fifth switch having a first side and a second side-the first side is connected to the second side of the first capacitor and to the second side of the fourth switch, the second side is coupled to a voltage source -; And
A second capacitor having a first side and a second side, wherein the first side is connected to the first side of the fourth switch, and the second side is connected to the second side of the fifth switch-
Including, circuit. According to claim 1,
The at least one of the first switch, the second switch, the third switch, the fourth switch, and the fifth switch is a circuit. According to claim 2,
And at least one of the first switch, the second switch, the third switch, the fourth switch, and the fifth switch is a MOSFET. According to claim 2,
Wherein at least one of the first switch, the second switch, the third switch, the fourth switch, and the fifth switch is controlled by a controller. According to claim 1,
When the circuit is in the first state,
The first switch is closed;
The second switch is opened;
The third switch is opened;
The fourth switch is closed;
The fifth switch is opened;
When the circuit is in the second state,
The first switch is closed;
The second switch is opened;
The third switch is closed;
The fourth switch is opened;
Wherein the fifth switch is closed. The method of claim 5,
When the circuit is in the third state,
The first switch is opened;
The second switch is closed;
The third switch is opened;
The fourth switch is closed;
The fifth switch is opened;
When the circuit is in the fourth state,
The first switch is opened;
The second switch is opened;
The third switch is closed;
The fourth switch is opened;
Wherein the fifth switch is closed. According to claim 1,
A sixth switch having a first surface and a second surface, the first surface being connected to the second surface of the inductor;
A seventh switch having a first surface and a second surface, wherein the first surface is connected to the input voltage;
A third capacitor having a first side and a second side, the first side being connected to the second side of the seventh switch;
An eighth switch having a first surface and a second surface, wherein the first surface is connected to the second surface of the sixth switch;
A ninth switch having a first surface and a second surface, the first surface being connected to the second surface of the eighth switch; And
Tenth switch having a first side and a second side-the first side is connected to the second side of the third capacitor and to the second side of the ninth switch, the second side is coupled to the voltage source Ringed-
The circuit further comprising. The method of claim 7,
When the circuit is in the first state,
The first switch is opened;
The second switch is closed;
The third switch is opened;
The fourth switch is closed;
The fifth switch is opened;
The sixth switch is opened;
The seventh switch is opened;
The eighth switch is closed;
The ninth switch is opened;
The tenth switch is closed;
When the circuit is in the second state,
The first switch is opened;
The second switch is opened;
The third switch is closed;
The fourth switch is opened;
The fifth switch is closed;
The sixth switch is opened;
The seventh switch is closed;
The eighth switch is opened;
The ninth switch is closed;
Wherein the tenth switch is open. The method of claim 8,
When the circuit is in the third state,
The first switch is closed;
The second switch is opened;
The third switch is opened;
The fourth switch is closed;
The fifth switch is opened;
The sixth switch is opened;
The seventh switch is opened;
The eighth switch is closed;
The ninth switch is opened;
The tenth switch is closed;
When the circuit is in the fourth state,
The first switch is opened;
The second switch is opened;
The third switch is opened;
The fourth switch is closed;
The fifth switch is opened;
The sixth switch is closed;
The seventh switch is opened;
The eighth switch is closed;
The ninth switch is opened;
The tenth switch is closed;
When the circuit is in the fifth state,
The first switch is opened;
The second switch is opened;
The third switch is closed;
The fourth switch is opened;
The fifth switch is closed;
The sixth switch is closed;
The seventh switch is opened;
The eighth switch is opened;
The ninth switch is closed;
The tenth switch is opened;
When the circuit is in the sixth state,
The first switch is closed;
The second switch is opened;
The third switch is closed;
The fourth switch is opened;
The fifth switch is closed;
The sixth switch is opened;
The seventh switch is opened;
The eighth switch is opened;
The ninth switch is closed;
Wherein the tenth switch is open.

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