KR100995051B1 - Method of transmitting and recieving data in softhandoff of a wireless communication system - Google Patents

Abstract

The present invention relates to a method for transmitting and receiving data in a soft handoff environment of a wireless communication system. In a method for receiving data in a terminal in a soft handoff environment of a wireless communication system according to an aspect of the present invention, the terminal receives a first sequence in which transmission data is interleaved from a first base station using a first interleaver pattern. Receiving a second sequence in which the transmission data is interleaved using a second interleaver pattern from a second base station, and combining the first sequence and the second sequence before receiving the entire frame to which the first sequence is assigned. To decode it.

Code-coupled soft handoff, early termination

Description

METHOD OF TRANSMITTING AND RECIEVING DATA IN SOFTHANDOFF OF A WIRELESS COMMUNICATION SYSTEM}

The present invention relates to a wireless communication system, and more particularly, to a method for transmitting and receiving data in a soft handoff environment of a wireless communication system.

First, the power control technique according to the prior art will be described.

In a mobile communication system, power control is a technique of adjusting a power level of a received signal at a receiving end so that the system can be operated at a level required by a modulation and coding technique used according to a transmission rate of transmission data. In particular, the power control is to solve the near-far problem that occurs in the reverse link, by controlling the transmit power of the terminals so that the transmit power of the terminal close to the base station and the transmit power of the far terminal is different. This is to adjust the power level of the terminals received by the base station to a certain level.

The terminal transmits the pilot signal along with the data signal to the base station through the reverse link, and the reverse power control is performed by adjusting the transmit power of the terminal so that the received energy of the reverse pilot channel (R-PICH) is constant. The receiving end of the base station measures the received energy of the reverse pilot channel, and if the received energy is higher than a predetermined reference point setpoint, a down power control bit (PCB) means to lower the transmission power. When the received energy is lower than the set point, the terminal transmits an up power control command to the terminal through a forward power control subchannel (F-PCSCH).

Based on the pilot channel power control, power control of a reverse traffic channel (R-TCH) through which data is transmitted through the reverse link is performed. That is, the transmit power of the reverse traffic channel is determined using the transmit power ratio (TPR) of the traffic channel to the transmit power of the pilot channel. The TPR for each data rate of data transmitted through the traffic channel is predetermined, and the transmit power of the pilot channel is variable in PCB units according to the reverse link power control, and the transmit power and the predetermined TPR of the variable pilot channel are variable. The transmission power of the traffic channel through which data is transmitted is determined by the relation of.

Next, a hybrid automatic repeat request (HARQ) technique and an early termination technique according to the prior art will be described.

HARQ, which is used to improve the transmission efficiency of packet data with less sensitivity to transmission delay, has a conventional forward error correction (FEC) method and automatic retransmission request through error detection. repeat request (ARQ). The HARQ scheme is used in conjunction with the physical layer and combines the retransmitted data with previously received data to ensure a high decoding success rate. That is, the HARQ scheme is a method of storing a packet that failed to be transmitted without discarding it and then decoding the combined packet with the retransmitted packet.

According to the HARQ scheme, the transmitting end transmits by dividing the coded bits into a plurality of subpackets by FEC coding the data packet information. The subpacket can be decoded with only one subpacket and can be used to know whether the transmission succeeds or fails. In addition, the receiving end may combine and decode a subpacket of the same packet previously received and a currently received subpacket, and confirm the success or failure of the transmission. The transmitting end receives an acknowledgment (ACK / NACK) for packet transmission from the receiving end after transmitting the first subpacket, and if another negative acknowledgment (hereinafter referred to as "NACK"), further transmits another subpacket. Acknowledgment (hereinafter referred to as "ACK"), the transmission of the corresponding packet is terminated.

When there are N subpackets generated by the HARQ scheme, when the transmitting end transmits the M (<N) th subpacket and receives ACK feedback, the transmitting end does not transmit the remaining subpackets and terminates transmission of the corresponding packet. It is called an early termination technique. Early termination can significantly increase packet transmission efficiency because unnecessary subpackets are not transmitted.

Next, the early termination technique of the circuit channel (circuit channel) according to the prior art will be described.

Voice services, which are sensitive to transmission delay and continuously generate data, are transmitted through the circuit channel. A circuit channel is a type of channel in which data is transmitted without interruption.

1 is a diagram illustrating a power control method of a reverse link in a CDMA 2000 system.

As shown in FIG. 1, in the currently commercially available code division multiple access (CDMA) 2000 system, a frame of a traffic channel of a circuit channel structure is usually 20 ms, and one frame includes 16 slots. One slot is 1.25 ms. Since the receiving end transmits one PCB for each slot, the slot is called a power control group (PCG).

In order to improve the transmission efficiency of the traffic channel of the circuit channel structure, the 3rd Generation Partnership Project (3GPP2) standardization organization is recently discussing the application of the early termination scheme to the circuit channel. In the early termination scheme of the circuit channel, unlike the conventional method in which the receiving end decodes the data after receiving the entire frame of 20 ms, the receiving end attempts to decode the data in the middle of receiving the frame and feeds back an ACK to the transmitting end when the data reception is successful. This is a method of stopping transmission of a frame. This stops unnecessary transmission in the CDMA system, thereby reducing the interference to other users, thereby increasing the total system capacity.

2 is a diagram illustrating an example of applying an early termination scheme to a reverse link traffic channel. As shown in FIG. 2, the base station attempts to decode the data in the middle of receiving the frame, and if the data reception is successful, the base station transmits an ACK to the terminal through a forward acknowledgment subchannel (F-ACKSCH) and sends the ACK. The received terminal stops transmitting the corresponding frame.

 In a soft handover situation, the terminal receives a traffic channel containing the same information from two or more base stations. The terminal demodulates the traffic channel received from each of the two or more base stations, and then performs decoding by combining the demodulated traffic channels.

In a CDMA system, traffic channels transmitted by one base station are distinguished by spread codes. That is, the base station assigns different Walsh codes to the traffic channels, modulates the signal with the assigned Walsh codes, and transmits the signals. At this time, in order to transmit a large number of traffic channels without interference with each other in one base station, the coding rate of the FEC channel coding of the traffic channel should be high. In the case of radio configuration 4 in the CDMA 2000 system, the coding rate of the FEC channel coding of the traffic channel of the forward link is 1/2.

If the coding rate is 1/2, the early termination scheme can be used to decode at the time of the decoding attempt only after receiving more than half of the 20ms frame. In other words, the decoding success probability is 0 when half or less of the frames are received.

Therefore, there is a problem that does not improve the benefit of the early termination scheme.

As described above, according to the prior art, there is a problem that does not improve the benefit of the early termination technique.

It is an object of the present invention to provide a method for transmitting and receiving data in a soft handoff environment that can improve the coding gain and the gain of an early termination scheme.

Technical problems to be achieved in the present invention are not limited to the above-mentioned technical problems, and other technical problems not mentioned above will be clearly understood by those skilled in the art from the following description. Could be.

In order to achieve the above object, in a method for receiving data in a terminal in a soft handoff environment of a wireless communication system according to an aspect of the present invention, the terminal transmits data from a first base station using a first interleaver pattern Receive an interleaved first sequence, receive a second sequence from the second base station in which the transmission data is interleaved using a second interleaver pattern, and before receiving the entire frame to which the first sequence is assigned, the first sequence And combine and decode the second sequence.

In order to achieve the above object, a terminal receiving data in a soft handoff environment of a wireless communication system according to another aspect of the present invention receives a first sequence in which transmission data is interleaved from a first base station using a first interleaver pattern. And a receiving module for receiving a second sequence in which the transmission data is interleaved from a second base station using a second interleaver pattern, and the first sequence and the second sequence before receiving the entire frame to which the first sequence is assigned. It includes a decoder to combine and decode.

In this case, the second sequence may be a sequence in which the first sequence is cyclically moved by (length / 2 of the first sequence).

In addition, the terminal may transmit an ACK to the base station if the decoding is successfully performed.

In addition, the first sequence and the second sequence may be encoded in a convolutional code.

In addition, the transmission data may be voice data.

In order to achieve the above object, in a method for transmitting data in a first base station in communication with a terminal in a soft handoff environment of a wireless communication system according to another aspect of the present invention, the first base station is configured to transmit data; A first sequence generated by interleaving using a 1 interleaver pattern is transmitted to the terminal, and upon receiving an acknowledgment (ACK) from the terminal, the transmission of the frame to which the first sequence is allocated is stopped. The first sequence is different from the second sequence generated by the second base station communicating with the terminal using the second interleaver pattern.

A base station in communication with a terminal in a soft handoff environment of a wireless communication system according to another aspect of the present invention for achieving the above object, the base station is an encoder for encoding the transmission data and the encoded data to a first interleaver An interleaver for interleaving using a pattern to generate a first sequence, and when the first base station receives an acknowledgment (ACK) from the terminal, stops transmitting the frame to which the first sequence is allocated; The first sequence is different from a second sequence generated by another base station communicating with the terminal using the second interleaver pattern.

In this case, the second sequence may be a sequence in which the first sequence is cyclically moved by (length / 2 of the first sequence).

In addition, the first sequence and the second sequence may be encoded in a convolutional code.

In addition, the transmission data may be voice data.

According to embodiments of the present invention, each of a plurality of base stations in communication with a terminal in a soft handoff environment may improve the gain of early termination in a handoff environment by transmitting data using different patterns or codes.

The effects obtainable in the present invention are not limited to the above-mentioned effects, and other effects not mentioned above may be clearly understood by those skilled in the art from the following description. will be.

DETAILED DESCRIPTION Hereinafter, exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings so that those skilled in the art may easily implement the present invention. The present invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. In the drawings, parts irrelevant to the description are omitted in order to clearly describe the present invention, and like reference numerals designate like parts throughout the specification.

Throughout the specification, when a part is said to "include" a certain component, it means that it can further include other components, without excluding other components unless specifically stated otherwise. In addition, the terms “… unit”, “… unit”, “module”, etc. described in the specification mean a unit that processes at least one function or operation, which may be implemented by hardware or software or a combination of hardware and software. have.

An embodiment of the present invention describes methods for improving the gain of an early termination scheme when an early termination scheme is applied to a circuit channel.

First, a method of transmitting a frame while changing a transmission to pilot ratio (TPR) of a traffic channel to a transmission channel of a pilot channel according to an embodiment of the present invention will be described.

TPR means a ratio of power allocated to a pilot channel to power allocated to a traffic channel. That is, in order to ensure the performance required for the traffic channel, the power allocated to the traffic channel is maintained at a certain ratio compared to the power allocated to the pilot channel, and this is a value representing the power allocation ratio of the traffic channel and the pilot channel.

TPR depends on the transmission rate, coding scheme, and transmission frame duration of the traffic channel. For example, in a CDMA 2000 system, the TPR is 3.75 dB when a voice signal is transmitted through a reverse fundamental channel (R-FCH) at 9600 BPS. That is, the transmission power of the traffic channel is 3.75 dB higher than the transmission power of the pilot channel.

According to the prior art, the TPR is kept constant except when it is necessary to change the channel environment. If it is necessary to change the TPR due to a change in the channel environment or the like, the base station selects an appropriate value again and informs the terminal of the new TPR value. That is, a fixed value is used within one frame.

The frame transmission method according to an embodiment of the present invention transmits the traffic signal of each slot by applying the optimized TPR for each slot in the frame according to the channel and the system situation.

3 is a view showing an example of a method for transmitting a frame while changing the TPR according to an embodiment of the present invention.

As shown in FIG. 3, the early part of a frame transmits a traffic channel with a high TPR and the second part transmits a traffic channel with a low TPR. When the early termination scheme is applied to the circuit channel, at least two slots or more signals are unnecessarily transmitted from the time when the receiving end decodes until the transmitting end stops transmitting the corresponding frame. Therefore, by lowering the TPR at the back of the frame, where the possibility of ACK feedback increases, reducing the amount of unnecessary signal transmission can reduce the overall system interference.

In the method for transmitting a frame while changing the TPR according to an embodiment of the present invention, the base station may change the TPR in various ways.

First, according to the step reduction TPR method, the TPR has two values in one frame, a high TPR value from the first slot to the Nth slot, and a low value from the N + 1th slot to the last slot is used. Use the TPR value.

According to the prior art, when the transmission data rate is 9600 BPS, all 16 slots use 3.75 dB of TPR in a normal channel environment. According to the step-decreasing TPR method, the first 8 slots use 1.5 times (1.75 dB) of the TPR. It uses a larger 5.5 dB and the remaining eight slots can use 0.75 dB less than 50% less than before.

Next, according to the multi-step reduction TPR method, the TPR has three or more values in one frame, and slots of one frame are divided into a plurality of zones, so that slots of the first zone have the highest TPR value. Slots in the next zone use the next higher TPR value sequentially.

4 is a view showing a two-step reduction TPR method according to an embodiment of the present invention.

As shown in FIG. 4, according to the two-step reduction TPR method, TPR has three values in one frame, slots of one frame are divided into three zones, and slots of the first zone use the highest TPR value. The slots in the second zone use the second highest TPR value, and the slots in the third zone use the lowest TPR value.

Next, according to the multi-step varying TPR (TPR) method, the TPR has a plurality of values in one frame, the slots of one frame are divided into a plurality of zones, and the slots of the first zone use the first TPR value. The slots in the next zone then use the next TPR value sequentially.

5 is a diagram illustrating an example of a multi-step change TPR method according to an embodiment of the present invention.

In Figure 5, the slots of one frame are divided into eight zones, each area comprising two PCGs. Slots in each zone use the appropriate TPR value for each zone. In FIG. 5, a high TPR value is used at the beginning of the frame, and the TPR value used decreases as the PCG index increases, and then uses a high TPR value later in the frame. This is to increase the early termination probability by using a high TPR value at the beginning of the frame and to increase the reception success probability of the frame by using a high TPR value later in the frame. The multi-step change TPR method is also extensible by assigning independent TPR to all PCGs.

The base station and the terminal know and use a predetermined default value of the TPR. If the TPR value needs to be changed according to the channel environment of the terminal, the base station informs the terminal by using higher signaling. However, according to the multi-step change TPR method, since the TPR value is defined for each zone, signaling overhead becomes too large to inform the UE of the TPR value of each zone through higher signaling. Therefore, an embodiment of the present invention proposes a method in which a terminal and a base station know a predetermined TPR boost value set, and the base station informs the index of the modified TPR _MOD value and the TPR increase value set.

Table 1 shows an example of a TPR increase value set according to an embodiment of the present invention.

When the TPR increase value set is determined between the UE and the base station as shown in Table 1, when the base station informs the modified TPR _MOD value and the index of the TPR increase value set, the UE calculates TPR (i) of the i-th PCG. Can be obtained as

TPR (i) = TPR_boost (i) * TPR _MOD

Here, TPR_boost (i) indicates a TPR_boost value of i-th PCG in Table 1.

Next, according to an embodiment of the present invention, the transmit power ratio of the forward traffic channel to the transmit power of the forward power control subchannel in the forward link (F-TCH to F-PCSCH ratio, hereinafter referred to as "F-TCH / F-PCSCH power ratio"). Will be described.

The pilot channel of the forward link is a common channel and thus is not subject to power control. Therefore, the power control of the forward link should directly control the received power of the forward traffic channel (hereinafter referred to as "F-TCH"), when the traffic channel is serving a variable data rate such as voice service. The receiver cannot measure the received power of the traffic channel directly due to the uncertainty of the transmission rate.

6 is a diagram illustrating a power control method of a forward link.

As shown in FIG. 6, the base station transmits a forward power control subchannel (hereinafter referred to as “F-PCSCH”), which is a PCB feedback channel for backward transmission power control along with a traffic channel to the terminal through the forward link. send. Since the F-PCSCH has a fixed data rate, it can be used directly for receiving power measurement. The transmit power of the F-TCH is defined as the F-TCH / F-PCSCH power ratio, and according to the prior art, the F-TCH / F-PCSCH power ratio is maintained within one frame. The UE measures the received power of the F-PCSCH and uses the known F-TCH / F-PCSCH power ratio to determine the noise density (Eb / No) of energy per received bit when the data rate of the F-TCH is 9600 bps. Calculate and compare the Eb / No with the setpoint to generate a power control command (hereinafter referred to as "PCB") to generate a reverse power control subchannel (hereinafter referred to as "R-PCSCH"). Through the transmission to the base station to control the transmission power of the F-TCH and F-PCSCH.

7 is a diagram illustrating a power control method of a forward link according to an embodiment of the present invention.

In an embodiment of the present invention, the F-TCH / F-PCSCH power ratio is varied within one frame. For example, when the data rate is 9600 BPS and the reference value is 0 dB, as shown in FIG. 7, the F-TCH / F-PCSCH power ratio is 1.5 higher than the reference value in the first 8 slots by applying a 1-step reduction method. Use 1.75dB, which is twice as large, and -3dB in the remaining 8 slots, which are 50% less than the baseline.

Then, the UE performs forward power control by measuring the received power of the F-PCSCH, comparing the received Eb / No of the FL-PCB with the set point, and generating a reverse PCB (RL-PCB) to the base station.

In addition, the base station may divide slots of one frame into a plurality of regions and inform the UE of the F-TCH / F-PCSCH power ratio of each region in advance. Then, the UE measures the reception power of the F-PCSCH in each region and uses the known F-TCH / F-PCSCH power ratio in that region, and the reception bit of the F-TCH when the data rate of the F-TCH is 9600bps. It is also possible to generate a PCB by calculating the noise energy ratio (Eb / No) per sugar energy and comparing the Eb / No of the F-TCH with the set point of the region.

Next, a method of controlling an outer power control loop according to an embodiment of the present invention will be described.

In general, power control is performed through an inner power control loop and an external power control loop.

The internal power control loop measures the energy of the received signal at the receiving end and transmits a down power control command to the transmitting end if the energy of the received signal is higher than the predetermined set point, and controls the up power if the energy of the received signal is lower than the set point. Power control is performed by sending a command to the transmitter. External power control is to control the setpoint used in the inner power control loop to meet the target frame error rate (FER).

According to the general external power control loop control method, when the target FER is F, the receiver increases the setpoint by x dB when a frame error occurs and sets by x / (1-1 / F) dB when the frame is successfully decoded. Decreases the point. For example, if the target FER is 1%, the receiver increases the setpoint by 1 dB if a frame error occurs and 1 / (1-1 / 0.01) = 1/99 dB if the frame is successfully decoded. Decreases.

In this case, if the x value of the set point increment x dB is set to a large value, the receiver may change the set point quickly when the required set point is changed due to a change in the channel environment, but the required set point changes stably. In this environment, the setpoint used may fluctuate greatly around the required setpoint. In addition, when frame errors occur consecutively due to instantaneous burst noise, the set points used may be set too high than the required set points, and may take a long time to return to the required set points.

Therefore, in order to solve this problem, an embodiment of the present invention proposes a method of controlling an external power control loop when an early termination scheme is applied to a circuit channel.

First, a method of controlling an external power control loop according to a first embodiment of the present invention will be described with reference to FIGS. 8 and 9.

According to the early termination scheme, the receiver attempts to decode while receiving a part of a frame. In an embodiment of the present invention, one or more target decoding attempts are set from among decoding attempts, and thus the target FER at the time of receiving the entire frame. The target FER at the target decoding attempt point is determined to satisfy the control, and the setpoint of the inner power control loop is controlled to satisfy the target FER at the target decoding attempt point.

For example, when the target FER at the time of receiving the entire frame is 1%, the target FER at the time of the target decoding attempt may be set to about 20 to 50%, and the internal power control to satisfy the target FER at the time of the target decoding attempt. The set point of the loop can be controlled.

8 illustrates a method of controlling an external power control loop of a reverse link according to a first embodiment of the present invention, and FIG. 9 is a diagram of controlling an external power control loop of a forward link according to a first embodiment of the present invention. A diagram illustrating the method.

Referring to FIG. 8, the base station controls the target FER at the time of the target decoding attempt to satisfy the final FER which is the target FER at the time when the entire frame is received. The base station controls the setpoint to satisfy the target FER at the time of the target decoding attempt. When the base station receives a signal from the terminal, the base station generates a power control command by comparing the energy of the received signal with the set point and transmits the power control command to the terminal.

9, the terminal controls the target FER at the target decoding attempt time to satisfy the final FER which is the target FER at the time when the entire frame is received. The terminal controls the setpoint to satisfy the target FER at the target decoding attempt. When the terminal receives a signal from the base station, the terminal generates a power control command by comparing the energy of the received signal with the set point and transmits the power control command to the base station.

Next, a method of controlling an external power control loop according to a second embodiment of the present invention will be described with reference to FIGS. 10 and 11.

According to the second embodiment of the present invention, when the receiving end transmits the target FER at the time of receiving the entire frame to the transmitting end, the transmitting end sets the target FER at the time of the target decoding attempt so that the target FER at the time of receiving the entire frame is satisfied. In this case, the receiver controls the set point of the internal power control loop to satisfy the received target FER.

If the data rate is variable, such as voice data, there is a zero data rate. That is, there is a case in which data is not substantially transmitted to the frame. When decoding of the frame fails, the receiver cannot distinguish whether the decoding of the frame has failed due to a channel error or whether the decoding of the frame has failed because there is no transmission data. Therefore, in the second embodiment of the present invention, when the receiving end informs the transmitting end of the number of successfully decoded frames for a predetermined time, the transmitting end measures the length of time for measuring the number of successfully decoded frames, In consideration of the number and the number of frames for which data is not transmitted, the target FER at the time of the target decoding attempt is set to be notified to the means so that the target FER at the time of receiving the entire frame is satisfied.

FIG. 10 is a diagram illustrating a method for controlling an external power control loop of a reverse link according to a second embodiment of the present invention, and FIG. 11 is a diagram for controlling an outer power control loop of a forward link according to a second embodiment of the present invention. A diagram illustrating the method.

Referring to FIG. 10, the base station transmits a final FER which is a target FER at the time of receiving the entire frame and the number of frames successfully decoded for a predetermined time to the terminal. Then, the terminal decodes the target to satisfy the target FER when the entire frame is received in consideration of the length of time for measuring the number of successfully decoded frames, the number of successfully decoded frames, and the number of frames for which data has not been transmitted. Sets a target FER at the time of attempt and informs the base station. The base station controls the set point of the internal power control loop so that the received target FER is satisfied. When the base station receives a signal from the terminal, the base station generates a power control command by comparing the energy of the received signal with the set point and transmits the power control command to the terminal.

Referring to FIG. 11, the terminal transmits a final FER which is a target FER at the time of receiving the entire frame and the number of frames successfully decoded for a predetermined time to the base station. Then, the base station decodes the target to satisfy the target FER at the time of receiving the entire frame in consideration of the length of time for measuring the number of successfully decoded frames, the number of successfully decoded frames, and the number of frames for which no data has been transmitted. Sets the target FER at the time of the attempt and informs the terminal. The terminal controls the set point of the internal power control loop to satisfy the received target FER. When the terminal receives a signal from the base station, the terminal generates a power control command by comparing the energy of the received signal with the set point and transmits the power control command to the base station.

Next, a method of controlling an external power control loop according to a third embodiment of the present invention will be described with reference to FIGS. 12 and 13.

According to the third embodiment of the present invention, if the receiving end transmits the target FER at the time when the entire frame is received to the transmitting end, the transmitting end corrects the TPR of the transmission signal such that the target FER at the time of receiving the entire frame is satisfied.

12 is a diagram illustrating a method of controlling an external power control loop of a reverse link according to a third embodiment of the present invention, and FIG. 13 is a diagram of controlling an external power control loop of a forward link according to a third embodiment of the present invention. A diagram illustrating the method.

Referring to FIG. 12, the base station transmits a target FER to the terminal at the time when the entire frame is received. Then, the terminal calculates the target FER at the target decoding attempt point to satisfy the target FER at the time of receiving the entire frame, and calculates the FER at the target decoding attempt point with the ACK / NACK received from the base station. The terminal corrects the TPR of the transmission signal by comparing the FER at the target decoding attempt time calculated by ACK / NACK with the target FER.

At this time, the base station uses a predefined value of the set point of the internal power control loop.

Referring to FIG. 13, the terminal transmits the target FER to the base station at the time when the entire frame is received. Then, the base station calculates the target FER at the target decoding attempt point so that the target FER at the time of receiving the entire frame is satisfied, and calculates the FER at the target decoding attempt point with the ACK / NACK received from the terminal. The base station compares the FER at the target decoding attempt calculated by ACK / NACK with the target FER to correct the TPR of the transmission signal. Here, TPR means F-TCH / F-PCSCH power ratio.

In this case, the terminal uses a predefined value of the set point of the internal power control loop.

Next, an acknowledgment (negative acknowledgment) (hereinafter referred to as "ACK / NACK") transmission method according to an embodiment of the present invention will be described.

In applying the early termination scheme to the circuit channel, the performance of the Acknowledgment Channel (hereinafter referred to as "ACKCH") is important. The acknowledgment error includes an ACK2NACK error in which the receiver recognizes the ACK as a NACK and a NACK2ACK error in which the receiver recognizes the NACK as an ACK. If an ACK2NACK error occurs, the transmitting end of the frame cannot be prematurely terminated, so the gain of early termination cannot be obtained. If a NACK2ACK error occurs, the transmitting end of the frame is transmitted even though the frame is not successfully decoded by the receiving end. Early termination leads to an increase in FER.

Therefore, in order to solve the above problem, the receiver repeatedly transmits ACK / NACK until the corresponding frame is completed.

FIG. 14 is a diagram illustrating a case where an ACK is repeatedly transmitted according to an embodiment of the present invention, and FIG. 15 is a diagram illustrating a case where a NACK is repeatedly transmitted according to an embodiment of the present invention.

14 and 15 illustrate ACK / NACK for forward traffic, the present invention can also be applied to ACK / NACK for reverse traffic.

As shown in FIG. 14, if the terminal decodes at the decoding attempt time and succeeds, the terminal continuously transmits the ACK signal to the base station until the corresponding frame is completed. Therefore, even when an ACK2NACK error occurs, frame transmission can be terminated early if the base station receives the next ACK signal without error.

As shown in FIG. 15, when a NACK2ACK error occurs, the base station receives an ACK and stops transmitting a frame. When the NACK signal is received without error, the base station resumes frame transmission again.

Next, a data rate indicating method according to an embodiment of the present invention will be described.

When the early termination scheme is applied to the circuit channel, the receiver performs decoding each time a decoding attempt is performed. Thus, the complexity of the receiver increases compared to trying to decode once at the end of the frame. In particular, when the data rate of the traffic channel is a variable rate, blind rate decoding should be performed assuming all rates in the variable rate set at every decoding attempt.

In order to increase the effectiveness of the early termination scheme, the receiver must speed up decoding since the decoding must be completed within a short time, and an ACK feedback is sent to the transmitter to stop further unnecessary transmission. However, if the receiver assumes all rates in the variable rate set and decodes quickly, the receiver complexity increases.

Accordingly, an embodiment of the present invention proposes a method for notifying a receiving end of a data rate or a subset of data rates of a frame.

16 (a) is a diagram illustrating a data rate indicating method according to an embodiment of the present invention on a forward link, and FIG. 16 (b) is a diagram showing a data rate indicating method according to an embodiment of the present invention on a reverse link.

ACKSCH is unlikely to be used at the beginning of the frame. Therefore, as shown in FIGS. 16A and 16B, the resource of the ACKSCH can be used to indicate the data rate at the beginning of the frame. That is, the resource of the ACKSCH may be used as a rate indication subchannel (hereinafter referred to as "RISCH") at the beginning of the frame. According to an embodiment of the present invention, the same radio resource or the same CDMA code resource is used as an RISCH at the beginning of the frame and as an ACKSCH at the end of the frame.

In the case of transmitting data of a voice service, taking a CDMA 2000 system as an example, a data channel of a traffic channel has 5 variable data rates of 9600bps, 4800bps, 2400bps, 1200bps, and 0bps. In this case, the data rate may be shown in Table 2. Table 2 shows an example of modulation symbols transmitted through RISCH for each data rate. That is, the transmitting end transmits a symbol corresponding to the data rate of the frame in Table 2 to the receiving end to inform the receiving end of the data rate of the frame.

Data rate Modulation symbol on RISCH 9600 bps One 4800 bps -One 2400 bps j 1200 bps -j 0 bps 0

In addition, the transmitting end may modulate the RISCH as shown in Table 3 or 4. Table 3 shows another example of a modulation symbol transmitted on the RISCH for each data rate, and Table 4 shows another example of a modulation symbol transmitted on the RISCH for each data rate.

Data rate Modulation symbol on RISCH 9600 bps One 4800bps or 2400bps or 1200bps -One 0 bps 0

Data rate Modulation symbol on RISCH 4800 bps One 2400 bps or 1200 bps -One 0 bps or 9600 bps 0

As shown in Tables 3 and 4, if a plurality of data rates are modulated into the same symbol, even if an error occurs during the RISCH transmission, the receiver is more likely to modulate the signal correctly. Since the receiver can decode the highest data rate, it is possible to blind rate decode a plurality of lower data rates simultaneously.

Table 4 has an advantage of reducing the overhead of RISCH transmission power by allocating modulation symbol 0 to 9600 bps and 0 bps, which are the most frequent in the case of voice service.

As shown in Tables 1 to 3, when a transmitting end transmits a modulation symbol to a receiving end through a RISCH, the receiving end assumes a data rate corresponding to the modulation symbol and performs decoding at a decoding attempt. If the decoding is not successful at the time of the decoding attempt, the receiving end performs blind rate decoding on all data rate sets after receiving the entire frame.

Referring to the case where an error occurs in the RISCH, since the RISCH is transmitted in the front part of the frame, the front part of the frame is faded. However, when the front part of the frame fades, the probability of early termination of the frame is reduced, so that there is almost no performance degradation of the traffic channel due to the RISCH error.

Next, an emergency power control method using negative NACK according to an embodiment of the present invention will be described.

When the early termination scheme is applied to the circuit channel, ACKSCH is transmitted in modulation symbol 1 and NACK is transmitted in modulation symbol 0 to reduce overhead of transmission power. That is, in the case of NACK, since the power of the signal transmitted through the ACKSCH is 0, the overhead of the transmit power of the ACKSCH can be reduced.

In the embodiment of the present invention, it is proposed to transmit a negative NACK. According to an embodiment of the present invention, ACK is transmitted in modulation symbol 1, NACK is transmitted in modulation symbol 0, and negative NACK is transmitted in modulation symbol -1.

Negative NACK may be used for emergency power control.

As an example, the receiving end measures the received energy of the traffic channel at the time of decoding attempt and transmits a negative NACK to the transmitting end when it is determined that the received energy of the frame does not satisfy the energy required to successfully receive the frame at the end of the frame. This allows the transmitting end to increase the transmission power of the traffic channel.

As another example, when the energy of the signal received by the receiver is lower than a predetermined level above the set point of the power control, the receiver transmits a negative NACK to the transmitter, and the transmitter that receives the negative NACK transmits the transmit power to PC_UP_SIZE + BOOST_UP [ in [dB] increments.

That is, the receiving end transmits a negative NACK to the transmitting end when the received energy Rx_Pwr of the power control reference channel is lower than the set point of the power control by more than a predetermined level Boost_Th (Rx_Pwr <(setpoint- Boost_Th)). send. At this time, since the received energy is smaller than the setpoint in the general power control process (Rx_Pwr < setpoint), the up power control command is transmitted to the transmitter. In general, the transmitter increases the transmission power by PC_UP_SIZE when receiving the up power control command, but increases the transmission power by PC_UP_SIZE + BOOST_UP [dB] when receiving the up power control command and the negative NACK.

Alternatively, if the ACK / NACK feedback channel is more reliable than the PCB feedback channel, when the transmitting end receives a negative NACK, the transmitting end ignores the received power control command and increases the transmission power by PC_UP_SIZE + BOOST_UP [dB]. It may be.

When the terminal receives power control commands from two base stations in a handover situation and performs power control of a reverse channel, according to an embodiment of the present invention, the terminal receives a negative NACK from both base stations within a predetermined time interval (window). Upon reception, increases the transmit power by PC_UP_SIZE + BOOST_UP [dB].

Next, a method of transmitting and receiving data in a soft handoff environment according to an embodiment of the present invention will be described.

According to the prior art, since the terminal receives the same information from the plurality of base stations in the soft handoff environment, it is not possible to take advantage of the early termination. Therefore, in the embodiment of the present invention, the plurality of base stations in communication with the terminal in the soft handoff environment transmit data using different patterns or codes, thereby transmitting and receiving data that can improve the gain of early termination in the handoff environment. Suggest a method.

A code combining soft handoff (code combining) means that a plurality of base stations communicating with a terminal in a soft handoff environment transmit data using different patterns or codes, and the terminal obtains a high coding gain by combining different patterns or codes. soft handoff).

First, a method of transmitting and receiving data in a soft handoff environment according to a first embodiment of the present invention will be described.

According to the first embodiment of the present invention, when a plurality of base stations communicating with a terminal in a soft handoff environment transmit a traffic channel containing the same information, early termination is performed by different transmission order of channel coded coded bits. Improve the gain of the technique. 17 and 18, a case where there are two base stations communicating with a terminal in a soft handoff environment will be described as an example.

17 (a) is a block diagram of a first base station according to the first embodiment of the present invention, and FIG. 17 (b) is a block diagram of a second base station according to the first embodiment of the present invention.

As shown in FIGS. 17A and 17B, a base station according to a first embodiment of the present invention includes a cyclic redundancy check (hereinafter referred to as a “CRC”) and tail bits addition unit. (add CRC & tail bits) 171, encoder 172, rate matching 173, interleaver 174 including cyclic shifter and spread and modulation And a spreader & modulator 175.

When the information bit string is input, the CRC and tail bit adding unit 171 adds the CRC and tail bits to the information bit string, and the encoder 172 performs FEC encoding on the information bit string.

The rate matching unit 173 performs rate matching that matches the encoded information bit string to the transmission bits of the channel. That is, rate matching is an operation of matching the maximum amount of data to be transmitted with the amount of data to be transmitted for each transmission time interval (TTI).

The interleaver 174 cyclically shifts an existing interleaved and interleaved sequence that rearranges the order of the information bit streams in a predetermined unit, and the spread and modulator 176 spreads and modulates the cyclically shifted sequence. The modulated sequence is transmitted via the transmit antenna.

The interleaver 174 moves the sequence by a predetermined cyclic shift value. In the first embodiment of the present invention, the cyclic shift value of the first base station and the second base station is different from each other. The sequence output from the interleaver is b ₀ , b ₁ ,. , b If _N-1, if the cyclic shift value of the cyclic shift unit is _a , the bit sequence output from the cyclic shift unit is b _a , b _{a + 1} ,. , b _N-1 , b ₀ , b ₁ ,... , b _a-1 . In this case, N is the length of the sequence output from the interleaver.

For example, in a CDMA 2000 system, when a terminal in a handoff environment is communicating with two base stations and two base stations perform FEC channel coding on an information bit to be transmitted on a forward link with a coding rate of 1/2, the cyclic shift of the first base station If the negative cyclic shift value is 0 and the cyclic shift value of the cyclic shift part of the second base station is N / 2, the bit sequence output from the cyclic shift part of the first base station is b ₀ , b ₁ ,. , b _N-1 , and the bit sequence output from the cyclic shifter of the second base station is b _{N / 2} , b _{N / 2 + 1} ,... , b _{N / 2-1} . Therefore, the first base station is b ₀ , b ₁ ,. , b _N-1 , and the second base station transmits b _{n / 2} , b _{N / 2 + 1} ,... , b Transmit data in _{N / 2-1} order. Then, when the terminal in the handoff environment receives 1/2 of the 20 ms frame, the terminal receives the entire sequence (b ₀ , b ₁ , ..., b _N-1 ). The reception coding rate is 1/2, which increases the probability of decoding success at the time when 1/2 of the 20 ms frame is received. In addition, the probability of success in decoding in a state of receiving 1/4 or more and 1/2 or less of a 20 ms frame also increases.

In the forward link, when a base station performs FEC channel coding on an information bit to be transmitted at a coding rate of 1/2, one information bit is transformed into two parity bits and interleaved with the first parity sequence interleaved by an interleaver. The second parity sequence is transmitted sequentially. Applying the first embodiment of the present invention to such a transmission scheme, a first base station transmits an interleaved first parity sequence to a terminal in a handoff environment, and then transmits an interleaved second parity sequence, and the second base station interleaves. The second parity sequence and then the interleaved first parity sequence.

In order to send a power control command for reverse power control on the forward link, the coded bits of some traffic channels are punched and an F-PCSCH is inserted to send the power control command. Unless the cyclic shift of bit sequences transmitted by a plurality of base stations communicating with a terminal in a handoff environment is performed, the same encoding is performed at each of the plurality of base stations because the positions of the traffic channels punched for transmitting the F-PCSCH are the same. The bit is punched out. However, as in the first embodiment of the present invention, when each of the plurality of base stations cyclically shifts a bit sequence to be transmitted by different cyclic shift values, the location of the traffic channel punched for transmitting the F-PCSCH is determined by each of the plurality of base stations. Each is different, so additional coding gains can be obtained.

As shown in FIG. 17, the interleaver 174 may include a cyclic mobile unit, and the interleaver and the cyclic mobile unit may be implemented as other components of the base station. When the interleaver 174 includes a cyclic mobile unit, each of a plurality of base stations communicating with a terminal having a handoff environment may transmit a sequence of sequences differently using different interleaver patterns.

For example, when there are two base stations communicating with a terminal in a handoff environment, the first base station may use the first interleaver pattern, and the second base station may use the second interleaver pattern. At this time, the interleaved sequence using the second interleaver pattern is a cyclic shift of the interleaved sequence using the first pattern.

When the length of the output sequence of the interleaver is N, when the interleaved sequence using the second pattern is a cyclic shift of the interleaved sequence by N / 2, the interleaving is performed using the first pattern. Sequence is b ₀ , b ₁ ,. , b _N-1 , the sequence interleaved using the second pattern is b _{N / 2} , b _{N / 2 + 1} ,. , b _{N / 2-1} .

That is, when there are two base stations communicating with the terminal in the handoff environment, the cyclic shift value of the first base station may be 0, and the cyclic shift value of the second base station may be N / 2.

And, if there are two or more base stations communicating with the terminal in the handoff environment, the cyclic shift value of each of the base stations may be 0 or N / 2.

On the other hand, various cyclic shift values can also be considered. For example, it is also possible to determine the cyclic shift value as a multiple of 1/4 rather than a multiple of 1/2. That is, when there are two or more base stations communicating with the terminal in the handoff environment, the cyclic shift value of each of the four base stations may be one of {0, N / 4, 2 * N / 4, 3 * N / 4}. have.

When the base station communicating with the terminal in the handoff environment is changed, when the base station transmits a handover direction message to the terminal, the base station informs the cyclic shift value used by the added base station and the newly allocated decoding attempt time. .

18 is a configuration diagram of a terminal according to the first embodiment of the present invention.

As shown in FIG. 18, the terminal according to the first embodiment of the present invention includes a radio frequency & analog-to-digital converter (RF & AD converter) 181, and a D for a first base station. A deinterleaver 183a for the first base station including a spreader & demodulator for BS1 182a, a cyclic shifter for BS1, and a second base station Deinterleaver 183b for the second base station, including a despreader & demodulator for BS1 182b, a cyclic shifter for BS1, and both base stations A combiner 184 and a decoder buffer 185 that combine the deinterleaved information from the.

The high frequency and analog digital converter 181 converts the received analog signal into digital. The despreader and demodulator 182a for the first base station despreads and demodulates the signal received from the first base station, and the deinterleaver 183a for the first base station including the cyclic mobile unit for the first base station. The signal received from the first base station is cyclically moved in consideration of the cyclic shift value of the first base station, and the interleaved deinterleaved signal is deinterleaved. In this case, the circular moving unit and the deinterleaver 183a may be implemented as separate components of the terminal.

The despreader and demodulator 182b for the second base station despreads and demodulates the signal received from the second base station, and the deinterleaver 183b for the second base station including a cyclic shifter for the second base station. Cyclically moves the signal received from the second base station in consideration of the cyclic shift value of the first base station, and deinterleaves the cyclically shifted received signal. In this case, the circular moving unit and the deinterleaver 183b may be implemented as separate components of the terminal.

The signal of the deinterleaved first base station and the signal of the deinterleaved second base station are combined into one signal in the mixer 184 and then stored in the decoding buffer 185. In this way, the terminal combines and decodes the signal of the deinterleaved first base station and the signal of the deinterleaved second base station. The terminal attempts to decode the data in the middle of receiving the frame before receiving the entire frame. If the data reception is successful, the terminal transmits an ACK to the base station through a reverse acknowledgment channel. Stops transmission. At this time, the base station may inform the terminal when the terminal tries to decode. As in the first embodiment of the present invention, if the terminal combines and decodes the signal of the first base station and the signal of the second base station, the possibility of early termination can be increased.

Next, a method of transmitting and receiving data in a soft handoff environment according to a second embodiment of the present invention will be described.

According to the second embodiment of the present invention, two or more base stations in communication with a terminal in a soft handoff environment are FEC channel coded data to be transmitted using a convolutional code. Since the code generation polynomial is used and the terminal combines and decodes the signals received from two or more base stations, the coding rate is lower than the coding rate of one base station, thereby improving the gain of the early termination scheme. have.

19 illustrates a data transmission / reception method in a soft handoff environment according to a second embodiment of the present invention.

19, a terminal in a soft handoff environment is communicating with two base stations, and the two base stations perform FEC channel coding on data to be transmitted using a convolutional code having a coding rate of 1/2. The convolutional code generation polynomial used by the base station and the second base station is different. Then, since the terminal combines and decodes the signals received from each of the first base station and the second base station, the coding rate is 1/4, and the probability of success of decoding in a state of receiving less than 1/2 of the frame is increased. .

If the coding rate of the base station is 1/2 and the frame length is 20 ms, the terminal that is not in the soft handoff environment attempts to decode at 10 ms or more because the probability of decoding success is 0 while receiving less than 1/2 of the frame. The time point is assigned from the base station. However, when a terminal that is not in the soft handoff region moves to the soft handoff region and communicates with a plurality of base stations, the terminal is additionally allocated a decoding attempt time located within 10 ms.

When the base station communicating with the terminal in the handoff environment is changed, when the base station transmits a handover direction message to the terminal, the cyclic shift value used by the added base station and a newly allocated decoding attempt time point are used. Tells. Alternatively, the decoding attempt may be determined in advance according to the number of base stations communicating with the terminal in the handoff environment, and the terminal may attempt decoding at a predetermined decoding attempt.

In the second embodiment of the present invention, a method of designing a convolutional code to be used by two base stations when a terminal in a handoff environment is communicating with two base stations will be described.

FIG. 20 (a) shows an encoder structure of convolutional code with the generated polynomial (561,753) and an encoder structure of convolutional code with the generated polynomial (557,751), and FIG. 20 (b) is an encoder combined with two convolutional codes. A diagram showing the structure of the.

Two convolutional codes with different generational polynomials generate different codewords even with the same input sequence. However, as shown in FIG. 20 (b), two convolutional codes having different generation polynomials may be combined into one convolutional code having a low coding rate.

Assuming that two base stations communicating with a terminal in a soft handoff environment use convolutional codes with a coding rate of 1/2, the terminal combines different codes received from the two base stations, so that the coding rate is 1/4 and The same effect occurs. Therefore, the generation polynomial used by the two base stations should be determined so that the combined convolutional code with 1/4 coding rate is good.

In addition, since the terminal communicates with one base station immediately before and after the handoff process, the generation polynomial should be determined so that the performance of the coding rate 1/2 convolutional code used by each of the two base stations is good. That is, the terminal communicates with the serving base station before entering the handoff process, communicates with the serving base station and the target base station during the handoff process, and communicates with the target base station after the handoff process is completed, so that each of the two base stations uses coding. The performance of rate 1/2 convolutional code is just as important as that of combined convolutional code with 1/4 coding rate.

However, considering that the coding gain when the coding rate is 1/4 is much higher than when the coding rate is 1/2, the performance of the coding rate 1/2 convolutional code used by each of the two base stations should be considered first.

Therefore, in the second embodiment of the present invention, the criterion for designing a convolutional code to be used by two base stations is that first, the performance of the coding rate 1/2 convolutional code used by each of the two base stations should be good, and secondly, the coding rate. The performance of this 1/4 combined convolutional code should be as good as possible.

Table 5 shows the generated polynomials with a coding rate of 1/2 and a constraint length of K = 9.

Notation Generating polynomial in octal d _∞ (free distance) Johannesson 557, 751 12 Chambers 515, 677 12 3GPP2 561, 753 12

The best performing polynomial of the production polynomials of Table 5 is (561, 753). Thus, selecting the production polynomial (561, 753), combining the production polynomial (561, 753) with the production polynomial (557, 751) and combining the production polynomial (561, 753) with the production polynomial (515, 677). Look at the case.

Table 6 shows the combination of product polynomials.

FIG. 21 is a diagram illustrating an upper limit of a bit error rate (BER) of each code having a coding rate of 1/2 and a code having a combined coding rate of 1/4.

In FIG. 21, when the coding rate is 1/4, the performance of 3GPP2 + Johannesson is slightly decreased. However, when the coding rate is 1/2, 3GPP2 + Johannesson has the best performance. It can be seen that the performance of the 1/4 3GPP2 + Johannesson code does not make a big difference compared to the best 1/4 3GPP2 code when the coding rate is 1/4. Therefore, according to the criteria of the second embodiment of the present invention, the 3GPP2 + Johannesson code is selected.

Next, a method of transmitting and receiving data in a soft handoff environment according to a third embodiment of the present invention will be described.

According to the third embodiment of the present invention, when a plurality of base stations communicating with a terminal in a soft handoff environment rate match data to be transmitted, each of the plurality of base stations uses different rate matching patterns to add additional coding gain and early stage. Improve the benefit of the termination technique.

22 is a configuration diagram of a base station according to the third embodiment of the present invention.

As shown in FIG. 22, the base station according to the third embodiment of the present invention may include a CRC and tail bits adder 221, an encoder 222, and a rate matching unit. 223, an interleaver 224, and a spreader & modulator 225.

The CRC and tail bit adder 221 adds the CRC and tail bits to the information bit string when the information bit string is input, and the encoder 222 FEC encodes the information bit string.

The rate matching unit 223 performs rate matching that matches the encoded information bit string to the transmission bits of the channel. That is, rate matching is an operation of matching the maximum amount of data to be transmitted with the amount of data to be transmitted for each transmission time interval (TTI). In this case, the plurality of base stations communicating with the terminal in the handoff environment use different rate matching patterns, so that the sequences transmitted by the plurality of base stations are different from each other.

The interleaver 224 performs interleaving to rearrange the order of the information bit streams in a predetermined unit, and the spread and modulator 225 spreads and modulates the bit sequence. The modulated bit sequence passes through the RF stage and is transmitted through the antenna.

Next, a radio configuration according to an embodiment of the present invention will be described.

Applying the voice capacity enhancement techniques described above to a wireless communication system increases the maximum number of users that the wireless communication system can accommodate. However, since the traffic channels in the forward link of the CDMA system are distinguished by Walsh codes, the number of traffic channels that can be supported by the CDMA system is limited by the number of Walsh codes. In a CDMA 2000 system forward link, each voice traffic channel is defined by a Walsh code of length 128, so that the maximum supportable voice traffic on the forward link at 1.25 MHz, unless code extension is made to quasi-orthogonal code. There can be no more than 128 channels.

When the terminal is in the handoff region, since a traffic channel is allocated from a plurality of base stations, Walsh code resources of each of the plurality of base stations are used. That is, if the terminal is in an N-way handover region in which N sectors are set as active sectors, Walsh codes having a length of 128 are allocated from the N sectors.

If all the terminals are in the non-handover region, up to 128 users can be accommodated in the 1.25 MHz band per sector, but if all the terminals are in the two-way handover region, then substantially in the 1.25 MHz band per sector The number of users accommodated is reduced to 64. That is, the more terminals in the handover area and the larger the number of active sectors in the handover area, the smaller the maximum number of users that can be substantially accommodated per sector.

In an embodiment of the present invention, in order to save Walsh code resources that are excessively required during handover, Walsh codes are time-divided to form a base channel and channel allocation is performed in units thereof. Thus, the existing circuit channel is defined by the Walsh code index according to the Walsh code length, but in the embodiment of the present invention, the base channel is defined by the Walsh code index and time index according to the Walsh code length.

For example, if one base channel is defined with an even-numbered PCG of one Walsh code index and another base channel is defined with an odd-numbered PCG, two base channels may be defined with one Walsh code.

As another example, if you define one base channel as the first 10 ms of a 20 ms frame of one Walsh code index and another base channel as the last 10 ms of a 20 ms frame, two Walsh codes You can define a basic channel.

Alternatively, one or more Walsh codes may be time-divided to define three or more basic channels.

When a plurality of base channels are defined by time-division of one Walsh code, each of the base channels may have a transmission coding rate of 1 or more. In this case, in order for the receiving end to successfully receive data, the transmitting end transmits the same data to a plurality of basic channels so that the combined coding rate of the receiving end is lower than one.

23 is a diagram illustrating an example of a transmission chain of a transmitting end using a wireless configuration according to an embodiment of the present invention.

As shown in FIG. 23, in the transmission chain of a transmitting end using a wireless configuration according to an embodiment of the present invention, a forward primary traffic channel (hereinafter, "F-") is defined as two primary channels. PTCH ") and a forward secondary traffic channel (hereinafter referred to as" F-STCH ").

23 illustrates that one Walsh code is time-divided into even-numbered PCGs and odd-numbered PCGs to define two basic channels, traffic information is coded at a 1/2 coding rate, and the same traffic information is transmitted to two basic channels. Shows. In this case, the transmission coding rate of each base channel is 1, and the receiving end must receive the same traffic information from two or more base channels in order to successfully receive the information.

In FIG. 23, each of the basic channels receives a sequence of bits passing through the same interleaver, performs cyclic shift independently for each basic channel, and spreads and modulates the result using a Walsh code assigned to each basic channel. In this case, a signal is transmitted from the PCG assigned to each of the basic channels, and no signal is transmitted from an unassigned PCG. In FIG. 23, the spreading and modulator and the PCG selector may be reversed.

The UE in the non-handover area is allocated two basic channels, F-PTCH and F-STCH, to successfully receive traffic information. The cyclic shift value of the F-PTCH and the F-STCH is 0, the Walsh code indices of the F-PTCH and the F-STCH are the same, the F-PTCH is assigned to the odd-numbered PCG of the frame, and the F-STCH is the even number of the frame. If it is assigned to the first PCG, the transmission signal of the transmitter according to the embodiment of the present invention is the same as the transmission signal of the transmitter according to the prior art.

24 illustrates another example of a transmission chain of a transmitting end using a wireless configuration according to an embodiment of the present invention.

As shown in FIG. 24, the rate matched bit sequence is divided into two sequences in a serial to parallel block so that each of the two sequences is interleaved, cyclically moved, spread and modulated. The modulated signal is mapped to the PCG assigned to the base channel and transmitted.

A case of using a wireless configuration according to an embodiment of the present invention in a soft handover environment will be described.

25 is a diagram illustrating a process in which two base stations using a wireless configuration according to an embodiment of the present invention communicate with a terminal in a handoff environment.

In FIG. 25, the cyclic shift value of the F-PTCH is 0, when the length of the output sequence of the interleaver is N, the cyclic shift value of the F-STCH is N / 16, and the Walsh code indexes of the F-PTCH and the F-STCH are Different from each other, if both F-PTCH and F-STCH are assigned to the odd-numbered PCG of the frame, the signal transmission has a 50% duty cycle in PCG units, which is combined with an early termination scheme, resulting in early termination. Has the effect of reducing the signal power transmitted unnecessarily until is completed and the ACK feedback is received.

FIG. 26 illustrates an example of a handoff procedure when using a wireless configuration according to an embodiment of the present invention, and FIG. 27 illustrates another example of a handoff procedure when using a wireless configuration according to an embodiment of the present invention. .

Referring to FIG. 26, the terminal receives data from the first base station through the F-PTCH and the F-STCH while being connected to the first base station BS1. At this time, the cyclic shift value of the F-PTCH is 0, and the cyclic shift value of the F-STCH is N / 16.

Thereafter, the terminal moves toward the second base station BS2, so that a pilot signal to interference ratio (hereinafter referred to as "C / I") from the second base station sets a traffic channel addition threshold (T_ADD threshold). If exceeded, the base station controller (BSC) informs the terminal of allocating the F-PTCH of the second base station to the terminal through a handover message. Then, after the UE normally receives the F-PTCH of the second base station and transmits a handover complete message to the base station controller, the base station controller may confirm that the handover of the terminal is completed. At this time, if the cyclic shift value of the F-PTCH of the second base station is (N / 2 + N / 16), it is possible to maximize the gain of the code combining soft handoff.

When the pilot C / I from the first base station is lower than a predetermined threshold, the base station controller informs the terminal of de-allocation of the F-STCH of the first base station through a handover message. When the terminal normally receives the handover message and transmits the handover complete message to the first base station, the first base station stops transmitting the F-STCH and retrieves the Walsh code resource allocated to the terminal.

If the terminal moves further toward the second base station and the pilot C / I from the second base station becomes higher than a predetermined threshold, the base station controller informs the terminal that the F-STCH of the second base station is allocated to the terminal through a handover message. At this time, if the cyclic shift value of the F-PTCH of the second base station is N / 2, it is possible to maximize the gain of the code combining soft handoff.

When the pilot C / I from the first base station is lower than the traffic channel release threshold (T_Drop threshold), the base station controller informs the terminal of the release of the F-PTCH of the first base station through a handover message. When the terminal normally receives the handover message and sends the handover complete message to the first base station, the first base station stops transmitting the F-PTCH signal and recovers the Walsh code resource allocated to the terminal.

In the example shown in FIG. 26, between the transmission point of the second handover message and the transmission point of the third handover message, the first base station and the second base station transmit only the F-PTCH to the terminal.

In FIG. 27, the F-STCH of the first base station is released and the F-STCH of the second base station is simultaneously allocated. That is, the UE may be allocated an F-PTCH from N base stations in an N-way handover region and may be allocated an F-STCH only from one of the best base stations. Alternatively, the UE may be allocated an F-PTCH from N base stations in an N-way handover region and may be allocated an F-STCH from some of the N base stations.

As described above, using the radio configuration according to an embodiment of the present invention, the Walsh code resources allocated from each base station in the N-way handover region are reduced by half compared to the conventional scheme, thereby alleviating the Walsh code resource shortage phenomenon. Can be.

In the example of FIG. 25, since both F-PTCH and F-STCH are allocated to odd-numbered PCGs of a frame, gain of early termination can be increased, but a problem of unbalanced Walsh code resource utilization rates of odd-numbered and even-numbered PCGs may occur. have. Therefore, to solve this problem, we propose a scheme in which each of the F-PTCH and the F-STCH is independently and flexibly allocated to the PCG.

In FIG. 25, the F-PCSCH is punched on the F-PTCH and transmitted. That is, the F-PCSCH is allocated together with the F-PTCH allocation process. In contrast, the control channel is not punched into the F-STCH. Therefore, in the handover procedure, the UE is allocated an F-PTCH from all base stations of the active sector, and the F-STCH is allocated as necessary. In addition, the base station transmits the F-ACKSCH in the forward direction for early termination of the reverse link channel. In FIG. 25, the F-ACKSCH is transmitted to the forward-indicator control channel (hereinafter referred to as "F-ICCH"). A time division multiplexer (TDM) is transmitted with other indication signals.

28 illustrates an example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention.

In FIG. 28, the base station punches and transmits the F-PCSCH and the F-ACKSCH to the F-PTCH without additionally using the F-ICCH. The example shown in FIG. 28 does not require Walsh code resources for the F-ICCH, but has the disadvantage that the F-PTCH is excessively punched.

29 shows another example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention.

In FIG. 29, the base station performs time division multiplexing with other indicator signals on the F-ICCH and transmits the F-PCSCH and the F-ACKSCH. The example illustrated in FIG. 29 has an advantage of freely selecting a transmission rate of a power control command and a transmission rate of an ACK. Since there is no priority of the basic channels, it is free to assign which channel among F-TCH1 and F-TCH2 and to release which channel in channel allocation.

30 shows another example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention. In FIG. 30, the base station punches and transmits the F-PCSCH to the F-TCH1 and transmits the F-ACKSCH to the F-TCH2.

Embodiments according to the present invention may be implemented by various means, for example, hardware, firmware, software, or a combination thereof. In the hardware implementation, the sleep mode operation method in the wireless communication system according to an embodiment of the present invention is one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs) , Programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors, controllers, microcontrollers, microprocessors, and the like.

In the case of the implementation by firmware or software, the sleep mode operation method in the wireless communication system according to an embodiment of the present invention may be implemented in the form of a module, procedure, function, etc. to perform the functions or operations described above. The software code may be stored in a memory unit and driven by a processor. The memory unit may be located inside or outside the processor, and may exchange data with the processor by various known means.

It will be apparent to those skilled in the art that the present invention can be embodied in other specific forms without departing from the spirit and essential features of the present invention. Accordingly, the above detailed description should not be construed as limiting in all aspects and should be considered as illustrative. The scope of the invention should be determined by reasonable interpretation of the appended claims, and all changes within the equivalent scope of the invention are included in the scope of the invention.

It is obvious that the claims may be combined to form an embodiment by combining claims that do not have an explicit citation relationship in the claims or as new claims by post-application correction.

1 is a diagram illustrating a power control method of a reverse link in a CDMA 2000 system.

2 illustrates an example of applying an early termination scheme to a reverse link traffic channel.

3 is a view showing an example of a method for transmitting a frame while changing the TPR according to an embodiment of the present invention.

4 is a view showing a two-step reduction TPR method according to an embodiment of the present invention.

5 is a diagram illustrating an example of a multi-step change TPR method according to an embodiment of the present invention.

6 is a diagram illustrating a power control method of a forward link.

7 is a diagram illustrating a power control method of a forward link according to an embodiment of the present invention.

8 illustrates a method of controlling an external power control loop of a reverse link according to the first embodiment of the present invention.

9 is a diagram illustrating a method of controlling an external power control loop of a forward link according to a first embodiment of the present invention.

10 is a diagram illustrating a method for controlling an external power control loop of a reverse link according to a second embodiment of the present invention.

11 is a diagram illustrating a method for controlling an external power control loop of a forward link according to a second embodiment of the present invention.

12 is a diagram illustrating a method of controlling an external power control loop of a reverse link according to a third embodiment of the present invention.

13 is a diagram illustrating a method of controlling an external power control loop of a forward link according to a third embodiment of the present invention.

14 is a diagram illustrating a case in which ACK is repeatedly transmitted according to an embodiment of the present invention.

15 is a diagram illustrating a case in which a NACK is repeatedly transmitted according to an embodiment of the present invention.

16 (a) is a diagram illustrating a data rate indicating method according to an embodiment of the present invention on a forward link, and FIG. 16 (b) is a diagram showing a data rate indicating method according to an embodiment of the present invention on a reverse link.

17 (a) is a block diagram of a first base station according to the first embodiment of the present invention, and FIG. 17 (b) is a block diagram of a second base station according to the first embodiment of the present invention.

18 is a configuration diagram of a terminal according to the first embodiment of the present invention.

19 illustrates a data transmission / reception method in a soft handoff environment according to a second embodiment of the present invention.

FIG. 20 (a) shows an encoder structure of convolutional code with the generated polynomial (561,753) and an encoder structure of convolutional code with the generated polynomial (557,751), and FIG. 20 (b) is an encoder combined with two convolutional codes. A diagram showing the structure of the.

FIG. 21 is a diagram illustrating an upper limit of a bit error rate (BER) of each code having a coding rate of 1/2 and a code having a combined coding rate of 1/4.

22 is a configuration diagram of a base station according to the third embodiment of the present invention.

23 is a diagram illustrating an example of a transmission chain of a transmitting end using a wireless configuration according to an embodiment of the present invention.

24 illustrates another example of a transmission chain of a transmitting end using a wireless configuration according to an embodiment of the present invention.

25 is a diagram illustrating a process in which two base stations using a wireless configuration according to an embodiment of the present invention communicate with a terminal in a handoff environment.

26 shows an example of a handoff procedure when using a wireless configuration according to an embodiment of the present invention.

27 shows another example of a handoff process when using a wireless configuration according to an embodiment of the present invention.

28 illustrates an example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention.

29 shows another example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention.

30 shows another example of a configuration of an F-PCSCH and an F-ACKSCH control channel when using a radio configuration according to an embodiment of the present invention.

Claims (22)

A method for receiving data at a terminal in a soft handoff environment of a wireless communication system, Receiving a first sequence in which transmission data is interleaved from a first base station using a first interleaver pattern; And Receiving a second sequence from the second base station in which the transmission data is interleaved using a second interleaver pattern; And Combining and decoding the first sequence and the second sequence before receiving the entire frame to which the first sequence is assigned, And the second sequence is a sequence in which the first sequence is cyclically shifted. delete The method of claim 1, And transmitting an ACK to the first base station and the second base station if the decoding is successfully performed. The method of claim 1, And the second sequence is a sequence in which the first sequence is cyclically shifted by (length / 2 of the first sequence). The method of claim 1, And the first sequence and the second sequence are encoded in a convolutional code. The method of claim 1, And the transmission data is voice data. A terminal for receiving data in a soft handoff environment of a wireless communication system, A receiving module for receiving a first sequence in which transmission data is interleaved using a first interleaver pattern from a first base station, and receiving a second sequence in which the transmission data is interleaved using a second interleaver pattern from a second base station; And And a decoder for combining and decoding the first sequence and the second sequence, wherein the second sequence is a sequence in which the first sequence is cyclically shifted. The method of claim 7, wherein And the decoder combines and decodes the first sequence and the second sequence before receiving the entire frame to which the first sequence is assigned. The method of claim 7, wherein And the second sequence is a sequence in which the first sequence is cyclically shifted by (length / 2 of the first sequence). The method of claim 7, wherein And if the decoding is successfully performed, transmitting an ACK to the first base station and the second base station. The method of claim 7, wherein The first sequence and the second sequence is characterized in that the terminal is encoded in a convolutional code (Convolutional code). The method of claim 7, wherein And the transmission data is voice data. A method for transmitting data in a first base station communicating with a terminal in a soft handoff environment of a wireless communication system, Transmitting a first sequence generated by interleaving transmission data using a first interleaver pattern to the terminal; And Stopping transmission of a frame to which the first sequence is allocated when receiving an acknowledgment (ACK) from the terminal; And wherein the first sequence is different from a second sequence generated by the second base station communicating with the terminal using the second interleaver pattern. The method of claim 13, And wherein the second sequence is a sequence in which the first sequence is cyclically shifted. The method of claim 14, And the second sequence is a sequence in which the first sequence is cyclically shifted by (length / 2 of the first sequence). The method of claim 13, And the first sequence and the second sequence are encoded in a convolutional code. The method of claim 13, And the transmission data is voice data. A base station communicating with a terminal in a soft handoff environment of a wireless communication system, An encoder for encoding the transmission data; And An interleaver for interleaving the encoded data using a first interleaver pattern to generate a first sequence, When the base station receives an acknowledgment (ACK) from the terminal, the base station stops transmitting the frame to which the first sequence is assigned, and the first sequence indicates that the other base station communicating with the terminal transmits the transmission data to the second base station. And a second sequence generated by using an interleaver pattern. The method of claim 18, And the second sequence is a sequence in which the first sequence is cyclically shifted. The method of claim 19, And wherein the second sequence is a sequence in which the first sequence is cyclically shifted by (length / 2 of the first sequence). The method of claim 18, The encoder is characterized in that for encoding the transmission data using a convolutional code (Convolutional code). The method of claim 18, And the transmission data is voice data.

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