JPWO2013084901A1 - motor - Google Patents

Abstract

An induction motor and a synchronous reluctance motor capable of concentrated winding are provided. A motor (100) includes a stator (20) and a rotor (10) arranged so as to be capable of relative movement via a magnetic gap (S). The stator (20) includes a yoke (21) and a magnetic gap from the yoke (21). The plurality of teeth 22 provided so as to protrude toward the S side, and the plurality of windings 23 wound around the teeth 22 by a concentrated winding method. The plurality of teeth 22 are arranged in parallel in the circumferential direction. The teeth groups 24 and 25 comprising the teeth 22 are arranged in two rows in the axial direction, and the first teeth group 24 and the second teeth group 25 adjacent in the axial direction are shifted by 1/2 teeth pitch in the circumferential direction. Are arranged.

Description

  The disclosed embodiment relates to an AC motor.

  For example, a stator that constitutes a rotary motor is a fixing in which steel plates each having an annular yoke, a plurality of teeth protruding radially inward from the yoke, and a slot formed between adjacent teeth are laminated. Has a child iron core. The winding is wound around the teeth while being inserted into the slot of the stator core. There are a concentrated winding method and a distributed winding method for winding the windings. The concentrated winding method is a form in which a winding is wound for each tooth, and the distributed winding method is a form in which a winding is wound across a plurality of teeth. A motor having a stator around which windings are wound by these methods is described in Patent Document 1, for example.

JP 2001-128404 A

  Generally, according to the concentrated winding method, the winding is wound for each tooth, so that the length of the winding end (coil end) protruding from the end of the stator core is shorter than that of the distributed winding method. There is an advantage that the motor can be easily downsized. Further, there is an advantage that the space factor composed of the ratio of the winding cross section to the slot cross section can be easily increased and the production efficiency is high. On the other hand, the distributed winding method has an advantage that the magnetic flux density distribution created by the winding can be made closer to a sine wave.

  By the way, in recent years, due to the soaring of Nd (neodymium) and Dy (dysprosium), which are raw materials for rare earth magnets, motors for making rare earth-free motors are increasing. Induction motors and synchronous reluctance motors are often cited as motors suitable for rare earth free.

  For induction motors and synchronous reluctance motors, it is preferred that the magnetic flux density distribution due to the stator field be close to a sine wave. For this reason, the distributed winding method is generally adopted. However, the downsizing of the physique of the motor is always required as a general technical problem, and the concentrated winding method is more preferable from this viewpoint. Therefore, an induction motor and a synchronous reluctance motor that can adopt a concentrated winding method that can be downsized have been desired.

  The present invention has been made in view of such problems, and an object of the present invention is to provide an induction motor and a synchronous reluctance motor capable of making a winding a concentrated winding.

  In order to solve the above-described problems, according to one aspect of the present invention, a motor including a stator and a mover that are opposed to each other so as to be relatively movable via a magnetic gap, the stator and the moveable Either one of the children has a yoke, a plurality of teeth provided to protrude from the yoke to the magnetic gap side, and a plurality of windings wound in a concentrated winding manner for each of the teeth, The plurality of teeth includes a plurality of teeth arranged in parallel with each other in a direction perpendicular to the relative movement direction, and a group of teeth including a plurality of teeth arranged in parallel in the relative movement direction is adjacent to the direction perpendicular to the relative movement direction. The first tooth group and the second tooth group are applied with motors that are arranged with a 1/2 tooth pitch shift in the relative movement direction.

  According to the present invention, a winding can be concentrated winding in an induction motor or a synchronous reluctance motor.

It is a longitudinal section showing the whole motor composition concerning a 1st embodiment. It is a cross-sectional view equivalent to the II-II cross section in FIG. It is explanatory drawing for demonstrating the structure of the magnetic flux crossing member provided in the front-end | tip of teeth. It is explanatory drawing for demonstrating the arrangement configuration of a tooth | gear, a coil | winding, and a magnetic flux crossing member. It is explanatory drawing for demonstrating the model for analyzing magnetic flux density distribution. It is explanatory drawing for demonstrating the analysis result of magnetic flux density distribution. It is explanatory drawing for demonstrating the modification which uses a magnetic flux crossing member as a plate-shaped member. It is explanatory drawing for demonstrating an example of the detailed structure of the magnetic flux crossing member which is a plate-shaped member. It is explanatory drawing for demonstrating an example of the laminated steel plate of the magnetic flux crossing member which is a plate-shaped member. It is explanatory drawing for demonstrating the variation of a slot combination. It is a longitudinal section showing the whole composition at the time of applying a 1st embodiment to a linear motor. It is a longitudinal section showing the whole motor composition concerning a 2nd embodiment. FIG. 13 is a transverse cross-sectional view corresponding to the XIII-XIII cross section in FIG. 12. It is explanatory drawing for demonstrating the arrangement structure of a tooth | gear and a coil | winding. It is explanatory drawing for demonstrating the function of the slit provided in the cylindrical conductor. It is explanatory drawing for demonstrating the model for analyzing the thrust with respect to a movable part speed. It is explanatory drawing for demonstrating the analysis result of the thrust with respect to a movable part speed. It is a longitudinal cross-sectional view showing the whole structure at the time of applying 2nd Embodiment to a linear motor.

<First Embodiment>
First, a first embodiment will be described with reference to the drawings.

<1-1. Motor configuration>
First, the overall configuration of the motor 100 according to the present embodiment will be described. In this embodiment, the case where the motor 100 is a rotary induction motor using a three-phase alternating current and the slot combination in the cross section is a 2-pole 3-slot (2P3S), which is a permanent magnet synchronous motor, will be described as an example. . As shown in FIGS. 1 and 2, the motor 100 includes a rotating shaft 1, a frame 2, a bracket 3 provided at one end (right side in FIG. 1) of the frame 2, and an outer ring fitted into the bracket 3. A combined bearing 4, a bracket 5 provided at the other end (left side in FIG. 1) of the frame 2, and a bearing 6 in which an outer ring is fitted to the bracket 5 are provided. The rotating shaft 1 is rotatably supported by a bearing 4 and a bearing 6.

  The rotating shaft 1 is provided with a rotor 10 (corresponding to an example of a movable element) so as to have the same axis as the rotating shaft 1. The rotor 10 includes a laminated core body 11 formed by laminating annular steel plates in the axial direction, and a cylindrical conductor 12 made of copper or aluminum fixed to the outer periphery of the laminated core body 11. . A stator 20 is provided on the inner periphery of the frame 2. The rotor 10 and the stator 20 are opposed to each other in the radial direction with the magnetic gap S therebetween, and are configured to be relatively movable in the circumferential direction by the rotation of the rotating shaft 1.

  The configuration of the rotor 10 is not limited to the above, and may be a structure in which both ends of a plurality of rod-shaped conductors that penetrate the outer periphery of the laminated core body 11 are fixed to an end ring (so-called “cage structure”).

  The stator 20 includes a cylindrical yoke 21, a plurality (12 in this example) of teeth 22 projecting from the yoke 21 toward the magnetic gap S (radially inward), and concentrated winding for each of the teeth 22. And a plurality (12 in this example) of windings 23 wound in a manner. The yoke 21 and the teeth 22 are formed by laminating steel plates in the axial direction. The plurality of teeth 22 is configured by a plurality of teeth groups 24 and 25 including a plurality (6 in this example) of teeth 22 arranged in parallel in the circumferential direction arranged in a plurality of rows (two rows in this example) in the axial direction. . Hereinafter, a group of teeth on one axial side (right side in FIG. 1) is referred to as a first tooth group 24, and a group of teeth on the other axial side (left side in FIG. 1) is referred to as a second tooth group 25. As shown in FIG. 4, the first teeth group 24 and the second teeth group 25 that are adjacent to each other in the direction perpendicular to the relative movement direction (the axial direction of the rotating shaft 1; the up and down direction in FIG. 4) Direction (left and right direction in FIG. 4) are shifted by 1/2 tooth pitch. FIG. 4 shows the teeth 22 and the like arranged in the circumferential direction in a state where they are arranged on a plane for convenience of explanation.

  The plurality of windings 23 included in the motor 100 include a first winding group 27 wound around the first tooth group 24 and a second winding group 28 wound around the second tooth group 25. The first winding group 27 and the second winding group 28 are arranged such that the winding direction of the winding 23 is determined in accordance with the slot combination of the motor 100 and the electrical angles of the in-phase are substantially matched. Yes. Specifically, as described above, the slot combination of the motor 100 is a two-pole three-slot (2P3S) as the slot combination in the cross section of the permanent magnet synchronous motor, as shown in FIG. The winding directions of the windings 23 of the group 27 and the second winding group 28 are opposite to each other. Note that U, V, and W shown in FIG. 4 indicate the windings 23 corresponding to the U-phase, V-phase, and W-phase, and the windings 23 that are opposite to the winding directions are U, V, and W, respectively. It is shown (the same applies to other figures). Further, as shown in FIG. 4, the in-phase tooth pitches of the first tooth group 24 and the second tooth group 25 are arranged so as to deviate from each other by approximately 180 degrees in electrical angle. In this way, the first winding group 27 and the second winding group 28 are different from each other in that the windings 23 of the same phase whose winding directions are opposite are shifted by approximately 180 degrees in electrical angle, so that the first teeth group 24 and the second teeth The in-phase teeth pitch of the group 25 is arranged so as to deviate from each other by approximately 180 degrees in electrical angle. As a result, 180 degrees (deviation by winding direction) −180 degrees (deviation by teeth pitch) = 0 degree, The electrical angle is substantially the same.

  A magnetic flux crossing member 26 is provided at the tip of each tooth 22 on the magnetic gap S side. The magnetic flux intersecting member 26 is referred to as a magnetic flux interlinking with a winding 23 (hereinafter referred to as “first winding 23” as appropriate) constituting the first winding group 27 (hereinafter referred to as “first magnetic flux” as appropriate). And a magnetic flux interlinking with a winding 23 (hereinafter referred to as “second winding 23” as appropriate) constituting the second winding group 28 (hereinafter referred to as “second magnetic flux” as appropriate). ) Are members for crossing. FIG. 3 shows the structure of the magnetic flux crossing member 26. For convenience of explanation, FIG. 3 shows three windings corresponding to the U-phase, V-phase, and W-phase among the six windings 23 arranged in the circumferential direction constituting the winding groups 27 and 28. The windings 23 and the like are extracted, and the windings 23 and the like arranged in the circumferential direction are shown in a state of being arranged on a plane. Further, the magnetic flux crossing member 26 corresponding to the first winding group 27 and the magnetic flux crossing member 26 corresponding to the second winding group 28 are arranged to mesh with each other as shown in FIG. In order to facilitate understanding of the structure of the magnetic flux crossing member 26, the magnetic flux crossing member 26 is shown separated. Further, in practice, there is a gap between the windings 23 as shown in FIG. 2, but this gap is not shown in FIG.

  As shown in FIG. 3, the magnetic flux crossing member 26 extends in the axial direction from the tip of the tooth 22 corresponding to one of the first winding 23 and the second winding 23 toward the tip of the tooth 22 corresponding to the other. This is a comb-like member having a plurality of (three in this example) comb teeth 261. Each comb tooth 261 is formed so that the shape seen from the circumferential direction is a substantially triangular shape with a pointed tip on the side of the opposing tooth 22, and is arranged at substantially equal intervals in the circumferential direction in each tooth 22. Has been. As shown in FIG. 4, each magnetic flux crossing member 26 is located between two magnetic flux crossing members 26, 26 opposed to each other by a comb tooth 261 located at the center, and two concave portions formed by three comb teeth 261. By inserting the comb teeth 261 of the two magnetic flux crossing members 26 and 26 facing the 262, the magnetic flux crossing members 26 are arranged so as to mesh with each other with a predetermined gap therebetween. With such a configuration, the first magnetic flux and the second magnetic flux can be efficiently crossed.

  In the present embodiment, the number of comb teeth 261 of each magnetic flux crossing member 26 is three, but the number is not limited to this, and may be two or more. However, an odd number is preferable to an even number. This is because when the number of the comb teeth 261 is an odd number, the number of the recessed portions 262 to be formed is an even number, so that the same number of comb teeth 261 can be meshed with both sides of the comb teeth 261 located at the center. This is because the member 26 can be disposed in a uniform manner without waste (in other words, there is no excess recess 262).

  In the present embodiment, the shape of the comb teeth 261 is substantially triangular as viewed from the circumferential direction. However, the present invention is not limited to this, and other shapes such as a trapezoidal shape or a rectangular shape may be used. .

  With the configuration as described above, a magnetic circuit is configured between the stator 20 of the motor 100 and the laminated iron core body 11, and an eddy current is generated in the cylindrical conductor 12 by passing a magnetic flux through the cylindrical conductor 12. The electromagnetic force generated from the magnetic flux passing through the cylindrical conductor 12 and the magnetic flux generated by the eddy current acts as torque (rotational force) of the rotor 10.

<1-2. Analysis results of magnetic flux density distribution>
The inventors of the present application analyzed the magnetic flux density distribution of the magnetic gap S for two models A and B having different tooth shapes and the like. The analysis result will be described with reference to FIGS. In FIG. 5, the yoke and teeth are separated from the winding to make the tooth shape easier to see.

  Model A shown in FIG. 5 (a) is a model of the general shape of teeth and windings in which the slot combination is a 2-pole 3-slot (2P3S), for example in a permanent magnet synchronous motor. An example model. That is, in the model A, three teeth 22 'are provided so as to protrude from the yoke 21' to the magnetic air gap S side (lower side in FIG. 5), and the three windings 23 'are concentrated winding methods for each tooth 22'. Wrapped in.

  On the other hand, model B shown in FIG. 5B is a model of the tooth and winding shapes corresponding to the present embodiment, which is the same slot combination as model A. That is, in the model B, the first tooth group 24 and the second tooth group 25 are arranged with a 1/2 tooth pitch shift in the relative movement direction. Further, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are opposite to each other, and the in-phase windings 23 (the winding direction is opposite) are shifted from each other by approximately 180 degrees in electrical angle. Has been placed. A magnetic flux crossing member 26 having three comb teeth 261 is provided at the tip of each tooth 22.

  FIG. 6A shows the magnetic flux density distribution of the magnetic air gap S in the central cross section of the model A and model B in the steel plate lamination direction (axial direction of the rotating shaft 1). As shown in FIG. 6A, it can be seen that the magnetic flux density distribution in the model B is closer to a sine wave than in the model A. Moreover, the Fourier analysis result about the magnetic flux density distribution of the model A and the model B is shown in FIG.6 (b) and FIG.6 (c), respectively. As shown in FIG. 6B, in the model A, the magnetic flux density distribution is not a sine wave distribution including only the primary component (fundamental wave) but includes a harmonic component. It can be seen that the secondary component of the harmonic components is about 60% of the primary component and is particularly large.

  On the other hand, as shown in FIG. 6C, in the model B, the secondary component is almost 0, and the total of all the harmonic components other than the primary component is 13% or less of the primary component. This is because the primary component of the first magnetic flux interlinked with the first winding 23 and the second magnetic flux interlinked with the second winding 23 have the same electrical angle phase and the same magnitude, but the secondary component is This is because the same magnitude and direction are opposite at the same electrical angle, and the second component can be canceled out by crossing the first magnetic flux and the second magnetic flux by the magnetic flux crossing member 26. Therefore, it can be seen from the Fourier analysis result that the magnetic flux density distribution in model B approaches a sine wave.

<1-3. Effects of First Embodiment>
In the motor 100 of the present embodiment, the stator 20 has a first tooth group 24 and a second tooth group 25 arranged with a 1/2 tooth pitch shifted in the circumferential direction. The wire 23 is wound by a concentrated winding method. The winding directions of the windings 23 of the first winding group 27 and the second winding group 28 wound around the first tooth group 24 and the second tooth group 25 are determined according to the slot combination, and the same It arrange | positions so that the electrical angle of phases may correspond substantially. By doing in this way, as above-mentioned, the 1st magnetic flux and the 2nd magnetic flux can be made to cross, and the secondary component with especially big influence can be canceled mutually. Therefore, the magnetic flux density distribution can be mainly made only of the primary component, and a magnetic flux density distribution close to a sine wave can be created while the winding 23 is concentrated winding. As a result, it is possible to apply concentrated winding to an induction motor or a synchronous reluctance motor that is a motor suitable for rare earth-free, and it is possible to achieve a rare earth-free while miniaturizing the motor.

  In the present embodiment, in particular, a magnetic flux crossing member 26 is provided at each of the tips of the plurality of teeth 22, and the magnetic flux crossing member 26 links the first magnetic flux interlinked with the first winding 23 and the second winding 23. Cross the intersecting second magnetic flux. Thereby, the first winding 23 and the second winding 23 can be arranged on one side of the magnetic gap S (in the present embodiment, on the outer peripheral side). As a result, the following effects are obtained. That is, in order to cancel the secondary component of the magnetic flux density distribution, for example, two stators are arranged opposite to each other on both the axial and radial sides of the rotor, and the winding direction of the windings between the two stators It is conceivable that the windings in the same phase are arranged so as to be shifted by approximately 180 degrees in electrical angle. In this case, it can be applied only to a motor having a special structure in which stators are arranged on both sides of the rotor, and there is a problem that versatility is low. On the other hand, in the present embodiment, by providing the magnetic flux crossing member 26, one stator 20 is arranged on one side (in this example, radially outside) of the rotor 10, and the first among the stators 20 is arranged. In addition, the winding directions of the second winding 23 and the second winding 23 can be opposite to each other, and the first and second windings 23 having the same phase can be arranged so as to deviate from each other by approximately 180 degrees in electrical angle. Therefore, it can be applied to a motor having a widely used structure in which the stator 20 is disposed outside the rotor 10, and there is an advantage that versatility is high.

  In the present embodiment, in particular, the magnetic flux crossing member 26 is a comb-like member having a plurality of comb teeth 261, whereby the first magnetic flux and the second magnetic flux are efficiently crossed, and the secondary component of the magnetic flux density distribution. The offset effect can be enhanced. In particular, by setting the number of the comb teeth 261 to an odd number, the magnetic flux crossing member 26 having a good symmetry, in which one comb tooth 261 is located at the center and the same number of concave portions 262 are symmetrically arranged on both sides thereof. Can do. As a result, the magnetic flux crossing members 26 can be disposed in a regular manner with no waste (no extra concave portions 262), and the secondary component canceling effect of the magnetic flux density distribution can be enhanced.

<1-4. Modification>
In addition, it is not restricted to the said 1st Embodiment, A various deformation | transformation is possible within the range which does not deviate from the meaning and technical idea. Hereinafter, such modifications will be described in order.

(1) When the magnetic flux crossing member is a plate-like member In the first embodiment, the magnetic flux crossing member 26 is a comb-like member having a plurality of comb teeth 261. However, the shape of the magnetic flux crossing member is limited to this. Not what you want. For example, the magnetic flux crossing member may be a plate-like member. This modification will be described with reference to FIGS. 7 and 8 are shown in a state where the teeth 22 and the like arranged in the circumferential direction are partially extracted and arranged on a plane as in FIG. 3 and the like for convenience of explanation. ing.

  As shown in FIG. 7, in the present modification, the magnetic flux crossing member 29 is a plate-like member that connects the tip of the tooth 22 corresponding to the first winding 23 and the tip of the tooth 22 corresponding to the second winding 23 ( As a result of laminating steel plates in the circumferential direction, the whole is formed into a plate shape). As in the above embodiment, the first tooth group 24 and the second tooth group 25 are arranged with a 1/2 tooth pitch shift in the relative movement direction, and the windings of the first winding group 27 and the second winding group 28 are arranged. The winding directions of the wires 23 are opposite to each other, and the in-phase windings 23 (the winding directions are opposite) are arranged so as to be shifted from each other by approximately 180 degrees in electrical angle.

  An example of the detailed structure of the magnetic flux crossing member 29 is shown in FIGS. 8 and 9, the yoke 21 is not shown. As shown in FIGS. 8 and 9, the tooth 22 and the magnetic flux crossing member 29 are formed by laminating three types of steel plates 291, 292, and 293 in the circumferential direction via an adhesive layer 294. Also in this modification, the same effect as the above-described embodiment can be obtained. Furthermore, in the above embodiment, the laminated structure is complicated because the shape of the magnetic flux crossing member 26 is complicated. However, according to the present modification, a plurality of simple shapes of steel plates can be laminated and formed. The structure of the child 20 can be simplified.

(2) Variation of slot combination In the first embodiment, the case where the slot combination of the motor 100 is a two-pole three-slot (2P3S), which is a permanent magnet synchronous motor, has been described as an example. However, the present invention can be applied to motors of various slot combinations. An example of applicable slot combinations is shown in FIG.

  As shown in FIG. 10A, the slot combination may be applied to a motor having two poles and three slots (2P3S). In this case, since the tooth pitch is 120 degrees in electrical angle as in the above embodiment, the in-phase pitch interval in the first teeth group 24 and the second tooth group 25 is shifted by 1.5 teeth pitch, and the electrical angle is 180 degrees. Degree of deviation (120 degrees x 1.5 teeth pitch). Furthermore, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are opposite to each other, and are arranged so as to be deviated by approximately 180 degrees in electrical angle, thereby 180 degrees (deviation due to teeth pitch) − 180 degrees (displacement due to the winding direction) = 0 degrees, and the electrical angles of the in-phases can be substantially matched.

  Further, as shown in FIG. 10B, the slot combination may be applied to a motor having four poles and three slots (4P3S). In this case, since the teeth pitch is 240 degrees in electrical angle, the pitch interval of the in-phase in the first teeth group 24 and the second teeth group 25 is shifted by 1.5 teeth pitch, and the electrical angle is 360 degrees (240 degrees × 1. 5 teeth pitch). Further, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are the same, and are arranged at an electrical angle of approximately 0 degrees, so that 360 degrees (deviation due to the teeth pitch)-0 degrees (Displacement due to the winding direction) = 360 degrees = 0 degrees (electrical angle), so that the electrical angles of the in-phases can be substantially matched.

  Further, as shown in FIG. 10C, the slot combination may be applied to an 8-pole 9-slot (8P9S) motor. In this case, since the teeth pitch is 160 degrees in electrical angle, the in-phase pitch interval in the first teeth group 24 and the second teeth group 25 is shifted by 4.5 teeth pitch, and the electrical angle is 720 degrees (160 degrees × 4. 5 teeth pitch). Furthermore, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are the same as shown in FIG. (Displacement due to teeth pitch) −0 degree (displacement due to winding direction) = 720 degrees = 0 degree (electrical angle), so that the electrical angles of the in-phases can be substantially matched.

  Further, as shown in FIG. 10D, the slot combination may be applied to a motor having 10 poles and 9 slots (10P9S). In this case, since the teeth pitch is 200 degrees in electrical angle, the in-phase pitch interval in the first teeth group 24 and the second teeth group 25 is shifted by 4.5 teeth pitch, and the electrical angle is 900 degrees (200 degrees × 4. 5 teeth pitch). Furthermore, by arranging the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 to be opposite to each other as shown in FIG. 900 degrees (deviation due to teeth pitch) −180 degrees (deviation due to winding direction) = 720 degrees = 0 degrees (electrical angle), so that the electrical angles of the in-phases can be substantially matched.

  Further, as shown in FIG. 10 (e), the slot combination may be applied to a motor having 10 poles and 12 slots (10P12S). In this case, since the teeth pitch is 150 degrees in electrical angle, the in-phase pitch interval in the first teeth group 24 and the second teeth group 25 is shifted by 2.5 teeth pitch, and the electrical angle is 375 degrees (150 degrees × 2. 5 teeth pitch). Further, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are the same as shown in FIG. (Displacement due to teeth pitch) −0 degrees (deviation due to winding direction) = 375 degrees (≈0 degrees), so that the electrical angle between the in-phases can be within the vicinity.

  Further, as shown in FIG. 10 (f), the slot combination may be applied to a motor having 14 poles and 12 slots (14P12S). In this case, since the teeth pitch is 210 degrees in electrical angle, the in-phase pitch interval in the first teeth group 24 and the second teeth group 25 is shifted by 2.5 teeth pitch, and the electrical angle is 525 degrees (210 degrees × 2. 5 teeth pitch). Furthermore, by arranging the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 to be opposite to each other as shown in FIG. 525 degrees (deviation due to teeth pitch) -180 degrees (deviation due to winding direction) = 345 degrees (≈0 degrees), so that the electrical angle between the in-phases can be within the vicinity range.

  Even when the present invention is applied to the above-described slot combination motor, the same effects as those of the first embodiment can be obtained.

(3) When applied to a linear motor The configuration according to the first embodiment and the modification described above can also be applied to a linear motor. This modification will be described with reference to FIG.

  In this modification, the case where the motor 200 is a linear induction motor will be described as an example. As shown in FIG. 11, the motor 200 includes a stator 220 and a mover 210 that are opposed to each other so as to be relatively movable in the left-right direction in FIG.

  The stator 220 includes a flat yoke 221, a plurality of teeth 222 provided so as to protrude from the yoke 221 toward the magnetic gap S, and a plurality of windings 223 wound around each of the teeth 222 by a concentrated winding method. have. The plurality of teeth 222 is a direction in which the teeth groups 224 and 225 (only the teeth group 224 is shown in FIG. 11) composed of a plurality of teeth 222 arranged in parallel in the relative movement direction (left and right direction in FIG. 11). The first teeth group 224 and the second teeth group 225, which are arranged in a plurality of rows (in a direction perpendicular to the paper surface in FIG. 11) and are adjacent to each other in the direction perpendicular to the relative movement direction, are ½ teeth in the relative movement direction. The pitch is shifted. Further, in the first winding group 227 wound around the first tooth group 224 and the second winding group 228 (not shown) wound around the second tooth group 225, the winding direction of the winding 223 is the same as that of the motor 200. It is determined according to the slot combination, and is arranged so that the electrical angles of the in-phases are substantially the same. Furthermore, a magnetic flux crossing member 226 (not shown) is provided at the tip of each tooth 222 on the magnetic gap S side, as in the above-described embodiment.

  On the other hand, the mover 210 includes a secondary conductor 211 made of copper or aluminum, and an iron plate 212 fixed to the side opposite to the magnetic gap S of the secondary conductor 211. A magnetic circuit is formed between the stator 220 and the iron plate 212, and a magnetic flux is passed through the secondary conductor 211, thereby generating an eddy current in the secondary conductor 211 and passing through the secondary conductor 211. An electromagnetic force generated from the magnetic flux generated by the magnetic flux and the eddy current acts as a thrust of the mover 210.

  Also in the present modification applied to the linear motor, the same effect as in the first embodiment can be obtained.

<Second Embodiment>
Next, a second embodiment will be described with reference to the drawings. In the first embodiment, the magnetic flux crossing member 26 is provided at the tip of the tooth 22, and the first magnetic flux interlinked with the first winding 23 and the second magnetic flux interlinked with the second winding 23 are crossed. Although the structure cancels out the secondary component of the magnetic flux density distribution, it is not limited to this. In the second embodiment, by providing a plurality of slits on the secondary conductor, the induced voltage generated by the secondary component of the magnetic flux density distribution is canceled.

<2-1. Motor configuration>
The overall configuration of the motor 100A according to the present embodiment will be described. Also in the present embodiment, as in the first embodiment, the motor 100A is a rotary induction motor using a three-phase alternating current, and the slot combination in the cross section is a 2-pole 3-slot (a permanent magnet synchronous motor). 2P3S) will be described as an example.

  As shown in FIGS. 12 and 13, the stator 20 includes a cylindrical yoke 21 and a plurality (12 in this example) of teeth protruding from the yoke 21 toward the magnetic gap S (radially inward). 22A and a plurality (12 in this example) of windings 23 wound in a concentrated winding method for each tooth 22A. The yoke 21 and the teeth 22A are formed by laminating steel plates in the axial direction. The plurality of teeth 22A is configured by a plurality of teeth groups 24 and 25 including a plurality (six in this example) of teeth 22A arranged in parallel in the circumferential direction arranged in a plurality of rows (two rows in this example) in the axial direction. . In the present embodiment, no magnetic flux crossing member is provided at the tip of each tooth 22A on the magnetic gap S side, and each tooth 22A is formed in a prismatic shape.

  Hereinafter, the tooth group on one axial side (right side in FIG. 12) is referred to as a first tooth group 24, and the tooth group on the other axial side (left side in FIG. 12) is referred to as a second tooth group 25. As shown in FIG. 14, the first teeth group 24 and the second teeth group 25 adjacent to each other in the direction perpendicular to the relative movement direction (the axial direction of the rotary shaft 1; the up-down direction in FIG. 14) Direction (left and right direction in FIG. 14) with a 1/2 tooth pitch shift. For convenience of explanation, FIG. 14 shows the teeth 22 and the like arranged in the circumferential direction on a plane.

  The plurality of windings 23 included in the motor 100 </ b> A include a first winding group 27 wound around the first tooth group 24 and a second winding group 28 wound around the second tooth group 25. The first winding group 27 and the second winding group 28 are arranged such that the winding direction of the winding 23 is determined in accordance with the slot combination of the motor 100 and the electrical angles of the in-phase are substantially matched. Yes. Specifically, since the slot combination of the motor 100 is the two-pole three-slot (2P3S) in the cross section of the permanent magnet synchronous motor as described above, as shown in FIG. The winding directions of the windings 23 of the group 27 and the second winding group 28 are opposite to each other. Further, as shown in FIG. 14, the in-phase tooth pitches of the first tooth group 24 and the second tooth group 25 are arranged so as to deviate from each other by approximately 180 degrees in electrical angle. In this way, the first winding group 27 and the second winding group 28 are different from each other in that the windings 23 of the same phase whose winding directions are opposite are shifted by approximately 180 degrees in electrical angle, so that the first teeth group 24 and the second teeth The in-phase teeth pitch of the group 25 is arranged so as to deviate from each other by approximately 180 degrees in electrical angle. As a result, 180 degrees (deviation by winding direction) −180 degrees (deviation by teeth pitch) = 0 degree, The electrical angle is substantially the same.

  The rotor 10 includes a laminated core body 11 formed by laminating annular steel plates in the axial direction, and a cylindrical conductor 12A (secondary conductor made of copper or aluminum) fixed to the outer periphery of the laminated core body 11. Equivalent to an example). As shown in FIG. 13, the cylindrical conductor 12 </ b> A includes a plurality of slits 31 along the direction perpendicular to the relative movement direction (the axial direction of the rotating shaft 1, the direction perpendicular to the paper surface in FIG. 13). Each slit 31 is formed so as to penetrate the cylindrical conductor 12A in the radial direction, and is arranged at substantially equal intervals over the entire circumferential direction of the cylindrical conductor 12A.

  The cylindrical conductor 12A provided with the slit 31 may be formed by cutting a cylindrical conductor using a circular saw or the like, or formed by arranging rod-shaped conductors having recesses corresponding to the slit 31 in the circumferential direction. May be. In these cases, each slit 31 is a gap. Further, the insulator portion may be the slit 31 by laminating a rod-shaped conductor and an insulator in the circumferential direction. In this case, each slit 31 is filled with an insulator. The other configuration of the motor 100A is the same as that of the motor 100 described above.

<2-2. Induced voltage generated in cylindrical conductor>
Next, the function of the slit 31 will be described with reference to FIG. In FIG. 15, for convenience of explanation, the cylindrical conductor 12A is shown in a plate shape. Further, the length of the arrow in FIG. 15 indicates the magnitude of the induced voltage.

  In FIG. 15A, the area 12A1 on the near side in the figure corresponds to the first winding group 27 wound around the first teeth group 24, and the area 12A2 on the back side in the figure is wound around the second teeth group 25. This corresponds to the second winding group 28. The first teeth group 24 and the second teeth group 25 are disposed in the respective regions 12A1 and 12A2 of the cylindrical conductor 12A by being displaced by a 1/2 tooth pitch in the relative movement direction (left and right direction in FIG. 15). The induced voltage has a distribution as shown in FIG. By providing the slits 31, the induced voltage generated by the secondary component is canceled out in each current path of the cylindrical conductor 12 </ b> A between the slits 31, and only the induced voltage generated by the primary component can be extracted. Become. As a result, as shown in FIG. 15B, the distribution of the induced voltage generated in the cylindrical conductor 12A has a shape close to a sine wave.

<2-3. Analysis results of torque (thrust) against rotor speed (moving part speed)>
The inventors of the present application examined the torque with respect to the rotor speed for the two models A and C. However, for convenience of analysis, the inventors of the present application analyze as a linear motor and analyze the thrust against the moving part speed. The analysis result will be described with reference to FIGS. In FIG. 16, for convenience of explanation, the cylindrical conductor is illustrated in a plate shape.

  Model A shown in FIG. 16A is the same as that shown in FIG. The cylindrical conductor 12 is not provided with a slit. On the other hand, model C shown in FIG. 16B is a model of the tooth and winding shapes corresponding to the present embodiment, which is the same slot combination as model A. That is, in the model C, the first teeth group 24 and the second teeth group 25 are arranged with a 1/2 tooth pitch shift in the relative movement direction. Further, the winding directions of the windings 23 of the first winding group 27 and the second winding group 28 are opposite to each other, and the in-phase windings 23 (the winding direction is opposite) are shifted from each other by approximately 180 degrees in electrical angle. Has been placed. Each tooth 22 has a prismatic shape, and the cylindrical conductor 12A is provided with a plurality of slits 31 along a direction perpendicular to the relative movement direction.

  FIG. 17A shows the analysis result of the thrust with respect to the moving part speed of model A. FIG. As shown in FIG. 17A, in model A, the thrust when the moving part speed is 2.4 m / s is about 20% or less of the thrust when the moving part speed is 0 m / s. The thrust has dropped significantly. That is, it can be seen that in the induction motor employing concentrated winding, the torque (thrust) decreases as the rotor speed (movable part speed) increases. As shown in FIG. 6B described above, in the model A, the magnetic flux density distribution includes not only the primary component but also the harmonic component. Therefore, it is presumed that the reason why the thrust is reduced in this way is a harmonic component having a different order from the primary component contributing to the thrust. That is, since the traveling direction of the primary component and the secondary component is opposite, when changing the rotor speed (moving part speed), either the slip frequency for the primary component or the slip frequency for the secondary component is selected. However, it can only be made constant. For this reason, when the rotor speed (movable part speed) is changed while the slip frequency for the primary component is constant, the slip frequency for the secondary component also changes as the rotor speed (movable part speed) changes. It is considered that the influence of the secondary component on the thrust changes and the torque (thrust) decreases.

  On the other hand, as shown in FIG. 17 (b), in model C, the thrust is hardly reduced even when the moving part speed is changed from 0 m / s to 2.4 m / s. This is presumably because in Model C, only the primary component contributes to the thrust, and the influence of the secondary component on the thrust is eliminated. Therefore, it can be seen that the induced voltage generated by the secondary component of the magnetic flux density can be canceled by providing the slit 31 in the cylindrical conductor 12A.

<2-4. Effect of Second Embodiment>
In the motor 100A of the present embodiment, the cylindrical conductor 12A includes a plurality of slits 31 along a direction perpendicular to the relative movement direction. Thereby, the induced voltage generated by the secondary component of the magnetic flux density is canceled out, and the distribution of the induced voltage generated in the cylindrical conductor 12A can be made a shape close to a sine wave. That is, according to the present embodiment, the magnetic flux density distribution close to a sine wave is created by providing the slit 31 in the cylindrical conductor 12A without providing the magnetic flux crossing member at the tip of the tooth 22 as in the first embodiment. The same effect as that obtained can be obtained. As a result, it is possible to apply concentrated winding to an induction motor or a synchronous reluctance motor that is a motor suitable for rare earth-free, and it is possible to achieve a rare earth-free while miniaturizing the motor. Further, since the concentrated winding induction linear motor can be realized, the copper loss on the primary side can be reduced and the number of assembly steps can be reduced as compared with the distributed winding induction linear motor.

<2-5. Modification>
In addition, it is not restricted to the said 2nd Embodiment, A various deformation | transformation is possible within the range which does not deviate from the meaning and technical idea. For example, as shown in FIG. 18, the configuration according to the second embodiment described above can be applied to a linear motor. In the motor 200A, the secondary conductor 211A of the mover 210 includes a plurality of slits 231 along a direction perpendicular to the relative movement direction (direction perpendicular to the paper surface in FIG. 18). The slits 231 are formed so as to penetrate the secondary conductor 211A and are arranged at substantially equal intervals over the entire relative movement direction of the secondary conductor 211A. The other configuration of the motor 200A is the same as that of the motor 200 shown in FIG. Also in the present modification applied to the linear motor, the same effect as in the second embodiment can be obtained.

  Further, the configuration according to the second embodiment can be applied to motors of various slot combinations shown in FIG. 10 as in the first embodiment.

  In the first and second embodiments described above, the case where the motor is an induction motor has been described as an example. However, the present invention is not limited to this and can be applied to a reluctance motor. Also, in the above, as an example, the configuration in which the first tooth group and the second tooth group adjacent to each other in the direction perpendicular to the relative movement direction are arranged on the stator side with a shift of 1/2 tooth pitch in the relative movement direction is taken as an example. Although described, it is not limited to this, and it may be provided on the mover side.

  In the first and second embodiments, the case where the motor is an inner rotor type in which the rotor 10 is provided inside the stator 20 has been described as an example. However, the rotor 10 is disposed outside the stator 20. The present invention can also be applied to an outer rotor type motor provided.

  In addition to those already described above, the methods according to the above-described embodiments and modifications may be used in appropriate combination.

  In addition, although not illustrated one by one, the present invention is implemented with various modifications within a range not departing from the gist thereof.

S Magnetic gap 10 Rotor (mover)
12A Cylindrical conductor (secondary conductor)
20 Stator 21 Yoke 22 Teeth 22A Teeth 23 Winding, First Winding, Second Winding 24 First Teeth Group 25 Second Teeth Group 26 Magnetic Flux Crossing Member 27 First Winding Group 28 Second Winding Group 29 Magnetic Flux Cross member 31 Slit 100 Motor 100A Motor 200 Motor 200A Motor 210 Movable element 211A Secondary side conductor 220 Stator 221 Yoke 222 Teeth 223 Winding 224 First teeth group 227 First winding group 231 Slit 261 Comb teeth

Claims (7)

A motor having a stator and a mover which are arranged so as to be capable of relative movement via a magnetic gap;
One of the stator and the mover is
York,
A plurality of teeth provided protruding from the yoke to the magnetic gap side;
A plurality of windings wound in a concentrated winding manner for each of the teeth,
The plurality of teeth are:
A group of teeth each including a plurality of teeth arranged in parallel in the relative movement direction are arranged in a plurality of rows in a direction perpendicular to the relative movement direction, and the first teeth group and the second teeth adjacent in the direction perpendicular to the relative movement direction The motor is characterized in that the teeth group is arranged with a 1/2 tooth pitch shift in the relative movement direction. The plurality of windings are:
A first winding group wound around the first tooth group; and a second winding group wound around the second tooth group; the windings of the first winding group and the second winding group The motor according to claim 1, wherein the winding direction is determined according to a slot combination of the motor, and the electrical angles of the in-phases are arranged so as to be substantially coincident or in the vicinity range. A first magnetic flux provided at each of the tips of the plurality of teeth and interlinked with the first winding constituting the first winding group and the second winding constituting the second winding group. The motor according to claim 2, further comprising a magnetic flux crossing member for crossing the two magnetic fluxes. The magnetic flux crossing member is
It is a comb-like member having a plurality of comb teeth formed from the tip of the tooth corresponding to one of the first winding and the second winding toward the tip of the tooth corresponding to the other. The motor according to claim 3. The motor according to claim 4, wherein the number of the comb teeth is an odd number. The magnetic flux crossing member is
4. The motor according to claim 3, wherein the motor is a plate-like member that connects the tip of the tooth corresponding to the first winding and the tip of the tooth corresponding to the second winding. One of the stator and the mover is
The motor according to claim 1, further comprising a secondary-side conductor having a plurality of slits along a direction perpendicular to the relative movement direction.

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