JPS6412181B2 - - Google Patents
Info
- Publication number
- JPS6412181B2 JPS6412181B2 JP59052962A JP5296284A JPS6412181B2 JP S6412181 B2 JPS6412181 B2 JP S6412181B2 JP 59052962 A JP59052962 A JP 59052962A JP 5296284 A JP5296284 A JP 5296284A JP S6412181 B2 JPS6412181 B2 JP S6412181B2
- Authority
- JP
- Japan
- Prior art keywords
- output
- voltage
- power supply
- resistor
- output current
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 238000001514 detection method Methods 0.000 claims description 30
- 230000010355 oscillation Effects 0.000 claims description 8
- 238000010586 diagram Methods 0.000 description 8
- 239000003990 capacitor Substances 0.000 description 4
- 238000009499 grossing Methods 0.000 description 2
- 230000020169 heat generation Effects 0.000 description 2
- 230000002265 prevention Effects 0.000 description 2
- 230000003247 decreasing effect Effects 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000012886 linear function Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Direct Current Feeding And Distribution (AREA)
- Dc-Dc Converters (AREA)
Description
【発明の詳細な説明】
本発明は、出力垂下特性を有する電源装置に関
する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a power supply device having output drooping characteristics.
従来より、複写機などに用いられる電源装置
は、温度ドリフトを補償し複写むら発生を防止す
る等の目的により、第１図に示すように出力電圧
V0、出力電流I0の特性にある一定の勾配をもたせ
たいわゆる出力垂下特性が要求される。このた
め、従来の電源装置では、第２図に示すように高
圧トランスT0の二次側の出力段に出力抵抗R0を
設け、この出力抵抗R0による電圧降下により所
要の出力垂下特性を得ている。ところが、このよ
うな装置では、出力抵抗R0に高圧が加わる関係
上、該抵抗R0は高耐圧用のものが必要となり、
また、形状も大きくなる。さらに、出力抵抗R0
の電力損失が大きいと、この抵抗R0自体の発熱
や、発振トランジスタの効率低下による対策のた
めヒートシンクの形状も大きくせねばならず、こ
れらのために、装置が大型化、高価になり小型、
低廉化が図れないという問題がある。 Conventionally, power supplies used in copying machines and the like have been designed to adjust the output voltage as shown in Figure 1 in order to compensate for temperature drift and prevent uneven copying.
A so-called output droop characteristic is required in which the characteristics of V 0 and output current I 0 have a certain slope. For this reason, in conventional power supplies, an output resistor R 0 is provided at the output stage on the secondary side of the high-voltage transformer T 0 as shown in Figure 2, and the voltage drop caused by this output resistor R 0 provides the required output droop characteristics. It has gained. However, in such a device, since a high voltage is applied to the output resistor R0 , the resistor R0 needs to be a high voltage resistor.
Also, the shape becomes larger. Additionally, the output resistance R 0
If the power loss is large, the shape of the heat sink must be made larger to counter the heat generation of this resistor R0 itself and the reduction in efficiency of the oscillation transistor, which makes the device larger and more expensive.
There is a problem that the price cannot be lowered.
本発明は従来のかかる問題点を解決し、小型
化、低廉化が図れ、しかも効率を損うことなく所
要の出力垂下特性が設定できるようにすることを
目的とする。 SUMMARY OF THE INVENTION An object of the present invention is to solve these conventional problems, to achieve miniaturization and cost reduction, and to set a required output droop characteristic without impairing efficiency.
本発明は、このような目的を達成するため、高
圧トランスの二次側の出力電圧、出力電流を共に
検出し、これを一次側にフイードバツクして高圧
トランスの一次側の発振回路を制御するように構
成したものである。 In order to achieve such an object, the present invention detects both the output voltage and output current on the secondary side of a high voltage transformer, and controls the oscillation circuit on the primary side of the high voltage transformer by feeding this back to the primary side. It is composed of
以下、本発明を実施例について図面に基づいて
詳細に説明する。なお、この実施例では複写機に
適用した場合について説明する。 DESCRIPTION OF THE PREFERRED EMBODIMENTS The present invention will be described in detail below with reference to the drawings. In this embodiment, a case where the present invention is applied to a copying machine will be explained.
第３図はこの実施例の負の出力電圧、電流が得
られるようにした電源装置の回路図である。この
電源装置１は高圧トランスＴを備える。高圧トラ
ンスＴの一次側のコイルN1には、発振トランジ
スタTrのコレクタが接続されている。また、発
振トランジスタTrは、エミツタが接地され、ベ
ースにはベース電流制御用の制御回路２が接続さ
れている。一方、高圧トランスＴの二次側のコイ
ルN2には整流ダイオードD2、平滑コンデンサC2
でなる整流回路および火花放電防止用抵抗R2が
順次接続されている。RLはこの電源装置１の出
力端子４に接続された複写機のチヤージヤ負荷で
ある。さらに、この電源装置１には、高圧トラン
スＴの一次側と二次側との間に出力電圧検出回路
６、出力電流検出回路８および出力電圧検出回路
６の出力電圧と出力電流検出回路８の出力電圧と
を比較する比較手段、本例では比較増幅器１０と
が設けられている。上記出力電圧検出回路６は、
高圧トランスＴの二次側の出力電圧V0を検出す
る出力電圧検出抵抗RH、分圧用抵抗R1および電
圧引上用の補助電圧電源Vkでなる直列回路と、
この直列回路の分圧用抵抗R1および補助電圧電
源Vkに対して並列接続されたノイズ除去用コン
デンサC4とで構成される。そして、出力電圧検
出抵抗RHの一端が火花放電防止用抵抗R2と出力
端子４の中点X1に、また、補助電圧電源Vkの負
極側が接地され、さらに出力電圧検出抵抗RHと
分圧抵抗R1との接続点X2が前記比較増幅器１０
の非反転入力端子（＋）に接続されている。前記
出力電流検出回路８は、高圧トランスＴの二次側
の出力電圧I0を検出する出力電流検出抵抗Rfを基
準電圧電源Vsとでなる直列回路にノイズ除去用
コンデンサC3を並列接続して構成される。そし
て、出力電流検出抵抗Rfの一端が、高圧トラン
スＴの二次側のコイルN2と、平滑コンデンサC2
との接続点X3と比較増幅器１０の反転入力端子
（−）とにそれぞれ共通に接続され、基準電圧電
源Vsの負極側が接地されている。また、比較増
幅器１０の出力端子は制御回路２に接続されてい
る。なお１２は高圧トランスＴの電源入力端子で
ある。 FIG. 3 is a circuit diagram of a power supply device that can obtain negative output voltage and current according to this embodiment. This power supply device 1 includes a high voltage transformer T. The collector of the oscillation transistor Tr is connected to the coil N1 on the primary side of the high voltage transformer T. Further, the emitter of the oscillation transistor Tr is grounded, and the base thereof is connected to a control circuit 2 for base current control. On the other hand, a rectifier diode D 2 and a smoothing capacitor C 2 are connected to the secondary coil N 2 of the high voltage transformer T.
A rectifier circuit and a spark discharge prevention resistor R2 are connected in sequence. R L is a charge load of the copying machine connected to the output terminal 4 of this power supply device 1. Furthermore, in this power supply device 1, an output voltage detection circuit 6, an output current detection circuit 8, and an output voltage of the output voltage detection circuit 6 and an output current detection circuit 8 are provided between the primary side and the secondary side of the high voltage transformer T. Comparing means for comparing the output voltage with the output voltage, in this example, a comparison amplifier 10 is provided. The output voltage detection circuit 6 is
a series circuit consisting of an output voltage detection resistor R H for detecting the output voltage V 0 on the secondary side of the high voltage transformer T, a voltage dividing resistor R 1 and an auxiliary voltage power supply Vk for voltage pull-up;
This series circuit is composed of a voltage dividing resistor R 1 and a noise removal capacitor C 4 connected in parallel to the auxiliary voltage power supply Vk. One end of the output voltage detection resistor R H is connected to the midpoint X 1 of the spark discharge prevention resistor R 2 and the output terminal 4, and the negative electrode side of the auxiliary voltage power supply Vk is grounded, and is further connected to the output voltage detection resistor R H. The connection point X 2 with the piezoresistor R 1 is the comparison amplifier 10
Connected to the non-inverting input terminal (+) of The output current detection circuit 8 is constructed by connecting a noise removal capacitor C3 in parallel to a series circuit consisting of an output current detection resistor Rf for detecting the output voltage I0 on the secondary side of the high voltage transformer T and a reference voltage power supply Vs. configured. One end of the output current detection resistor Rf is connected to the secondary coil N2 of the high voltage transformer T and the smoothing capacitor C2.
and the inverting input terminal (-) of the comparison amplifier 10 , respectively, and the negative electrode side of the reference voltage power supply Vs is grounded. Further, the output terminal of the comparator amplifier 10 is connected to the control circuit 2. Note that 12 is a power input terminal of the high voltage transformer T.
このような構成において、チヤージヤ負荷RL
が接続されている場合には、高圧トランスＴで発
生する出力電流I0は第３図に示すように出力電流
検出抵抗Rfを流れる。今、所定の出力電流I0が流
れている場合、比較増幅器の反転入力端子（−）
には出力電流検出抵抗Rfを流れる出力電流I0によ
る電圧降下分に基準電圧電源Vsの基準電圧を重
畳した電圧が加わる。一方、非反転入力端子
（＋）には出力電圧検出抵抗RHと分圧抵抗R1とで
分圧された電圧に補助電圧電源Vkの電圧を重畳
した電圧が加わる。従つて、比較増幅器１０の非
反転、反転の各入力端子（＋）（−）に同じレベ
ルの電圧が加わるように設定したときには次式が
成立する。 In such a configuration, the charge load R L
is connected, the output current I 0 generated by the high voltage transformer T flows through the output current detection resistor Rf as shown in FIG. Now, if a predetermined output current I 0 is flowing, the inverting input terminal (-) of the comparison amplifier
A voltage obtained by superimposing the reference voltage of the reference voltage power supply Vs on the voltage drop due to the output current I 0 flowing through the output current detection resistor Rf is added to . On the other hand, a voltage obtained by superimposing the voltage of the auxiliary voltage power supply Vk on the voltage divided by the output voltage detection resistor R H and the voltage dividing resistor R 1 is applied to the non-inverting input terminal (+). Therefore, when setting is made so that the same level of voltage is applied to each of the non-inverting and inverting input terminals (+) and (-) of the comparator amplifier 10, the following equation holds true.
（−V0＋Vk）・R1／RH＋R1＋Vk＝Vs＋I0・Rs (1)
(1)式から
Vo＝｛−（Vk−Vs）／R1／RH＋R1＋Vk｝
＋I0・Rf／R1／RH＋R1 (2)
ここで
α＝−（Vk−Vs）／R1／RH＋R1＋Vk (3)
β＝−Rf／R1／RH＋R1 (4)
とすると(2)式は
V0＝α−βI0 (5)
出力電圧検出抵抗RH、分圧抵抗R1、出力電流検
出抵抗Rf、基準電圧Vs、補助電圧Vkは予じめ設
定されているので(3)(4)式におけるα，βは定数で
あり、従つて、第６図に示すように出力電圧V0
は出力電流I0の一次関数となる。つまり、チヤー
ジヤ負荷RLを接続しないときにはI0＝０なので、
α＝V0
となり、これにより無負荷電圧を設定できる。ま
た、(4)式のβは電圧降下分となり、出力電圧V0
の勾配が定まる。ゆえに、高圧トランスＴの出力
電流I0の変動により比較増幅器１０の非反転、反
転の各入力端子（＋）（−）に加わる電圧のバラ
ンスがくずれた場合に、この比較増幅器１０から
出力される信号を出力制御信号として次段の制御
回路２に加えると、制御回路２は、この入力され
た出力制御信号に対応して発振トランジスタTr
に加えるベース電流を増減するので、高圧トラン
スＴの一次側の発振回路が制御され、所要の出力
垂下特性が得られることになる。なお、出力電流
検出抵抗Rfを可変抵抗にすれば、必要な任意の
勾配βをもつ出力垂下特性を選定できるようにな
る。さらに上記実施例では、基準電圧電源V5と
補助電圧電源Vkとをそれぞれ別個に設けている
が、第４図に示すように、電圧電源Vs′を共用
し、分圧抵抗R4，R5により比較増幅器１０の非
反転、反転の各入力端子（＋）（−）に所定の電
圧が加わるようにすることもできる。(−V 0 +Vk)・R 1 /R H +R 1 +Vk=Vs+I 0・Rs (1) From equation (1), Vo={−(Vk−Vs)/R 1 /R H +R 1 +Vk} +I 0・Rf/R 1 /R H +R 1 (2) where α=-(Vk-Vs)/R 1 /R H +R 1 +Vk (3) β=-Rf/R 1 /R H +R 1 (4) Then, equation (2) is V 0 = α−βI 0 (5) The output voltage detection resistor R H , voltage dividing resistor R 1 , output current detection resistor Rf, reference voltage Vs, and auxiliary voltage Vk are set in advance. Therefore, α and β in equations (3) and (4) are constants, and therefore, as shown in Figure 6, the output voltage V 0
is a linear function of the output current I0 . That is, when the charge load R L is not connected, I 0 = 0, so α = V 0 , and the no-load voltage can be set thereby. Also, β in equation (4) is the voltage drop, and the output voltage V 0
The slope of is determined. Therefore, when the voltages applied to the non-inverting and inverting input terminals (+) and (-) of the comparator amplifier 10 become unbalanced due to fluctuations in the output current I0 of the high-voltage transformer T, the output from the comparator amplifier 10 When the signal is applied as an output control signal to the control circuit 2 at the next stage, the control circuit 2 controls the oscillation transistor Tr in response to the input output control signal.
Since the base current applied to the high voltage transformer T is increased or decreased, the oscillation circuit on the primary side of the high voltage transformer T is controlled, and the desired output droop characteristic is obtained. Note that if the output current detection resistor Rf is made a variable resistor, it becomes possible to select an output drooping characteristic having an arbitrary gradient β. Furthermore, in the above embodiment, the reference voltage power supply V5 and the auxiliary voltage power supply Vk are provided separately, but as shown in FIG. 4, the voltage power supply Vs' is shared and the voltage dividing resistors R4 , R5 Accordingly, a predetermined voltage can be applied to each of the non-inverting and inverting input terminals (+) and (-) of the comparator amplifier 10.
第５図は、第３図に示した電源装置を逆に正の
出力電圧、電流が得られるようにした電源装置の
回路図であり、第３図と対応する部分には同一の
符号を付す。この実施例の電源装置１′の第３図
に示したものと異なる点は、高圧トランスＴの二
次側の整流ダイオードD′2が極性を逆にして接続
されており、また、比較増幅器１０′の非反転入
力端子ｔが出力電流検出回路８に、反転入力端子
（−）が出力電圧検出回路６にそれぞれ接続され、
さらに、出力電圧検出回路６の電圧引上用の補助
電圧電源が設けられていないことである。 Figure 5 is a circuit diagram of a power supply device in which the power supply shown in Figure 3 is reversed so that positive output voltage and current can be obtained, and parts corresponding to those in Figure 3 are given the same symbols. . The difference between the power supply device 1' of this embodiment and the one shown in FIG. The non-inverting input terminal t of ' is connected to the output current detection circuit 8, the inverting input terminal (-) is connected to the output voltage detection circuit 6,
Furthermore, an auxiliary voltage power source for pulling up the voltage of the output voltage detection circuit 6 is not provided.
従つて、この電源装置１′では、第５図に示す
ように出力電流I0が流れるので、前述の(1)式に代
えて次式が成立する。 Therefore, in this power supply device 1', the output current I 0 flows as shown in FIG. 5, so the following equation holds true in place of the above-mentioned equation (1).
V0・R1／RH＋R1＝Vs−I0・Rf (6)
(6)式から
V0＝Vs／R1／RH＋R1
−I0・Rs／R1／RH＋R1 (7)
ここで
α′＝Vs／R1／RH＋R1 (8)
β′＝Rf／R1／RH＋R1 (9)
とすると(7)式は
V0＝α′−β′I0 (10)
(8)(9)式におけるα′，β′は定数ゆえ、I0＝０でV0
＝α′となり、これにより無負荷電圧を設定でき
る。また(10)式のβ′は電圧降下分となり、出力電圧
V0の勾配が定まる。従つて、この場合も第３図
の実施例と同様、所要の出力垂下特性が得られ
る。 V 0・R 1 /R H +R 1 =Vs−I 0・Rf (6) From equation (6), V 0 =Vs/R 1 /R H +R 1 −I 0・Rs/R 1 /R H +R 1 (7) Here, α′=Vs/R 1 /R H +R 1 (8) β′=Rf/R 1 /R H +R 1 (9) Then, equation (7) becomes V 0 =α′−β′ I 0 (10) Since α' and β' in equations (8) and (9) are constants, I 0 = 0 and V 0
= α', which allows the no-load voltage to be set. Also, β′ in equation (10) is the voltage drop, and the output voltage
The slope of V 0 is determined. Therefore, in this case as well, the required output droop characteristic can be obtained, similar to the embodiment shown in FIG.
なお、第３図および第５図に示した実施例にお
いて、高圧トランスの二次側の整流回路を倍電圧
構成としてもよいのは勿論である。 In the embodiments shown in FIGS. 3 and 5, it goes without saying that the rectifier circuit on the secondary side of the high-voltage transformer may have a voltage doubler configuration.
以上のように本発明によれば、高圧トランスの
二次側の出力電圧、出力電流を共に検出し、これ
を一次側にフイードバツクして、高圧トランスの
一次側の発振回路を制御するので、従来のよう
に、出力垂下特性を得るために高圧トランスの二
次側に大きな形状の抵抗を設ける必要がなくな
る。このため、発熱も少なく小型化およびコスト
ダウンを図れる。しかも、低圧での制御になるの
で信頼性も高く、効率を損うことなく所要の出力
垂下特性が得られるという実用上優れた効果が発
揮される。 As described above, according to the present invention, both the output voltage and output current on the secondary side of the high voltage transformer are detected, and this is fed back to the primary side to control the oscillation circuit on the primary side of the high voltage transformer. This eliminates the need to provide a large resistor on the secondary side of the high-voltage transformer in order to obtain output droop characteristics. For this reason, there is less heat generation and miniaturization and cost reduction can be achieved. Furthermore, since the control is performed at low pressure, the reliability is high, and the desired output drooping characteristics can be obtained without impairing efficiency, which is an excellent practical effect.
第１図は電源装置の出力垂下特性図、第２図は
従来の電源装置の一部を示す回路図、第３図ない
し第６図は本発明の実施例を示し、第３図は電源
装置の回路図、第４図は第３図の一部変形例を示
す回路図、第５図は他の実施例の電源装置の回路
図、第６図は本発明の電源装置で得られる出力垂
下特性の説明図である。
１，１′……電源装置、６……出力電圧検出回
路、８……出力電流検出回路、１０，１０′……
比較増幅器、Ｔ……高圧トランス、RH……出力
電圧検出抵抗、Rf……出力電流検出抵抗。
Fig. 1 is an output droop characteristic diagram of a power supply device, Fig. 2 is a circuit diagram showing a part of a conventional power supply device, Figs. 3 to 6 show embodiments of the present invention, and Fig. 3 is a power supply device. 4 is a circuit diagram showing a partial modification of FIG. 3, FIG. 5 is a circuit diagram of a power supply device of another embodiment, and FIG. 6 is a diagram showing the output droop obtained with the power supply device of the present invention. It is an explanatory diagram of characteristics. 1, 1'... Power supply device, 6... Output voltage detection circuit, 8... Output current detection circuit, 10, 10'...
Comparison amplifier, T...High voltage transformer, RH ...Output voltage detection resistor, Rf...Output current detection resistor.
Claims (1)
次側と二次側との間に、二次側の出力電圧を検出
する出力電圧検出抵抗を有する出力電圧検出回路
と、二次側の出力電流を検出する出力電流検出抵
抗を有する出力電流検出回路と、前記出力電圧検
出回路の出力電圧と前記出力電流検出回路の出力
電圧とを比較する比較手段とをそれぞれ設け、こ
の比較手段の出力により前記高圧トランスの一次
側の発振回路を制御することにより出力垂下特性
をもたせることを特徴とする電源装置。1 Equipped with a high voltage transformer, an output voltage detection circuit having an output voltage detection resistor between the primary side and the secondary side of this high voltage transformer to detect the output voltage on the secondary side, and detect the output current on the secondary side. an output current detection circuit having an output current detection resistor, and comparison means for comparing the output voltage of the output voltage detection circuit and the output voltage of the output current detection circuit, and the output of the comparison means is used to detect the high voltage transformer. A power supply device characterized in that an output drooping characteristic is provided by controlling an oscillation circuit on the primary side of the power supply device.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP59052962A JPS60197160A (en) | 1984-03-19 | 1984-03-19 | Power source |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP59052962A JPS60197160A (en) | 1984-03-19 | 1984-03-19 | Power source |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS60197160A JPS60197160A (en) | 1985-10-05 |
| JPS6412181B2 true JPS6412181B2 (en) | 1989-02-28 |
Family
ID=12929511
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP59052962A Granted JPS60197160A (en) | 1984-03-19 | 1984-03-19 | Power source |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS60197160A (en) |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH083200Y2 (en) * | 1986-01-29 | 1996-01-29 | 株式会社メレツク | Stepping motor drive circuit |
| DE3717919C2 (en) * | 1986-05-30 | 1997-09-04 | Murata Manufacturing Co | High voltage supply device |
| JPH01147682U (en) * | 1988-03-29 | 1989-10-12 | ||
| JPH0226263A (en) * | 1988-07-15 | 1990-01-29 | Murata Mfg Co Ltd | Switching power circuit |
-
1984
- 1984-03-19 JP JP59052962A patent/JPS60197160A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS60197160A (en) | 1985-10-05 |
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Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| EXPY | Cancellation because of completion of term |