JPS6394706A - Horn antenna in common use with polarized wave - Google Patents

Abstract

PURPOSE:To make the radiation angle from an aperture equal even in both a parallel polarized wave and an orthogonal polarized wave by providing a dielectric whose cross section within a face in parallel with a parallel conductor is uniform, the slope of the output face of which with respect to an input face is proportional with a special proportion constant to an angle between a progressing direction of a radio wave made incident in the dielectric and a direction at a right angle to the aperture. CONSTITUTION:The dielectric 27 whose cross sectional shape in parallel with and orthogonal to the parallel conductor plates 22 is uniform is provided in the inside near the aperture 25. The input face 28 of the dielectric 27 is formed with the aperture 25 at an angle beta, and the output face 29 forms a curved face at a specific slope at a part where a radio wave not orthogonal thereto made incident. In this case, a slope angle alphap of the output face 29 with respect to the input face 28 is proportional with a specific proportional constant K to an angle I0 of a radio wave 30 made incident on the input face 28 with respect to the aperture 25 by the provision of the dielectric 27 to make the progressing direction of the radio wave 30 radiated externally from the aperture 25 identical to both a parallel polarized wave 31 and an orthogonal polarized wave 32 even in a radio wave 30 whose progressing direction is not at a right angle to the aperture 25.

Description

[Detailed Description of the Invention] (Industrial Field of Application) The present invention relates to a polarized horn antenna that shares two orthogonal polarized waves and is used in fields such as radar and communication using microwaves. be.

(Prior Art) Conventionally, there have been technologies in this field as shown in FIGS. 2 and 3. This type of dual-polarization horn antenna (hereinafter simply referred to as a horn antenna) emits mutually orthogonal polarized waves simultaneously or by switching between them. A polarized wave parallel to the parallel conductor (hereinafter referred to as parallel polarized wave) is radiated to the outside from the opening of the horn antenna. The configuration will be explained below using figures.

Figures 2 (A) and 2 (B) show a horn antenna that forms a conventional modified beam, for example, a beam with square-law characteristics.
is a side view. Figures 3 (A) and 3 (B) show a horn antenna that performs offset feed in combination with a parapolis cylinder type reflector; Figure 3 (A) is a plan view, and Figure 3 (B) is a side view. It is a diagram.

Figure 2 (A), (B) and Figure 3 (A), (B
), each of the antenna bodies 1-1 and 1-2 includes a pair of parallel conductor plates 2-1 and 2-2 whose entire surfaces constitute parallel conductor parts, and a radio wave input surface 3-1 for transmission.
, 3-2, a linear equivalent power supply position located in front of the radio wave input surfaces 3-1 and 3-2 and set in a direction perpendicular to the parallel conductor plates 2-1 and 2-2, respectively. 4-1,
4-2, reflecting surfaces 5-1, 5-2 for reflecting the radio waves emitted from the power source positions 4-1, 4-2, and aperture surfaces 6-1, 6- for radiating the reflected radio waves. 2.

The operation of the horn antenna of FIGS. 2(A), (B) and 3(A), (B) constructed as described above will be explained.

As shown by the dashed line in the figure, the radio waves emitted from the equivalent feed source positions 4-1 and 4-2 are reflected by the reflecting surfaces 5 and 5 in the antenna bodies 1-1 and 1-2. -1
, 5-2 and reaches the aperture surfaces 6-1, 6-2, and is radiated to the outside from the aperture surfaces 6-1, 6-2.

These radio waves have their respective propagation directions at the aperture plane 6-
1 and 6-2, and the directions of the orthogonal polarizations are shown by solid arrows 7-1 and 7-2.

These orthogonally polarized waves 7-1 and 7-2 pass through the parallel conductor plates 2-1 and 2-2 of the antenna body 1-1 and 1-2 at approximately TEN
(plane wave) mode, the antenna body 1
The wavelength within the pipe within -1°1-2 is almost equal to the free space wavelength, and when exiting from the aperture surfaces 6-1 and 6-2, it is not refracted and travels straight.

On the other hand, parallel polarized waves propagate in parallel conductor plates 2-1 and 2-2 in TE mode (usually ■E1o fundamental mode), so the wavelength within the antenna body 1-1 and 1-2 is free. It becomes larger than the spatial wavelength. Due to this change, the refractive index of the radio wave becomes smaller than 1 with respect to free space, and the chain line arrow 8-1
, 8-2, a refraction phenomenon occurs when the light exits from the aperture surfaces 6-1 and 6-2.

In this way, the traveling direction of the radio waves is 1-1°1-
If there is a radio wave that is not perpendicular to the aperture surfaces 6-1 and 6-2 of 2, the radiation angles of the orthogonally polarized waves and the parallel polarized waves exiting from the aperture surfaces 6-1 and 6-2 will be different. become.

(Problems to be solved by the invention) However, in the horn antenna with the above configuration,
Since the radiation angles of orthogonally polarized waves and parallel polarized waves are different, in the case of deformed beams as shown in FIGS. When performing offset feeding as shown in Figures 3 (A) and (B), the main radiation direction will be different for both polarized waves, and in either case, circularly polarized waves cannot be obtained within a predetermined angular range. The problem was that there was no. Furthermore, when both polarized waves are switched and used, problems such as differences in reception levels between the two polarized waves occur.

The present invention solves the problem that the prior art had, in that when there is a radio wave whose traveling direction is not perpendicular to the aperture surfaces 6-1 and 6-2, the radiation angles of orthogonally polarized waves and parallel polarized waves are different. The present invention provides a horn antenna that solves these problems.

(Means for Solving the Problems) In order to solve the above-mentioned problems, the present invention provides a pair of conductor side plates each having parallel conductor portions formed in parallel at least a predetermined interval, and a gap between the pair of conductor side plates. a reflecting surface that is formed between the pair of parallel conductor parts and reflects a radio wave having at least one of a polarization parallel to the parallel conductor part and a polarization perpendicular thereto; and a reflected radio wave that is formed between the pair of parallel conductor parts and reflected by the reflection surface. and an aperture surface that radiates the reflected radio waves to the outside, and in which at least a part of the reflected radio waves propagates in a direction different from a direction perpendicular to the aperture surface, the parallel polarization horn antenna near the aperture surface A dielectric material is formed between the conductor parts and perpendicular to the parallel conductor parts. Here, the dielectric has a uniform cross-sectional shape parallel to the parallel conductor part, and has an input surface that faces the reflective surface and inputs reflected radio waves, and an output surface that faces the aperture surface and outputs the input reflected radio waves. and α
=KI0, which almost satisfies the relationship.

However, the above α is the inclination angle formed by the output surface at the point where the reflected radio wave is output from the dielectric with respect to the input surface near the input point of the reflected radio wave to the dielectric, and the above includes the wavelength of the reflected radio wave and It is a constant related to the dielectric constant of the dielectric material and the spacing between parallel conductor parts, and is also a constant related to the above-mentioned (2). is the angle between the traveling direction of reflected radio waves input to the dielectric and the direction perpendicular to the aperture surface.

(Function) According to the present invention, since the dual-polarization horn antenna is constructed as described above, the dielectric material provided between the parallel conductor parts near the aperture surface of the horn antenna is parallel to the parallel conductor parts. Even when the direction of propagation of the polarized wave perpendicular to the polarized wave is not perpendicular to the aperture plane of the horn antenna, it functions to equalize the radiation angles of the two polarized waves at the aperture plane. Therefore, the above problem can be eliminated.

(Embodiment) FIGS. 1(A) and 1(B) show a first embodiment of the present invention. FIG. 1(A) is a side view of a dual-polarized horn antenna, and FIG. ) is a cross-sectional view taken along line 8-A in the same figure (A).

This dual-polarized horn antenna (hereinafter simply referred to as a horn antenna) 21 is used by forming a modified beam, for example, a beam with square-law characteristics, and the entire surface of a pair of conductor side plates having a distance a is a parallel conductor. It has a parallel conductor plate 22 forming a structure, a radio wave input surface 23 provided at the bottom of the horn antenna 21, a reflecting surface 24 for reflecting radio waves, and an aperture surface 25 for radiating the reflected radio waves to the outside. In front of the radio wave input surface 23 inside the horn antenna 21, an isometric power supply position 26 is set in a line in a direction perpendicular to the parallel conductor plate 22.

Further, a dielectric material 27 having a uniform cross-sectional shape parallel to and perpendicular to the parallel conductor plate 22 is provided inside the opening surface 25 . The input surface 28 of this dielectric 27 is formed to form an angle of β with respect to the aperture surface 25, and the output surface 29 is a curved surface with a specific inclination at a portion where radio waves are incident, which is not perpendicular to the aperture surface 25. has been achieved.

- one = In the horn antenna 21 configured as described above,
Radio waves 30 that are part of the radio waves emitted from the power source position 26
The traveling direction of the vehicle is indicated by broken lines and solid arrows in the figure.

FIG. 4 is a partially enlarged sectional view of the dielectric 27 provided in the phone antenna 21 of FIG. 1, and the progress of the radio wave 30 shown in FIG. be.

Angle between the opening surface 25 and the direction perpendicular to it ■. Said radio wave 3
0 at the incident point P on the input surface 28 of the dielectric 27 at an incident angle ■
Inject at 1. When the incident radio wave 30 is a parallel polarized wave, it is refracted inside the dielectric 27 at a refraction angle R1 as shown by a solid line 31, and then is emitted at the output point Q-2 of the output surface 29 at an incident angle 2. . The angle that the output surface 29 makes with the input surface 28 at the output point Q at this time is α. Output point Q
- Radio waves 31 emitted to the outside of the dielectric 27 at a refraction angle R2
Further, after entering the output point S of the aperture surface 25 at an incident angle of 3, the light beam exits at a refraction angle of R3. However, if the above incident angle is 11°-, -10---- I2. I3 and the angles of refraction R1, R2, R3 are relative to the normal to the respective plane 28.29.25.

On the other hand, if the radio wave 30 is orthogonally polarized, the broken line 32
As shown in , the radio wave incident on the incident point P of the dielectric 27 is refracted and reaches the output point Q of the output surface 29, and is further refracted and exits the dielectric 27 to the output point S of the aperture surface 25. - reach this point. At the output point Sr, the light travels straight without being refracted and is radiated to the outside. At this time, the refraction angle at the incident point P is rl
, the incident angle and the refraction angle at the output point Q-ko are i2.
r2, the incident angle and the refraction angle at the output point S are respectively L
3°r3. Further, the inclination angle of the output surface 29 with respect to the input surface 28 at the output point Qrl/Q is assumed to be α.

Note that the coordinates shown in FIG. 4 are such that the coordinate origin O is set at an arbitrary position on the intersection line of the cross section of the figure and the input surface 28, and the direction of the intersection line is the coordinate axis U, which is orthogonal to the coordinate axis U on the cross section of the figure. The direction is set as the coordinate axis ■.

Next, the operation of the above embodiment will be explained using FIGS. 1 and 4.

The radio waves 30 input from the radio wave input surface 23 in FIG.
After being reflected by the reflective surface 24 , the light passes through the dielectric 27 and is radiated to the outside from the aperture surface 25 . The distance a is selected such that λ/2<a<λ with respect to the free space wavelength λ of the radio wave,
It is also assumed that the length of the aperture surface 25 is sufficiently long compared to the wavelength λ. At this time, when parallel polarized waves are input from the radio wave input surface 23, the propagation mode in the horn antenna 21 becomes the TE1o mode in 22 in the parallel conductor plate, and orthogonally polarized waves are input from the radio wave input surface 23. At this time, the propagation mode within the horn antenna 21 becomes approximately the TEN mode.

Therefore, the wavelengths inside the horn antenna 21 are different for both polarized waves, and the ways in which the two polarized waves travel after entering the dielectric 27 are different. Below, we consider the behavior of radio waves in terms of geometric optics, and find the refractive index of both polarized waves.

For parallel polarized waves, the wavelength inside the parallel conductor plate 22 is λ. , the internal wavelength λpd in the dielectric 27, the refractive index of the dielectric 27 with respect to the outside of the dielectric, n, d, the refractive index n with respect to the outside from the opening surface 25 of the parallel conductor plate 22, and the dielectric 27 with respect to O1 orthogonal polarization. When the wavelength inside the tube is λ, the refractive index of the d dielectric 27 with respect to the outside of the dielectric is nrd, and the relative permittivity of the dielectric 27 is ε, the following equations (1) to (6) hold true.

(4) However, according to the above explanation, it is assumed that the channel wavelength in the parallel conductor plate 22 for orthogonally polarized waves is equal to the free space wavelength λ. Therefore, no refraction occurs at the aperture surface 25 for orthogonally polarized waves.

Since the relative dielectric constant ε>1, the above formula (4).

From (5) and (6), the relationship npd>nrd>1>npp-<7 is established. Therefore, in FIG. 4, the orthogonally polarized wave 32 is refracted upward at the incident point P to a lesser extent than the parallel polarized wave 31, so the output point Q is lower than the output point Q. Similarly, the degree of refraction of the orthogonally polarized wave 32 downward at the output point Q is less than that of the parallel polarized wave 31. Furthermore, the orthogonally polarized wave 32 is
5, the parallel polarized wave 31 is not refracted at the aperture surface 25.
is refracted upward.

Hence the inclination angle α. By appropriately selecting the value of
, r3 can be made equal. This point will be explained in more detail below using equations.

For parallel polarized waves 31 and orthogonally polarized waves 32, the following equations (8) to (12) are obtained from geometric conditions.

11-I. -β ... (8) I2"R1 + αp ... (9) I 3 "" R2 - αp + β ... (10) i2
=r1+α, ...(11)i3""r2-α,
+β...(12) Also, the incident point P, the output point Q,...
Q, and the output points s, , s - the law of refraction (snel
1's law), the following equations (13) to (18) are obtained.

3! n i2 1 □−□ ... (17) sin r2 nrd r3"'i3 ... (18) Here, assuming ■.-β-0, considering from Figure 4, α, -0
It can be seen that the radiation directions of both the parallel and perpendicular polarized waves 31 and 32 become equal as R3=r3=O. From this, the corner ■. If and β are significantly smaller than 1, it can be inferred that all other angles are also significantly smaller than 1.

Therefore, using approximate expressions such as Sln 11 Yu11,
Another corner ■. Assuming that the change with respect to the position on the input surface 28 is gradual, the following equations (19) and (20) can be derived because an approximation of α and α can be made. That is, the expression (
8), (9), (13) and (14) to R2
Yu I. −β+npdαp is obtained, and from this equation and equations (10) and (15), R3=np
pIo+npp(npd-1) (2p - (19) is obtained. Similarly, formulas (8), (11), (1
2), (16).

From (17) and (18) r3 steps ■. +(n, d-1) αp (20) is obtained. The conditions for the radiation angles from the aperture surface 25 of both parallel and perpendicular polarized waves 31 and 32 to be equal are expressed by equations (19) and (20).
), by setting R3=r3, the following can be obtained.

αp=K I o, (21) That is, in order to equalize the refraction angle R3°r3 for both polarized waves 31, 32, the inclination angle α of the output surface 29 of the dielectric 27 with respect to the input surface 28 is determined according to equation (21). is the input surface 28
An angle (■) between the traveling direction of the radio wave 30 incident on the opening surface 25 and the direction perpendicular to the aperture surface 25. It can be seen that it is sufficient to make it proportional to . The proportionality constant at this time is given by equation (22). Since equations (21) and (22) are unrelated to the angle β, the input surface 28 may not be a flat surface but a curved surface that changes gradually within a range where the value of β does not become too large.

The angle ■ in equation (21). is the value at the input point P, while the angle I as mentioned above. When the change with respect to the position on the input surface 28 is gradual, the U coordinate is the same as the U coordinate of the output point Q.
The value of angle I in coordinates ■. (U) can be used approximately. If the coordinates of the output point Q are (u, v), then d
Since V/d u =a p, using equation (21) and the above approximation, v ■ - v1 -, /LL! ■o(u)du...(23)
get. Here, ul is the value of U at the lower end of the dielectric 27, ■1
is the value of ■ at u=u1. Equation (23) is an expression for the cross-sectional curve of the output surface 29 of the dielectric 27, and is the value of the angle 2 in the U coordinate. It is shown that when (U) is given, the relationship between U and ■, which determines the shape of the above-mentioned cross-sectional curve, can be found.

Until now, it was corner ■. In this case, β is considerably smaller than 1, but the angle ■. When and β are large, the above formula (
8) to (18) are set to = 21- so that they are satisfied as they are, and α and ■ become R3"1"3. All you have to do is find the relationship. However, the calculation in this case is complicated.

In this embodiment, the inclination angle α of the output surface 29 with respect to the input surface 28 is the angle ■ formed by the aperture surface 25 of the radio wave 30 incident on the input surface 28 . Since the dielectric material 27 is provided so that the direction of movement is proportional to the aperture surface 2 with a specific proportionality constant K,
Even for radio waves 30 that are not perpendicular to 5, the aperture surface 2
The traveling direction when radiated to the outside from 5 is parallel polarized wave 31
There is an advantage that the polarization and orthogonal polarization 32 can be made the same.

FIG. 5 shows a cross section perpendicular to the parallel conductor portion 41 and the aperture 25 of a horn antenna showing a second embodiment of the present invention. In the first embodiment, the spacing a between the conductor side plates was set to a constant value, whereas in this embodiment, in order to appropriately spread the directivity in a plane perpendicular to the parallel conductor portion 41, the spacing a between the opening surfaces 25 was changed. is set to a value different from the interval a.

In order to change the spacing between the aperture surfaces 25, step conversion is performed to form a step shape, and a step 42 is provided between the dielectric 27 and the aperture surface 25 for the spacing a of the parallel conductor portion 41, and the spacing between the aperture surfaces 25 is changed. b is narrower than a.

In the case of such a step conversion, when a radio wave passes through it, orthogonally polarized waves are not refracted, but parallel polarized waves are refracted. For parallel polarized waves, the refractive index to the outside from the aperture surface 25 of the conductor side plate portion at a distance is n <-%>, the incident angle at step 42 is la, the refraction angle is ra, and the aperture surface 25 for the parallel polarized waves. If the incident angle is ib and the radiation angle is rb, then 5inia/Sin ra=nq/n
pp' sin 'b/sin rb=1/n,,1
The relational expression b=ra holds true. From the above relational expression, Sin
We get rb=nppsin ia.

On the other hand, if there is no step, the parallel polarized wave has an incident angle of 1a
It will be incident on the aperture surface 25, and if the radiation angle at this time is Y''c, 5ini8/sin r = 1
/n,, the formula is established, and from this formula, Sin r,
, -n,, Sin ia are obtained. Therefore, from the above relationship Sin rb=nppSin ia, rC
-rb relationship is obtained. In other words, for parallel polarization,
It can be seen that the radiation angles rb and rc from the aperture surface 25 are the same whether there is a step or not.

Even if step conversion is performed in this manner, there is an advantage that the radiation angles for both the parallel and perpendicular polarized waves of the first embodiment are the same.

FIG. 6 shows a cross section perpendicular to the parallel conductor portion 41 and the aperture 25 of a horn antenna according to a third embodiment of the present invention, in which a taper 43 is provided in contrast to the step 42 of the second embodiment. This is the result of taper conversion.

As shown in the second embodiment, even if the step 42 is provided, the radiation angles rb and rC from the aperture surface 25 do not change, so the number of steps is increased between the interval a and the interval between the steps is gradually increased. Even if it is changed, the radiation angle from the aperture surface 25 does not change. Therefore, even in the case of the taper transformation of this embodiment as a limit case, there is an advantage that the radiation angle does not change as in the second embodiment.

Figure 7 (A), (B) and Figure 8 (A), (B
) respectively show the fourth and fifth embodiments of the present invention, and are block diagrams in which the horn antenna according to the present invention is applied to the primary horn of a parapolis cylinder antenna.

FIGS. 7(A) and (B) show the configuration diagrams for the deformed beam, and FIGS. 8(A) and (B) show the configuration diagrams for the offset feed. 1.51-2 has focal axes F1 and F2. The horn antennas 52-1, 52-2 each have a focal axis F1. Its opening surface 53-1.53 near F2
-2 is placed so that it is facing.

In the case of Fig. 7 (^) and (B), the horn antenna 52
-1 emits a modified beam of radio waves, and reflects the main radio waves from mirror 5.
1-1 to form the final beam, but the focal axis F1
The beam shape in the plane including the angle is approximately equal to the deformed beam of the horn antenna 52-1.

In the case of Fig. 8 (A) and (B), the horn antenna 52
-2 emits radio waves that are tilted upward from the direction perpendicular to the aperture surface 53-2, and this radio wave is reflected by the reflecting mirror 51-2 to form a final beam, but the main direction of the final beam is the focal axis. The direction is different from the direction perpendicular to F2.

Figures 9 and 10 show examples of the propagation direction of radio waves in the horn antenna 52-1. , FIG. 9 shows the case of a deformed beam, and FIG. 10 shows the case of an offset feed.

Figure 9 shows the case of a deformed beam, for example, an inverse cosecond squared beam, in which some radio waves in the lower part are radiated in the main direction, but some radio waves in the upper part are gradually radiated away from the main direction. In this case, the dielectric 54-1 has a constant thickness at the bottom and gradually decreases in thickness at the top. The inclination angle β is not zero and the radio waves do not enter the dielectric 54-1 at right angles in the downward direction, so the radio waves reflected on the input/output surface of the dielectric 54-1 follow a different radio wave path from the radio wave path before the incident. Therefore, the input standing wave ratio of the horn antenna 52-1 is improved. Such an inclination angle β is useful for improving the input standing wave ratio characteristics of the horn antenna.

-26= In the case of Fig. 10, the inclination angle β is selected to be zero, so the radio waves will be incident on the dielectric 54-2 at a diagonal constant angle, and the shape of the dielectric 54-2 will be directed upward. The thickness increases linearly.

In this case, even if the inclination angle β is zero, the radio waves do not strike at right angles on the input and output surfaces, so the input standing wave ratio of the horn antenna 52-2 is good.

In addition, in the offset feed shown in FIG. 10 above, the directivity in the plane parallel to the parallel conductor plate of the horn antenna 52-2 is not deformed, but even when offset feed is used, the deformed beam as shown in FIG. 9 naturally occurs. It is possible to do so. In this case, the shape of the dielectric 54-2 is such that the input surface of the dielectric 54-1 in FIG. 9 is superimposed on the output surface of the dielectric 54-2 in FIG. 10.

The fourth and fifth embodiments have the advantage that the input standing wave ratio characteristics of the horn antennas 52-1 and 52-2 are improved.

Note that the present invention is not limited to the illustrated embodiment, and various modifications are possible. For example, in the first, fourth, and fifth embodiments, the entire surfaces of a pair of conductor side plates were provided in parallel, and this was used as a parallel conductor part. 53-1. Only the vicinity of 53-2 may be made parallel to form a parallel conductor portion. Furthermore, the horn antenna 21.52-1.52-2 can be of either integral or assembled construction.

(Effects of the Invention) As described above in detail, according to the present invention, the cross section in a plane parallel to the parallel conductor portions of the dual polarization horn antenna is uniform, and the output surface is uniform. A dielectric whose inclination with respect to the input plane is proportional to the angle between the direction of propagation of the radio waves incident on the dielectric and the direction perpendicular to the aperture plane with a special proportionality constant is provided, so that the direction of propagation is aligned with the aperture plane. Even for parallel polarized waves and orthogonally polarized waves that are not at right angles, the radiation angles from the aperture surface can be made equal.

Furthermore, even if the interval between the apertures and the interval between the parallel conductor parts is different, by providing a stepped or tapered propagation section, the radiation angles of both polarized waves can be made equal = 28-.

Furthermore, when the above-mentioned dual polarization horn antenna is used as the primary horn of a parapolished cylinder antenna, even if a modified beam, an offset feed, and an offset feed of the modified beam are implemented, the radiation angle will be the same for the two polarized waves. can do.

In this way, the conventional problems when forming circularly polarized waves with a single horn antenna or a parapolished cylinder antenna can be solved, and even when switching between both polarized waves, the beam shape and beam shape for both polarized waves can be solved. Conventional inconveniences due to differences in direction, etc. can be eliminated. Therefore, the dual polarization horn antenna of the present invention is highly effective when applied to various fields that utilize microwaves, such as radar and communications.

[Brief explanation of the drawing]

FIGS. 1(A) and 1(B) show a polarized horn antenna according to the first embodiment of the present invention, and FIG. 1(A) is a side view thereof,
Figure 2 (B) is a cross-sectional view taken along the line A-A of the side view, Figures 2 (A) and 2 (B) are conventional polarized horn antennas, and Figure 2 (A) is a plan view and Figure 2 (B) is ) is a side view, Figure 3 (
A) and (B) are other conventional polarized horn antennas; FIG. 4 is a plan view, FIG. 4 is a side view, FIG. 4 is a partially enlarged sectional view of FIG. The figure is a sectional view of a main part of a dual polarization horn antenna showing a second embodiment of the present invention.
The figure is a sectional view of essential parts of a dual-polarized horn antenna according to a third embodiment of the present invention, and FIGS. 8(A) is a plan view, FIG. 8(B) is a side view, and FIGS. 8(A) and 8(B) are diagrams of a combination with a polygon cylinder antenna. A combination diagram of a horn antenna and a parapolis cylinder antenna, where (A) is a plan view, (B) is a side view, FIG. 9 is an enlarged view of the polarized horn antenna shown in FIG. 7, and FIG. The figure is an enlarged view of the dual polarization horn antenna shown in FIG. 21, 52-1.52-2...Polarized wave horn antenna, 22...Parallel conductor plate, 24...
... Reflective surface, 25.53-1゜53-2 ... Opening surface, 27.54-1.54-2 ... Dielectric,
28...Input surface, 29...Output surface, 4
1...Parallel conductor portion, 42...Step, 43...Taper. Applicant's agent: Sei Kakimoto, 21 A. Side view of common horn antenna (A'1) Figure 1 (B) Figure 3 Fig. 4 Fig. 5 Fig. 6 Fig. 7 Polarized 5-skin common horn antenna Fig. 8 Fig. 7 polarized polarization common Hoofan antenna Fig. 9 Fig. 10

Claims (1)

[Scope of Claims] 1. A pair of conductor side plates each having parallel conductor parts formed in parallel at least at a predetermined interval, and a polarized wave formed between the pair of conductor side plates parallel to the parallel conductor parts and perpendicular thereto. a reflective surface that reflects radio waves having at least one of the polarized waves, and an aperture surface that is formed between the pair of parallel conductor parts and radiates the reflected radio waves reflected by the reflective surface to the outside,
In the dual-polarized horn antenna in which at least a part of the reflected radio waves propagates in a direction different from a direction perpendicular to the aperture surface, a polarized wave antenna is provided between the parallel conductor portions near the aperture surface, the antenna being perpendicular to the parallel conductor portion. an input surface that faces the reflecting surface and inputs the reflected radio wave, and an output surface that faces the aperture surface and outputs the input reflected radio wave, and has a uniform cross-sectional shape parallel to the parallel conductor portion. What is claimed is: 1. A dual-polarization horn antenna, characterized in that it has a dielectric material which substantially satisfies the relationship α=KI_0. However, the α is an inclination angle formed by the output surface at the point where the reflected radio wave is output from the dielectric with respect to the input surface near the input point of the reflected radio wave to the dielectric; It is a constant related to the wavelength of radio waves, the dielectric constant of the dielectric, and the spacing between the parallel conductor parts, and the I_0
is the angle between the traveling direction of the reflected radio waves input to the dielectric and the direction perpendicular to the aperture surface. 2. The conductor side plate has a stepped shape with a uniform cross-sectional shape in a plane orthogonal to the opening surface and the parallel conductor portion between the opening surface and the dielectric body. The dual polarization horn antenna according to item 1. 3. The conductor side plate has a tapered shape with a uniform cross-sectional shape in a plane perpendicular to the opening surface and the parallel conductor portion between the opening surface and the dielectric body. The dual polarization horn antenna according to item 1.