JPS63184079A - Electronic scanning monopulse receiver and electronic scanning monopulse radar using same - Google Patents

Abstract

PURPOSE:To increase the oscillation angle of an antenna beam and reduce the number of antenna elements by frequency-dividing signals received by antennas and conducting phase processing and signal processing by a monopulse comparator. CONSTITUTION:First frequency-divided signal 55 to which signal 71 received by a first antenna 74 is frequency-divided by a frequency divider 54 and second frequency- divided signal 57 to which signal 73 received by a second antenna 76 is frequency- divided by another frequency divider 56, and they are phase-adjusted in phase shifters 20 and 21, respectively, and applied to a monopulse comparator 24 to be converted to sum signal 25 and difference signal 27 therein. The sum signal 25 and the difference signal 27 are amplitude-detected and which one of two amplitude detection outputs is larger than the other is discriminated by a magnitude discriminator. The larger signal is utilized as a signal for automatic gain control. The larger one of the sum signal 25 and the difference signal 27 is made constant and a multiplying operation is conducted on the sum signal 25 and the difference signal 27 in a multiplier by using channel changeover signal indicating which one of the sum signal 25 and the difference signal 27 is larger whereby angle error signal is taken out.

Description

Detailed Description of the Invention (Industrial Application Field) The present invention irradiates radio waves to targets such as aircraft, flying objects, or vehicles, and uses the radio waves reflected from the targets as a medium to determine the angle of the target. In a radar mounted on a guided flying vehicle for tracking, an electronic scanning monopulse receiver and an electronic scanning monopulse receiver are capable of driving the antenna beam using an electronic method rather than a mechanical servo device, and also achieve spatial stabilization. It is related to radar.

(Summary of the Invention) The present invention provides an electronically scanned monopulse comparator and an electronically scanned monopulse radar that drive the beam of an antenna by an electronic method rather than a mechanical servo device, and also achieve spatial stabilization. Therefore, by performing phase processing and signal processing using a monopulse comparator after frequency-dividing the received signal of each antenna, the swing angle of the antenna beam can be increased even if the distance between the antennas is increased. This makes it possible to reduce the number of antenna elements.

(Prior Art) Problems with conventional electronic scanning monopulse antennas will be described using a conventional example of the PtS3 diagram.

In the fpJ3 diagram, the first received signal 71 is received at the first antenna 74 and becomes the P,1 antenna output cuff 5, and in the f51 phase shifter 20, the first received signal 71 is output from the phase generator 1 which is the output of the phase generator 28. The phase amount according to the signal of the output 29 changes and becomes the first phase shifter output 21, which is input to the monopulse comparator 24.

The second reception signal 73 is received by the second antenna 76 and becomes the second antenna output cuff 7, and the second reception signal 73 is changed in phase amount according to the signal of the phase generator second output 31 in the second phase shifter 22, and the 2 phase shifter output 23, monopulse comparator 2
4 is input.

In the monopulse comparator 24, the first phase shifter output 21 and the second
The sum and difference with the phase shifter output 23 are calculated, resulting in a monopulse comparator sum output 25 and a monopulse comparator difference output 27.

The angular velocity detector 86 is an electronic scanning monopulse antenna.
It detects the angular velocity of the flying object on which the seeker is mounted, and is composed of, for example, a gyro. The angular velocity detector output 87, which is the output of the angular velocity detector 8G, is integrated in an integrator 88 to become an integrator output 89, and further non-linearly corrected in a tangent corrector 32 to become a tangent correction output 33, resulting in the above-mentioned phase. The signal is input to a generator 28.

Here, when the target is in the boresight direction of the antenna (the direction of maximum gain of the antenna), the first antenna output cuff 5 (X7S) and the second antenna output cuff 7 (X,,)
becomes as follows.

X'S = sinωt ・(1
)X7v = sinωt −(
2) The following signals are output to the first phase shifter output 21 (X2.) and the PJ2 phase shifter output 23 (X23), respectively.

X21 = 5in (ωt+θ) ・
(3)X23 = 5in (ωt-θ)
-(4) However, θ is the phase amount of each phase shifter.

And jll phase shifter output 21 (X21) and! @2 phase shifter output 23 The target position (angle) is determined by taking the sum and difference of (X2.).

(Problems to be Solved by the Invention) Conventional angle tracking radars can be roughly divided into methods of mechanically driving the antenna beam and methods of driving the antenna beam electronically.

In order to mechanically drive the antenna beam, the antenna beam is driven by a mechanical servo device, which makes it difficult to reduce the size and weight and drive the antenna beam at high speed.

On the other hand, the technique of driving the antenna beam electronically is tj
As shown in Figure s3, it is already in use.

However, in the conventional electronic scanning monopulse antenna shown in FIG. When is large, the range of the swing angle of the antenna directivity angle becomes narrow. Therefore, when it is desired to increase the antenna directivity direction, the distance d between the antennas must be reduced, which inevitably increases the number of antenna elements, resulting in an expensive device.

In order for a guided missile equipped with a small radar device to fly stably toward its target using proportional navigation, it is necessary to keep the antenna beam always pointing toward the target even if the missile is shaken (vibrated). , spatial stabilization performance is required.

Therefore, there is a need for an electronically scanned monopulse receiver and an electronically scanned monopulse radar that can (a) drive an antenna beam at high speed, have a small quantization error, and (c) have a small number of antenna elements.

(Means for Solving the Problems) In view of the above points, the present invention provides an electronic scanning monopulse receiver that can drive an antenna beam at high speed and has a small number of antenna elements, and uses the receiver. The aim is to provide an electronically scanned monopulse radar.

The present invention phase-shifts a first frequency-divided signal obtained by dividing a signal received by one antenna using a frequency divider and a frequency-divided signal of tjrJ2 obtained by dividing a signal received by another antenna by a frequency divider. The monopulse comparator converts the sum signal and the difference signal into a sum signal and a difference signal, respectively amplitude-detects the sum signal and difference signal, and outputs the two amplitudes in a magnitude discriminator. The larger signal is used as a signal for automatic gain control, the larger output signal of the sum signal or the difference signal is made constant, and the sum signal and the difference signal are used in a multiplier to A means is provided for extracting an angular error signal by performing a multiplication operation using a channel switching signal indicating which of the sum signal and the difference signal is larger, thereby solving the problems of the prior art described above.

Prior to detailed explanation of the present invention in Fig. ttS1, the second
The most basic means of the present invention will be explained using explanatory diagrams of the figures.

Assuming that the distance between the first antenna 74 and the second antenna 76 is d (senna meters), and the wavelength of the radio waves used is λ (senna meters), the radio waves from the target are α
(radians) from the front (central axis A of the antenna), two antennas (74 and 76)
If the phase difference between the first antenna output cuff 5 and the second antenna output cuff 7 when receiving is 2φ, then 2φ = (2πd/in) sinα ・ (5
). However, π is pi.

Similarly, when the directivity angles of the two antennas are changed by β (radians), if the phase difference between the signals received by the two antennas is 2θ, then 2θ = (2πd/λ) sinβ − (6) or θ = ( πd/λ) sinβ...(7)
becomes.

If a phase difference 2θ is created between the signals of two antennas, the antenna can swing its head by β, but θ is the phase, and due to the periodicity of the trigonometric function, there is a one-to-one relationship between θ and β. In order to maintain
...It is necessary to keep it in the range of (8), and the swing angle β is −arcsin[λ/(2d)]<β< arcs
in[λ/(2d)]...(9) From equation (9), when λ/(2d) is small, the swing angle β becomes a small value.

In order to solve this problem, the present invention attempts to make it possible to make a large swing in the antenna pointing direction even when the distance d between the antennas is large by effectively increasing the size of the person. To this end, the present invention uses an analog frequency divider (54 or 56) as configured in the f56 diagram. This analog frequency divider contains both amplitude and phase information of the original signal in its output.

In the plS6 diagram, the third transmitting/receiving switch second output 47
Since b (X47b) can be expressed in the same way as the first antenna output cuff 5 (X'S) shown in Figures 1 and 2,
). The first and π/2 phase shifter output 67 (X, 7), which is the output of the first and π/2 phase shifter 66 in FIG.
7 = cos[(ω is one φ)/2] −(11
), and is mixed in the first mixer 50 with the third transmission/reception switching cylinder 2 output 47b to produce the first mixer output 51.
The high-frequency component is passed through the low-pass filter 78 and becomes the output cuff 9 of the low-pass filter. The first power divider output 61 and the first analog frequency divider output 55, which are the outputs of the t51 power divider 60, can be expressed in the same way as the low-pass filter output cuff 9, and are expressed as X7. = X, , = X, 5 = sin [(ω is one φ) X21 ... (12)
becomes. In this way, the analog frequency divider maintains correct amplitude information while having the function of a frequency divider. This completes the explanation of one channel of the most basic receiving system.

Next, we will discuss the case of transmission. The first transmitting/receiving switch tube 1 output 37a (Xz7a
) and the second power divider first output 63 (X6.) is X )7 a = X 63 = sin[(t
a t-θ)/2]...(13) Then, fjS2·π/2 phase shifter output 69 (X6.) is! 's1 Send/receive switch tube 1 output 37 a (X *t
Since the phase is delayed by π/2 compared to a), X69 = cos[(ωt-θ)/2] −(
14), and the first analog multiplier output 43 (X,
, ) are the first transmitting/receiving switch cylinder 1 output 37a and the second π
/2 is produced by the product of phase shifter output 69, so X43 = 5in (ω is - θ) ・(1
5). This completes the explanation of the most basic transmission channel.

(Operation) The following describes how the configuration described so far functions to reduce the number of antenna elements.

If the angular frequency of the radio wave to be used is ω (7 radians), the fjIJ1 antenna 74 in FIG. 2 receives the f51 reception signal 71, and the first antenna output cuff 5 is
(X7S).

X7S = 5in (ωt-φ)
- (16) The following second received signal 7 is sent to the 12 antenna 76.
3 is received, @2 antenna output cuff 7 (
It becomes X',,).

X,, = 5in(ωL+φ) ・(17
) However, the first antenna output cuff 5 (X, 5), the formula (
The phase difference 2φ between the second antenna output 't''t (X7. This is the phase difference corresponding to .

fjS1 The first analog frequency divider 54 shown in the embodiment of FIG.
pA1 analog frequency divider output 55 (Xss
a) is X55a: sin[(ωt-φ)/2] ・(1
8). The second analog frequency divider output 57 (xsta), which is the output of the second analog frequency divider 56, is
a = sin [(ω to 1φ)/2] ・ (1
9).

The first phase shifter second output 21 is the output of the first phase shifter 20
b (X2.ba) is X21ba = sin[(ωt-φ)/2+θ]-(
20), and the second output of the second phase shifter 23 b (X23
ba) is X2. ba = sin[(ωt+φ)/2−
θ] ・(21).

In this case, the monopulse comparator sum output 25 is created by the sum (addition) of the first phase shifter second output 21 b (X2.ba) and the 12 phase shifter second output 23 b (Xzsba), so X' 2 ．． = X2sba +X; +ba= cos
(φ/2-θ) sin [(ω/2) tl...(22) However, monopulse comparator sum output 25 (X2sa
) is delayed in phase by π/2 in the monopulse comparator 24, so X2sa: cos(φ/2−θ)cO3[(ω/2
)tl...(23) The monopulse comparator difference output 27 (X27a) is
In this case, the first phase shifter second output 21 b(X 2+ba
) and @2 phase shifter ptS2 output 23b (X23ba)
It is made by the difference (subtraction) of X2. a=X2. ba-X2. ba = 5in(φ/2-θ)cos[(ω/2)t
l...(24) becomes.

The output of the multiplication demodulator 34 in FIG. 4 is the monopulse comparator sum output 25 (X2sa) and the monopulse comparator difference output 27 (
The error angle output is 35 (X
ssa) is approximately X=sa':5in(φ/2−θ)−(2
5). In order to make equation (25) zero, φ becomes φ/
2, indicating that θ only requires half the amount of phase shift.

The phases of the tjS1 analog frequency divider output 55 and the second analog frequency divider output 57 in FIG. Since it is difficult to do so, it is necessary to check whether it can be used as a monopulse receiver even in such a case. Therefore, the output signals of the two antennas (75) and (77
), create a phase difference of 2π between them.

Substituting equation (26) into equations (18) and (19) gives X5s
b=sin[(ω−yr−φ)/2]=cos[(
ω is one φ)X21...(27)xs7b: si
n[(ωt+π+φ)X21= cos[(ωt+φ)
/2] ...(28) respectively. The first phase shifter second output 2 l b is the output of the first phase shifter 20
(X2.bb) is Xz+bb =-cos[(ωt-φ
)/2+θ]・(29), and the second output 2 of the second phase shifter
3 b (X23bl]) is X 2sbb= cos[
((+J t+φ)/2−θ] (30).

In this case, the monopulse comparator sum output 25 is created by the sum (addition K) of the first phase shifter second output 21 b (X2.bb) and the second phase shifter second output 23 b (X2.bb). Therefore, similar to equation (16), X' 2sb = X2zbb + X2+bb = -
5in(φ/2-θ)si, [(ω/2)tl...(
31) X 25 b = 5in (φ/2-θ) cos[
(Cd/2)tl (32). The monopulse comparator difference output 27 is created by the difference between the f51 phase shifter 2 output 21 b (X,, bb) and the second phase shifter 2nd output 23 b (X2.bb), so X 2
7 b = X 2zbb X 2+bb= co
s(φ/2-θ)cos[(ω/2)cl...(
33) The output of the multiplication demodulator 34 in FIG. )
Comparing these, we find that the equations for the relationship between sum and difference are simply interchanged, so both have an error angle output of 35 (
X3S) is approximately X cosb job -5in(φ/
2- θ ) ・(34).

In the magnitude discriminator 80 of FIG. 4, the first amplitude detector output 91
(Xs+) and the second amplitude detector output 93 (X93).
x because it distinguishes between small and small! When I>X13, Ls = Lsa = 5in (φ/2-θ) ・(3
5>, so X! II<X91), then X ss = X :lS b = ! 3! n(φ
/2-θ)·(36'), it can be seen that a constant angular error signal can be obtained.

From the above explanation, we can use an analog frequency divider to reduce the operating frequency to 1/2, and replace the conventional synchronous detector with a multiplication demodulator 34.
This shows that if you create a circuit that includes this, you can construct an electronic scanning monopulse receiver with twice the swing angle of the antenna.

Next, the transmission state will be described using FIGS. 5 and 7. Transmission source output 41 (X4.) which is the output of transmission source 40
is X41=sin[(ω/2)L]・(3
7), the first phase shifter first output 21
a (X21 a) and the first transmitting/receiving switch tube 1 output 37 a (X3.a) are X21 a = X :17 a = sin[(ω
L+θ)/21...(38)

In FIG. 7 showing the analog multiplier, the second π/2 phase shifter output 69 (
X69) is X69 = CO3 [((JJ+θ)/2] ・
(39)! @1 analog multiplier output 43 CX43'
) is the first output 37a of the first transmission/reception switch in equation (38).
(X 371L ) and the second π/2 phase shifter output 69 (X69) of equation (39), so X43 =
5in(ωL+θ)−(40), and the first transmission output cuff 1a (X7.
a) is emitted towards the target.

X 71 a = 5in (ωL 10) ・(
41) Similarly, the second transmission cuff 3 is transmitted from the second antenna 76.
A is emitted toward the target.

Xtsa=5in(alt-〇)
- (42) From equations (41) and (42), the transmission signal is radiated in a direction angularly shifted by β (radian) from the center, as shown by equation (6).

As explained above, by using an analog multiplier on the transmitting side and an analog frequency divider on the receiving side, it is possible to continuously swing the antenna beam greatly during transmission and reception even if the spacing between antenna elements is widened. I understand.

(Example) Embodiments of the present invention will be described below with reference to drawing □.

FIG. 1 shows the reception state of the high frequency section in the embodiment, and FIG. 5 shows the transmission state.
2, and a second transmitting/receiving module including a second antenna 76, a second analog frequency divider 56, a second analog multiplier 44, etc.

First, a detailed explanation will begin with the block diagram shown in FIG. 1 showing the reception state. However, in FIG. 1, the portions used only in the transmission state are indicated by dotted lines.

The PA1 reception signal 71, which is a reflected wave from the target, is received by the first antenna 74, becomes the tIS1 antenna output cuff 5, and is input to the third transmission/reception switch 46, and now,
Since the switch 46 is in the receiving state, the output of the third transmit/receive switch 46 becomes the third transmit/receive switch 4 second output 47b, is input to the first analog frequency divider 54, and is input to the first analog frequency divider 54. The output will be 55. Since the 11 transmission/reception switch 36 is in the receiving state, the output of the 1st transmission/reception switch 36 becomes the 1st transmission/reception switch 4 2nd output 37b,
The signal is input to the phase shifter 20, undergoes phase modulation by the signal of the phase generator first output 29, becomes the 11 phase shifter second output 21b, and is input to the monopulse comparator 24. Note that the configuration for obtaining the phase generator first output 29 can be the same as the conventional case shown in FIG. 3.

The second received signal 73, which is also a reflected wave from the target, is @2
received by the antenna 76 and sent to the second antenna output cuff 7;
This is input to the fourth transmission/reception switching device 48, and since the switching device 48 is now in the receiving state, the output of the l@4 transmission/reception switching device 48 becomes the 14 transmission/reception switching 4 second output 49b, and the second It is input to the analog frequency divider 56 and becomes the 27th analog frequency divider output 57. Since the second transmission/reception switch 38 is in the reception state, the output of the second analog frequency divider 56 becomes the second output 39b of the second transmission/reception switch 4, and the second
It is input to the phase shifter 22, receives phase modulation by the signal of the phase generator second output 31, and is input to the fjS2 phase shifter second output 23.
b, and is input to the monopulse comparator 24.

The monopulse comparator 24 calculates the sum and difference between the first phase shifter second output 21b and the second phase shifter second output 23b, and calculates the monopulse comparator sum output 25 and the monopulse comparator difference output 27. become.

Continuing, the signal processing section shown in FIG. 4 will be explained.

The monopulse comparator sum output 25 is the AGC amplifier output 59
The signal is inputted to the first intermediate frequency amplifier 82 whose amplification degree is controlled by and is amplified, and becomes the first intermediate frequency amplifier output 83. One output of the tlIJ1 medium open frequency amplifier output 83 is input to the fjS1 amplitude detector 90 and becomes the first amplitude detector output 91.

The monopulse comparator difference output 27 is the AGC amplifier output 59
The signal is inputted to a second intermediate frequency amplifier 84 whose amplification degree is controlled by , is amplified, and becomes a second intermediate frequency amplifier output 85 . One output of the second intermediate frequency amplifier output 85 is connected to the second intermediate frequency amplifier output 85.
It is input to an amplitude detector 92 and becomes a second amplitude detector output 93.

In the magnitude discriminator 80, the first amplitude detector output 91 and f52
The amplitude detector output 93 is inputted, the larger of the two is outputted as the magnitude discriminator output 81, inputted to the AGC amplifier 58 and becomes the AGC amplifier output 59, and the first intermediate frequency amplifier 82 and Second intermediate frequency amplifier 84
is input.

As a result, the larger output of the first intermediate frequency amplifier 83 or the second intermediate frequency amplifier 85 is controlled to be constant.

The other output of the first intermediate frequency amplifier output 83 is a second output of the first intermediate frequency amplifier output 83.
A channel switching signal 95 that is input to the multiplication demodulator 34 together with the other output of the intermediate frequency amplifier output 85 and is the other output of the magnitude discriminator 80 is input to the first amplitude detector output 91 and the second detector output 93. are compared, and which signal is larger is input to the multiplication demodulator 34. This multiplication demodulator 34 functions equivalent to using the output 83.85 with a larger amplitude as a reference signal and synchronously detecting the output with a smaller amplitude. In the multiplication demodulator 34, the equation (35
) or a multiplication operation corresponding to equation (36) is performed to obtain an angular error signal of elevation angle or azimuth angle which is an output proportional to the angular difference between the target position (angle) and the pointing direction (angle) of the antenna. The error angle output 35 is used as a signal for locating and tracking the target position.

Next, FIG. 5, which is an explanatory diagram of the transmission state, will be explained in detail. However, in the PJ5 diagram, the parts that are used only in the reception state are indicated by dotted lines.

The transmitting source output 41 produced by the transmitting source 40 is input to the monopulse comparator 24 and passes through the path opposite to the receiving state to become the transmitting source first output 26 and the transmitting source fi2 output 30. The transmitting source first output 26 is connected to the first phase generator 20 in the first phase shifter 20.
The signal of the output 29 is phase modulated and the first phase shifter first
Since it is in the transmitting state, the first output 21a of the first phase shifter input to the first transmitting/receiving switch 36 becomes the output 21a.
becomes the first output 37a of the first transmission/reception switching 4, is input to the first analog multiplier 42 (having a multiplication ratio that is the reciprocal of the frequency division ratio of the frequency divider 54), is multiplied, and becomes the first analog multiplier output 43. The signal passes through the third transmitting/receiving switch 46 and the third transmitting/receiving switch 46
The transmission/reception switching 4 becomes the first output 47a, and the first antenna 7
4 to the target as the first transmitting cuff 1a.

Similarly, the second output 30 of the transmission source is phase modulated in the second phase shifter 22 using the signal of the second output 31 of the phase generator to become the first output 23a of the second phase shifter, and is now in the transmission state. Therefore, the second phase shifter first output 23a input to the second transmission/reception switching device 38 is the second transmission/reception switching 4 first output 39a.
is input to the second analog multiplier 44 (having a multiplication ratio that is the reciprocal of the frequency division ratio of the frequency divider 56), is multiplied, becomes the second analog multiplier output 45, and is output to the fourth transmission/reception switch 48.
It passes through and becomes the 4th transmission/reception switching 4 1st output 49a,
The signal is transmitted from the second antenna 76 to the target as the second transmitting cuff 3a.

The analog frequency divider (
54 or 56), an example will be explained using FIG. Third transmission/reception switch! @2 output 47b is expressed by formula (10)
, (11) and (12), the first π/2 phase shifter output 67 is a signal with a frequency of 1/2 of the third transmission/reception switching 4 second output 47b (X<ya). with the first
It is mixed in the mixer 50 to become the first mixer output 51, which is input to the low-pass filter 78, where the high-frequency component is passed through to become the low-pass filter output cuff 9, and then to the first power divider. 6
0, one output becomes the first analog divider output 55 (XSS) and the other output @
1 power divider output 61 (X61), 1st π
/2 phase shifter 66 and the first π/2 phase shifter output 6
7 (X6t), and by configuring such a negative feedback loop, the amplitude information is accurate while maintaining the frequency and phase synchronization relationship as shown by the relationships in equations (10), (11), and (12). In other words, the first analog divider output 55 (X55) is output.

An example of the analog multiplier (42 or 44) used in the embodiment of FIG. 5 will be explained using the block diagram of FIG. The first transmission/reception switching 4 first output 37a is the second
In the power divider 62, one output becomes the 12 power divider first output 63 (X63), the other output becomes the second power divider second output 65, and the f52·π/2 phase shifter 6
8, the phase is delayed by π/2 and becomes the second π/2 phase shifter output 69 (X6.), which is mixed with the second power divider second output 65 in the second mixer 52, As shown in equations (13), (14), and (15), the first analog multiplier output 43 (X, 3) accurately maintains the frequency and phase relationship between the input and output.

A supplementary explanation of the example will be provided.

(stomach) ! @ In Figure 6, the frequency division ratio is set to 1/2, but other frequency division ratios may be used, for example, 1/4.

(b) In FIG. 7, the multiplication ratio is 2, but other multiplication ratios, for example 4, may be used.

(A) In Fig. 7, an analog multiplier is used for explanation, but since it is a transmission system, it is not necessary to use an analog system = (Effects of the Invention) Electronic scanning monopulse receiver and the receiver according to the present invention According to electronic scanning monopulse radar using , the following effects can be obtained.

(b) Even if the spacing between the antenna elements, which are the constituent units of an electronic scanning antenna, is widened, the swing of the antenna can be greatly increased during transmission and reception.

(b) Since the number of transmitting/receiving modules, which are the constituent units of the electronic scanning antenna, can be reduced, it is extremely economical and highly reliable.

(A) If an analog phase shifter is used as the phase shifter (20 or 22), it will not have the quantization error inherent in a digital phase shifter, so even four transmitting/receiving modules can adjust the elevation angle and azimuth. It can be configured as a small monopulse radar for tracking, and is extremely effective as a radar for mounting on missiles, which requires small size and light weight.

(2) If you use an angular velocity detector attached to the projectile, even if the projectile oscillates, as shown in Figure 3,
With a small number of antenna elements, the antenna
The beam can be directed towards one target.

[Brief explanation of the drawing]

FIG. 15 is a block diagram showing the reception state of the high frequency section in an embodiment of the electronic scanning monopulse receiver and electronic scanning monopulse radar according to the present invention, and FIG. 2 is a block diagram showing the reception state.
Fig. S1 is an explanatory diagram showing the relationship between the signal from the target and the directivity angle of the antenna to explain the embodiment, Fig. 3 is an explanatory diagram showing a conventional example of an electronic scanning monopulse antenna, and Fig. f54 is an explanatory diagram of the embodiment. FIG. 5 is a block diagram of the signal processing section; FIG. 5 is a block diagram of the high frequency section in the embodiment and shows the transmission state; FIG. 6 is a block diagram of the analog frequency divider used in the embodiment; FIG. 7 is a block diagram of the analog frequency divider used in the embodiment. FIG. 2 is a block diagram of an analog multiplier used in the embodiment. 20...First phase shifter, 21...First phase shifter output (
X, ), 21a-first phase shifter first output, 2 l b...
・First phase shifter second output (X z+bay X z+bb
), 22... Second phase shifter, 23... Second phase shifter output (X23), 23a... Second phase shifter first output, 23
b...Second phase shifter second output (X2sbat X2zb
b), 24... Monopulse comparator, 25... Monopulse comparator sum output (X2.), 26... Transmission source first output (X26), 27... Monopulse comparator difference output (X 27), 28... Phase generator, 29... Phase generator first output, 30... Transmission source second output, 31...
・Phase generator @ 2 outputs, 32...tangent corrector, 33・
...Tangential corrector output, 34...Multiply zero demodulator, 35...
・Error angle output (X, s), 36...tjS1 transmission/reception switch, 37a-1st transmission/reception switching 4 1st output (X:
+7a), 37b... 1st transmission/reception switching 4 2nd output (
X *ta), 38... second transmission/reception switch, 39a
...Second transmission/reception switching 4 first output, 39b...second
Transmission/reception switching 4 second output, 40... transmission source, 41...
- Transmission source output (X4+), 42...first analog multiplier, 43...first analog multiplier output (X43), 4
4... Second analog multiplier, 45... PJ2 analog multiplier output, 46... Third transmission/reception switch, 47a
...Third transmission/reception switch pA1 output, 47b...f
J&3 transmission/reception switching 4 2nd output (X4□b), 48...
- Fourth transmission/reception switch, 49a... Fourth transmission/reception switch 4 first output, 49b... Fourth transmission/reception switch rjS2
Output, 50...first mixer, 51...f:lS1 mixer output, 52...PIS2 mixer, 54...first
Analog frequency divider, 55...first analog frequency divider output (
Xss), 56... second analog frequency divider, 57...
2nd analog frequency divider output (Xst), 58...AGC
Amplifier, 59... AGC amplifier output, 60... First
Power divider, 61...first power divider output (X61)
, 62... Second power divider, 63... Second power divider first output, 65... Second power divider second output, 66
... 1st/π/2 phase shifter, 67... 1st/π/2 phase shifter output (X 67), 68... 2nd/π/2 phase shifter, 69... fjS2・π/2 phase shifter output ('X, 9
), 71... fjS1 received signal, 71 a-p, 1
Transmission output (X 7.a), 73... second received signal,
73 a-Pt52 transmission output (xtia), 74...
First antenna, 75...First antenna output (X 7s
), 76... Second antenna, 77... ptS2 antenna output (X 7?), 78... Low pass, filter,
79...Low pass filter output (X 7s), 80...
- Size discriminator, 81... Size discriminator output, 82...
First intermediate frequency amplifier, 83... First intermediate frequency amplifier output, 84... Second intermediate frequency amplifier, 85... Second intermediate frequency amplifier output, 86... Angular velocity detector, 87...
- Angular velocity detector output, 88... Integrator, 8... Integrator output, 90... First amplitude detector, 91... First
Amplitude detector output (X91), 92... Second amplitude detector, 93... Second amplitude detector output (X, 3), 95...
・Channel switching signal.

Claims (2)

[Claims] (1) In an electronic scanning monopulse receiver having multiple antennas, a first frequency-divided signal is obtained by dividing the signal received by one antenna using a frequency divider, and a signal received by another antenna is divided by a frequency divider. The phase of the frequency-adjusted second frequency-divided signal is adjusted by a phase shifter and added to a monopulse comparator, and the monopulse comparator converts it into a sum signal and a difference signal,
The sum signal and the difference signal are amplitude-detected, and a magnitude discriminator discriminates the magnitude of the two amplitude detection outputs, and the large signal is used as a signal for automatic gain control, and the sum signal or the difference signal is detected. The angular error signal is obtained by holding the larger output signal constant and multiplying the sum signal and the difference signal using a channel switching signal indicating which of the sum signal and the difference signal is larger in a multiplier. An electronic scanning monopulse receiver characterized by taking out. (2) In an electronic scanning monopulse radar having multiple transceiver modules, the first frequency-divided signal obtained by dividing the signal received by one antenna by a frequency divider and the signal received by another antenna are divided by a frequency divider. The phase of the frequency-divided second frequency-divided signal is adjusted using a phase shifter and added to a monopulse comparator, where the monopulse comparator converts the sum signal and the difference signal into a sum signal and a difference signal, and the sum signal and the difference signal are subjected to amplitude detection, respectively. Then, in a magnitude discriminator, these two amplitude detection outputs are distinguished in magnitude, and the larger signal is used as a signal for automatic gain control, and the output signal of the larger of the sum signal or difference signal is kept constant. , an electronic scanning monopulse receiver capable of extracting an angular error signal by performing a multiplication operation on the sum signal and the difference signal in a multiplier using a channel switching signal indicating which of the sum signal and the difference signal is larger. An electronic scanning monopulse radar having a transmitting system in which the phase shifter is commonly used in the transmitting system, and further, the transmitting system transmits data using a multiplier having a multiplication ratio that is the reciprocal of the frequency division ratio of the frequency divider.