JPS62290353A - Switching power source - Google Patents
Switching power sourceInfo
- Publication number
- JPS62290353A JPS62290353A JP61131850A JP13185086A JPS62290353A JP S62290353 A JPS62290353 A JP S62290353A JP 61131850 A JP61131850 A JP 61131850A JP 13185086 A JP13185086 A JP 13185086A JP S62290353 A JPS62290353 A JP S62290353A
- Authority
- JP
- Japan
- Prior art keywords
- current
- controllable switch
- transformer
- turn
- period
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 239000003990 capacitor Substances 0.000 claims abstract description 9
- 230000003534 oscillatory effect Effects 0.000 claims abstract description 5
- 238000004804 winding Methods 0.000 claims 1
- 230000007423 decrease Effects 0.000 abstract description 3
- 230000010355 oscillation Effects 0.000 abstract description 3
- 230000005284 excitation Effects 0.000 description 14
- 238000010586 diagram Methods 0.000 description 6
- 230000000694 effects Effects 0.000 description 2
- 241000750004 Nestor meridionalis Species 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000004907 flux Effects 0.000 description 1
- 238000007493 shaping process Methods 0.000 description 1
Abstract
Description
【発明の詳細な説明】
3、発明の詳細な説明
〔産業上の利用分野〕
本発明は、スイッチング電源に係り、特にマグネトロン
のような負荷を駆動する電源の、可制御スイッチのター
ンオフ損失の低減に好適なスイッチング電源に関する。Detailed Description of the Invention 3. Detailed Description of the Invention [Field of Industrial Application] The present invention relates to a switching power supply, and in particular to reducing the turn-off loss of a controllable switch in a power supply that drives a load such as a magnetron. The present invention relates to a switching power supply suitable for.
41212号公報に記載のように、高圧変圧器に加えら
れる入力周波数を周波数変換器により変化せしめてマグ
ネトロンの発振出力を変化しうるようにしていた。しか
し周波数変換器にスイッチング素子を用いた場合のスイ
ッチング損失の点について配慮されていなかった。As described in Japanese Patent No. 41212, the oscillation output of the magnetron can be changed by changing the input frequency applied to the high voltage transformer using a frequency converter. However, no consideration was given to switching loss when switching elements are used in frequency converters.
可制御スイッチのオン期間に変圧器の励磁インダクタン
スにエネルギーを蓄えると共に負荷に電力を供給し、可
制御スイッチのオフ期間にこの蓄えた励磁エネルギーを
負荷に供給するフォワードコンバータでは、励磁インダ
クタンスに蓄えるエネルギーを大きくすると、可制御ス
イッチに流れる電流は励磁電流と負荷電流の和になるた
め大きくなり、ターンオフ損失が大きくなると共にオフ
時に可制御スイッチに印加する電圧が過大となるという
問題がある。In a forward converter, energy is stored in the excitation inductance of the transformer during the ON period of the controllable switch and supplies power to the load, and this stored excitation energy is supplied to the load during the OFF period of the controllable switch. If , the current flowing through the controllable switch becomes the sum of the excitation current and the load current, which increases the turn-off loss, and the voltage applied to the controllable switch when turned off becomes excessive.
本発明の目的は、可制御スイッチのターンオフ損失の低
減とターンオフ時に可制御スイッチに印加する電圧を低
く抑えることにある。An object of the present invention is to reduce the turn-off loss of a controllable switch and to keep the voltage applied to the controllable switch low during turn-off.
可制御スイッチのオン期間に可制御スイッチに流れる電
流は、変圧器の励磁電流と、2次回路電流の和である。The current flowing through the controllable switch during the on-period of the controllable switch is the sum of the transformer's excitation current and the secondary circuit current.
2次回路の電流は変圧器のリーケージインダクタンスと
二次側コンデンサ及び負荷の定数で決まるが、リーケー
ジインダクタンスとコンデンサの値を適切に選定するこ
とにより2次回路電流を振動的にすることが可能である
。そこで、2次回路電流が振動的になるように回路定数
を選定すると共に可制御スイッチのオン期間を上記振動
周期の半周期以上にすることにより、上記目的が達成さ
れる。The current in the secondary circuit is determined by the leakage inductance of the transformer and the constants of the secondary side capacitor and load, but it is possible to make the secondary circuit current oscillating by appropriately selecting the values of the leakage inductance and capacitor. be. Therefore, the above object is achieved by selecting the circuit constants so that the secondary circuit current becomes oscillatory, and by making the ON period of the controllable switch longer than half the oscillation period.
可制御スイッチのオン期間の2次回路電流を振動波形に
する事により、従来ターンオフ時に可制御スイッチに流
れていた電流を小さくする事ができ、それにより可制御
スイッチのターンオフ損失と可制御スイッチの印加電圧
を小さくする。By making the secondary circuit current during the on-period of the controllable switch into an oscillating waveform, the current that conventionally flows through the controllable switch during turn-off can be reduced, thereby reducing the turn-off loss of the controllable switch and the controllable switch's turn-off loss. Reduce the applied voltage.
本発明の一実施例を第1図に示す0図に於いて1は直流
電源、2は変圧器、3は可制御スイッチ。An embodiment of the present invention is shown in FIG. 1. In FIG. 0, 1 is a DC power source, 2 is a transformer, and 3 is a controllable switch.
4は制御回路、5はダイオード、6はコンデンサ、7は
負荷である。実施例の動作を第2図の等価回路と第3.
4.5図の動作波形を用いて説明する。4 is a control circuit, 5 is a diode, 6 is a capacitor, and 7 is a load. The operation of the embodiment is shown in the equivalent circuit shown in Fig. 2 and in Fig. 3.
This will be explained using the operating waveforms shown in Figure 4.5.
第2図においてトランジスタ8のオン期間に直流電圧1
が励磁インダクタンス9に印加され、励磁電流ILが流
れ、二次側の直列共振回路を構成するコンデンサ6、リ
ーケージインダクタンス10及び負荷7を介し負荷電流
IONが流れ、励磁電流エムと共振電流IONの和とし
てトランジスタ8にトランジスタ電流Itが流れ次式で
表わせる。In FIG. 2, a DC voltage of 1 is applied during the ON period of transistor 8.
is applied to the excitation inductance 9, an excitation current IL flows, a load current ION flows through the capacitor 6, the leakage inductance 10, and the load 7 that constitute the secondary side series resonant circuit, and the sum of the excitation current Em and the resonance current ION is A transistor current It flows through the transistor 8 and can be expressed by the following equation.
Ir=It、+IoN
第3図、第4図は、電源電圧変動時の励磁電流IL及び
トランジスタ電流Itの動作波形を示す。Ir=It, +IoN FIGS. 3 and 4 show operating waveforms of the excitation current IL and the transistor current It when the power supply voltage fluctuates.
ただし、負荷7に流れる電流は振動的でない場合である
。オン期間を一定とすると、直流i!!源の電圧が上が
った場合(破線I)には励磁電流も大きく(破線■)、
下がった場合(破線■)には励磁電流も小さく(破線■
)なる。However, this is a case where the current flowing through the load 7 is not vibrating. If the on period is constant, the DC i! ! When the source voltage increases (dashed line I), the excitation current also increases (dashed line ■),
When the current decreases (dashed line ■), the excitation current also decreases (dashed line ■).
)Become.
トランジスタ電流ITは、励磁電流ILに共振電流IO
Nが上積みされ、ターンオフ時には励磁電流が大きけれ
ば、トランジスタ電流も大きくなる。The transistor current IT is the excitation current IL and the resonance current IO.
If N is added and the excitation current is large at turn-off, the transistor current also becomes large.
トランジスタ電流において、励磁電流の上積み分となる
負荷電流IONの波形を整形することで、従来のターン
オフ時のトランジスタ電流を小さくできることを第5図
の動作波形により説明する。負荷電流を振動的にし図に
示す様にターンオフ時が最大とした場合、またはオン期
間束に最小になる様にした場合の波形を示す。負荷電流
をオン期間束に最小になる波形に変化させることでター
ンオフ時のトランジスタ電流を従来の値より小さくでき
る。Regarding the transistor current, it will be explained with reference to the operating waveforms of FIG. 5 that by shaping the waveform of the load current ION, which is an added portion of the excitation current, the transistor current at the time of conventional turn-off can be reduced. The waveforms are shown when the load current is made to oscillate and is maximized at turn-off as shown in the figure, or when it is minimized during the on-period. By changing the load current to a waveform that minimizes the on-period flux, the transistor current at turn-off can be made smaller than the conventional value.
第6図に示す様に、トランジスタ8をオン・オフデユー
ティ制御をした場合、例えば直流電源1の電圧が上がっ
た場合(破gT)ではトランジスタ8のデユーティを小
さくし、励磁電流は小さくなる(破ml)が、このよう
にデユーティ制御をした場合にも前記した事柄は成立す
る。As shown in Fig. 6, when the on/off duty of the transistor 8 is controlled, for example, when the voltage of the DC power supply 1 increases (break gT), the duty of the transistor 8 is reduced and the excitation current becomes small (break ml). ), but the above-described matters also hold true when duty control is performed in this way.
本発明の具体的な実施例を第7図の回路、第8は、負荷
となるマグネトロン7Aに安定した出力を供給する回路
であり、変圧器2のリーケージインダクタンスとコンデ
ンサ6A、6Bにより第8図に示す如く可制御スイッチ
をオンした時変正量2次回路に流れる電流を振動的にし
、ターンオフ時のトランジスタ電流波形を従来より小さ
くする。A specific embodiment of the present invention is shown in the circuit shown in FIG. As shown in FIG. 2, the current flowing through the time-varying positive secondary circuit when the controllable switch is turned on is made oscillatory, and the transistor current waveform at turn-off is made smaller than before.
本発明によれば、フォワードコンバータを用いたマグネ
トロンのような高電圧出力を得る高周波スイッチング電
源において、可制御スイッチのターンオフ時のスイッチ
ング損失と印加電圧の低減バできるので、従来より小容
量の可制御スイッチを用いることができる。According to the present invention, in a high frequency switching power supply that obtains a high voltage output such as a magnetron using a forward converter, it is possible to reduce the switching loss and applied voltage when turning off the controllable switch, so it is possible to reduce the switching loss and the applied voltage with a smaller capacity than before. A switch can be used.
第1図は本発明の一実施例の回路図、第2図は第1図回
路の等価回路図、第3図、第4図は第1図の動作波形図
、第5図、第6図は第2図の動作波形図、第7図は本発
明の他の実施例の回路図、第8図は第7図の動作波形図
である。
1・・・膚ジ左雷糧 9・・・亦;鼎 3・・・可伽1
例スI・ソ壬4・・・制御回路、5・・・ダイオード、
6・・・コンデンサ。
7・・・負荷、9・・・励磁インダクタンス、10・・
・リーケージインダクタンス。Fig. 1 is a circuit diagram of an embodiment of the present invention, Fig. 2 is an equivalent circuit diagram of the circuit shown in Fig. 1, Figs. 3 and 4 are operational waveform diagrams of Fig. 1, and Figs. 5 and 6. 2 is an operating waveform diagram of FIG. 2, FIG. 7 is a circuit diagram of another embodiment of the present invention, and FIG. 8 is an operating waveform diagram of FIG. 7. 1...Skin left thunder food 9...亦;鼎 3...Kaka 1
Example 4: Control circuit, 5: Diode,
6... Capacitor. 7...Load, 9...Exciting inductance, 10...
・Leakage inductance.
Claims (1)
列に接続され、該変圧器の一次側はダイオードとコンデ
ンサ及び負荷で構成されるスイッチング電源において、
変圧器のリーケージインダクタンスとコンデンサにより
可制御スイッチのオン期間に変圧器の2次回路に流れる
電流波形を振動的になるようにしたことを特徴とするス
イッチング電源。1. A switching power supply in which a DC power supply, the primary winding of a transformer, and a controllable switch are connected in series, and the primary side of the transformer is composed of a diode, a capacitor, and a load,
A switching power supply characterized in that the leakage inductance and capacitor of the transformer cause the current waveform flowing in the secondary circuit of the transformer to become oscillatory during the ON period of the controllable switch.
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP61131850A JPS62290353A (en) | 1986-06-09 | 1986-06-09 | Switching power source |
US07/031,533 US4777575A (en) | 1986-03-25 | 1987-03-23 | Switching power supply |
KR1019870002646A KR900004448B1 (en) | 1986-03-25 | 1987-03-23 | Switching power supply |
EP87104305A EP0239072B1 (en) | 1986-03-25 | 1987-03-24 | Switching power supply |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP61131850A JPS62290353A (en) | 1986-06-09 | 1986-06-09 | Switching power source |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS62290353A true JPS62290353A (en) | 1987-12-17 |
Family
ID=15067574
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP61131850A Pending JPS62290353A (en) | 1986-03-25 | 1986-06-09 | Switching power source |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS62290353A (en) |
-
1986
- 1986-06-09 JP JP61131850A patent/JPS62290353A/en active Pending
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