JPS6157728B2 - - Google Patents
Info
- Publication number
- JPS6157728B2 JPS6157728B2 JP55052465A JP5246580A JPS6157728B2 JP S6157728 B2 JPS6157728 B2 JP S6157728B2 JP 55052465 A JP55052465 A JP 55052465A JP 5246580 A JP5246580 A JP 5246580A JP S6157728 B2 JPS6157728 B2 JP S6157728B2
- Authority
- JP
- Japan
- Prior art keywords
- transistor
- circuit
- terminal
- voltage
- oscillation
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 230000010355 oscillation Effects 0.000 description 26
- 239000003990 capacitor Substances 0.000 description 10
- 238000000034 method Methods 0.000 description 5
- 238000010586 diagram Methods 0.000 description 3
- 230000008878 coupling Effects 0.000 description 2
- 238000010168 coupling process Methods 0.000 description 2
- 238000005859 coupling reaction Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 230000003321 amplification Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 239000004065 semiconductor Substances 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1231—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device the amplifier comprising one or more bipolar transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1206—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device using multiple transistors for amplification
- H03B5/1212—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device using multiple transistors for amplification the amplifier comprising a pair of transistors, wherein an output terminal of each being connected to an input terminal of the other, e.g. a cross coupled pair
- H03B5/1215—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device using multiple transistors for amplification the amplifier comprising a pair of transistors, wherein an output terminal of each being connected to an input terminal of the other, e.g. a cross coupled pair the current source or degeneration circuit being in common to both transistors of the pair, e.g. a cross-coupled long-tailed pair
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1206—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device using multiple transistors for amplification
- H03B5/1221—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device using multiple transistors for amplification the amplifier comprising multiple amplification stages connected in cascade
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1237—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator
- H03B5/124—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator the means comprising a voltage dependent capacitance
- H03B5/1243—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator the means comprising a voltage dependent capacitance the means comprising voltage variable capacitance diodes
Description
【発明の詳細な説明】
本発明はトランジスタとコイルを用いた発振器
に関し、特に電子同調方式を採用したスーパヘテ
ロダイン受信機の局部発振器に最適な発振回路に
関するものである。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an oscillator using a transistor and a coil, and more particularly to an oscillation circuit optimal for a local oscillator of a superheterodyne receiver employing an electronic tuning method.
一般のスパーヘテロダイン受信機の電子同調方
式としては同調回路に可変容量ダイオードを使用
している。 The electronic tuning method of a general superheterodyne receiver uses a variable capacitance diode in the tuning circuit.
可変容量ダイオードはその特性として、印加さ
れる交流信号の振幅が大きいと発振波形が歪むた
めにその電圧は200ｍVrms程度以下に制限され
る。このため、電子同調回路としては、これまで
一般の受信機で用いられてきたコイルのインダク
タンスを可変とするμ同調回路方式は発振電圧が
大きいために同いることができず、トランジスタ
差動増幅器のベース回路に同調回路を設けた低レ
ベル発振器が作られている。 As a characteristic of the variable capacitance diode, when the amplitude of the applied alternating current signal is large, the oscillation waveform is distorted, so the voltage is limited to about 200 mVrms or less. For this reason, as an electronic tuning circuit, the µ tuning circuit system that has been used in general receivers, which makes the coil inductance variable, cannot be used because the oscillation voltage is large, and the transistor differential amplifier cannot be used as an electronic tuning circuit. Low-level oscillators have been created with a tuned circuit in the base circuit.
このような従来の電子同調方式の局部発振器に
おいては、発振器の発振特性は満足できるもので
あるが、同調回路を外付けするための外部端子が
２個特別に必要であり、外部に取出すピン数に制
限のある集積回路では特に問題となつている。 In such a conventional electronically tuned local oscillator, the oscillation characteristics of the oscillator are satisfactory, but two external terminals are specially required to connect the tuning circuit externally, and the number of external pins is limited. This is a particular problem for integrated circuits that have limited capacity.
第１図は従来の電子同調方式の局部発振器の回
路図である。トランジスタ１，２で構成される差
動増幅器の共通エミツタは定電流源３に接続さ
れ、各々のコレクタは抵抗４，５を通して電圧基
準ダイオード９およびトランジスタ８から成る基
準電圧電源に導かれる。一方、差動増幅器は正帰
還ループを形成し、トランジスタ１のコレクタか
ら抵抗６を通して、トランジスタ２のベースに、
且つトランジスタ２のコレクタから抵抗７を通し
てトランジスタ１のベースに接続される。他方ト
ランジスタ１，２のベースには共振コイル１０、
可変容量ダイオード１１（結合コンデンサおよび
可変容量ダイオードの直流制御電圧回路は省略）
およびバイパス用コンデンサ１２よりなる並列共
振回路が接続され、この共振周波数で端子Ｂに生
ずる発振電圧の周波数が決定される。この回路で
は端子Ａ，Ｂ間に発生する発振電圧は、定電流源
３の電流値および負荷抵抗４，５および帰還抵抗
６，７および共振回路のＱによつて決定され、負
荷抵抗４，５あるいは定電流源３の定電流値を適
当に選らぶことにより容易に発振電圧を小さく設
定できる。 FIG. 1 is a circuit diagram of a conventional electronically tuned local oscillator. The common emitter of the differential amplifier composed of transistors 1 and 2 is connected to a constant current source 3, and the collector of each is led through resistors 4 and 5 to a reference voltage power supply composed of a voltage reference diode 9 and a transistor 8. On the other hand, the differential amplifier forms a positive feedback loop, from the collector of transistor 1 through resistor 6 to the base of transistor 2.
It is also connected from the collector of transistor 2 to the base of transistor 1 through resistor 7. On the other hand, a resonant coil 10 is provided at the base of the transistors 1 and 2.
Variable capacitance diode 11 (coupling capacitor and variable capacitance diode DC control voltage circuit are omitted)
A parallel resonant circuit consisting of a bypass capacitor 12 and a bypass capacitor 12 is connected, and the frequency of the oscillation voltage generated at terminal B is determined by this resonant frequency. In this circuit, the oscillation voltage generated between terminals A and B is determined by the current value of constant current source 3, load resistances 4 and 5, feedback resistances 6 and 7, and Q of the resonant circuit. Alternatively, by appropriately selecting the constant current value of the constant current source 3, the oscillation voltage can be easily set to a small value.
一方、この発振器を半導体集積回路で構成する
場合を考えると、端子Ａ，Ｂの２つの端子が同調
回路を取付けるための外部引出し端子として必要
である。この事は外部に取出すピン数に制限のあ
る集積回路では大きな問題となる。そこで、この
端子数を減す方法として発振特性に本質的には影
響のない１方の端子（こゝでは端子Ａ）を例えば
他の回路への基準電圧の供給端子として併用する
などの要求が生じる。しかしながらこの発振回路
において端子Ａの直流電圧ＶAは基準電源電圧を
ＶB、トランジスタ１，２の直流電流増幅率をｈF
Ｅ（トランジスタ１，２で等しいとする）、負荷抵
抗４，５をそれぞれR4，R5とし、帰還抵抗６，
７をそれぞれR6，R7とし、且つ、R4＝R5および
R6＝R7とすると(1)式で表わされる。 On the other hand, if this oscillator is constructed from a semiconductor integrated circuit, two terminals A and B are required as external lead-out terminals for attaching a tuning circuit. This becomes a big problem in integrated circuits where the number of pins that can be taken out to the outside is limited. Therefore, as a way to reduce the number of terminals, there is a demand for one terminal (terminal A in this case) that does not essentially affect the oscillation characteristics to be used, for example, as a terminal for supplying reference voltage to other circuits. arise. However, in this oscillation circuit, the DC voltage V A at terminal A is the reference power supply voltage V B , and the DC current amplification factor of transistors 1 and 2 is h F
E (assuming transistors 1 and 2 are equal), load resistances 4 and 5 are R 4 and R 5 , respectively, and feedback resistances 6 and
7 as R 6 and R 7 respectively, and R 4 = R 5 and
When R 6 =R 7 , it is expressed by equation (1).
ＶA＝ＶB−Ｉｏ／２（R4＋Ｒ６／ｈＦＥ） ……(1)
これから明らかなように端子Ａの直流電圧ＶA
は、基準電圧電源電圧ＶBからトランジスタの特
性変動の影響を受ける(1)式の第２項の電圧成分を
差引いた形で与えられる。従つて、このまゝの形
でＶAを基準電圧として用いることはできない。V A = V B - Io/2 (R 4 + R 6 /h FE ) ...(1) As is clear from this, the DC voltage V A at terminal A
is given by subtracting the voltage component in the second term of equation (1), which is affected by variations in transistor characteristics, from the reference voltage power supply voltage V B . Therefore, V A cannot be used as a reference voltage in this form.
又、バイパスコンデンサ１２がない場合には端
子Ａには端子Ｂに発生する発振電圧と逆相の発振
電圧が生じ、そのまゝ端子Ａの電圧ＶAを基準電
圧として用いることができない。 Furthermore, if the bypass capacitor 12 is not provided, an oscillation voltage that is opposite in phase to the oscillation voltage generated at the terminal B is generated at the terminal A, and the voltage V A at the terminal A cannot be used as it is as a reference voltage.
本発明の目的は、かゝる電子同調方式を用いた
局部発振器の発振特性の向上を計り、且つ同調回
路取付け用として必要な２つの端子のうちの１つ
を他の目的と共用できるようにした発振器を提供
することにある。 The purpose of the present invention is to improve the oscillation characteristics of a local oscillator using such an electronic tuning method, and also to make it possible to use one of the two terminals required for attaching the tuning circuit for other purposes. The purpose of this invention is to provide an oscillator with
本発明の発振回路は、エミツタが共通に結合さ
れた第１、第２のトランジスタの共通エミツタに
バイアス電流供給のための定電流源が接続され、
該第１、第２のトランジスタのそれぞれのコレク
タに第１、第２の負荷抵抗が基準電圧電源との間
に各々接続され、前記第１のトランジスタのコレ
クタは第１の帰還抵抗を通し、さらに第２のレベ
ルシフト回路を介して第２のトランジスタのベー
スに接続され、又前記第２のトランジスタは第２
の帰還抵抗を通しさらに第１のレベルシフト回路
を介して第１のトランジスタのベースに接続さ
れ、且つ、前記第２の帰還抵抗の前記第２のトラ
ンジスタと接続された端子の他端子を前記基準電
圧電源と接続し、該基準電圧電源と前記第１の帰
還抵抗の前記第１のトランジスタと接続された端
子の他端子との間に発振コイルを含む同調回路を
接続して構成される。 In the oscillation circuit of the present invention, a constant current source for supplying a bias current is connected to the common emitters of the first and second transistors whose emitters are commonly coupled,
First and second load resistors are respectively connected between the collectors of the first and second transistors and a reference voltage power supply, the collectors of the first transistors are connected through a first feedback resistor, and is connected to the base of the second transistor via a second level shift circuit, and the second transistor is connected to the base of the second transistor.
is connected to the base of the first transistor through the feedback resistor and further via the first level shift circuit, and the other terminal of the second feedback resistor connected to the second transistor is connected to the reference. A tuning circuit including an oscillation coil is connected between the reference voltage power source and the other terminal of the first feedback resistor connected to the first transistor.
次に、第２図を用いて本発明の一実施例による
発振回路を説明する。 Next, an oscillation circuit according to an embodiment of the present invention will be explained using FIG.
第１、第２のトランジスタ１，２で構成される
差動増幅器の共通エミツタは定電流源３に接続さ
れ、各々のコレクタは第１、第２の負荷抵抗４，
５を通して、電圧基準ダイオードおよびトランジ
スタ８から成る基準電圧電源に導かれる。一方、
差動増幅器は正帰還ループを構成し、第１のトラ
ンジスタ１のコレクタから第１の帰還抵抗６を通
り、さらにトランジスタ１４および抵抗１６で構
成されるエミツタホロワによるレベルシフト回路
を介して第２のトランジスタ２のベースに、且つ
第２のトランジスタ２のコレクタから第２の帰還
抵抗７を通り、さらにトランジスタ１３および抵
抗１５で構成されるエミツタホロワによるレベル
シフト回路を介して第１のトランジスタのベース
に接続される。更に第２の帰還抵抗７の第２のト
ランジスタ２のコレクタと接続された端子の他端
子（レベルシフト用トランジスタ１３のベースと
同じ、図で端子Ａとして示す。）を前記基準電源
と接続し、該基準電源と第１の帰還抵抗６の第１
のトランジスタ１のコレクタと接続された端子の
他端子（レベルシフト用トランジスタ１４のベー
スと同じ、図で端子Ｂとして示す。）との間に発
振コイル１０、可変容量ダイオード１１（結合コ
ンデンサおよび可変容量ダイオードの直流制御電
圧回路は省略）およびバイパス用コンデンサ１２
よりなる並列共振回路が接続され、この共振周波
数で端子Ｂに生ずる発振電圧の周波数が決定され
る。又、発振電圧は定電流源３の電流値および負
荷抵抗４，５および帰還抵抗６，７および共振回
路のＱによつて決定され、負荷抵抗４，５あるい
は定電流源３の電流値を適当に選らぶことにより
容易に発振電圧を小さく設定できる。 The common emitter of the differential amplifier composed of the first and second transistors 1 and 2 is connected to a constant current source 3, and the collector of each is connected to the first and second load resistors 4,
5 to a reference voltage supply consisting of a voltage reference diode and a transistor 8 . on the other hand,
The differential amplifier constitutes a positive feedback loop, passing from the collector of the first transistor 1 through the first feedback resistor 6, and further through a level shift circuit with an emitter follower composed of a transistor 14 and a resistor 16 to the second transistor. 2, from the collector of the second transistor 2, through the second feedback resistor 7, and further connected to the base of the first transistor via a level shift circuit using an emitter follower composed of a transistor 13 and a resistor 15. Ru. Further, the other terminal of the second feedback resistor 7 connected to the collector of the second transistor 2 (same as the base of the level shifting transistor 13, shown as terminal A in the figure) is connected to the reference power supply, the reference power supply and the first feedback resistor 6.
An oscillation coil 10, a variable capacitance diode 11 (a coupling capacitor and a variable capacitor diode DC control voltage circuit is omitted) and bypass capacitor 12
A parallel resonant circuit consisting of the following is connected, and the frequency of the oscillation voltage generated at terminal B is determined by this resonant frequency. The oscillation voltage is determined by the current value of the constant current source 3, the load resistors 4, 5, the feedback resistors 6, 7, and the Q of the resonant circuit. By selecting , the oscillation voltage can be easily set to a small value.
即ち、上述のように本発明の発振器は電子同調
方式の局部発振器として、基本的な回路は前記の
従来例と同じであり、従つて電子同調方式の局部
発振器として要求される低レベル発振器としての
性能を満足している。 That is, as mentioned above, the oscillator of the present invention is an electronically tuned local oscillator, and the basic circuit is the same as that of the conventional example, so it is suitable as a low-level oscillator required as an electronically tuned local oscillator. I am satisfied with the performance.
ところで本発明の発振器においては、上述のよ
うに端子Ａは直接基準電圧電源に接続されている
のでその端子電圧ＶAは常に基準電圧電源電圧ＶB
に等しい。しかもこの基準電圧は電圧基準ダイオ
ード９を適当に選ぶことにより、電圧値の絶対値
又はその温度特性を比較的自由に設定できる。従
つて従来の回路では変動が大きくて基準電圧電源
として使用できなかつた端子Ａの電圧ＶAは、基
準電圧電源として本発振器とは別の回路へ自由に
供給できることになる。即ち、発振器の同調回路
を外付けするために必要な２つの端子（図のＡ，
Ｂ）のうちの１つ（図のＡ）が基準電圧電源端子
と共用される結果外付け用の端子は実質的には１
つで良いことになる。このことは、特に外部に取
出すピン数に制限のある集積回路において大きな
特点となる。さらに発振特性の要求がきびしくな
く、本実施例で示した基準電圧電源が必要でない
場合にはこの端子Ａは直接電源Vcc端子に接続す
ることになり一層簡単化されることになる。 By the way, in the oscillator of the present invention, as mentioned above, the terminal A is directly connected to the reference voltage power supply, so the terminal voltage V A is always the reference voltage power supply voltage V B
be equivalent to. Furthermore, by appropriately selecting the voltage reference diode 9, the absolute value of the voltage value or its temperature characteristics can be relatively freely set. Therefore, the voltage V A at terminal A, which could not be used as a reference voltage power source due to large fluctuations in the conventional circuit, can be freely supplied to a circuit other than the present oscillator as a reference voltage power source. In other words, the two terminals (A and A in the figure) necessary for externally connecting the oscillator tuning circuit
B) One of the terminals (A in the figure) is shared with the reference voltage power supply terminal, and as a result, the number of external terminals is essentially one.
That's a good thing. This is a major feature, especially in integrated circuits where the number of pins that can be taken out to the outside is limited. Furthermore, if the requirements for oscillation characteristics are not severe and the reference voltage power supply shown in this embodiment is not required, this terminal A can be directly connected to the power supply Vcc terminal, which further simplifies the process.
更に、本発明の発振器においては、上述のよう
に端子Ａは直接基準電圧電源に接続されるので、
交流的には近似的に接地されていると見ることが
できる。従つて発振特性の要求がきびしくない場
合は端子Ａに接続されているバイパス用のコンデ
ンサを省略しても差支えない。又、省略した場合
に前記の従来の発振器では問題となつていた端子
Ｂに発生する発振電圧と逆相の発振電圧が端子Ａ
に生じるということもない。 Furthermore, in the oscillator of the present invention, since terminal A is directly connected to the reference voltage power supply as described above,
In terms of AC, it can be seen as approximately grounded. Therefore, if the oscillation characteristics are not strictly required, the bypass capacitor connected to terminal A may be omitted. In addition, if omitted, the oscillation voltage generated at terminal B, which was a problem with the conventional oscillator described above, and the oscillation voltage that is in opposite phase to the oscillation voltage generated at terminal A
There is no such thing as occurring.
次に本発明の発振回路では、帰還抵抗６，７は
それぞれトランジスタ１４と抵抗６およびトラン
ジスタ１３と抵抗１５から成るエミツタホロワに
よるレベルシフト回路を介して第２、第１のトラ
ンジスタ２，１のベースに接続されているので、
該差動増幅器の動作の安定度が向上し、その結果
として発振器の温度特性などが従来例に比べて格
段に改善される。なお、第２図に示した一実施例
ではレベルシフトの段数が一段の場合について示
してあるが、必要に応じてこのレベルシフトの段
数を多くしても本発明の効果には変りはない。 Next, in the oscillation circuit of the present invention, the feedback resistors 6 and 7 are connected to the bases of the second and first transistors 2 and 1 via a level shift circuit using an emitter follower composed of a transistor 14 and a resistor 6, and a transistor 13 and a resistor 15, respectively. Since it is connected,
The stability of the operation of the differential amplifier is improved, and as a result, the temperature characteristics of the oscillator are significantly improved compared to the conventional example. Although the embodiment shown in FIG. 2 shows the case where the number of level shift stages is one, the effect of the present invention does not change even if the number of level shift stages is increased as necessary.
以上詳述したように、本発明の発振器は電子同
調方式を用いた局部発振器として従来のものに比
べて、温度特性などの安定度の向上、同調回路用
バイパスコンデンサの省略および同調回路を外付
けするために必要な２つの外付け端子のうちの１
つを他の目的の端子として共用できるという効果
がある。 As detailed above, the oscillator of the present invention is a local oscillator using an electronic tuning method, and has improved stability such as temperature characteristics, eliminates the bypass capacitor for the tuning circuit, and connects the tuning circuit externally. One of the two external terminals required to
This has the effect that one can be shared as a terminal for other purposes.
第１図は従来の発振器の一例の回路図、第２図
は本発明の発振器の一実施例の回路図である。
１，２……第１、第２のトランジスタ、３……
定電流源、４，５……第１、第２の負荷抵抗、
６，７……第１、第２の帰還抵抗、８……トラン
ジスタ、９……電圧基準ダイオード、１０……発
振コイル、１１……可変容量ダイオード、１２…
…バイパスコンデンンサ、１３，１４……トラン
ジスタ、１５，１６……抵抗。
FIG. 1 is a circuit diagram of an example of a conventional oscillator, and FIG. 2 is a circuit diagram of an embodiment of the oscillator of the present invention. 1, 2...first and second transistors, 3...
constant current source, 4, 5...first and second load resistances,
6, 7...First and second feedback resistors, 8...Transistor, 9...Voltage reference diode, 10...Oscillation coil, 11...Variable capacitance diode, 12...
...Bypass capacitor, 13, 14... Transistor, 15, 16... Resistor.
Claims (1)
ンジスタと、これら第１および第２のトランジス
タのコレクタと電位供給端との間にそれぞれ設け
られた第１および第２の負荷と、前記第１のトラ
ンジスタのコレクタと前記第２のトランジスタの
ベースとの間に設けられた第１の抵抗および第１
のエミツタホロワトランジスタの第１直列回路
と、前記第２のトランジスタのコレクタと前記第
１のトランジスタのベースとの間に設けられた第
２の抵抗および第２のエミツタホロワトランジス
タの第２直列回路と、前記第１および第２のエミ
ツタホロワトランジスタのベース間に接続された
共振回路とを有し、前記第１のエミツタホロワト
ランジスタのベースに基準電圧を供給したことを
特徴とする発振器。1 first and second transistors connected in a differential manner, first and second loads respectively provided between the collectors of these first and second transistors and a potential supply end; a first resistor provided between the collector of the first transistor and the base of the second transistor;
a first series circuit of emitter follower transistors; a second resistor provided between the collector of the second transistor and the base of the first transistor; 2 series circuit, and a resonant circuit connected between the bases of the first and second emitter follower transistors, and supplying a reference voltage to the bases of the first emitter follower transistors. Characteristic oscillator.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP5246580A JPS56149104A (en) | 1980-04-21 | 1980-04-21 | Oscillator |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP5246580A JPS56149104A (en) | 1980-04-21 | 1980-04-21 | Oscillator |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS56149104A JPS56149104A (en) | 1981-11-18 |
| JPS6157728B2 true JPS6157728B2 (en) | 1986-12-08 |
Family
ID=12915460
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP5246580A Granted JPS56149104A (en) | 1980-04-21 | 1980-04-21 | Oscillator |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS56149104A (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE3333402A1 (en) * | 1983-09-15 | 1985-04-04 | Siemens AG, 1000 Berlin und 8000 München | INTEGRATED OSCILLATOR CIRCUIT |
| EP1547236A2 (en) * | 2002-08-08 | 2005-06-29 | Koninklijke Philips Electronics N.V. | Voltage controlled oscillator |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5274263A (en) * | 1975-12-17 | 1977-06-22 | Sony Corp | Oscillation circuit |
-
1980
- 1980-04-21 JP JP5246580A patent/JPS56149104A/en active Granted
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5274263A (en) * | 1975-12-17 | 1977-06-22 | Sony Corp | Oscillation circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS56149104A (en) | 1981-11-18 |
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