JPS612402A - Multiport high frequency circuit network - Google Patents

Abstract

(57) [Summary] This bulletin contains application data before electronic filing, so abstract data is not recorded.

Description

TECHNICAL FIELD This invention relates generally to high frequency circuits, and more particularly to multi-port high frequency networks.

BACKGROUND OF THE INVENTION As is well known in the art, multi-port high frequency networks have a wide range of applications. One application is as a power divider/combiner to distribute radio frequency energy between a first port and a plurality of second ports of the network.

In a power divider/combiner play antenna application, an array of antenna elements is coupled to a plurality of second ports. The energy sent to the 17th port during transmission is coupled to the antenna element array, and the energy received by the array antenna elements is coupled conversely at the first port. An example of such an array antenna is In a phased'' array antenna, a plurality of electrically controlled phase shifters are coupled between the plurality of second ports of the splitter/combiner and the array antenna elements. The energy delivered to or combined at the first port of the power divider/combiner is collimated into a single beam that is responsive to an electrical signal applied to a phase shifter and is collimated by a phase shift provided by the phase shifter. be directed. In other array antennas, a radio frequency lens is used as a power divider/combiner, and the radio frequency lens has a plurality of first ports, each port receiving multiple radio frequency energies simultaneously generated and collimated in different directions.・Corresponding beam 1
associated with one. Each of the beams is formed by a common aperture provided by an array antenna element coupled to a plurality of second ports of the lens. In a phased array antenna or a lens array antenna, it is generally desirable to have a relatively high degree of electrical isolation between the plurality of second ports, and in the case of a lens array antenna, a relatively high degree of electrical isolation between the plurality of first ports. It is generally desirable to have a relatively high degree of separation. ′This separation is the result of sZ being “separated”
- It is desirable to prevent the effects of reflections generated on one of the ports from adversely affecting another "isolated" port. For example, in a phased array antenna, it is desirable that any energy reflected by one phase shifter not be coupled into another phase shifter. In a lens array antenna, when configured to transmit high frequency energy, an amplifier, such as a traveling wave tube amplifier, is typically coupled between each second port and the antenna element coupled to the second port; If one of the amplifiers fails, energy will be reflected back into the lens and coupled into the nearby second port, degrading the performance of the antenna. Additionally, when the lens array is configured as a receiving array antenna, a radio frequency energy receiver is typically connected to each of the plurality of lenses, 14-).

The energy received by the array of antenna elements is
According to its angle of arrival, the energy is directed (ie, focused) to a receiver coupled to one of the first ports.

However, some of the energy focused on the receiver will be reflected by the receiver. If there is not a high degree of electrical isolation between the first ports, the reflected energy will be coupled to other receivers coupled to the adjacent first ports, which will adversely affect the performance of the antenna device. .

In the array antenna applications described above, the necessary electrical isolation has generally been provided by a single power divider/combiner component with the required port isolation. More specifically, one type of power divider component having a relatively high degree of electrical isolation between output ports for phased-controlled array antenna applications is:
An example is McGraw Hill:L Book
[RadarHandbook J] published by Company, New York
, Editor-in-Chief - Merrill Engineering 5kolnik.

1970) Figure 38a and Figures 11-52 to 11-5
It is described on page 3. As stated there,
The feed often includes multiple matched two-way splitters, and the "out of phase" components of the unmatched reflections are absorbed by the terminating load.

The network provides the desired electrical isolation between the output ports, but when configured as a monolithic corporate structure, the terminating loads are located internally within the structure, complicating assembly and increasing manufacturing costs. do. Furthermore, the two-way dividers are arranged in cascaded rows, the number of two-way dividers increasing binary from row to row. Thus, if the feed powers, say, 16 amplifiers, then 4
If a row divider is required, the power sent from the input divider to each of the 16 antenna elements must pass through four series cascaded dividers. Since the energy passing through the divider undergoes some loss, the power loss in Fee 1 increases proportionally with the number of antenna elements in the array.

SUMMARY OF THE INVENTION According to the present invention, a high frequency network is provided that couples high frequency energy between at least one network port and at least a pair of second network ports, the network connecting a pair of similar a high frequency component, each having at least one first component port and at least a pair of second component ports electrically coupled to the component port; at least one pair of second conyd −
an energy source between the at least one first network port and the at least one first component port of the pair of components; at least one pair of second feed means for coupling a first similar port to at least one pair of second component ports U of said at least one pair of components; one of the second network ports, the other of the second feed means coupling energy between a second like port of the at least one second component port of the pair of components and a second like port of the at least one pair of second component ports of the pair of components; a second feed means for coupling energy between the at least one first feed means and at least one pair of second feed means for coupling energy to and from the other of the network ports; and providing the at least one pair of second circuitry hearts with an electrical isolation greater than an electrical isolation between the at least one pair of second components of each of the pair of components.

In a preferred embodiment of the invention, the first feed means and the at least one pair of second feed means are four port devices, the first pair of four ports being electrically coupled to the second pair of four ports, The ports have a relatively large degree of electrical isolation between them. One of the first pair of ports of each of the four-port devices is terminated with a matched load, and the other of the first pair of ports supplies a corresponding one of the network ports. A second pair of ports on each of the four-port devices is coupled to a pair of like ports on a pair of components. The phase shift from one of the at least one pair of second circuitry ports to the other of the at least one pair of second circuitry ports via one of the pair of components is such that The phase shift from one network port to the other differs by nπ (n is an odd number) radians. However, the phase shift from one of the at least one pair of first network ports through one of the pair of components to one of the at least one pair of second network ports through the other of the pair of components a phase shift from one to one of the at least one pair of second circuitry ports and one of the nπ (n is even number) ports, wherein the energy is delivered from the pair of components to one of the at least one pair of second circuitry ports; The load connected to the 4-port device coupled to the other network port is [added with in-phase J,
consumed by that load.

In one embodiment of the invention, the pair of components is a power divider/combiner. The first and second feed means have a pair of mutually isolated first feed ports coupled to a pair of mutually isolated second feed ports. One of the pair of first feed ports is terminated with a matched load,
The other is coupled to a corresponding one of the networks ye-to. The pair of second feed ports are similarly coupled to a similar pair of ports on the pair of components. With this configuration, the at least one pair of second circuit networks 1-
electrical isolation (in decibels) between at least one pair of second component ports coupled to a network port and between at least one second feed port of said feed means coupled to said pair of second component ports; It has an electrical separation degree (decibel) equal to the sum of the electrical separation degree (decibel) and the electrical separation degree (decibel).

When such an arrangement is used as a power divider/combiner network, the matched loads used to terminate each of the first and second feed means are placed external to the component, thereby facilitates assembly. Additionally, the pair of components has a plurality of second component ports coupled to the second network port via a corresponding plurality of second feed means, the first network port and the second network port The energy coupled to either of the second network ports passes through only two matched load termination feed means regardless of the number of second network ports, thereby reducing power losses in the network.

(Explanation of Examples) The present invention will be explained in detail below according to examples.

Referring to FIG. 1, a multi-port high frequency network 10
is shown, the network couples radio frequency energy between the plurality of first circuit networks yl-) 1'2α to 12n and the plurality of second network ports 14α to 14m; 12+2 to 12W are substantially electrically isolated from each other and a plurality of second network ports 14α to 14wL
are also substantially electrically isolated from each other. The network IO includes a pair of electrically independent high frequency energy components 16□, 16□, each component having a
Multiple first components z+? -to18α□~18r
L, 18α2~18n, 2 and a plurality of second components/4-toes 20α□~20m□.

20α2 to 20m2, respectively. component 16
□.

16□ are substantially identical (i.e. similar to each other), each of the components 16□, 16 has substantially the same scattering coefficient in relation to the waves reflected and transmitted at the individual ports, i.e. , port 18a0~ of component 16□
The scattering coefficients associated with 18n□ and 20α□~20m0 are substantially the same as the scattering coefficients associated with the 4-tooths 18α2~18rL2 and 20α2~20m2 of component 16□. Therefore, component 16□.

Each of 16□ is characterized by having the same scattering matrix 5−~481+)ft, where, as is well known, Sij is the reflection coefficient at port 1, and Si) is the transmission coefficient from port 1 to port 2. All other ports are terminated with matched impedances.

The components 16□, 16□ have a plurality of first component ports 18α to 18rL, , 18α2 to 18rL2.
and a plurality of second component ports 20α1-18
77L□.

20α to 20m2, respectively, and have a relatively high degree of electrical coupling between the second component ports 20α and 20m (
or the ports 20a2-20m2) themselves have a relatively low degree of electrical coupling, and the first component-z-t 18a, ~18yb, <or 18α2-18rL2
) 1212-12rL, but the degree of electrical isolation between the first component ports 18α-18n (or 18n) is relatively low.
The electrical isolation between the second component ports 20α, .about.207+, is substantially greater than the electrical isolation between the second component ports 20α, .

(or 20α to 20 m2) is also substantially large.

The circuit network 10 further includes a plurality of first power supply circuit networks 22a to 22.
n and a plurality of second power supply circuit networks 24fZ to 24m. Each of the first power supply networks 22a to 22n is connected to a corresponding one of the first circuit networks yd-tots 12α to 1'2n and components, 16□, 16° first component ports 18α to tsn, as shown in the figure. 18a2
˜18n2 are respectively coupled between a pair of similar ports. Each of the second feeder circuits 24α to 24m is a second component board of the components 16□, 16□)
20a, ~20m□, 20α2~20m2 and a corresponding one of the first network ports 14α~14m, respectively. Thus, as shown, network port 12α is coupled to like component ports 18α0, 18α2 via feed network 22α, and port 12.6 is coupled to like component ports 18b□, 18b2 via feed network 22h. ... and port 12n is coupled to similar component ports 18rL, , 18fL2 via power supply network 22n. The similar component ports 20α□, 20α2 are coupled to the second circuit network port 14cL via the power supply network 24α, and the similar component ports 20h, 20h2 connect the power supply network 24h to the second circuit network port 14h. combined through
...and similar component ports 20m
, 20mz connects the power supply network 24 to the second network port 14m.
connected via m. First power supply circuit network 22a to 22n
, and the second power supply circuit network 24α to 24m are the circuit network S? −
Z2α~12n and circuit network = d-to14α~1477
Between L and power supply circuit network 22 ct-22'yL, 24
a ~24m and a pair of components 16□, 16
□ to couple energy to the first network port 12
a to 12n, the first component ports 18α to 1
8n (or 18a to 18rL2); e-) 1;
2nd component in 4α~14m, rl-120a~
20 m (or 20 α to 20 m 2 ).

The power supply circuit networks 22a to 227, 24a to 24m each have 4
In the hold network, each first pair, p-4A, B, is electrically coupled to a second pair of ports C, D, while the first pair, p-4, A, B,
, B are substantially electrically isolated from each other, and a second pair of ports C
1D are substantially electrically isolated from each other and port A
Matches when %B is match terminated. That is, yE-tA
Between %B and Po1-C.

0 (when the other pair is matched terminated) between the first component rl-t 18a.

-181L (or 18a2 to 18n2) or second component -7-12 (c, ~20m, (or 20α
2 to 20 m2) (when all ye-tos are matched terminated) (i.e.
one order of magnitude larger). Here, the power supply circuit networks 22α to 22yb,
Each of 24α to 24m is a quadrature hybrid coupler (Qu
ad, -rature hybrid, couple
r). As is well known, 5.1# - When either A or B is terminated with a matched load, % (i), +? −
A signal applied to an unterminated port of port A or B appears in four quadrature phases at ports C and D (if port B is terminated, the signal at port D is equal to the signal at port C). (When port A is terminated, the phase of the signal at port C is delayed by 90 degrees with respect to the signal at port D.) Then, (21 ho) the signals applied to C and D in "quadrature" phase with each other are! -) D signal! When the phase is 90 degrees behind the -40 signal,
+”-appears “in phase” at port B and is erased at port A. (3) Signals that are applied to ports C and D mutually in [quadrature J phase] are applied to port A when the signal at port C is 90 degrees behind the signal at $-)I). It is added in “in-phase” and erased at port B. Here, the I-to-B of the first power supply circuit networks 22a to 227L is terminated at the matched load 21, and the second power supply circuit networks 24a to 227L
It should be noted that 4n J-)A is terminated with a matched load 23. Also, power supply networks 22α to 22n terminated with matched impedance loads 2 and 23, respectively.

Component ports 18 by 24a-24m
α, ~18n, 18a2~18n2.20a□~20n
It should be noted that □ and 20a-20rL2 are terminated with matched loads (when looking at the feed network).

Considering the high frequency signal Ea f sent to one of the first network ports 12α to 1271, for example the network 12a, the first
In response to the signal, the power supply network 22α generates signals E a /l'': and -Eα/fi()=Fr) on e-1, 0 and D of the network 22α, respectively.
The signal at port D is sent to the first component port tgα of component 16□, and the signal at port D is sent to the first component port 18a2 of component 162. The signal sent to port 18a□11842 is distributed by components 16□, 16° according to the scattering coefficient of components 16□, 16□. The voltage sent to ports 18a1 (and 18a2) is connected to the second component port 20α, ~20m
and 20α2~20m2) are Saa, Sba, Soa...S□, respectively, then the voltage generated at the second component port 20a~20m□ of component 16□ are each (
Ea/v/'r)Saa, (Ea/g)Sb, ,
-(Ea/#)S,,.

, the second port 2 of component 16□
The voltages from 0α2 to 20m2 are respectively C-j'f2a/('1
)Sa, .

(-jEa/6>Sba, ・-・-・-<-)Ea7
('z)S-. Here, the second component port 2 (M.

~20m, each similar pair of 20a~20m2 (i.e., similar pair 20a20a, similar pair 20h0.20h2...
- Similar pairs 1' 2 23m, 20''2) are connected to a plurality of second power supply circuit networks 24α~
It should be noted that 24m is combined with the corresponding one. More specifically, as shown, the second component ports 20a to 20m1 are connected to the second cemetery route network 2, respectively.
The second component ports 20α-20m2 are coupled to the D ports of the second feed networks 24α-24m, respectively.

Thus, since the voltages at terminals C and D of feed networks 24a-24m are equal in magnitude and the phase of the signal at port D lags the signal at port C by 90 degrees, network port 14α
The signals at ~14 m are each (-)Eα)Saa.

It is expressed as (-)'Eα]Sba,... directly-ノEα)8. Similarly, first network ports 12b to 12
The respective signals Eb to Eb sent to the yH-t 14
Signal at a-14m (-)ESab, (-)E7
)Sbb position,,,,(-)Eb)Sml to (-)
ErL)ScLrL, . . . (SuEn)Smn is generated, and no energy is coupled to the load 23. In this way, in general, the [A
The energy sent to component 16
□.

The second feed network 24fZ~2 according to the scattering coefficient of 162
However, as will be described later, [AJ,n-t of the first feed network 22α to 22rL is coupled to lBJ,i”-t of 4m, regardless of the scattering coefficient of components 16□, Similarly, the "B" ports of the second feed network 24α~2.4m are substantially electrically isolated from each other, independent of the scattering coefficients of the components 16□, 16□. be done. Next, between the pairs of first network ports 124 to 12n or the second network ports 124 to 12n,
the influence of network 10 on the separation between pairs of 4α to 14m;
That is, consider, for example, the influence of the energy sent to the second network port 14a at the second network port 14A. If the signal sent to port 14a is denoted by ET, then the signal generated at ports C and D of second feed network 24α in response to Er is expressed as k(−)Er/
f) and <Er/Fi). If component 16□, 16° has a scattering coefficient Sb'a that relates the signal appearing at component port 120A (or 201) 2) to the signal sent to port 20α, (or 20a2), then the signal Eγ The signals generated at ports 20b□ and 20b2 in response are C-
)'Er/f)Sla and (Er/i)S'hate. 4- The signals 2oh, 2ob2 of the second power supply circuit network 24h are transmitted as described above. - Sent to C and D. Therefore, the signals at ports C and D of network 24h have the same magnitude, and the phase of the signal at port C is N-4D
signals at ports C and D of network 24A join in phase at port A of network 24α, so that energy is connected to port A of network 24b. The signal is terminated at a load 23, and erased at port B of network 24b. That is, from port 14a to port 2
0a, port 2 (1,, the phase of the signal passing to port 14h is baud) 14a to port 20α2+bo) 2
0I! '2. The phase of the signal passing through port 14A differs by 1 (n is an odd integer). and,
Although there is an electrical coupling between component ports 20a□ and 20b0 given by the scattering coefficient S'ha, component port 2oα□.

The second network ports 14a, 14b coupled to 20a2 and 20h1, 20h2 are substantially electrically isolated.

Similarly, considering the isolation between a typical pair of first network ports 12a-12n, ie between network ports 12α and 12A, when the energy delivered to port 12α is E'r, then Signal E to ports C and D respectively
'r15 and -noE'γ/1 appear. Assuming that the scattering coefficient between the first component ports 18b1 and 18a (or 18b2 and 18a2) is S//bcL, the signals of the ports 18b1 and 18b2 are respectively (E'7
/4) S'- and (-j'''r/Fi) sttb. The signals at ports 18b□ and 18h2 are sent to Petes C and D of network 22b, respectively. Since the signal at port D lags the signal at port C by 90 degrees, the signal at port D is 18A.

The energy Er of 7-112a coupled to 18z2
A part of
Port 12+2 is electrically isolated from port 12b even though port 8b2) is electrically coupled.

Further generalizing the description in FIG. 1, component 16
Each of □ and 16□ includes a plurality of first component ports 18α to 18rL (or 18α2 to 18n2), designated as 1 to n, and a plurality of second component ports 20α to 20n1 (or 20α2 to 20rL).
It is clear that 2) can be considered as a multi-port network 16' (FIG. 2) with ports designated D+1) to Cn+m). Thus, the scattering matrix [C] for component 16' can be expressed as follows.

Simplifying equation (1), we have: Therefore, the plurality of first power supply circuit networks 22a to 22L (FIG. 1) and the plurality of second power supply circuit networks 24α to 24m (FIG. 1)
Each of the following scattering matrices [F'), A=S
B, B=l/u and HSA, B=SB, A=
−ノ/fΣ, and its effect is as follows in the scattering matrix [N) network 1
It is to give 0.

It should be noted that the scattering matrix [N] of network 10 in equation (9) can be simplified as follows.

In this way, in the scattering matrix [N], Sx, x=SY,
Since it is Y-0, the first and second power supply circuit networks 2212 to 2212
24n, 24a to 24m and by the use of a pair of similar components 16□, 16°, the component I6□, 16° itself becomes the first component i-
Even if there is some degree of coupling between ports 16a-16n (or 16a2-16n2), the second component ISa-18m, (or 18a2-187
Even if there is some degree of coupling between the first ports 12α to 1271 of the network (i.e. 5xX-0) and the second ports 14α to 14 of the network
It is clear that substantial electrical isolation between m (ie 5YY=O) f: is provided in the network 10.

More precisely, although we have assumed that ports A and B (or C and D) have perfect isolation, all real Hainolirad couplers have some finite isolation, typically 20
(11) degree of separation. Thus, the separation between the first or second pair of network ports is 20 db and the first
component port pair or second component port pair
It is the sum of the degree of separation between the port pair and the amount of dl).

Referring to FIG. 3, a multi-port high frequency network 10
' is shown as an m:1 power divider/combiner that couples high frequency energy between a single first network 12' and a plurality of second networks 14α' to 14m'. and the second
Networks 14α'-14m' are substantially electrically isolated from each other. Network 10' includes a pair of substantially identical (i.e. similar) electrically independent radio frequency energy components 16'.

16□', each of which includes a single first continent port 18□', 18°' and a plurality of second component ports 20a' to 20m1' *2
It has 0α2' to 20m2'. Component 16□
'(or 16□') is the first component port 18
' (or 18□') and a plurality of second components z−h 2oa, ' ~2om, '<2oa2' ~
207712/ ), and has a relatively high degree of electrical coupling between the second component port 20a□′ and 20m
□' (or 20α2' to 20m2') itself has a relatively low degree of electrical coupling, and the second network ports 14a' to 1
The electrical separation between 4m' and 2nd connected port 20α
2' ) is substantially wider than the electrical separation between the two. First feed network 22' Herein, a quadrature hybrid coupler such as that described in connection with FIG.
' and the first component , e-t1sα□'118a
2', a plurality of second power supply circuit networks 24a'
~24m', here 20b', 20b';
.=-20yn'+20m2' and the second network ports 114a' to 14m'. For the reasons stated in connection with FIG.
a' to 14m' are substantially electrically isolated from each other.

Additionally, the energy coupled between the first network port 12' and each of the plurality of component ports 14α'-14m' is coupled between the first network port 12' and each of the plurality of component ports 14α'-14m'.
passes through only two hybrid 8 combiners, regardless of the number of .

Thus, when the energy F2i is sent to the network port 12', the energy at the network ports 14a' to ]4m' is )StLa + jSh a"" +...
Sm,Ei is expressed as Sm, Ei, where Sa is the scattering coefficient, s, between component port 20a' (or 20a') and component port 18,' (or] 8°').

is component port 20h□' (or 20b2'
) and component port 18□′ (or 18°′)
The scattering coefficient between...and Sm, , a is the component port 20m' (or 20m2')
and component =1−)18□′ (or 18□′)
is the scattering coefficient between Furthermore, component 7-
Considering the energy gr sent to port 14a', a portion of that energy Eγ, here -Eγ/p, is transmitted to component port 20α1' of component 16'.
and another part of the energy Eγ, here F2r/
σ is sent to component tansort 20a2' of component 16°'. When the scattering coefficient of component ports 20h' and 20a□' of component 16' is Sba',
If the scattering coefficients between the component ports 20h' and 20a2' are the same <Sba', then the feed network 24h'
The signals sent to z'-to C and D are -Er5, respectively.
It is expressed as ba'/g and EγSba'/F.

Thus, the signal at z-p of feed network 24h' is equal to Eγ5bcL', which signal is absorbed by matched load 23' connected to port A of network 24b';
The signal of #0-B of network 24b' and therefore the signal of network 14A' is zero. Therefore, the feed network 22
Due to the influence of '+24'' to 24m' and similar components attached ', 16□', energy can pass between the first network port 12' and the plurality of second network ports) 14fZ' to 14m'. 2nd component port 20α1'~20m,' (or 20α2
14m' to the second port 14a' are separated from each other even though there is some coupling between them.

Referring now to FIGS. 4A and 4B, the feed network 10' of FIG. 3 is shown as an 11:1 sector divider/combiner. Here, components 16□′, 1 in FIG.
6°' each is a well-known fan-shaped horn. The fan-shaped horn 16', 16° has a pair of opposing triangular wide side walls 51a, 51h and a pair of narrow walls 52a, 52h. Each sector horn 16□'.

A rectangular waveguide section 54 is provided at the top of the horn, and a plurality of rectangular waveguide sections 56, here 11, are provided at the base of the horn.
~56□ are provided. Here, fan-shaped horn 16□/
, 162/ and a plurality of waveguide sections 56□ to 56□□
Taper transition portions 58□ to 58□1 are provided between the
A degree of electrical isolation is provided between the plurality of waveguide sections 56□-56□1, with TEl to be coupled between the top of each horn and each of the plurality of waveguide sections.

It is noteworthy that the electromagnetic wave propagation mode is established.

The sector horns 16□', 16□' are mounted together in parallel and have one side wall in common, here the side wall 51A-i of the horn 16□', and the side wall 5112 of the horn 16□' together Although mechanically connected, it should be noted that components 16□', 16□' are electrically independent of each other. Right angle hybrid 9 coupler 22
' is connected to the waveguide section 54 at the top of each of the horns 16□', 16□', and the coupler is connected to the first feed network 22 of FIG.
′ can be considered. The waveguide 54 of the horn 16□' can be considered as the port 18□' in FIG. 3, and the waveguide 54 of the horn 2' can be considered as the port 18□'. The load 21 is connected to port B of the supply network 22'
z-)C and D are located at the horns 16□' and 1, respectively.
6□' is connected to the waveguide section 54. Port A thus provides a network port 11' as shown in FIG. The rectangular hip couplers 24' to 24□,' are coupled to a plurality of waveguide sections 56□ to 56□□ as shown, and are connected to the second feed network 24α' to 24m' (here, m can be considered as 11). Here, coupler 24
It is noted that ports C and D of □'-24□,' are coupled to similar pairs of waveguide sections 56□-56□1, as shown in the block diagram of FIG. In this way, the waveguide portions 56□ to 56□□ of the horn 16□' can be considered as the second component ports 20α□' to 20m□' (Fig. 3), and the waveguide portions of the horn 16□' 56□〜
56□2 can be considered as the second component ports 20α2' to 20m2' (FIG. 3) of the horn 16□'. Furthermore, hybrid ″′24□′～24□□′
The matched load 23' of y-t A is shown in FIG. 4A (
The circuit is shown in Figure 3). In this way, hybrid 24□′~2
Is port B of 4□1' juice in Figure 3? -t14α'~1
Eleven second network ports 14□' to 14□,' are provided, as shown as 4m'. Power supply network 10'
A circuit diagram of is shown in FIG. 4C. Horn 16□′.

Although there is some degree of electrical coupling between each waveguide 56□-56□□ of 162', the second network port 1
4□' to 14□□' are substantially electrically isolated from each other. Furthermore, the matched load 23' is connected to the horns 16', 16
It is placed outside ゜′. Furthermore, the energy sent to the first port 12' is the second yt? -114' to 14□□' passes through only two hybrid 9 combiners.

Here, referring to FIG. 5, the microwave power combiner 5
7 is shown, the combiner including the power divider 10' described in connection with FIGS. 4A, 4B and 4C. The first port 12' of the coupler 57 is connected to port A of the well-known circulator 59.
and port B of the circulator 59 is connected to the transmitter (
transmitter) 61 and is also powered by port C
supplies power to the antenna 63. 2nd port 14□'~14
．． 1' are coupled to negative resistance amplifiers 63□ to 63□□, respectively.

(Although 11 secondary ports are shown for illustration purposes, the number need not be limited to 11.) In operation, from transmitter 1 to 2 of circulator 59
The high frequency energy applied to t-B is coupled to y-LA and then via network 10' to negative resistance (or reflective) amplifiers 63□-631 for amplification. After being amplified, the energy is reflected back to port A, and circulator 59 directs the amplified energy to port C and to antenna 63. Here, the amplifier 63
It should be noted that there is considerable electrical isolation between the amplifiers □-63□□ for the reasons discussed above in connection with Figures 4A-40.

Referring now to Figures 6A, 6B and 6C, 16:
1 power divider/combiner 10'' is shown, this combiner 10
” is shown in FIG. 6D. Power divider/combiner 1
0" is a pair of substantially equal split tees (spl
electrically independent power divider/combiner components 16'', 1 which are strip transmission lines
Contains 6□′. Thus, the power divider/combiner 10"
includes a pair of sl-'J tube conductor circuits 64.74 separated from a pair of upper and lower ground plane conductors 62.72 by a pair of upper and lower insulating substrates 60.70. A strip conductor circuit 64 is formed on the upper surface of a relatively thin insulating substrate 90, and a strip conductor circuit 74 is formed on the upper surface of a relatively thin insulating substrate 90.
IJ Sogelaf - Substrate 9 using chemical etching technology
formed on the lower surface of 0. The component 161' includes a strip conductor circuit 74 and a substrate 60 . arranged above and below the conductor circuit. '70 and a portion of the ground plane conductor 62.72. The component) 16□' includes a strip conductor circuit 64, a portion of the substrate 60.70 and a portion of the ground plane conductor 62.72 located above and below the conductor circuit 64. Thus, referring to FIG. 6B, component 16□〃 is visible in the upper portion;
Component 16□' appears in a different non-overlapping part, namely the lower part. And component 16□″
.

16□'' are electrically isolated from each other and are each 16:1 split-T-strip transmission line components. Components 16'', 1
6□〃 are respectively the first component ports 18□//,
ls□' and a plurality (here 16) of second component ports 2oα□〃 to 20p□'.

It has 20α2′ to 20p2//. A first component port 18□//, tB□' is coupled to a first network port 12'' via an overlay orthogonal directional high-zolith 9 coupler 22'', and a second component port similar pair 20α□〃, 20α2 '～20p, '+20
12" is an overlay orthogonal directivity... second circuit network meet 14a via hybrid couplers 24α" to 24P.
``~14f)''. More specifically, the conductor 64
The upper strip is patterned as a 16:1 split-tee network having 15 T-shaped sections 66□-66□5 as shown. The largest or first tee section 66□ serves as its leg 67 as the first component! -To 1s. ' and is divided into a pair of arms 68 and 69.

Arm 68 is coupled to the leg of tee section 66□, and arm 69 is coupled to the leg of tee section 663. The arms of tee section 66□ are connected to the legs of section 664.66. The arm of section 664 is connected to the second component port 20
α2" + 20b2"120C2" and 20d2'
The sections 668 and 669 are joined to the legs forming sections 668 and 669. The arms of the tee section 66 are connected to the second component ports 20, 2//, 20 f 2/
/.

Tee forming 20 g2// and 20h 2//
It is coupled to the leg of section 66□o166□1.

The arms of the tee section 666 are:
, 20 k2// and 2012" are connected to the legs of section 6612.66□3 forming the second component 6 port 2orn2" + 20rL2// l 2oo2
' and 20P2''?: Shadow forming section 66□4
．． Connected to 66□5 legs. Thus, tee 6
The energy delivered to the leg 67 of 6□ is coupled substantially equally to the second component port 20α2'~20p2// and vice versa to the second component port 20α2~20p2'' equally and in phase. is coupled or summed in phase to the leg 67 or first component port 18□'. However, the energy provided by
It is noteworthy that there is a relatively low degree of electrical isolation between 2// itself. It should also be noted that the legs of the tees 668-66□5 extend vertically for a predetermined length, where they turn 90 degrees to the right and terminate in the disc-like region of the z-ts 14a"-14P". (The left leg of 668 is partially excluded for clarity).

As shown in FIG. 6A, these disc-shaped regions are the center conductors 71a-717 of well-known coaxial connectors 73a-73p.
) is electrically connected to the

Referring now to component 16□', it is noted that this component is substantially identical to component 16'' with respect to the split-tee network portion. Component 16□' is also a stripline power divider. /A strip conductor circuit 7 formed in the coupler on another part of the insulating substrate 60.70, another part of the conductive ground plane conductor 62.72, and on the side surface of the substrate 900.
Therefore, 16□' and 16□' are substantially electrically independent. As previously mentioned, the split-tee network portion of strip conductor circuit 72 serves as the split-tee network portion of circuit 62.
Substantially identical to the tee network section, 15 branch tees (i.e. T-shaped sections) 76□ to 76□5
including. Thus, the leg 77 of the tee 76□ provides the first component port 18□' and the leg 77 of the tee 76□
The energy given to passes through tees 76□ and 763,
Next, Tee 76417651766°767 and Tee 768,769.76□. ,76□,.

76 76 76 and 76□5. The arms of tees 768 to 76□5 are the second components, respectively! The legs of the tees 768 to 76□5 extend vertically downward for a predetermined length, then bend 90 degrees to the left and form rectangular conductive pads. It is noted that the conductive pads 80a to 80p are terminated at s o a to 80p. Resistive loads 81a to 81p (i.e., matched load 23) are connected between these conductive pads 80a to 80p and the ground plane conductor 72. Load 814-817
) is inserted into an opening formed or pierced in a region of the substrate 70 located below . The main portion is located below the main portion of each of the vertically upwardly extending tees 668-66□5 (the left side/lug of 668 is shown partially removed for clarity) as shown. It is noteworthy that they are arranged together (
The length L (FIG. 6B) is substantially equal to λ/4, where λ is the nominal operating wavelength of coupler 10'').

Therefore, tee 768~76□5 and 668~66□5
The overlapping part of the vertically extending legs is the ground plane 627
2 and insulators 60.70.90 to form well-known stripline overlay orthogonal directional hybrid couplers 24a//~24P//-+. Furthermore, a portion of leg 77 of tee 76 is similar to leg 6 of tee 661.
7 under a portion of the ground plane 62.72 and the insulator 60
, 70.90 and the well-known stripline overlay orthogonal directional hybrid 9 coupler (i.e. coupler 22
“). Thus, the arm 77 of the tee 76□
The disc portion coupled to provides a second network board 12" and is coupled to the center conductor of a conventional coaxial connector 96 as shown. The upper vertical portion of leg 67 of tee 66□ It is terminated with a 90 degree bent conductive pad 69. A resistive load 99 (FIG. 6A) (ie, matched load 21) is connected between ground plane conductor 72 and conductive pad 69.

The resistive load is inserted into a section formed or penetrated in the area of the insulating substrate 60 above the pad 969.

The overlapping portion of the tees 66i and 76□ is part of the first power supply network 22'. Thus, the lower part of the lower leg 77 is considered to be ports A and 1 of the coupler 22'', and the upper part of the lower leg 77 is considered to be the port A and 1 of the coupler 22''.
Think of it as port C of 1K, thus connected to the first component 18□'. The lower part of the upper leg 67 can be considered as port D of the coupler 22'' and thus the first component port 182.
', and the upper part of the upper leg 67 is connected to the coupler 2
Similarly, if we consider one of the second feed networks, say coupler 24a'/, the lower tee 768
The upper portion of the left leg of coupler 24a'' can be considered as port C of coupler 24a'', the lower portion of the left leg of upper tee 668 can be thought of as port D of coupler 24f2'', and the left leg of lower tee 768 The lower part of the leg is the coupler 2
4a// is connected to the load 23, and the upper portion of the left leg of the upper tee 668 is connected to the network port 14a', considered as e-t B. With this configuration, the tees 768 to 76
Even though the electrical isolation between the legs of □5 and between the legs of tees 668-66□5 is relatively low, the second network port 2
0 a//~207)// are substantially electrically isolated from each other. It should be noted that the power divider/combiner 10" is a reciprocal device, and this very well decoupled structure allows the second network $-11,4α" to 14 p//
It should be noted that only two directional couplers are required for the engineering circuit passing between any one of the two networks and the first network d-to-12''. Thus, the circuit of power divider/combiner 10// is shown as shown in FIG.
air insulators 60', 70', 9(')' may be used as shown in Figure 6E, in which case the ground planes 62, 72 are conductive sheets. or with a cover, the striped conductor circuit 64, 74 is insulated by a strut or post 9 as shown in Figure 6E.
1 to be placed in the air between these covers. Also, a resistive load, here load 81a, is exposed to the outside. More specifically, Noset ″80a~BOp
For example, as shown in pad S80α, the conductive feed path passes from pad 80a through the air insulator and through conductive ground plane 72 to load 814, with the other end of the load connected to the ground plane. 72. As shown for the load 81α, the load 99 also applies to the loads 81b to 817).
(Fig. 6C).

Referring now to FIG. 7A, there is shown a high frequency energy lens antenna device 10'', which comprises a pair of electrically independent high frequency lenses 161'', 16□''.
', each of which has a plurality of first or beam notes 18a''' to 18y+, □''', IB a 27
//~I B n 2/// and a plurality of second or array peats 20a□'''~20m,'''r
2o α2″˜2 (1 m 2 ///). The first or beam port analogous pair of the pair of lenses has a plurality of first feed networks 22α″˜22 n ///
a plurality of first or beam beams via a corresponding one of the
are coupled to a corresponding one of the antenna device ports 12α'' to 12,'///. The first feeding network 22a///
~22n/// are coupled to a corresponding one of the first system ports 12a///~12n'' with a quadrature hybrid coupler as described in connection with FIG. It has an A port, a B port coupled to a matched load 21, and C and D ports coupled to a similar pair of first ports of lenses 16□///, 16□'''.

Each of the second power supply circuit networks 24a///~24m"' is
A quadrature hybrid coupler as described in connection with FIG.
has a B port coupled through a corresponding one of T amplifiers 62a-62m. Each C and D port of the second feed network is connected to a lens 16□///, 1 as shown in the figure.
6□″' electrical length from each of the antenna elements 6oα to 60m to the second or pair of array ports connected thereto and the lens 1
6□''' and 16□''' are the same as those of U.S. Pat.
No. 761936 [Multi-Beam Array
As described in Antenna J. element 60
The electrical length of one of the beams and associated system ports 12'' through 12n'' through one of the antenna elements from another point on the same wavefront of that one beam. to the same system port associated with that beam. That is,
Considering the wavefront 65 associated with the system point 12a"', from one point on the wavefront 65, the antenna element 60α, the lens 16□L//, the port 20a1" of 162///
', 20a2'' through system port 12α'''
is equal to the electrical length from another point on wavelength 65 to system port 12a/// via antenna element 6Qm, 4-) 20m"', 20m"'. However, the reflection of energy (Er) from amplifier 6212 to port B of feed network 24 a
Port C of /// as Ichino Er/σ! It is noteworthy that it appears as Er7p in -toB. $
-The energies of C and D are components・$-) 2
ob□'' and 2 o /, 2 ///. This energy is coupled to the lens 16'', 16°'
When coupled to the adjacent array port internally, port 2
-jKE/f and K from 0b1'', 20b2''' respectively
radiated as F, //'N. Here K is port 2
is the scattering coefficient between 0a11'' and 20b, /// (or 20α'' and 20b2///). The energy at ports 20h///, 20J2/// is sent to ports C and D of the feed network 24A///, being canceled at port B but summed at port A. The reflected energy is therefore absorbed by the matched load 23 of the feed network 24h/// coupled to IZ-A and does not enter the amplifier 62A.

Although the array device of FIG. 7A is shown as a transmitting device, it can also be configured as a receiving device as shown in FIG. 7B. Here, the amplifiers 60α to 60771 in FIG. 7A
are removed, but the receivers 66a to 667L are
It is coupled to system ports 12a"-12n"'.

Any reflected part of the energy received at one of the receivers 6flZ to 66rL, e.g. ~22rL"' is absorbed by the matched load 21 coupled to port B.

Referring now to FIG. 8, a radio frequency circuitry 10'' is shown that couples energy from the transmitter 100 to the antenna element 102 during the transmit mode and is received by the antenna element 102 during the receive mode. The received energy is directed to a receiver 1 (14), where a pair of electrically independent components 16□////.

16°"' is a well-known 3-port circulator.

Each circulator is! - irreversibly couples the energy of port 1 to port 2, irreversibly couples the energy of port 2 to port 3, and irreversibly couples the energy of port 3 to port 1;
Binds irreversibly to And circulator 16□
The scattering matrices of //// and 16□'' are expressed as follows.

Circulator 16. , //// , l6□'' is coupled to a first feed network 22'', here a well-known quadrature hybrid coupler such as 22a in FIG.

and ports C and D of S22////
are coupled to the pair of ports 1 of a pair of circulators 16"", 16□", respectively, port B of the hybrid "'22" is coupled to the matched load 21, and port A is coupled to the pair of ports 12" of the hybrid "'22".
A pair of second feed networks 24α, 2, i, //// are here a well-known quadrature hybrid coupler arranged as shown in the figure. One of the pair of circuit networks, here the circuit network 24α", is connected to a pair of circulators 16", 16□, respectively.
'' is coupled to port 2 of d-to-C and Di,
On the other hand, here 24b" are the circulators 16□/
/// , port C coupled to 2-to 3 of 16゜
and Di. Type A of the power supply network 24a
is coupled to matched load 23, and y knee 1-B is coupled to receiver 1 (
14. The power supply circuit network 24b", t?-)B
is coupled to transmitter 100 and sr-tA is coupled to matched load 23
is combined with

In operation, during transmission, the energy E from the transmitter 100
T is sent to port B of the feed network 24b"", and its J
-) C and D respectively -jET/F and ET/F and L7
appears. That energy is circulator 16 //
//, yl-) via port 3 of 15□''.

■ Pass through. In this way, J − of the feeder network 22 ““
The signals at ports C and D are respectively denoted by −Egf, E1/(i. As a result, the signal at port A of the feed network 22" and therefore the signal sent to the antenna element 102 is -)E
Represented by T. At the receiving mote 9, the energy received by the antenna element 102 is expressed as ET. and ports C and D of the power supply network 22////
The signals of can be expressed as hEr, q"'i and -jF2r/f. Circulator 16□////,
The energy at port 1 of 16□" is coupled to port 2 of the circulator, so that the energy at port 1 of feed network 24a""
The signals at c and D are Er/σ and −Er/, /T, respectively.
It can be expressed as Therefore, the signal at port B of network 24" is one Er, and its energy is
14.

However, any energy reflected by receiver 1 (14, i.e. energy E?-') is absorbed by network 24 a///
/ appears at ports C and D of -j'f2r'/ρ, respectively.
1 and Eγ'/β. These signals are sent to port 2 of a pair of circulators 16'', 16□'' and are therefore coupled to port 3 by the circulator. Therefore, the signals at ports C and D of network 24b//// are denoted by k-)Er'4 and Er'7f. These signals are added "in phase" to $-t/ of network 24b//// as -Er'/F, and their energy is absorbed by load 23 coupled to port A. Therefore, the energy from port 2 of the pair of circulators is coupled to port 3, and the energy reflected by receiver 1 (14) at network port 14α〃〃 (i.e. 1- of network 24α〃)B) is Network port 14h""
(i.e. port of network 24b) B) from the transmitter. Thus, the scattering matrix of the network 10 is expressed as follows.

Here, S′□, □=$ −21/// to E F 12///
/ scattering coefficient 8' = rr 17/
// p β 14α"" N2.1 s'=712"# # 14b"N3.1 3 / # 14 a//// p
N12 ///ll, 2- 8' -n 14d”rr rh '14
α"N2.2=S/,, 14, Z////,
, 14, ////.

3.2-3/, r 1477111
# # I Q //ノ1, 3- 3' -s 14h"l 〃 14α"//
.

2.3- 8'#14 b//// #, +
+ 14 b//// rr3.3- Thus, the 83.2 of the circulator has actually been zeroed out. Additionally, although port 1 is coupled to ports 2 and 3 (irreversibly), the energy received by antenna 102 is sent to receiver 1 (14);
Since the energy from the transmitter 100 is sent to the antenna element 102), ports 14α'' and 14b'' are coupled to each other even though the energy at port 2 of circulator 16□uti, 16□'' is coupled to port 3. Also, in the transmission mode 8, the action of the circulator is enhanced by the feed network 24α"" + 24b" as described above, and the circulator 16////,
, t 5□″″, the receiver 1 (14) is electrically isolated from the transmitter 100.

Referring now to FIG. 9, receiver 1 (14 of FIG. 8 is replaced with antenna element 102' and antenna element 102 of FIG. 8 is replaced with injection/reflection amplifier/power combiner 1 (18). Thus, low level transmit energy passes from transmitter 100 to injection amplifier/combiner 1 (18).
There, it is amplified and the amplified energy is then transmitted by antenna element 102'. Here, the amplifier/
Combiner 1 (18 is connected to the antenna element 02' after amplification), and amplifier/combiner 1 (18 is connected to the transmitter 100 before amplification)
The energy reflected from antenna element 102' is coupled to circulator 16□〃''.

It is noteworthy that the energy at port 2 of 16°" is coupled to port 3 of the circulator, but is isolated from the transmitter. Additionally, amplifier 1 (18) electrically isolated from the power input from the

Although the invention has now been described in accordance with preferred embodiments, it will be apparent that other embodiments are possible within the scope of the invention.

[Brief explanation of drawings]

FIG. 1 is a block diagram of a high frequency network according to the present invention. FIG. 2 is a block diagram of one of a pair of substantially identical components used in the circuitry of FIG. FIG. 3 is a block diagram of a high frequency power divider/combiner according to the present invention. 4A and 4B are schematic diagrams of the high frequency power divider/combiner of FIG. 3 applied to a waveguide. FIG. 4C is a circuit diagram of the power divider/combiner of FIGS. 4A and 4B. FIG. 5 is a circuit diagram of a microwave power combiner using all of the power divider/combiners of FIG. 3. Figures 6A, 6B, 6C, 6D and 6B show an example of the application of the high frequency power divider/combiner of Figure 3 to a strip transmission line divider/combiner; 6B is a cross-sectional front view taken along line 6A-6A of FIG. 6B; FIG. 6B is a cross-sectional plan view taken along line 6B-6B of FIG. 6A;
60 is a cross-sectional front view taken along line 6C-60 of the divider/combiner of FIG. 6B; FIG. 6D is a circuit diagram thereof; FIG. 6E;
The figure shows a portion of another embodiment of a strip transmission line power divider/combiner using air insulation and externally attached loads. FIG. 7A is a block diagram of a transmitting multi-beam antenna device according to the present invention. FIG. 7B is a block diagram of a receiving multi-beam antenna device according to the present invention. FIG. 8 shows a transmitting/receiving device including a non-reciprocal high frequency circulator arranged according to the invention. FIG. 9 shows a complete transmitting-amplifying system using a non-reciprocal high frequency circulator arranged in accordance with the present invention. (Explanation of symbols) 10: High frequency circuit network 12α to 12n: First circuit network 2-to 14a to 14m: Second circuit network port 16□, 16□: High frequency energy component 18
α1~18rL□, 18a2~18rL2: 1st component port 20α□~20m1120a2~20
m2: Second component port 21: Load 22 (1 to 22n: First power supply network 24a to 24m: Second power supply network Patent applicant Raytheon Company (5 others)

Claims (21)

[Claims] (1) A network for coupling energy delivered to a first portion of a plurality (n) of network ports to a second portion of the network ports, the network comprising: (a) a plurality of substantially equal components; a component, each having a plurality (n) of ports, and the degree of coupling between the ports of each component is characterized by a predetermined scattering coefficient; (b) a plurality (n) of feeding circuits; , each having a first port corresponding to one of a plurality (n) of network ports, and a plurality of second ports each coupled to a corresponding one of the respective plurality of ports of the plurality of components. and a feeding circuit network in which the degree of coupling between the first port and the plurality of second ports of each feeding circuit network is characterized by a predetermined scattering coefficient matrix, (c) the plurality of feeding circuits a network and the degree of coupling of this network to the component is defined by a matrix of associations between the n network ports, the scattering coefficient matrix being different from the scattering coefficient matrix characterizing each of the components. A circuit network that characterizes (2) the degree of coupling of the plurality of power supply circuit networks and this circuit network to the component for a pair of circuit network ports;
2. The circuitry of claim 1, wherein the circuitry provides a degree of coupling that is less than a degree of coupling between a pair of component ports coupled to said port. (3) a high frequency network having a first network port and a plurality of second network ports, comprising: (a) a pair of substantially identical high frequency components, each of which is connected to the first network port; the first coupled to
a component having a component port and a plurality of second component ports, the second component port having a degree of electrical isolation between the ports; (b) a second component port of the pair of components and the plurality of second component ports; and a power supply circuitry coupled between a second network port of the circuit and a power supply circuitry that provides a degree of isolation to the second network port that is greater than the degree of electrical isolation between the second component ports. (4) The network according to claim 3, wherein the feed network is a quadrature coupler. 5. The network of claim 4, further comprising a quadrature coupler coupled between the first network port and a first component port of the pair of components. (6) a phase shift between one of the pair of second network ports by one of the pair of components and the other of the pair of second network ports by one of the pair of components; differs by nπ (where n is an odd number) from a phase shift between one of the pair of second network ports and the other of the second pair of ports; m
6. Networks according to claim 5, which differ by π (m is an even number). 7. The circuitry of claim 6, wherein each of said components is a power divider/combiner. (8) A radio frequency network for coupling radio frequency energy between a first network port and a pair of second network ports, comprising: (a) a pair of substantially equal radio frequency components, each of which has a second network port; 1 component port and its first
a component having a pair of second component ports electrically coupled to the component, each second component port pair of the pair of components having a degree of electrical isolation therebetween; (b) the network port; the first of said pair of components;
(c) a pair of second feed means, one of which couples energy between a first similar port of a second pair of component ports of said pair of components and said second feed means; one of the second pair of network ports, the other of the second feed means coupling energy between a second similar port of the second pair of component ports of the pair of components and the other of the second pair of network ports; (d) the first feeding means and the pair of second feeding means couple energy associated therewith; a circuitry that provides said second network port pair with a degree of isolation that is greater than an electrical isolation between each second component port pair of said second component port pair. (9) a phase shift between one and the other of the second pair of network ports due to one of the pair of components is a phase shift between one and the other of the pair of second network ports due to the other of the pair of components; 9. Circuit networks according to claim 8, which differ by nπ (n is an odd number). (10) a phase shift between the first network port and one of the second pair of ports due to one of the pair of components is a phase shift between the first network port and one of the second pair of ports due to the other pair of components; 10. The circuitry according to claim 9, which differs from the other by a phase shift of mπ (m is an even number). (11) Each of the pair of second feed means comprises a four-port device, the first pair of four ports being connected to the second pair of four ports.
electrically coupled in pairs, the ports of each pair having a relatively high degree of electrical isolation between them, one of the first pair terminating at the load and the other one terminating at the corresponding one of the network ports. 10. The circuitry of claim 9, wherein said second pair is coupled to a like pair of said component pairs. (12) each of said second pair of feeds comprises a four-port device, a first pair of four ports electrically coupled to a second pair of four ports; one of the first pair is terminated at the load and the other supplies a corresponding one of the network ports;
11. The circuitry of claim 10, wherein said second pair is coupled to a like pair of said component pairs. (13) The network of claim 11, wherein the four-port device is a quadrature coupler. (14) The network of claim 12, wherein the four-port device is a quadrature coupler. (15) A radio frequency network for coupling radio frequency energy between at least one first network port and at least a pair of second network ports, comprising: (a) a pair of similar radio frequency energy components; , each having at least one first component port and at least a pair of second component ports electrically coupled to the first component port, the at least one pair of second component ports of each of the pair of components comprising: (b) a first component coupling energy between the at least one first network port and the at least one first component port of the pair of components; (c) at least one pair of second feeding means, one of which comprises a first like port of at least one second component port of said pair of components and a second network port of said at least one pair; and the other of the second feed means is coupled between a second analog port of the at least one second component port of the pair of components and the other of the at least one second network port of the pair of components. (d) said at least one first feeding means and at least one pair of second feeding means couple energy associated therewith; A network providing the at least one pair of second network ports with a degree of isolation that is greater than the degree of electrical isolation between the at least one pair of second component ports of each of the pair of components. (16) a phase shift between one of the at least one pair of second network ports and the other by one of the pair of components is such that a phase shift between one of the at least one pair of second network ports by the other of the pair of components; 16. The network of claim 15, wherein the phase shift between one and the other differs by nπ radians, where n is an odd number. (17) a phase shift between a first port of the at least one network port by one of the pair of components and one of the at least one second network port by the other of the pair of components; a phase shift between a first port of one network port and one of the at least one pair of second network ports;
17. The networks of claim 16, which differ by nπ (n is an even number) radians. (18) The first feed means and the at least one pair of second feed means are each four-port devices, the first pair of the four ports being electrically coupled to the second pair of the four ports, and the ports of each pair have a relatively high degree of electrical isolation therebetween, with one of the first pair terminating at the load and the other of the first pair supplying a corresponding one of said network ports, and the second of each four-port device. 18. The circuitry of claim 17, wherein a pair is coupled to like ports of a pair of said component pairs. (19)(a) a pair of substantially equal electrically independent radio frequency components, each having a first port and a pair of second ports, with the second port and the first port located between them; (b) first, second and third coupling means each electrically coupled to a pair of substantially electrically isolated second ports and to the second port; a coupled pair of substantially electrically isolated first ports, each coupling means responsive to a signal applied to one of the respective pair of first ports to provide π to the pair of second ports; /2 radians of phase shift, wherein the signal generated at one of the pair of second ports leads the signal generated at the other one;
When one signal of the pair of second ports leads the other signal of the pair of second ports by π/2 radians, the pair of signals sent to the second port is connected to one of the pair of first ports of the coupling means. When the other signal of the pair of second ports leads the signal of one of the pair of second ports by π/2 radians, the pair of signals sent to the second port are combined in the same phase. (c) coupling means for coupling one of the pair of second ports of the first coupling means to the first port of one of the pair of components;
The other of the pair of second ports of the coupling means is coupled to the first port of the other of the pair of components, and the one of the pair of second ports of one of the pair of components is coupled to the one of the pair of second ports of the second coupling means. , one of the second pair of ports of the other pair of components is coupled to the other of the second pair of ports of the second coupling means, and the other of the second pair of ports of one of the pair of components is coupled to the other of the second pair of ports of the third coupling means. a coupling device for coupling the other of the second pair of ports of the other component pair to the other of the second pair of ports of the third coupling means; (20) the other of the first port pair of the first coupling means, one of the first port pair of the third coupling means, one of the first port pair of the second coupling means, and the third coupling means; 20. The network of claim 19, having a load device coupled to one of the first pair of ports. (21) (a) a pair of substantially equal high frequency components each having three electrically coupled ports; and (b) a first port and a pair of first ports electrically coupled to the first port. A first power supply network having two ports,
a first power supply network, wherein one of the second pair of ports is coupled to a first port of one of the pair of components, and the other of the second pair of ports is coupled to a first port of the other pair of components; ) a second power supply network having a first port and a pair of second ports electrically coupled to the first port;
a second power supply, wherein one of a second pair of ports of the second power supply network is coupled to a second port of one of the pair of components, and the other of the second pair of ports is coupled to a second port of the other pair of components; (d) a third power supply network having a first port and a pair of second ports electrically coupled to the first port, the second port pair of the third power supply network; one of which is coupled to a third port of one of the pair of components, and the other of the second pair of ports is coupled to a third port of the other pair of components; ) (i) a first port of said first feed network and a first port of said second feed network by one of said pair of components;
the phase shift between the first port of the first feed network and the first port of the second feed network by the other of the component pair by nπ (where n is an even number); ii) a phase shift between a first port of the first feed network and a first port of the third feed network due to one of the component pair is such that a phase shift between the first port of the first feed network and the first port of the third feed network due to one of the component pair differs from the phase shift between the port and the first port of the third feed network by nπ (where n is an even number);
The phase shift between the first port of the feed network and the first port of the third feed network is such that the phase shift between the first port of the second feed network and the first port of the third feed network by the other of the pair of components A high-frequency network that differs by a phase shift between and mπ (where m is an odd number).