JPS60248028A - Service channel signal transmission system - Google Patents
Service channel signal transmission systemInfo
- Publication number
- JPS60248028A JPS60248028A JP59105240A JP10524084A JPS60248028A JP S60248028 A JPS60248028 A JP S60248028A JP 59105240 A JP59105240 A JP 59105240A JP 10524084 A JP10524084 A JP 10524084A JP S60248028 A JPS60248028 A JP S60248028A
- Authority
- JP
- Japan
- Prior art keywords
- signal
- circuit
- service channel
- pulse
- channel signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 230000008054 signal transmission Effects 0.000 title claims description 9
- 238000004891 communication Methods 0.000 claims description 3
- 230000000694 effects Effects 0.000 abstract description 7
- 230000002411 adverse Effects 0.000 abstract description 5
- 230000003111 delayed effect Effects 0.000 abstract description 3
- 230000000630 rising effect Effects 0.000 abstract description 3
- 230000010354 integration Effects 0.000 abstract description 2
- 230000005540 biological transmission Effects 0.000 abstract 1
- 230000004069 differentiation Effects 0.000 abstract 1
- 238000010586 diagram Methods 0.000 description 7
- 230000005236 sound signal Effects 0.000 description 6
- 238000012544 monitoring process Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 231100000989 no adverse effect Toxicity 0.000 description 1
- 230000001360 synchronised effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/06—Dc level restoring means; Bias distortion correction ; Decision circuits providing symbol by symbol detection
- H04L25/069—Dc level restoring means; Bias distortion correction ; Decision circuits providing symbol by symbol detection by detecting edges or zero crossings
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G3/00—Gain control in amplifiers or frequency changers
- H03G3/20—Automatic control
- H03G3/30—Automatic control in amplifiers having semiconductor devices
- H03G3/3036—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
- Dc Digital Transmission (AREA)
- Circuits Of Receivers In General (AREA)
Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は、打ち合わせ回線用の音声信号及び監視制御信
号よりなるサービスチャンネル信号で、送信局部発振器
をFM変調して送信するディジタル無線通信装置に係り
サービスチャンネル信号送信方式の改良に関する。[Detailed Description of the Invention] [Field of Industrial Application] The present invention relates to a digital wireless communication device that modulates a transmitting local oscillator with FM and transmits a service channel signal consisting of an audio signal for a meeting line and a supervisory control signal. This invention relates to improvements in related service channel signal transmission systems.
ディジタル無線通信装置ではサービスチャンネル信号を
送信する場合、経済化の為に、サービスチャンネル信号
で送信局部発振器をFM変調して送信する方法がよく用
いられるが、この場合当該FM変調波を被変調波とする
位相変1111a(PSK)波信号から成る主信号に悪
影響を与えず、サービスチャンネル信号も受信側で満足
に再生されることが望ましい。When transmitting a service channel signal in a digital wireless communication device, a method is often used in which the transmitting local oscillator is FM-modulated with the service channel signal for economical reasons. In this case, the FM modulated wave is converted into a modulated wave. It is desirable that the service channel signal be satisfactorily reproduced on the receiving side without adversely affecting the main signal consisting of a phase-shifted 1111a (PSK) wave signal.
第4図は従来例のサービスチャンネル信号送信方式のブ
ロック図であり、1は中間周波数帯の主信号を無線周波
数帯に変換する周波数変換器、2は周波数変換器1にて
周波数変換をする為の送信局部発振器、3は号−ビスチ
ャンネル信号の入力に設けられた、後方帰還A(、C又
はリミッタである。FIG. 4 is a block diagram of a conventional service channel signal transmission system, in which 1 is a frequency converter that converts the main signal in the intermediate frequency band to a radio frequency band, and 2 is a frequency converter for converting the frequency in the frequency converter 1. The transmitting local oscillator 3 is a backward feedback A (, C or limiter) provided at the input of the signal.
従来送信局部発振器2を、サービスチャンネル信号でF
M変調して送信する場合、サービスチャンネル信号の入
力に、送信局部発振器2が過変調にならないよう、後方
帰還AGC又はリミッタ3を設げる。The conventional transmitting local oscillator 2 is set to F by the service channel signal.
When transmitting with M modulation, a backward feedback AGC or limiter 3 is provided at the input of the service channel signal to prevent the transmitting local oscillator 2 from being overmodulated.
しかし後方帰還AGC3を設けた場合は、急に大きな音
声信号が入力すると後方帰還AGC3はこれに追従出来
なくレベルの高い信号が送信局部発振器2に入力し、過
変鋼となり、復調系にて主信号のディジタル信号の再生
に悪影響を及ぼす問題点があり、リミッタ3を設けた場
合は、第5図(A)に示す如く、打ち合わせ回線用の音
声信号と監視制御信号が多重化されており、音声信号が
大きくなると、リミットされる為過変鋼にはならないが
第5図(B)に示す如くレベルの小さい監視制御信号は
クリップされ、このクリップされた部分が受信側で再生
出来ない問題点がある。However, when the backward feedback AGC 3 is installed, if a large audio signal is suddenly input, the backward feedback AGC 3 will not be able to follow it, and a high level signal will be input to the transmitting local oscillator 2, resulting in an over-variable signal, which will cause the demodulation system to There is a problem in that it has an adverse effect on the reproduction of the digital signal, and when the limiter 3 is provided, the audio signal for the meeting line and the supervisory control signal are multiplexed, as shown in FIG. 5(A). When the audio signal becomes large, it is limited so that it does not become over-transformed, but as shown in Figure 5 (B), the low-level monitoring control signal is clipped, and this clipped part cannot be reproduced on the receiving side. There is.
上記説明の如(、従来のサービスチャンネル信号送信方
式では、後方帰還AGCを用いた場合は、急に大きな音
声が入力すると復調系にて主信号のディジタル信号の再
生に悪影響を及ばず問題点があり、リミッタを用いた場
合は、音声信号が大きくなるとレベルの小さい監視制御
信号はクリップされ、このクリップされた部分が受信側
で再生出来ない問題点がある。As explained above (in the conventional service channel signal transmission system, when backward feedback AGC is used, there is a problem that if a sudden loud voice is input, it does not adversely affect the reproduction of the main digital signal in the demodulation system. However, when a limiter is used, there is a problem that when the audio signal becomes large, the low-level monitoring control signal is clipped, and the clipped portion cannot be reproduced on the receiving side.
上記問題点は、サービスチャンネル信号の入力に該サー
ビスチャンネル信号が所定のレベルを越えた時のみ高速
応答のAGC動作をする前方帰還AGC回路を設けた本
発明のサービスチャンネル信号送信方式により解決され
る。The above problem is solved by the service channel signal transmission system of the present invention, which includes a forward feedback AGC circuit that performs a high-speed response AGC operation only when the service channel signal exceeds a predetermined level. .
本発明の場合は、音声が急に大きくなれば、高速応答の
前方帰還AGC回路で直ちに利得を下げるので、出力側
には大きなレベルの信号は表れず送信局部発振器は過変
調になることはなく、復調系にて主信号のディジタル信
号の再生に悪影響を及ぼすことはなくなるし、又レベル
の小さい監視制御信号が重畳されていても、これはクリ
ップされることはなく利得が圧縮され通過するので受信
側で再生可能である。In the case of the present invention, if the audio suddenly becomes louder, the gain is immediately lowered by the fast-response forward feedback AGC circuit, so no large level signal appears on the output side, and the transmitting local oscillator does not overmodulate. , there will be no adverse effect on the reproduction of the main digital signal in the demodulation system, and even if a low-level supervisory control signal is superimposed, it will not be clipped and its gain will be compressed and passed through. It can be played back on the receiving side.
以下本発明の実施例につき、図に従って説明する。 Embodiments of the present invention will be described below with reference to the drawings.
第1図は本発明の実施例のナービスチャンネル信号送信
方式のブロック図、第2図は第1図の各部の波形のタイ
ムチャートで(A)〜(E)は第1図のa −e点に対
応し、(F)は利得変化を示し、図中、10は遅延回路
、11は可変利得増幅器を示す。尚を企図を通じ同一符
号は同一機能のものを示す。Fig. 1 is a block diagram of a service channel signal transmission system according to an embodiment of the present invention, Fig. 2 is a time chart of waveforms of each part in Fig. 1, and (A) to (E) are points a to e in Fig. 1. (F) shows the gain change, and in the figure, 10 is a delay circuit and 11 is a variable gain amplifier. For the purpose of the present invention, the same reference numerals indicate the same functions.
第1図において、第2図(A)に示す入力信号は全波整
流回路4にて全波整流され比較器5に入力する。比較器
5では、送信局部発振器2が過変調にならない、しきい
値電圧Vが加えられており、この電圧■を越えると第2
図(B)に示す如きパルスを発する。In FIG. 1, the input signal shown in FIG. 2(A) is full-wave rectified by a full-wave rectifier circuit 4 and input to a comparator 5. A threshold voltage V is applied to the comparator 5 so that the transmitting local oscillator 2 does not become overmodulated.
A pulse as shown in Figure (B) is emitted.
このパルスは微分回路6に入力し、立ち上がり点及び立
ち下がり点にて第2図(C)に示す如き微分パルスを出
力し、整流回路7にて立ち下がり点の微分パルスはカッ
トされ、加算器9に入力する。This pulse is input to a differentiating circuit 6, which outputs differentiated pulses at the rising and falling points as shown in FIG. Enter 9.
一方比較器5の出力パルスは、積分回路8にも入力し積
分され第2図(D)に示す如きパルスとなり加算器9に
入力する。On the other hand, the output pulse of the comparator 5 is also input to an integrating circuit 8 and is integrated to become a pulse as shown in FIG. 2(D) and input to an adder 9.
加算器9では両者を加算し、第2図(E)に示す如き、
立ち上がりに対しては微分回路6による高速応答のパル
スを形成し、可変利得増幅器11に加え、第2図(F)
に示す如く利得を変化さす。The adder 9 adds the two, and the result is as shown in FIG. 2(E).
For the rising edge, a high-speed response pulse is formed by the differentiating circuit 6, and in addition to the variable gain amplifier 11, the pulse is
Change the gain as shown in .
−万人力信号は、遅延回路10にてAGCループによる
遅延分遅延され可変利得増幅器11に入力するようにし
て、入力信号のレベルの変化に対し可変利得増幅器11
の利得変化を同期させているので、送信局部発振器2が
過変調になる大きな音声信号は直ちに抑圧され、重畳さ
れている小さいレベルの監視制御信号は圧縮され通過す
る。- The universal power signal is delayed by the delay caused by the AGC loop in the delay circuit 10 and inputted to the variable gain amplifier 11, so that the variable gain amplifier 11 responds to changes in the level of the input signal.
Since the gain changes of the transmitting local oscillator 2 are synchronized, a large audio signal that causes overmodulation of the transmitting local oscillator 2 is immediately suppressed, and a superimposed small level supervisory control signal is compressed and passed.
従って、送信局部発振器2は過変調にならず、復調系に
て主信号のディジタル信号の再生に悪影響を及ぼすこと
はなくなるし、又レベルの小さい監視制御信号が重畳さ
れていても、これはクリップされることはなく★1j得
が圧縮され通過するので受信側で再生不能になることは
ない。Therefore, the transmitting local oscillator 2 will not be overmodulated and will not have a negative effect on the reproduction of the main signal digital signal in the demodulation system, and even if a low-level supervisory control signal is superimposed, it will not be clipped. Since the ★1j gain is compressed and passed through, it will not become unplayable on the receiving side.
第3図(A)は本発明の他の実施例のプロ′ンク図で、
第3図(B)はウィンド形比較器の特性図中である。FIG. 3(A) is a perspective view of another embodiment of the present invention.
FIG. 3(B) is a characteristic diagram of the window type comparator.
図中12はウィンド形比較器を示す。In the figure, 12 indicates a window type comparator.
第3図にて第1図と異なる点は全波整流回路4と比較器
5の代わりにウィンド形比較器12を用いた点である。The difference between FIG. 3 and FIG. 1 is that a window type comparator 12 is used instead of the full-wave rectifier circuit 4 and comparator 5.
このウィンド形比較器12の特性は、第3図(B)に示
す如(、送信局部発振器2が過変調になるレベルに対し
、しきい値電圧+V、−Vを設げてあり、このレベルを
越えた場合ルベルのパルスを発するもので、第1図の全
波整流回路4と比較器5の動作を1個のウィンド形比較
器12にて行うものである。The characteristics of this window type comparator 12 are as shown in FIG. When the voltage exceeds 1, a Lebel pulse is generated, and a single window type comparator 12 performs the operations of the full-wave rectifier circuit 4 and the comparator 5 shown in FIG.
従って、第3図(A)の場合の動作は第1図の場合と同
しである。Therefore, the operation in the case of FIG. 3(A) is the same as in the case of FIG.
以上詳細に説明せる如く本発明によれば、急に大きな音
声が入力しても、復調系にて主信号のディジタル信号の
再生に悪影響を及ぼすことはなくなり又レベルの小さい
監視制御信号が重畳されていても、これはクリップされ
ることはなく利得が圧縮され通過するので受信側で再生
不能になることばなくなる効果がある。As described in detail above, according to the present invention, even if a loud voice is suddenly input, it will not have an adverse effect on the reproduction of the main signal digital signal in the demodulation system, and a low level supervisory control signal will not be superimposed. Even if the signal is recorded, it is not clipped and the gain is compressed and passed through, which has the effect of eliminating problems that cannot be reproduced on the receiving side.
第1図は本発明の実施例のサービスチャンネル信号送信
方式のブロック図、
第2図は、第1図の各部の波形のタイムチャート、
第3図(A)は本発明の他の実施例のブロック図、
第3図(B)はウィンド形比較器の特性図、第4図は従
来例のサービスチャンネル信号送信方式のブロック図、
第5図は打ち合わせ回線用の音声信号と監視制御信号が
多重化されている場合の波形図である。
図において、
】は周波数変換器、
2は送信局部発振器
3ば後方帰還AGCまたはリミッタ、
4は全波整流回路、
5は比較器、
6は微分回路、
7は整流回路、
8は積分回路、
9は加算器、
10は遅延回路、
11は可変利得増幅器、
】2はウィンド形比較器を示す。
代理人 弁理士 松岡宏四部FIG. 1 is a block diagram of a service channel signal transmission system according to an embodiment of the present invention, FIG. 2 is a time chart of waveforms of each part in FIG. 1, and FIG. Block diagram: Figure 3 (B) is a characteristic diagram of the window comparator; Figure 4 is a block diagram of a conventional service channel signal transmission system; Figure 5 is a multiplexing of voice signals and supervisory control signals for the meeting line. FIG. In the figure, ] is a frequency converter, 2 is a transmitting local oscillator, 3 is a backward feedback AGC or limiter, 4 is a full-wave rectifier circuit, 5 is a comparator, 6 is a differentiator circuit, 7 is a rectifier circuit, 8 is an integration circuit, 9 is an adder, 10 is a delay circuit, 11 is a variable gain amplifier, and ]2 is a window comparator. Agent Patent Attorney Hiroshi Matsuoka
Claims (1)
て送信するディジタル無線通信装置において、該サービ
スチャンネル信号の入力に該サービスチャンネル信号が
所定のレベルを越えた時のみ商速応答のAGC動作をす
る前方帰還AGC回路を設けたことを特徴とするサービ
スチャンネル信号送信方式。In a digital wireless communication device that FM-modulates a transmitting local oscillator with a service channel signal and transmits the signal, forward feedback performs AGC operation with a commercial speed response only when the service channel signal exceeds a predetermined level at the input of the service channel signal. A service channel signal transmission system characterized by providing an AGC circuit.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP59105240A JPS60248028A (en) | 1984-05-24 | 1984-05-24 | Service channel signal transmission system |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP59105240A JPS60248028A (en) | 1984-05-24 | 1984-05-24 | Service channel signal transmission system |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS60248028A true JPS60248028A (en) | 1985-12-07 |
Family
ID=14402121
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP59105240A Pending JPS60248028A (en) | 1984-05-24 | 1984-05-24 | Service channel signal transmission system |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS60248028A (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5361395A (en) * | 1991-02-28 | 1994-11-01 | Kabushiki Kaisha Toshiba | Gain control circuit |
US6580905B1 (en) * | 1996-07-02 | 2003-06-17 | Ericsson Inc. | System and method for controlling the level of signals output to transmission media in a distributed antenna network |
-
1984
- 1984-05-24 JP JP59105240A patent/JPS60248028A/en active Pending
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5361395A (en) * | 1991-02-28 | 1994-11-01 | Kabushiki Kaisha Toshiba | Gain control circuit |
US6580905B1 (en) * | 1996-07-02 | 2003-06-17 | Ericsson Inc. | System and method for controlling the level of signals output to transmission media in a distributed antenna network |
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