JPS60147796A - Signal snthesizer - Google Patents

Abstract

(57) [Summary] This bulletin contains application data before electronic filing, so abstract data is not recorded.

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a signal synthesizing device that generates a wide band analog signal from a narrow band atherosclerotic signal.

This invention deals with technology related to the following patent application filed by the same applicant as the present application.

(a) Japanese Patent Application No. 58-45193 "Signal Synthesizer" (b) Japanese Patent Application No. 58-190331 "Distortion Synthesizer" There are many signal transmission systems that have no choice but to

Examples include a medium wave AM transmission/reception system and a recording/playback system using the audio track of a β or VH8 type VTR.

An object of the present invention is to provide a signal synthesis device that enables wideband transmission while maintaining compatibility with such narrowband signal transmission systems.

In order to achieve the above object, the signal synthesis device according to the present invention utilizes, for example, the following mathematical relationship to generate the second harmonic component of the force signal or 1/! The lower harmonic components are synthesized.

(1n 2txrri2ωt −1= ms2ωt (2
Next) In this invention, for example, 50 Hz to 10
30 Hz to 16 kHz narrowband analog input signal
The following measures are taken to generate a kHz wideband analog output signal. That is, high-frequency wave components (cos
2ωt) is obtained. By appropriately adjusting the amplitude and phase of the second harmonic component obtained in this way and adding it to the input signal, an analog output signal of 50I (z ~ 16kHz) is obtained.Next, the output signal of or From the input signal, 60 Hr ~ order subharmonic components (4 pieces) are obtained. By appropriately adjusting the amplitude and phase of this 1/2 order subharmonic component, all of these 50 Hz to 16 kHz analog outputs are obtained. When added to the signal, a broadband analog output signal from 30 Hz to 16 kHz is obtained.

In Figure 1, the second harmonic component 2ω is obtained from the input frequency component ωt by using the relationship 2ωt = 1 (1 + 2ωt).
3 shows a signal synthesizer for synthesizing t.

For example, for a narrowband analog input signal of 50 Hz to 10 kHz, a bandpass filter (BPF) 10
is input. The BPF 10 extracts high frequency components of, for example, 4 kHz to 8 kHz from the input signal Ei. The signal EIO extracted by the BPF JO is input to a function conversion circuit (analog square circuit) 11. Assuming the signal E 10 f Ecosωt (E is amplitude),
From the circuit 11, a signal El corresponding to E2QIS2ωt is output.
l is output. According to the frequency component only,
Signal Ell is 2+F! - Corresponds to 2ωt. From this signal Ell to Kya A? The second harmonic signal E12 corresponding to 21□□□2ωt is obtained by the shifter 12. This signal E12 is suitably advanced or delayed by the phase shifter 13. Signal E13 output from phase shifter 13
The amplitude of can be freely adjusted using the coefficient k of the coefficient multiplier 14, which can be changed arbitrarily. This coefficient multiplier 14 receives signals E10.
Level consolation control controlled by amplitude of E11 etc.
may include repellexno9nda.

The coefficient unit 14 outputs a composite signal E14. Signal E
14 has an amplitude (7-) corresponding to E2 to the amplitude ('E) of the input signal Ei, and has a frequency component (5+C8kHz to 16kHz) that is not found in the frequency components (4kHz to 8kHz) extracted from the signal Ei. This signal E14 is added and synthesized with the input signal Ei in an analog adder 15. From this adder 15, 50 Hz ~
10 kHz signal Ei to 8 kHz to 16 kHz
Wideband analog output No. 48 E on which the signal E14 of is superimposed
o (5'OHz to 16 kHz, , ) is obtained.

In the configuration shown in FIG. 1, since the function conversion circuit 11 is a nonlinear circuit, the signals EJJ to E14 contain waveform distortion. However, this distortion mainly consists of second harmonic components. 7
The frequency components of signals F, 11 to E14 are 8k.
Since it is high at Hz to 16 kHz, its second harmonic is 1
The frequency ranges from 6 kHz to 32 kHz. Therefore, the reproduced sound of the output signal E0 has substantially no audible distortion. Here, it is sufficient to divide by the amplitude component (E) of the wave signal E10 due to the nonlinearity (square characteristic) of the circuit 11.

When synthesizing the second-order harmonic component bunch 2ωt using the relationship ωt:=2 (1-(9)2ωt), the first
The configuration shown in the figure is fine.

FIG. 2 shows the input frequency component sinωtTh and the coefficient ω using the relationship sinωtcosωt=25in2ωt.
A signal synthesis device for synthesizing a second harmonic component image 2ωt from t is shown.

For example, a narrowband input signal E of 50 Hz to 10 kHz
1 to 4 kHz by BPF 20, e.g.
A high frequency component of 8 kHz is extracted. The signal E20 extracted by the BPF 20K is input to the phase shifter 2 with a phase shift amount φA and the phase shifter 22 with a phase shift amount φB.

The phase shift amounts φA and φB are the output signals E2 of the phase shifters 21 and 22.
1. The size is selected so that the phase difference of E22 is approximately 90° between 4 kHz and 8 kHz.

As a result, if the signal E21 is expressed by Eglnωt, the signal E22 becomes Ecosωt. Signal E21 and F, 2
2 is input to the analog multiplier 23.

The multiplier 23 outputs a signal E 2 B (E2slnO)teasωt corresponding to the product of the signal E21 and the signal E22.
) is output. Focusing only on the frequency component of this signal E23, slnωtcosωt corresponds to the pot S stone 2ωt.

Therefore, the signal E23 is between 8 kHz and 16 kHz
It corresponds to -5ln2ωt having a frequency component of z2. This time, it may be the same as the coefficient multiplier 14.

The signal E 25 (8 kHz to 16 kHz) is an input signal in the analog adder 26)4 (50 Hz to 1
0 kHz), and this adder 26 to 50
An analog output signal E0 whose band C) is expanded to the high frequency side of Hz to 16 kHz is obtained.

In the configuration shown in FIG. 2, since the multiplier 23 operates non-linearly, the signals E23 to E25 contain waveform distortion.

This distortion is caused by the signal F as described in the embodiment of FIG.
, 23 to E25 as signals E20 to E2.
It can be removed or reduced by dividing by any one of the amplitude components of 2.

FIG. 3 shows a signal synthesis device that synthesizes a second harmonic component tuft 2ωt from an input frequency component width ωtb and an image ωt using the relationship ωt−5lu2ωt=tuft 2ωt.

From a narrowband input signal Ei of e.g. 50 Hz to lQ kHz, the BPF 30 outputs a
A high frequency component of ~8kHz is extracted. Similarly to the case of FIG.
t). Signals E31 and E32 are input to 2-east circuits 33 and 34, respectively. A signal E3B corresponding to E2th2ωt is output from the circuit 33,
Fin ω from circuit 34! A signal E34 corresponding to the signal E34 is output. Signals E33 and EJ4 are sent to analog subtracter 35
is input. From the subtracter 35, the signal difference E34-E3
J.

That is, a signal E35 corresponding to E2 (cell 2ωt-gin2ωt) or E2 cell 2ωt is output. This signal E
35 becomes a composite signal E37 via a phase shifter 36 and a coefficient multiplier 37. This phase shifter 36 and coefficient multiplier 37 are
They may be the same as the phase shifter 13 and coefficient unit 14 in FIG.
0 kHz) from this adder 38 to 50
Wideband analog output signal E from Hz to 16 kHz.

is obtained.

In the configuration of FIG. 3, the square paths 33, 34 produce non-linear distortion. This distortion is applied to both signals E3B and EJ4 or signal ES as described in the embodiment of FIG.
S to E37 as signal 'E, 30 to E,
It can be removed or reduced by dividing by any one of the 32 amplitude components.

FIG. 4 shows a case where the function conversion circuit 11 of FIG. 1 is configured using an AGC (or ALC) circuit. That is, the signal E 10 (=EcmQ)t) is input to the AGC circuit 11k. Gain control signal v for 11 people in this circuit
g is obtained from the signal EIO via the limiter circuit (or ALC circuit) 11B. The limiter circuit JJB outputs a signal vg having the same frequency as the signal EIO and a substantially constant amplitude. The AGC circuit 11 has a gain corresponding to a control signal with a constant amplitude that changes depending on the signal frequency of the signal EIO, and uses this gain to amplify the signal EIO and output the signal Ell. do. In other words, the AGC circuit 11
The signal EIO (E house ωt) is changed to the signal Vg (oosωt).
It functions as an AM modulator that performs amplitude modulation. By this modulation, the frequency component of the sum of the signal EIO and the signal vg ((
9) Second-order high phrase wave signal E 11 (Ect
s2ωt) is obtained.

In the configuration shown in FIG. 4, when the control signal vg has a constant amplitude, the amplitude of the signal Ell is proportional to the signal EIO and tl, so that the waveform distortion described in the embodiment of FIG. 1 is less likely to occur. .

FIG. 5 shows a configuration in which the analog multiplier 23 in FIG. 2 is replaced with an AGC circuit.

That is, for example, the signal E 21 (Es1ncu) is input to the AGC circuit 23k as a modulated input.

The gain control signal V of this circuit 23A is the limiter circuit 23
It is obtained from the signal E22 (E■ωt) via B. Limiter circuit 2.9 B is the frequency component of signal E22 (ωt
) is output as a constant amplitude signal vg. Tsumashi, AGC
Circuit 2.9 A converts the signal E21 (Es stone ωt) into the signal V
The second harmonic component (s
[+12ωt) is produced.

According to the configuration shown in FIG. 5, as in the case shown in FIG. 4, the waveform distortion of the second harmonic component is small.

Figure 6 shows cos'','=8('1+cos(ut)
A signal synthesis device is shown that synthesizes a 1/2-order subharmonic component bunch from an input frequency component part ωt using the following relationship.

For example, a narrowband input signal E of 50 Hz to 10 kHz
1 to BPF 60 VC, for example 60H2~
A low frequency component of 120 Hz is extracted. Input signal Ei is also input to rectifier circuit 66. Circuit 66 outputs signal E
A signal EQ6 having a time-independent component proportional to the amplitude component (E) of i is output.

This rectifier circuit 66 is manufactured by W4, published by the same applicant as the present application.
It may be configured using the techniques disclosed in FIGS. 2, 15, 16, and others of Sareta PCT Application A JP/78100040. This PCT application (Es1
ncu )2+(Emωt)2=E2 or 〆(E
s1ncut)2〒(EQIISG) via = E
A method of obtaining only the amplitude component (E) regardless of the signal frequency component (ωt) by utilizing the following relationship, and a method of obtaining the amplitude component (E) with less resiliency by using a small rectification time constant from multiple multiphase signals that overlap each other. discloses how to obtain it.

The signal E60 (Eays
ωt) and the signal E66 (
E) is input to the analog adder 6. From the adder 6, the sum of the signal E66 and the signal ]C60, that is, E
A signal E61 indicating +E asωt or W(1+asωt) is output.

This signal E61 is input to a function conversion circuit (12 circuits) 62. In this case, the r characteristic of its 62 is, for example, FE
This can be obtained by utilizing the nonlinearity of dart voltage/drain current characteristics such as T. This signal E62 is converted from 30 Hz to 60 Hz via a phase shifter 63 and a coefficient multiplier 64.
The resulting composite signal E64 is distributed as follows. The basic configurations of the phase shifter 63 and the coefficient multiplier 64 may be the same as those of the phase shifter 13 and the coefficient multiplier 14 in FIG.

The signal E64 (30Hz to 6.0Hz) is input to the analog adder 65 as the input signal El (50Hz to 10k
Hz), and from this adder 65, 30 Hz
Analog output signal E with wide band on the low frequency side of ~10 kHz. is obtained.

Figure 7 shows sin” ” 〆' (] asm t)
A signal synthesis device is shown that synthesizes a 1/2-order subharmonic component 5ln-'7 from an input frequency component part ωt using the following relationship. The circuit elements in the 70s in FIG. 7 may be similar to the circuit elements in the 60s in FIG. 6, which have the same first digit.

However, due to the difference in the mathematical relationship used, an analog subtracter 71 is used in FIG. 7 instead of the analog adder 61 in FIG. 6. The frequency component (si+r'') of the synthesized signal E74 is equivalent to the frequency component Ca, -) of the synthesized signal E64 in FIG. 6, if the phase is ignored.

FIG. 8A shows a case where the function circuit 62 of FIG. 6 is constructed with a 7' digital path. That is, the signal E6J (E(1+tuple ω1)) has a sampling frequency of 40 kHz, for example.
At z, the data is converted into digital data D62A by the φ converter 62A. Data D62A is input to ROM 62B as 7PL/sdayp. Each address of ROM 62B contains input address data D62A.
No J? parameters are stored. These digital data are read from ROM 62B at a read rate of, for example, 40 kHz. ROM62
Digital data D62B read from B is color-converted by i-converter 62CK at a rate of, for example, 40 kHz. The analog output E62C of the converter 62C is
It passes through a low-nos filter (LPF) 62, D and becomes a signal corresponding to the signal E62 in FIG.

According to the configuration shown in FIG. 8A, EcXBωt or Es stone ω is stored in advance in the ROM 62B.
t to E2cJ'ωt, Ea2ωt + Es1n
2ωt rEsInωt other signals can also be obtained.

FIG. 8B shows that the signal E12 in FIG. 1 has a square amplitude component (E2
), this squared amplitude component is transformed into a first-order amplitude component (E
) is shown as an example of an analog divider. That is, 2
A signal E12 having a multiplied amplitude component E2cos2ωt is input to the AGC (i ta uALc) circuit 16 as a divided signal. The AGC circuit 16 functions as a Hall level conzore, and uses the amplitude component E of the signal EIO as its gain control signal vg. This signal ■g is the signal E1(1(
It is obtained by rectifying the E fish ωt) using the rectifier circuit 17.

According to the configuration shown in FIG. 8B, the gain of the AGC circuit 16 decreases (increases) in proportion to the increase (decrease) K in the amplitudes E of the signals F and 10. Therefore, the signal E12 having the square amplitude component E is substantially converted into the signal E16 having the -order amplitude component E. This signal E16 may be input to the phase shifter 13 in FIG.

FIG. 8C shows that the signal E62 in FIG. 6 has a 1/2 power amplitude component (
4), an example of an analog multiplier that returns this 1/2 power amplitude component to the primary amplitude component (E) 4C is shown below. That is, the signal E62 having the ]/22 power component V E ays 2 is used as the multiplicable signal by AGC (or ALC).
It is input to circuit 67.

AGC circuit 67 functions as a level expander 1-1
The amplitude component i of the signal B62 is used as the gain control signal vg. This signal vg is obtained by rectifying the signal P262 with a rectifier circuit 68.

According to the configuration of FIG. 8C, the gain of the AGC circuit 67 increases (decreases) in proportion to the increase (decreases) in the amplitude I/'i of the signal E62. Therefore, the signal E62 having the 1/2-th power amplitude component i is substantially the same as the signal E62 having the -th power amplitude component E.
Converts to 7. This signal E67 is applied to the phase shifter 6 in FIG.
All you have to do is enter 3.

In FIGS. 8B and 8C, a rectifier circuit 174,
Take 68 is the aforementioned PCT application, A Jp, '78
It may be configured using the technique of obtaining the control signal e4 (technique 4) of No. 100040.

Figure 9 shows 3B stone ωt-4g1n3ωt=gln:(ω
This figure shows a signal synthesis device that synthesizes a third harmonic component f, sInβωt from an input frequency signal p5iftωt using the relationship t.

For example, a narrowband input signal E of 50 Hz to 10 kHz
From l to BPF 90, for example 3kH2~6k
Mid-high frequency components of Hz are extracted. Signal E90 extracted by BPF 90 is input to 3-east circuit 91 and 3-fold circuit 94. When the signal E9θ is expressed as EsInωt, from the circuit 9), E'gb+3ωt or El
A signal E91 corresponding to lII+3ωt is output, and a signal E9'4 corresponding to 3&Inωt is output from the circuit 94. The configuration of the circuit 9 for producing E 3ωt from Ednωt may be the one shown in FIG. 8A.

Signal E90. E91 amplitude change is small, IE31=
When the approximation of iEl holds true, the circuit 91 may be a simple analog cube circuit. The signal E91 passes through the quadrupling circuit 92 and becomes the signal E92 corresponding to the 4Es stone ωt. - Signals E, 92 and E 9.4 are analog subtractor 93
is input. From the subtracter 93, the signal difference E94-E9
2, that is, 3Eslnωt-4EsIn'ωt or Egln3ωt (9 kHz & 18 kHz), a signal E93 is output. This signal E93 becomes a composite signal E96 via a phase shifter 95 and a coefficient multiplier 96. The phase shifter 95 and coefficient multiplier 96 may be similar to the phase shifter 13 and coefficient multiplier 14 in FIG.

The signal E 96 (9 kHz to 18 kHz) is input to the input signal Et (50 Hz to 1
0 kHz), and from this adder 50Hz~
A broadband analog output signal E0 of 18 kHz is obtained.

FIG. 1O shows a signal synthesizing device that synthesizes a third harmonic component 3ωt from an input frequency component part ωt using the relationship: 4 ωt−3 ωt=3ωt.

The circuit elements numbered in the 100s in FIG. 10 may be similar to the circuit elements numbered in the 90s in FIG. 9, which have the same first digit. However, due to the difference in the mathematical relationships used, the subtracter 93 in FIG. 9 outputs a signal E93 corresponding to E94-E92, whereas the subtracter 103 in FIG.
A signal E103 corresponding to E104 is output.

The frequency component (wavelength 3ωt) of the synthesized main signal EJ06 is:
If the phase is ignored, it will be the same as the frequency component (ldr+3ωt) of the composite signal E96 in FIG.

Figure 11 is 3 east circuit 9 in Figure 9 (or 3 in Figure 10).
An example of the configuration of the east circuit 101) is shown. Signal E 90 (Es
ioωt) is input to an analog multiplier 91 and a limiter (or ALC) circuit 91CIIC. The limiter circuit 91C outputs a signal E91'C having a frequency component (slnωt) of the signal E90 and having a substantially constant amplitude. This signal E91C is input to a multiplier 91k. Then, the multiplier 91A outputs a signal E91k corresponding to Egln2ωt.
is output.゛This signal E91kL- and signal E9J
C is multiplied by analog multiplier 91B, and Ell
-ωt is converted into a signal E91 corresponding to ωt.

FIG. 12 shows an example of a combination of the signal synthesizers shown in FIGS. 1, 10, and 6 and the distortion synthesizer disclosed in Japanese Patent Application No. 58-190331 mentioned above.

In FIG. 12, a second harmonic synthesizer 2HF corresponding to the configuration of FIG.
From kHz to 5 kHz components, 5kHz to 10
A kHz composite signal E14 is generated.

The differentiating circuit 12 in FIG. 12 corresponds to the DC cut capacitor 12 in FIG. When the differential time constant of the circuit 12 is small, for example, when the house ωt is differentiated with respect to time, it becomes 1ωt. In this case, the differential output signal has an opposite phase and its amplitude increases in proportion to ω. Therefore, if necessary, an equalizer for frequency characteristic compensation or a phase inverter (not shown) may be inserted between the differentiating circuit 12 and the phase shifter 13.

The third harmonic synthesizer 3HF corresponding to the configuration shown in FIG.
For example, from the 3 kHz to 6 kHz components of the signal Ei, a 9 kHz to 18 kHz composite signal E106 is generated.
produce. In the embodiment of FIG. 10, circuits 102, 104
specifies the magnification, but the circuits 102 and 10 in FIG.
4, the magnification can be arbitrarily adjusted by 2°k3. This adjustment allows the waveform of the composite signal E106 to be changed.

The 172nd harmonic synthesizer 2LF corresponding to the configuration shown in FIG. 6 generates a composite signal E64 of 25 Hz to 50 Hz from, for example, the 50 Hz to 100 Hz components of the signal Ei. In addition, in the low frequency distortion synthesis section 2HD, BPF J 2
For example, from 50 Hz to 100 Hz from the signal Ei.
The Hz component is extracted. The extracted signal E120 is suitably phase-shifted by a phase shifter 121, and adjusted to a suitable amplitude by a coefficient multiplier 122. The signal Eli! output from the coefficient unit 122! 2 (50 Hz to 100 Hz) is combined with the composite signal E64 in reverse phase (or in positive phase depending on the case) in an analog subtracter 65AFC.

The signal E122 of 50 Hz to 100 Hz is 25H
It is used to electrically cancel second-order distortion generated by a speaker (not shown) or the like by the signal E64 of 2 to 50 Hz.

The subtracter 65A outputs a low frequency composite signal E65k corresponding to E64-E65A. Signal E65A, E10
6 and E14 - together, analog adder 12
3Vc is input. Adder 123 receives these signals E6
5A, E106. Adding E J4 to the input signal Ei, 2
A wideband analog signal E0 of 5 Hz to 18 kHz is output. 13 shows that when the signal synthesis device according to the present invention is used in a radio or television transmitting/receiving system and the band is narrowed, the narrow band signal is converted to the original signal E.
A broadband signal E close to in. This is a system that returns the system to UT.

For example, a broadband signal Ei of 25 Hz to 16 kHz
n is input to AM transmitter 13 as a modulation input. A pilot signal E130 of, for example, 10 Hz is also input to the transmitter 131 from the pilot signal generator 130. From transmitter 13, signals Ein and E
A high frequency signal E of, for example, IMHz, modulated at 130
131 is sent to transmitting antenna 132. antenna 1
The radio waves of lM)fz emitted from the antenna 32 are captured by the receiving antenna 133. The received signal E133 from the antenna 133 is, for example, a superheterodyne AM signal.
The signal is input to the receiver 134. Receiver 134 receives signal E1
33 is amplified/detected to obtain signals Ein and EJ, ? Generates a signal corresponding to 0. From this signal, the signal EinK
The corresponding audio signal E134 and the detection signal P134 corresponding to the signal E130 are frequency separated by, for example, a filter.

During the process of transmission and reception, the audio signal E134 becomes a narrowband signal with a −3 dB bandwidth of, for example, 25 Hz to 3 kHz. However, if we consider the signal attenuation region, the signal E1
34 includes high frequency components up to 8 kHz, for example. This narrowband signal El 34 (corresponding to Ei in FIGS. 1 to 12) is input to a signal combiner 135. This synthesizer 135 includes FIGS. 1 to 3 and 9,
It is composed of either one of FIG. 10 or FIG. 12 or a combination of a plurality of them. This synthesizer 135 may include the signal synthesis device of Japanese Patent Application No. 58-45193 and/or the distortion synthesis device of Japanese Patent Application No. 58-190331 mentioned above. The signal synthesizer 135 converts the signal E134, which attenuates toward high frequencies, from 4 kHz to 8 kHz, for example.
In order to effectively extract the kHz component, it is desirable to include an equalizer (not shown) that compensates for high-frequency attenuation of the signal E134.

The signal combiner 135 converts the 25 Hz to 3 kHz narrowband signal E 134 into a 25 Hz to 16 kHz signal, for example.
A broadband signal EJss of z (corresponding to t in FIGS. 1 to 12) is produced. This signal E135 is applied to the first terminal of an analog switch 137. A narrowband signal E134 is applied to the second terminal of the switch 137. Switch 137 selects either narrowband signal E134 or wideband signal E135 to output signal E. Give ut.

The switch 137 may be operated manually, but it may also be switched automatically. The detection signal P134 is No'? The signal is input to the pilot signal detector 136. For example, the detector 136 has a center station □ wave number of 10! (Composed of a pantone matrix filter with high Q in Z and a level converter.Pyro from receiver 134.

10Hz detection signal P134 corresponding to signal E130
When this signal P134 is output, the detector 136 generates a switching command 5136 when the signal level is equal to or higher than a predetermined level.

This command 5134 causes the analog switch 137 to switch from the second terminal side to the first terminal side.

Tip 9: When a radio wave including a pilot signal E130 instructing wideband reception is emitted from the transmitter 131 side, signal synthesis is automatically performed by the signal synthesizer 135 on the receiver 134 side, and a wideband signal Eout is output. Ru. Transmitter 1
3) When the side does not transmit the pilot signal E130,
The receiver 134 side performs conventional narrowband reception.

In the configuration shown in Fig. 13, for example, what about broadcast programs such as news programs that may be difficult to receive in a narrow band? A?A broadcast program that does not generate the pilot signal E130 and is suitable for wideband reception of music programs, etc. Ilot signal E130
There are various benefits to allowing this to occur.

For example, assume that an AM radio having a configuration of elements 134 to 1.97 is commercially available, and that broadcast station A has element 130 and broadcast station B does not have element 130. In this case, on Needday with the above radio, broadcasting station A is pilot signal E13.
0 and the music aired by broadcast station B can always be listened to in good quality. From this, broadcast station A is more likely to have a higher audience rating than broadcast station B. On the other hand, from the user's perspective, AM radio A without elements 135 to 137) also has element 135.
AM Radio Otsu with ~132 has better sound, so Radio Otsu will sell better.

Note that the configuration shown in Fig. 13 is suitable for FM broadcasting, in addition to AM broadcasting.
It can also be used for music sources such as TV broadcasts, cable broadcasts, and music tapes (in the case of music tapes, record a pilot tone of 10 Hz - 30 dB on the tape, and put an element 135 on the tape player side.
to 137).

FIG. 14 shows that using the signal synthesis device according to the present invention,
An example of the configuration of a system that transmits wideband signals via a narrowband signal transmission system 143 such as a telephone line is shown. This configuration is
This corresponds to what is described on page 25, line 8 to page 28, line 1 of the aforementioned Japanese Patent Application No. 58-45193.

First, a wideband input signal M Ex of, for example, 20 Hz to 20 kHz is converted by a 1/N pitch converter (analog frequency dividing circuit) 140 into a signal E 140 whose frequency distribution is shifted to a lower frequency range. When N is 4, signal E14
The frequency distribution of 0 will be 5-Hz to 5kHz. This converter z4o1d, for example, can be configured by removing BPF 60 and adder 65 from FIG. ). The signal E140 passes through the pre-emphasis equalizer 141f and becomes a high rising signal E141. Even if the signal E141 is 5 kHz
The signal is input to a transmission output circuit 142 that includes a low-pass filter that cuts frequencies above z. The output circuit 142 has a predetermined output impedance and a predetermined signal level.
A signal E142 of z~5kHz1 is sent to the signal transmission system 143.

The signal transmission system 143 has a long signal transmission line, for example, and cannot perform good signal transmission at high frequencies;
It is assumed that the system is capable of signal transmission at frequencies below Hz.

The output signal E143 of the transmission system 143 is input to a reception input circuit 144 having an input impedance matched to the system 143. This circuit 144 has a muting (or squelch) function that outputs a signal Fj144 corresponding to the signal E143 only when the signal E143 is higher than the noise level, for example. This signal E144 undergoes frequency compensation for falling high by a de-emphasis equalizer 145, and is converted into a signal E145 (5 Hz to 5 kHz) having a frequency distribution similar to that of the signal E140. This signal E145 is converted to 20H by an N-times bina converter (analog multiplier circuit) 146, which is the same as the signal El.
Wideband output signal E with frequency distribution from z to 20 kHz
. is converted to If N is 4, converter 146 can be configured by removing BPF 20 and adder 26 from FIG. 2 and cascading them in two stages (in this case, E25 in the first stage is (E20 is busy).

The invention is limited to the embodiments disclosed herein.

Using well-known mathematical relationships, harmonic components of any order can be synthesized from a particular component of the input signal E1 to create a broadband signal. For example, if circuit 1 in FIG. 1 is made into an f (x)=x' type function conversion circuit, a fourth harmonic component can be obtained. Also, with the configuration shown in Figure 6, 172
After obtaining the lower harmonics, if the third harmonics are created using the configuration shown in FIG. 9, the 3/2nd (1st and 5th) harmonic components can be obtained. Similarly, by appropriately combining the configurations shown in FIGS. 1 to 10, the 5th order, 6th order, 7HPF (bypass), LPF (low pass), lclt may be replaced. These BPF, HPF, and LPF may be ordinary analog filters, comb filters, or digital filters. The configuration of the mBA diagram is ROM 62 B
If you choose the contents appropriately, not only 6 but also f + x2+
It can also be used when converting other variables such as x' r exp Jc. In the inverted implementation of FIGS. 1-12, the adders 16°26, . 98.65,75,97,1
The input signal E1 input to 07 or 123 does not necessarily have to be the signal Ei itself. The analog signal corresponding to the input signal El, which has been subjected to signal processing by a filter, phase shifter, coefficient unit, function conversion circuit, delay circuit, etc., is sent to the adder to generate a composite signal EJ4. E25',
E,? 7. E64. E74°F, 96. It may be superimposed on Ei06 or Ei23. In FIG. 4, FIG. 5 or FIG. 11, the limiter circuit JIB, 23B or 91
A suitable W shifter or delay circuit may be inserted on the output side of C.

Furthermore, the present invention can also be applied to Japanese Patent Application No. 55-54012 entitled "Analog Signal Recording and Reproducing Apparatus," filed by the same applicant as the present application.

If you would like to better understand the technical content of the present application, please refer to the aforementioned Japanese Patent Application No. 58-45193 and Japanese Patent Application No. 58
You may also refer to No.-190331.

[Brief explanation of the drawing]

FIG. 1 is a block diagram showing a first embodiment of the present invention, which is a signal synthesis device that generates a high-order frequency component by synthesizing cos2ωt from an image 2ωt or an image 2ωt; FIG. In the second embodiment, sinωt&cc
A block diagram showing a signal synthesis device that generates high-order frequency components by synthesizing 5in2ωt from the product of cos2ωt and sωt; FIG.
A block diagram showing a signal synthesis device that generates a high-order frequency component by synthesizing 2ωt from the difference between A diagram illustrating a case in which the function conversion circuit that generates μs2ωt is constructed by an AGC circuit; FIG. 6 is a fourth embodiment of the present invention, in which a low-order frequency component is created by synthesizing a cluster from a cluster ωt. Block diagram showing a signal synthesizer;
FIG. 7 shows a fifth embodiment of the present invention, in which the cells ωt to si
FIG. 8A is a block diagram showing an example of the configuration of the function circuit 62 in FIG.
The square amplitude component (E2) of the signal E12 in the figure is input to the input signal Ei
IEB c is a block diagram illustrating an analog divider that converts the amplitude component (E) corresponding to the signal E62 in FIG.
A block diagram illustrating an analog multiplier that converts the 1J squared amplitude component (0) into an amplitude component (E) corresponding to the input signal Ei; FIG. 9 is a sixth embodiment of the present invention.
Block diagram showing a signal synthesis device that produces high-order frequency components by synthesizing 6 stones 3ωt from inωt; Box 1
Figure 0 shows the seventh embodiment of this invention.
A block diagram showing a signal synthesis device that generates high-order frequency components by synthesizing 3ωt; Fig. 11 shows 3 in Fig. 9
Glock diagram showing an example of the configuration of Noriguchiji 9; Fig. 12 (ri
This is an eighth embodiment of the present invention, in which high-order (secondary, third-order) and low-order (1J2nd) frequency bands are created from the input signal Ei, and a low-frequency distortion canceling signal E1 is generated from the input signal Ei.
Block diagram showing a signal synthesis device that produces 22; 13th
The figure is a block diagram illustrating a case where the signal synthesis device according to the present invention is used in a radio or television transmission/reception system;
FIG. 14 is a block diagram illustrating a system for transmitting wideband signals via a narrowband signal transmission system 143, which is an application example of the signal synthesis device according to the present invention. Ei...analog input signal; Eo...analog output signal", Ei4.E25.E37.E64.E74゜E
96, Ei06-... composite signal; 1o12o, 3
o. 60, 70, 90, 100, 120...Band pass filter; -60A, 62D...Lonous filter", 11, 33, 34, 62, 72, 91°1
01... Function conversion circuit (non-linear function circuit); 12...
・DC cut capacitor (differential circuit); J,? ,
21 , 22 , 24 , J 1 , ? 2
, 36. e 3.7s, 9s, Jos, 72
J: Phase shifter (slow phase or phase advance); x4. zs, 3
v, e4°74.92,94,96,102. of . 4. 106.122...Coefficient unit (attenuator or amplifier);
15.26. ．． 31j, 61.65.75, 97°10
7.123...Analog adder: 35,65k. 71, 9.1, 103...analog subtractor; 23
191 people, 91B...Analog multiplier: xxh. 23A, 16.61...AGC circuit (AM modulator);
J J B, 2.9 B, 91 C...Limiter circuit (constant amplitude ALC circuit); J7, 66.6817
6... Rectifier circuit: 2HF... 2nd harmonic synthesis section:
3HF...Third harmonic synthesis section; 2LF...1/
2nd order low harmonic synthesis section; 2HD...low frequency distortion cancellation section; 137
...Analog switch: 8136...Switching command.

Claims (1)

[Scope of Claims] A first circuit that generates, from an analog input signal, a composite signal having an amplitude corresponding to the amplitude □ of this input signal and having a frequency component different from a frequency component of this input signal; or a second circuit that mixes the analog signal corresponding to this input signal and the composite signal to generate an analog output signal that corresponds to the input signal and has a frequency distribution wider than that of any input signal; A signal synthesizer equipped with