JPS596157Y2 - Generator voltage generation control device - Google Patents

Description

[Detailed description of the invention] This invention is suitable for applications that require a large output in as small a size as possible, such as a portable engine generator, and can be used in countries around the world with different load drive voltages as necessary. The present invention relates to an improvement of a voltage generation control device for a generator, which has a configuration that makes it possible to do this.

For convenience of explanation, an engine generator will be described as a specific example, although the scope of the present invention is not particularly limited, and the engine generator is generally configured to drive a load at 50 Hz or 60 Hz.

By the way, in an engine generator, in order to realize a large output, it is possible to increase the rotational speed of the engine and/or increase the number of field windings, as is well known.

However, there is a limit to the increase in the number of field windings, and therefore it can be safely assumed that the magnitude of the output depends on the engine rotation speed.

However, the output frequency of the generator itself is determined by the engine rotation speed. For example, in the case of a two-pole generator directly connected to the engine, the engine rotation speed to drive the load at 50 Hz is 3000 r. p. m, 3600 r.m to drive at 60 Hz. It must be set to p and m.

Therefore, for example, in a portable engine generator that is required to be as small as possible and have a large output, the engine rotation speed may be set to 5, for example.
000 r. p. m or 6000 r. p,m
A structure in which the rectified output is converted to the desired 50 or 60 output using an inverter circuit is being considered.

Such an engine generator is provided with a constant voltage control section in order to make the voltage supplied to the normal load as constant as possible.

Therefore, in conventional engine generators that are equipped with such a constant voltage control section and are equipped with a multi-voltage switching device to enable use in various countries around the world if necessary, the constant voltage control The multi-voltage switching device and the multi-voltage switching device are constructed independently from each other.

For this reason, not only is the structure relatively complex and varied, but it also has the disadvantage of increasing costs.

The present invention was developed based on the above circumstances, and it is possible to closely connect a constant voltage control section for supplying voltage to a load and a multi-voltage switching device section provided as necessary to enable simultaneous control, and to achieve a It is an object of the present invention to provide a voltage generation control device for a generator that is as simple and inexpensive as possible.

An embodiment of the device of the present invention will be described in detail below with reference to the accompanying drawings.

FIG. 1 is a schematic circuit diagram of one embodiment of the present invention. For example, as mentioned above, the engine rotational speed is set to 500 O r. p. m or 600
0 r. p. The AC output terminal of a generator main body G consisting of a portable engine generator set to m is connected between a pair of input terminals of a first bridge rectifier circuit 1 configured using four diodes.

A smoothing capacitor C1 and a bridge type silis inverter circuit 2 having the structure described below are connected in parallel between the pair of output terminals of the rectifier circuit 1.

That is, this inverter circuit 2 has a structure in which two sets of the same circuits are connected in parallel between the pair of output terminals of the rectifier circuit 1, and each set of circuits is connected to two power supply voltages 2. Equal dividing series capacitors C2-C3 (C4-C5) and two series feedback diodes D5-D6 each with the polarity shown.
(D 7-D 8) and one each commutation reactor Ll (
L2) consists of a parallel circuit of two switching elements, in this example thyristors Sl-82 (S3-S4), each with a forward-connected main current path provided at both ends of L2).

And connect the connection point of each set of power supply voltage dividing capacitor and feedback diode to each corresponding commutating reactor? In addition to connecting to the tap terminal between these two commutation reactors L
It has a structure in which a parallel circuit of a load L and a commutating capacitor C6 is connected between intermediate tap terminals of L and L2.

On the other hand, each thyristor S included in the inverter circuit 2
1 to S4 gate electrodes G1 to G4 at the above 50 Hz or 6
An unstable multi-vibrator circuit 3 having the following structure is provided as a trigger control source for performing alternate trigger control at a desired cycle such as zero rejection.

That is, this multivibrator circuit 3 is similar to the rectifier circuit 1 described above.
Two series resistors Rl and R2 connected between the pair of output terminals of
The non-grounded cathode side terminal of the voltage regulator diode D2 is operated using a constant voltage power source obtained by further connecting a smoothing capacitor C7 and a voltage regulator diode D2 in parallel between both resistance connection points and the ground point of the voltage divider circuit consisting of the voltage divider circuit. A pair of npn type emitter-grounded transistors Q, each collector of which is connected via a series circuit of a resistor R3 (R4) (in the center of the figure) and a forward-connected diode D9 (DIO), respectively.
1, including Q2.

The bases of these transistors Q1 and Q2 are connected to the other transistor Q2 via coupling capacitors C8 and C9, respectively.
, Ql and the respective base resistors Rh.
, Rb to the non-grounded positive terminal of the first operating power source.

Further, in order to appropriately increase the oscillation output voltage level from the transistors Ql and Q2 as necessary, for example, a capacitor C10 (C11) and a resistor R5 (R6) are connected to the collectors of the transistors Ql and Q2, respectively, as shown in the figure. A pair of npn-type common emitter transistors Q3 and Q4 are provided whose respective bases are connected through a parallel circuit of a series circuit of ) and a resistor R7 (R8).

Further, collector output windings Tp and Tp2 are respectively connected between the collectors of these transistors Q3 and Q4 and the non-grounded positive terminal of the first operating power supply, and two electromagnetically coupled secondary windings T8,
T84 (T53, T52) is provided.

and each diode D11 from these secondary windings,
The rectified pulse voltage obtained through D14 (D13, D12) is applied as a trigger pulse to the gate electrodes 61 to G4 of each thyristor S1 to S4 included in the inverter circuit 2 in the combination shown in the figure. Connect to apply.

As is well known, the diodes D15 and D16 connected in opposite directions to the collector output windings Tp1 and Tp2 are necessary for the purpose of suppressing the automatic sustained excitation phenomenon immediately after the corresponding transistors Q3 and Q4 are turned off. It will be added accordingly.

The precepts up to this point have been conventionally known. Therefore, in the present invention, in the generator circuit having the above-mentioned structure, the phenomenon of supply voltage fluctuation to the load L due to fluctuations in the AC output level from the generator body G as described below is continuously and automatically controlled. It is characterized by a constant voltage control unit that acts to suppress the voltage, and if necessary, for example, a multi-voltage switching device that can drive the load with several voltages for the purpose of common use in countries around the world is added. It is characterized by being configured as follows.

That is, first, a control rectifier circuit using the output voltage to be applied to the load L and using it as an input, for example, four diodes D.
17 to D20 is provided, and both resistance connection points of a voltage divider circuit consisting of two series resistors R 9 and R 10 connected between the pair of output terminals of this rectifier circuit 4 are provided. A voltage DC power source 5 is provided with a smoothing capacitor C12 connected between the ground points.

Then, to the non-grounded positive terminal of this DC power supply 5, that is, the connection point of the voltage dividing resistor, is connected to the desired type of load drive voltage (for example, in major countries of the world As shown in Figure 2, 240 V, 220 V, 115 V and 1
In this example, two interlocking type changeover switches Wl and W2 each having four fixed contacts are used. Connect the movable contacts.

Each of the fixed contacts of these changeover switches Wl and W2 is provided with four resistors R11 and R12 having mutually different resistance values determined by the generator load voltage value to be driven, as will be described in more detail later. , R 13, R14 (R 21
, R22, R23, R24) are individually connected, and the other ends of the four commonly connected resistors are grounded via capacitors C13 and (C14), respectively.

As will be clear from what will be described later, four resistors R11 to R14 each have one end individually connected to each of the changeover switches Wl and W2 and their respective fixed contacts, and the other ends commonly connected.
, R21 to R24 act as a multi-voltage switching device 6,7.

Also, one of the four ? Selective switching resistors R11 to R14 (R21 to
The parallel circuit portion of the two series-connected circuits constituted by R24) and each corresponding capacitor C13 (C14) connects the integrating circuits 8 and 9.

That is, as will be described later, a type of constant voltage control section according to the present invention acts as a constant voltage control section for constantly and automatically suppressing and controlling fluctuations in the voltage level supplied to the load L due to fluctuations in the AC output level from the generator main body G, etc. Integrating circuit 8 which is a delay circuit of
, 9.

Thus, the connection points of the respective resistors and capacitors of these integrating circuits 8 and 9 are connected to diodes D22 (D23) of the polarities shown, respectively.
A switching element, for example, an anode-cathode path of a programmable unijunction transistor PUT 1 (PUT 2) and a trigger transformer. It is grounded through a series circuit of the primary winding T1p (T2p) of TI (T2).

Note that the diode D22 (D23) corresponds to the synchronization circuit according to the present invention.

On the other hand, the trigger electrode of each of the switching elements PUT1 (PUT2) is connected to two series resistors R13-R14 (R
15-R16) via forward connection diodes D24 (D25), respectively.

Therefore, each trigger trunk-next winding T1p (T2p)
Each trigger transformer secondary winding T8 is electromagnetically coupled to
Each diode D 26 (D 27) from ('r2s)
As shown in the figure, the rectified pulse voltage obtained through
The configuration is such that it is applied as a trigger pulse as described later to the gate electrode Gl (G3) of the thyristor Sl (S3) in the inverter circuit 2.

Next, the operation of the circuit configured as described above will be explained in detail with reference to FIGS. 3a to 3k.

First, if the multi-voltage switching device sections 6, 7 and the constant voltage control sections 8, 9 consisting of integral circuits are not provided, the transistors in the multivibrator circuit 3 will be easily understood by those skilled in the art. Q3 (Q4) is each coupling capacitor C8 (C
9) A square wave oscillation output as shown in Fig. 3 a, l) is generated every predetermined period through an intermittent on/off operation controlled by a time constant determined by the product of the capacitance value and the base resistance R5, (Rbz) resistance value. occur alternately.

Each secondary winding Tsl, T coupled to the collector output winding Tp1 at the rise of each on-period of the transistor Q3.
A trigger pulse as shown in FIG. 3C consisting of the rectified output from s4 is applied to the gate electrodes Gl and G4 of the corresponding thyristors SL and S4 in the inverter circuit 2, and the thyristors SL and S4 are simultaneously turned off. and is set to the energized state.

As a result, the first load current iL1 flows through the load L in the direction shown by the solid arrow in the figure.

Similarly, at the rise of each on-period of transistor Q4, each secondary winding T coupled to collector output winding Tp2
A trigger pulse as shown in FIG. 3d consisting of the rectified outputs from sa and TS2 is applied to the gate electrodes G3 and G2 of each corresponding thyristor S3 and S2 in the inverter circuit 2, and the respective thyristors S3 and S2 are activated at the same time. At the same time, the thyristors Sl and S4 are simultaneously reverse biased and forcibly turned off by the back electromotive force induced in the upper half of each commutation reactor L1 and the lower half of L2. Set to de-energized state.

As a result, a second load current iL2 flows through the load L in the direction of the dashed arrow shown in the figure, that is, in the opposite direction to the first load current iL1.

Thereafter, by repeating the same operation alternately, a drive voltage having a waveform as shown by the solid line in FIG. 3E is applied to the load L.

This part has been conventionally known, and for the generator circuit that operates as described above, it is necessary to further stabilize the voltage supplied to the load L due to fluctuations in the AC output level from the generator main body G, etc. When adding a constant voltage control section and a multi-voltage switching device section for selectively driving loads with different drive voltages, conventionally the constant voltage control section and the multi-voltage switching device section were mutually connected. Because they were constructed independently, they had the disadvantage that they were relatively complex and diverse, and were prone to high costs.

On the other hand, the operation when using constant voltage control sections 8 and 9 constituted by multi-voltage switching device sections 6 and 7 and an integrating circuit functioning as a type of delay circuit will be described in detail below.

That is, when using the illustrated device, with the load to be driven connected to a predetermined connection terminal, each interlocking changeover switch Wl, W2 in the multi-voltage changeover devices 6, 7 is set according to the drive voltage of the load. All you have to do is switch.

FIG. 2 shows the structure of the panel surface of the adapter 10 according to the present invention, which is constructed for this purpose, and shows the switching operation of the interlocking type changeover switches Wl and W2 in the multi-voltage switching devices 6 and 7. A switching operation camera 11 for performing the switching operation and a plug terminal 12 for connecting an arbitrary load to be driven, such as a connector jack, are provided.

Thus, for example, as shown in FIG.
If a load of 110 V is to be selected and driven, the load is connected to the plug terminal 12 and the switching operation camera 11 is switched to the display position of 110V to drive the multi-voltage. The contact connection positions of the interlocking type changeover switches Wl and W2 in the changeover devices 6 and 7 are set to resistors R11 (R21) having the minimum resistance value among the four resistors R11 to R14 (R21 to R24), for example. You just have to adjust it to your location.

In this way, each of the integrating circuits 8 and 9 constituting the constant voltage control section has the selection switching resistance R 11 (R 2
1) and an integrating capacitor C13 (C14), each integrating circuit 8,
The charging voltage level of the integrating capacitor C13 (C14) in the multivibrator circuit 3 is the same as that of each diode D2 during the energization period of each corresponding transistor Ql (Q2) in the multivibrator circuit 3.
2 (D23) is in a forward bias state, it is set to approximately zero level, and therefore each corresponding trigger transformer TI (T
2) is not energized at all.

The charging voltage level of each integrating capacitor C 13 (C 14) is set such that each corresponding transistor Ql (Q2) in the multivibrator circuit 3 is set to a non-energized state, and each other side transistor Q2 (Ql) is set to a energized state. It starts from the moment when the voltage rises and gradually rises as time passes, and is determined by the time constant determined by the product of the resistance value of each corresponding integrating resistor R 11 (R 21) and the capacitance value of the integrating capacitor C 13 (C 14). After a predetermined time, the predetermined charging voltage level is reached and each corresponding switching element PUT1 (
PUT2) is triggered to turn on, thereby setting each corresponding trigger transformer TI(T2) to the energized state.

Therefore, if the integration time constants of the respective integration circuits 8 and 9 are appropriately selected in advance, for example, during the period when the thyristors S1 and S4 in the inverter circuit 2 are set to the energized state, as shown in FIG. t at the start of each energization.

That is, starting from the moment when the other side thyristors S3 and S2 are set from the energized state to the de-energized state, the trigger transformer is activated every time an appropriate time Δt elapses before these thyristors S3 and S2 are set to the energized state again. T2 can be biased as described above.

By doing this, the thyristor S3 can be triggered and turned every time the time Δt elapses after the start of each energization during the energization period of the thyristors S1 and S4, and the thyristor S3 can be turned. As is well known, when the commutation reactor L2 is turned on, voltages of the same level and opposite polarity are induced in the upper and lower halves of the commutation reactor L2, and the anode and cathode of the thyristor S4 become reverse biased, thereby causing the thyristor S4 to It is forcibly turned off together with the thyristor S1, and the supply path of the first load current iL1 to the load L is forcibly cut off (see FIG. 3g).

On the other hand, even when the thyristors S3 and S2 in the inverter circuit 2 are energized, the trigger transformer T1 performs the same operation as the trigger transformer T2 through the corresponding integrating circuit 8 and switching element PUT1, and the thyristor S
3 and S2 at the start of each energization during the energization period t.

Starting from , every time the above time △t elapses, the thyristor S
1 is triggered, thereby forcing thyristors S3 and 82 to turn off.

That is, the second load current iL2 is forcibly cut off.

In the above, as mentioned above, the interlocking type changeover switch Wl,
Assuming that the resistors Rll and R21 are selected by W2, even if the terminal voltage of the load L increases or decreases from 100 mm, the terminal voltage is controlled to be maintained at <100 mm.

That is, if the terminal voltage increases from 100V, the integration capacitor C 13 (C 14
) increases the charging current.

Therefore, the above-mentioned time Δt becomes small, the energization time of the load current iL2 (iL1) supplied to the load L is controlled to be reduced, and the terminal voltage of the load L is controlled to be decreased and maintained at 100V.

Conversely, when the terminal voltage of load L decreases, the above-mentioned time Δt becomes large, and the terminal voltage of load L is similarly increased to 100
controlled to maintain

Resistor R 1 is set by the interlocking type changeover switches Wl and W2.
2 (R22) is selected, the resistance R12 (R2
2) is selected, the above integral condenser C13 (C
14) The charging current supplied to
is increased, and the terminal voltage of the load L is switched to 115V, as is clear from a comparison of FIG. 3h and i.

In this state, even if the load voltage increases or decreases from 115■,
As in the case of 100 V described above, control is performed to maintain the voltage at 115 V correctly.

Other resistors R1
Similarly, when 3 (R 23) and R14 (R 24) are selected, the terminal voltage of load L is 220 V and 240 V, respectively.
After selecting V, voltage control is performed correctly.

As is clear from the detailed description above, the present invention is particularly useful for generators that aim to increase the engine speed and increase the output as much as possible by adding the inverter circuit 2 as described above. Therefore, it becomes possible to suppress and control fluctuations in the voltage level supplied to the load by directly using the control for the inverter.

[Brief explanation of drawings]

Figure 1 is a schematic circuit diagram showing an embodiment of the device of the present invention, Figure 2 is a schematic front view of the adapter panel of the device of the present invention, and Figures 3a to 3k are the same as those in Figure 1 above. FIG. 3 is a specific operation timing chart of main circuit parts. G... Generator main body, L... Load, 2.
...Inverter circuit, S1 to S4, PUT 1
, PUT 2... Switching element, 6, 7.
...Multi-voltage switching device, 8, 9...Delay (
integral) circuit.

Claims (1)

[Scope of utility model registration request] A power generation system that includes a generator and converts the DC voltage obtained by the generator into an alternating voltage using an inverter circuit that includes at least two switching elements that are alternately controlled on and off, and supplies the alternating voltage to a load. a self-running multivibrator circuit that generates a turn-on trigger signal to be supplied to the two switching elements; a selected one of the plurality of voltage levels to be supplied to the load; In response to this, an integrator circuit that generates a delay time and is reset when the delay time elapses, and at the timing when the integrator circuit is reset, a turn is applied to the switching element on the on-state among the switching elements.・In addition to providing a turn-off trigger signal control circuit that controls the turn-off trigger signal, the self-propelled multivibrator prohibits the integration operation by the integration circuit until the next switching of the self-propelled multivibrator. A voltage generation control device for a generator, characterized in that a synchronization circuit that starts the integration operation when switched is connected between the multivibrator and the integration circuit.