JPS59196629A - Fm receiver - Google Patents
Fm receiverInfo
- Publication number
- JPS59196629A JPS59196629A JP7048383A JP7048383A JPS59196629A JP S59196629 A JPS59196629 A JP S59196629A JP 7048383 A JP7048383 A JP 7048383A JP 7048383 A JP7048383 A JP 7048383A JP S59196629 A JPS59196629 A JP S59196629A
- Authority
- JP
- Japan
- Prior art keywords
- frequency
- output
- circuit
- input
- local oscillator
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D3/00—Demodulation of angle-, frequency- or phase- modulated oscillations
- H03D3/007—Demodulation of angle-, frequency- or phase- modulated oscillations by converting the oscillations into two quadrature related signals
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Superheterodyne Receivers (AREA)
Abstract
Description
【発明の詳細な説明】
本発明はFM受信機に係り、特にダイレクトコンバージ
ョン方式を用いた受信機の改良に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an FM receiver, and particularly to an improvement of a receiver using a direct conversion method.
受信変調波を、その中心周波数にほぼ等しい周波数を有
する局部発振器の出力から得られる信号を局部発振信号
として、直交検波するダイレクトコンバージョン方式は
、直接ベースバンド帯へ変換するだめに、中間周波数を
使用するヘテロダイン方式と比べて、帯域通過フィルタ
を必要とせず低域通過フィルタを使用できること、イメ
ージ応答の問題がないこと、局部発振周波数を変化する
のみで容易にチャンネルを広帯域にわたって選択できる
ことなどの利点を有している。ダイレクトコンバージョ
ン方式を用いた周波数検波器は例えは、英国特許、15
30602 「Demodulator for FM
signa!s Jに示されているような方式が知られ
ている。この方式は、上述した利点を備えてはいるもの
の、乗算器およびダイナミックレンジの広い自動利得制
御回路を必要とするために実現が困難となる問題がある
。The direct conversion method uses a received modulated wave as a local oscillation signal, which is a signal obtained from the output of a local oscillator with a frequency approximately equal to the center frequency, and performs orthogonal detection.In order to directly convert the received modulated wave to the baseband, an intermediate frequency is used. Compared to the heterodyne method, it has the following advantages: it can use a low-pass filter without requiring a band-pass filter, there is no image response problem, and channels can be easily selected over a wide band simply by changing the local oscillation frequency. have. For example, a frequency detector using the direct conversion method is described in the British patent, 15
30602 “Demodulator for FM
Signa! A method such as that shown in s J is known. Although this method has the above-mentioned advantages, it requires a multiplier and an automatic gain control circuit with a wide dynamic range, making it difficult to implement.
本発明の目的は、回路実現が容易な、ダイレクトコンバ
ージョン方式FM受信機を提供することにある。An object of the present invention is to provide a direct conversion type FM receiver whose circuit is easy to realize.
本発明によれば、周波数変調波の中心周波数にほぼ等し
い周波数を有する第1の局部発振器の出力を局部発振信
号とする直交検波器と、該直交検波器の二つの出力をそ
れぞれ入力する第1および第2の低域通過フィルタと、
第2の局部発振器と、該第2の局部発振器の出力を90
°の位相差を与えて二つに分岐する位相差分離回路と、
該位相差分離回路の一方の出力を局部発振信号として、
前記ルタの出力を周波数変換する第2の周波数変換器と
、前記第1および第2の周波数変換器の出力を加算また
は減算する回路と、該加算咬だは減算回路の出力を入力
とする振幅制限回路と、該振幅制限回路の出力を入力と
する周波数検波器とを有し、該周波数検波器の出力から
得られる信号を受信信号とすることKよって上記目的を
達成できる。According to the present invention, there is provided a quadrature detector whose local oscillation signal is the output of a first local oscillator having a frequency substantially equal to the center frequency of a frequency modulated wave; and a second low pass filter;
a second local oscillator; the output of the second local oscillator is 90 Hz;
a phase difference separation circuit that branches into two with a phase difference of °;
One output of the phase difference separation circuit is used as a local oscillation signal,
a second frequency converter that converts the frequency of the output of the frequency converter; a circuit that adds or subtracts the outputs of the first and second frequency converters; and an amplitude that receives the output of the addition or subtraction circuit as input. The above object can be achieved by having a limiting circuit and a frequency detector which receives the output of the amplitude limiting circuit as an input, and by using the signal obtained from the output of the frequency detector as the received signal.
以下図面を用いて詳しい説明を行う。本発明の実施例を
第1図に示す。受信入力端子lに入力されたFM変調波
は、二分岐されそれぞれミクサ21゜22に入力される
。このFM変調波は一般的に次のように表わすことがで
きる。A detailed explanation will be given below using the drawings. An embodiment of the invention is shown in FIG. The FM modulated wave input to the reception input terminal l is split into two and input to mixers 21 and 22, respectively. This FM modulated wave can generally be expressed as follows.
V’r(t ) = A cos (ωct 十P(t
) :] (1)ここで、Aは振幅、ωGは変調
波の中心角周波数、ここで、ωmは変調度を示す定数、
8(t)は送信信号である。局部発振器31は、その発
振周波数を受信FM変調波の中心周波数にほぼ等しく選
ばれる。V'r(t) = A cos (ωct 0P(t
) :] (1) Here, A is the amplitude, ωG is the central angular frequency of the modulated wave, here, ωm is a constant indicating the modulation degree,
8(t) is a transmission signal. The local oscillator 31 has an oscillation frequency selected to be approximately equal to the center frequency of the received FM modulated wave.
この出力は二分岐され、一方を90°移相器41に入力
することによシ、位相が90°異たる二つの局部発振信
号が得られる。受信信号は、これらの信号を局部発振信
号としてミクサ21,22によシ周波数変換された後、
イ彰域通過フィルタ57.52に入力される。この低域
通過フィルタは雑音および周波数の異なる妨害波を除去
するだめのものである。低域通過フィルタの51.52
出力の二つのベースバンド信号はそれぞれ次のように表
わされる。This output is branched into two, and by inputting one to a 90° phase shifter 41, two local oscillation signals having phases different by 90° are obtained. The received signals are frequency-converted by mixers 21 and 22 using these signals as local oscillation signals, and then
The signal is input to a bandpass filter 57.52. This low-pass filter is used to remove noise and interference waves of different frequencies. 51.52 of low pass filter
The two output baseband signals are respectively expressed as follows.
V、 (t) = B cos (P(t)+ΔQ(f
) ) (3)V2 (t) = B sin
(P(t)十ΔQ(t)l (4)ここで、
Bは人に比例する定数、ΔQ(t)は変調波の中心周波
数と局部発振周波数とがわずかに異なっていることによ
シゆっくシと変化する位相項である。V, (t) = B cos (P(t)+ΔQ(f
) ) (3) V2 (t) = B sin
(P(t)+ΔQ(t)l (4) Here,
B is a constant proportional to the person, and ΔQ(t) is a phase term that changes slowly due to the slight difference between the center frequency of the modulated wave and the local oscillation frequency.
二つのベースバンド信号■+ (t) l V2 (t
)は、角周波数の1の局部発振器32の出力を二分して
、一方を90°移相器に通して得られる信号を局部発振
信号として、ミクサ23,24によシ、周波数変換され
る。得られる信号vs (i) y V4 (t)はそ
れぞれ次のように表わされる、2
Vs (t) = E c o s (P(t)+ΔQ
(t))cos(ω、を十〇i)=委B cos (ω
it 十P(t)+ΔQCt)+θI)+ iB co
s (ωHt −P(t)−ΔQ(t)+θ;1(51
V4(t) = B s in (P(t)+ΔQ(t
))sin(ωit+θi)= ABcos(ω1t
+ P(t)+ΔQ(t)+θ1)(6)
ここで、θiは位相定数である。Two baseband signals + (t) l V2 (t
) divides the output of the local oscillator 32 with an angular frequency of 1 into two, passes one half through a 90° phase shifter, and uses the obtained signal as a local oscillation signal, which is frequency-converted by the mixers 23 and 24. The resulting signals vs (i) y V4 (t) are respectively expressed as follows, 2 Vs (t) = E cos (P(t) + ΔQ
(t)) cos (ω, 10i) = Committee B cos (ω
it 10P(t)+ΔQCt)+θI)+iB co
s (ωHt −P(t)−ΔQ(t)+θ;1(51
V4(t) = B s in (P(t)+ΔQ(t
)) sin(ωit+θi)=ABcos(ω1t
+P(t)+ΔQ(t)+θ1) (6) Here, θi is a phase constant.
これらの信号を減算回路6に入力することにより、その
出力信号■5 (t)は次のようになる。By inputting these signals to the subtraction circuit 6, its output signal 5(t) becomes as follows.
v、 (t) = VB<t)−・V4 (t)=B
cos (’ 7 t + P (t)十ΔQ、(t)
+0口 (7)この信号は、中心角周波数ωlの周波数
変調波であるから、これを振幅制限器7に通したのち、
周波数弁別器8に入力することによって、出力端子9に
受信信号
V a(t) −A。−(P(t)+ΔQ(t)+θ1
)i
= Ao (5(t) + Q(t) l
(8)t
が得られる。ここで、Aoは定数、−Q、(t)は受信
t
変調波の中心周波数と局部発掘器31の発振周波数との
差であシ、これは小さく選ばれるので、無視できる し
だがって受信出力は送信信号5(t)となる。v, (t) = VB<t)-・V4 (t)=B
cos (' 7 t + P (t) + ΔQ, (t)
+0 mouth (7) Since this signal is a frequency modulated wave with a center angular frequency ωl, after passing it through the amplitude limiter 7,
By inputting it to the frequency discriminator 8, the received signal V a(t) -A is output at the output terminal 9. −(P(t)+ΔQ(t)+θ1
)i = Ao (5(t) + Q(t) l
(8) t is obtained. Here, Ao is a constant, -Q, and (t) is the difference between the center frequency of the received t modulated wave and the oscillation frequency of the local excavator 31, which is chosen small and can be ignored. The output becomes the transmission signal 5(t).
本発明では、従来のダイレクトコンバージョン方式にお
いて必要であった微分器および乗算器が不要となる。一
般に乗算器の実現は困難であるから、この効果は大きい
。また、同じ〈従来、必要とされた自動利得制御回路の
代わシに、より実現が容易である、中間周波数帯におけ
る振幅制限器が使用できる。The present invention eliminates the need for a differentiator and a multiplier that were necessary in the conventional direct conversion method. This effect is significant because multipliers are generally difficult to implement. Also, instead of the same conventionally required automatic gain control circuit, an amplitude limiter in the intermediate frequency band, which is easier to implement, can be used.
本発明においては、中間周波数をイ吏用するけれども、
同じく中間周波数を使用する従来のヘテロダイン方式と
は、壕ず、イメージ周波数応答の問題が無いことが異な
る。すなわち、従来のヘテロゲイン方式においては、本
来の入力信号の他に局部発振周波数から、中間周波数だ
け反対側に離れた周波数であるイメージ周波数に対する
応答があシ、これを避けるために、周波数変換を測度も
行ったり、中間周波数の設定に制約を課したシする必要
があった。これと同時に受信変調波の中心周波数の変化
範囲が制約されていた。本発明では、中間周波数は一度
だけ使用すればよく、またその周波数の設定は、使用す
る周波数弁別器に適してた任意の周波数に選ぶことがで
きる。後者の特長は、例えば、パルスカウント型周波数
弁別器などのように、中間周波数を下げるほど検波感度
が上がる場合に効果がある。また、受信変調波の中IB
周波数が大きく変化しても、局部発振器31の発振周波
数を変化させるのみで、簡単に対応できるので、多数の
チャンネルを有する広帯域受信機を容易に実現できる。Although the present invention uses an intermediate frequency,
This differs from the conventional heterodyne method, which also uses an intermediate frequency, in that there is no trench or image frequency response problem. In other words, in the conventional hetero gain method, in addition to the original input signal, there is a response to the image frequency, which is a frequency separated from the local oscillation frequency by an intermediate frequency on the opposite side.To avoid this, frequency conversion is It was also necessary to set restrictions on the intermediate frequency settings. At the same time, the variation range of the center frequency of the received modulated wave is restricted. In the present invention, the intermediate frequency need only be used once, and its frequency setting can be chosen to be any frequency suitable for the frequency discriminator used. The latter feature is effective when the detection sensitivity increases as the intermediate frequency is lowered, such as in a pulse count type frequency discriminator. Also, in the received modulated wave, IB
Even if the frequency changes greatly, it can be easily handled by simply changing the oscillation frequency of the local oscillator 31, so a wideband receiver having a large number of channels can be easily realized.
本発明のさらに別の効果として、チャンネル選択フィル
タとして、低域通過フィルタを使用できるので、中間周
波数帯における帯域通過フィルタが不要になる。このこ
とは、変調波の帯域が狭くなった場合に、帯域通過フィ
ルりの実現が困難であるから、特に有効である。以上説
明したように、本発明は、ダイレクトコンノぐ−ジョン
方式FM受信機とヘテロゲイン方式FM受信機の両者の
利点のみを有するという効果がある。Another advantage of the present invention is that a low pass filter can be used as the channel selection filter, eliminating the need for a band pass filter in the intermediate frequency band. This is particularly effective since it is difficult to achieve bandpass filtering when the band of the modulated wave becomes narrow. As explained above, the present invention has the advantage of having only the advantages of both the direct connection type FM receiver and the hetero gain type FM receiver.
本発明の実施例では、直交検波を行う方法として、局部
発振信号の位相を90°異ならせたけれども、この代わ
シに、入力変調波の位相を90’だけ異々らせてもよい
ことは、よく知られていることである。また減算回路6
の代わ9に加算回路を用いても、検波出力の極性が変化
するのみで、同じように効果がある。In the embodiment of the present invention, as a method of performing quadrature detection, the phases of the local oscillation signals are made to differ by 90 degrees, but it is also possible to make the phases of the input modulated waves differ by 90 degrees instead of this. , is well known. Also, the subtraction circuit 6
Even if an adder circuit is used instead of 9, the same effect can be obtained, only the polarity of the detected output changes.
第1図は本発明の実施例を示すブロック図である。これ
らの図において、1は入力端子、21゜22.23.’
24はミクサ、31.32は局部発振器、41,42は
90°移相器、51,52は低域通過フィルタ、6は減
算回路、7は振幅制限回路、8は周波数弁別器、9は出
力端子である。
第1図
′ 姶
IFIG. 1 is a block diagram showing an embodiment of the present invention. In these figures, 1 is an input terminal, 21°22.23. '
24 is a mixer, 31 and 32 are local oscillators, 41 and 42 are 90° phase shifters, 51 and 52 are low-pass filters, 6 is a subtraction circuit, 7 is an amplitude limiting circuit, 8 is a frequency discriminator, and 9 is an output It is a terminal. Figure 1' 姶I
Claims (1)
波数にほぼ等しい周波数を有する第1の局部発振器の出
力を局部発振信号とする直交検波器と、該直交検波器の
二つの出力をそれぞれ入力とする第1および第2の低域
通過フィルタと、第2の局部発振器と、該第2の局部発
振器の出力を90°の位相差を与えて二つに分岐する位
相差分離回路と、該位相差分離回路の分岐された一方の
出力を局部発振信号として、前記第1の低域通過フィル
タの出力を周波数変換する第1の周波数変換器と、前記
位相差分離回路の分岐された他方の出力を局部発振信号
として前記第2の低域通過フィルタの出力を周波数変換
する第2の周波数変換器と、前記第1および第2の周波
数変換器の出力を加算または減算する回路と、該加算ま
たは減算回路の出力を入力とする振幅制限回路と、該振
幅制限回路の出力を入力とする周波数検波器とを有し、
該周波数検波器の出力から得られる信号を受鋼出力とす
ることを特徴とするFM受信機。A quadrature detector whose input signal is a frequency modulated wave and whose local oscillation signal is the output of a first local oscillator having a frequency approximately equal to the center frequency of the frequency modulated wave, and two outputs of the quadrature detector are respectively input. first and second low-pass filters, a second local oscillator, a phase difference separation circuit that branches the output of the second local oscillator into two with a 90° phase difference; a first frequency converter that converts the output of the first low-pass filter into a frequency by using one branched output of the phase difference separation circuit as a local oscillation signal; a second frequency converter that frequency converts the output of the second low-pass filter using the output as a local oscillation signal; a circuit that adds or subtracts the outputs of the first and second frequency converters; or has an amplitude limiting circuit that receives the output of the subtraction circuit as input, and a frequency detector that receives the output of the amplitude limiting circuit as input;
An FM receiver characterized in that a signal obtained from the output of the frequency detector is used as a receiving output.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7048383A JPS59196629A (en) | 1983-04-21 | 1983-04-21 | Fm receiver |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7048383A JPS59196629A (en) | 1983-04-21 | 1983-04-21 | Fm receiver |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS59196629A true JPS59196629A (en) | 1984-11-08 |
JPH0463574B2 JPH0463574B2 (en) | 1992-10-12 |
Family
ID=13432808
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP7048383A Granted JPS59196629A (en) | 1983-04-21 | 1983-04-21 | Fm receiver |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS59196629A (en) |
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS6337741A (en) * | 1986-07-28 | 1988-02-18 | テクトロニックス・インコ−ポレイテッド | Digital heterodyne circuit |
JPS63232507A (en) * | 1987-03-19 | 1988-09-28 | Fujitsu Ltd | Radio receiving system |
JPH0738455A (en) * | 1993-07-20 | 1995-02-07 | Matsushita Electric Ind Co Ltd | Radio receiver |
US6046628A (en) * | 1997-06-24 | 2000-04-04 | Nec Corporation | Demodulating device comprising a small circuit and a small consumption power |
US6334051B1 (en) | 1998-03-04 | 2001-12-25 | Kabushiki Kaisha Toshiba | Direct conversion receiver with wide band analog frequency conversion front end and digital demodulating and selecting back end |
-
1983
- 1983-04-21 JP JP7048383A patent/JPS59196629A/en active Granted
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS6337741A (en) * | 1986-07-28 | 1988-02-18 | テクトロニックス・インコ−ポレイテッド | Digital heterodyne circuit |
JPS63232507A (en) * | 1987-03-19 | 1988-09-28 | Fujitsu Ltd | Radio receiving system |
JPH0738455A (en) * | 1993-07-20 | 1995-02-07 | Matsushita Electric Ind Co Ltd | Radio receiver |
US6046628A (en) * | 1997-06-24 | 2000-04-04 | Nec Corporation | Demodulating device comprising a small circuit and a small consumption power |
US6334051B1 (en) | 1998-03-04 | 2001-12-25 | Kabushiki Kaisha Toshiba | Direct conversion receiver with wide band analog frequency conversion front end and digital demodulating and selecting back end |
Also Published As
Publication number | Publication date |
---|---|
JPH0463574B2 (en) | 1992-10-12 |
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