JPS5893482A - Drive circuit for 2-phase sinusoidal drive brushless motor - Google Patents

Abstract

PURPOSE:To obtain an accurate rotating speed control by respectively supplying 2-phase stator coil driving voltages through a low pass filter to two square calculating means, and controlling the Hall element driving current based on the addition signal outputs of both calculating means. CONSTITUTION:Stator coils L1, L2 respectively receive energization control by power amplifiers 23, 24 which input 2-phase AC signals of pi/2 phase difference from Hall elements H1, H2 through operational amplifiers 21, 22. The output voltages of the amplifires 23, 24 are respectively inputted through low pass filters 26, 27 which are composed of a resistor R6 and condensers C to square calculating units 28, 29, and are added via a resistor R7. Then, the added output e0 becomes a DC voltage which does not include a ripple component. The superposed voltage of the output voltage e0 and a DC power source E is supplied to an operational amplifier 20. Since the peak value of the AC voltage supplied to the units 28, 29 becomes large at the low speed time, the output of the amplifier 20 is increased, and the drive current of the Hall elements is increased. The operation becomes reverse to the above operation as compared with the reference speed at the high speed time.

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention is based on the outputs of Hall elements of 1 and 2 which are arranged at positions different from each other by 5 odd IIILWK in electrical angle. The present invention relates to a drive circuit of a two-root string linear drive brushless motor that supplies proportional sinusoidal drive voltages to these two-phase stator coils.

The VA rotation speed side control method of brushless motor is PLL.
There is a phase-frequency control system called (phase-locked loop) servo. Figure a11 shows the phase-frequency control method (servo system > OS configuration) in a conventional brushless motor drive circuit, and this servo system is
Aircraft generator (1) Single frequency voltage-voltage (y-v) converter (2)
and a frequency error detection means consisting of a low-pass filter (3) and a frequency tIL#! 11 aircraft (1) from L, standard departure fIA-
(4), a phase comparator φ) and a low-pass filter (a position 41i consisting of -), respectively.

Therefore, the frequency aM corresponding to the rotational speed of the rotor of the brushless motor (7) is determined from the frequency oscillation habit (1) by m*a-
It is supplied to the voltage converter (2) and converted into a voltage signal,
The rich voltage signal is summed from this converter (2) through a low-pass filter (3) 16.
(8). On the other hand, the frequency is actually m! I (1)
Frequency polarization and reference frequency f*! (4) is compared with the reference frequency signal in the phase comparator (5), and this phase ratio #i! Add if! from (5) through the low-pass filter (6). A voltage signal containing phase error information is supplied to (8). And this addition! ! At step (8), these voltage signals are superimposed and supplied to the motor drive circuit (9), thereby controlling both the rotational phase and rotational speed of the rotor of the brushless motor (7). Note that the frequency-voltage converter (2) and phase comparator (5) are provided with the low-pass filters (3) and (6).
) in order to compensate for the ripple included in the output.

According to the conventional phase/frequency iiL control method configured in this way, a frequency navigation shield (1) is provided to perform magnetic shielding in order to make the rotor (It) otg11i evenly straight.
Due to the mandatory tribute, it is disadvantageous in terms of space factor,
This is a major step toward making the motor itself a device and making it thinner. Moreover, the frequency axis electric machine (1) and the
Since the immediate configuration of the voltage converter uses a complex series, the servo thread OIP! There is an inconvenience that 1wr becomes complicated and expensive.

The present invention is of the above type 1! It was invented in a nutshell, and by making effective use of the special configuration of two mutual string wave drive-bushless motors, there is no need to use a single frequency generator, and the configuration is simple and safe. Regardless, the essence fj
The purpose of this invention is to provide a brushless motor drive circuit that is capable of controlling L<rotational speed flai.

Below are examples of the present invention! This will be explained with reference to figures s2 to 517.

First of all, Figures 2 to 14 show the configuration of a two-rooted string wave drive brushless motor, (Llm is the rotor, ■ is the stator, Aji is the 马＠浬, Present is the rotor yoke, and 141 is the rotor magnet. .The above-mentioned rotor magnets 1-14
) is formed into a ring shape as shown in Fig. 6, and the polarity is alternately arranged with equal spacing in the circumferential direction. (1651) ~ (1
6k) is formed. In this case, the 0 viewing area (
16m) to (16k) are arranged so that the magnetic flux distribution becomes sinusoidal. On the other hand, stator I has 414 of 241M.
IN blocks q% C2, C3, and C4 are provided. That is, as shown in Fig. 4, the rotor magnet (L4
The winding blocks C1 and C2, which are arranged in the same phase with respect to the acupuncture field formed by the above, are connected in series to form a stator coil of the human phase. Winding blocks C5 and C4 are connected in series to form a B-phase stator coil. In addition, these human-phase and B-phase stator coils L1 and L
The magnets 2 are arranged opposite to the rotor magnet (2) with a slight distance of one inch between them, and are arranged so that the electric pictures differ from each other by an odd number of times.

In addition, the rotor magnet a4o a field is detected and its @
@Detect position, human face and BaO stator coil L1s
A sinusoidal driving current fiL proportional to the IJ2o chain father
In order to supply these stator coils, a magneto-electric transducer, such as a Hall element, is arranged between the physiognomic block C2 and the BIl winding block C5, as shown in Figure 68. ing. In this case, the Hall element and the wire are different in electrical angle from each other by 7 electrical angles at the position where the wire bundle t from the rotor magnet can be detected. They are placed in 7 different positions. Then, the two-phase alternating flL voltages, which are out of phase with each other, obtained based on the outputs from these Hall Takakohato and H2 are applied to the human-phase and B-phase stator coils, respectively, and the low tag net 04 (DIg
The rotor blade is configured to be rotationally driven with a constant torque that is independent of the first rotation position.

Next, a first embodiment of the drive circuit for the two-rooted sinusoidal drive brushless motor constructed as described above will be described with reference to FIG. 1115.

First, a voltage is applied to the Hall element (excitation terminal) from the operational amplifier @- through the resistance range, and depending on the output voltage of the operational amplifier, [IL (D
m II m m Ka * -ru X Child H1, HziC
It 6 It's starting to look like this. Since these Hall elements H1%'2 are arranged to be shifted from each other by T in electrical angle, the phases from the pair of output terminals of Hall element '1 and HR are out of phase with each other according to the rotor magnet cno times. Two-phase AC voltages shifted by T are generated.

And this two-phase alternating voltage is passed through each resistor to an operational amplifier? 1 (2) and are supplied to the non-inverting input terminal and the inverting hexagonal terminal, respectively, and are differentially amplified.

Operator 1! The output from the capacitor is supplied to a single-end Przeple power amplifier (Kan) consisting of a complementary connection of an NPN transistor Tr1 and a PNP transistor Trt. And these power amplifiers @(
The output voltage from the stator coil is human phase and B phase.
1-, whereby the rotor blade is rotationally driven with a constant torque that is unrelated to the rotational position of the rotor magnet 1◆, which is conventionally known.

In the 1m5 diagram, the bird is the residual resistance of the amplifier circuit, which is composed of the operational amplifier @shi υ(2) and the power increase S*(2) (to), and the resistance area and the bird are the operational l# Adder 3υ@O This is for offset voltage correction.

On the other hand, the output voltage of the power amplifier rsrJ4o is supplied to the stator coil 1- as described above, and is passed through a low-pass filter consisting of a resistor and a capacitor C, respectively. Part (2)- is supplied.

These O-square calculation units (to) 4 output the squared voltage e2 when voltage e is input, and another person uses the power to the pair of @ calculation input terminals of the multiplier OI as shown in No. 6I11. The amplifiers (2) are configured to respectively supply output voltages from the amplifiers (2). Therefore, if a sinusoidal voltage is output from the Hall element section, one square calculation section (2) will have 110 (k is the rotor) 140 WA, a constant inversely proportional to the speed, and 0 is Rotation angle K of rotor magnet a4 for Hall element disease (
electrical angle)] is input, and this square calculation I
A voltage indicated by k"u"fl is output from l@. In addition, in this case, the cosine wave-like 0111L pressure is output from the other Hall element H.
The voltage expressed as k(2)0 is manually applied, and this square O
A voltage indicated by kcos''# is output from the IL calculation S@.

Then, the 2*-pressures output from these square operations xs@- through the respective resistors R7t are added, and further ζO addition S
% voltage is superimposed with DC power supply EO voltage and t*X amplification i!
40 Supplied to the non-inverting input terminal.

The output voltage from the square calculation section (to) 4 is as described above! Since these are full and k"cw2θ, these addition outputs e・hani'su"# + k2m2g == k"t. Therefore, a DC voltage of +E is supplied to the non-inverting input terminal of the operational amplifier!!(2).

Next, we will discuss the configuration of the brushless motor drive circuit O rotation evenness control operation as described above. The AC voltage 0IIL11i611 [input] supplied from the amplification system consisting of @iI four squares to the square operation 11S@(2) through the low-pass filter @(2) has a relatively - value. Therefore, the modest increase m* A relatively high voltage will be supplied to the non-inverting input voltage (to), and the output voltage from the The driving current of the element set and the coil is increased, and the output voltage thereof is increased, and the stator coil-s L2
o drive wJ voltage (wave ＾櫨) increases. This drives the rotor bale to rotate more forcefully.

Also, if the rotor wheel is 1gl@L four times below the reference speed, it is passed through a low-pass filter @@ and squared nN
The voltage Oa^ value k supplied to @(2) becomes relatively small, and thereby the DC voltage supplied to the non-inverting input terminal of the operational amplifier 4 becomes relatively low. As a result, the drive current caused by the Hall element becomes smaller, and the rotation speed of the rotor wheel is reduced.

According to the pushless motor drive circuit configured in this way, the rotation speed WLm can be controlled without using a frequency generator as a rotation speed detection means, which is advantageous in push drawings and is renamed to space factor 1. As a result, it is possible to reduce the wrinkles and thickness of equipment such as car stereos that use one-way drive, and even two-way sine wave drive brushless motors.

In the case of a two-root sinusoidal brushless motor, positive 1ttIL and cosine wave driving voltages are applied to the stator blue and -. Therefore, in this embodiment, the rotational speed control 1 of the rotor 1 is carried out by effectively utilizing the jlHiL, i-i-jukui-e-10 integrally. That is, by passing a coil drive voltage with a frequency that is appropriately proportional to the rotation of the rotor (II (Z)) through a low-pass filter @@, a voltage that is inversely proportional to the jla #L interval is obtained, and these voltages are then mutually By adding the ripple, a non-chord DC voltage is obtained as the IgI@speed control voltage.Therefore, a low-pass filter tA@ and a 21st power calculation section (2) are added to the conventional brushless motor drive. Rotational speed control can be performed with high precision using an extremely simple circuit that only requires

Further, No. 7 @ is a drive-tm road showing the second embodiment of the present invention, and in this embodiment, the special conditions of the structure of the two-root string direct drive-buttonless motor are effectively utilized, - A pair of hole main blocks, which are disposed at predetermined locations separately from the O-holes in the displacement detection layer, are used as square calculation means.

That is, the Hall element mass, for example, JII4mG Kooi r
@layer+111f shown in 5iC1Al1041iii is disposed between block C1 and m@o@- block C4, and is capable of detecting Ov&bundle from rotor magnet I@i
KooibiC4C) tg from the (to) and (to) sides, respectively
It is placed at a position of -2-1A at the & angle. Therefore,
The Hall element H1 and the hole and the hole and the stock are respectively arranged at positions different from each other by 4 g in electrical angle (π in mechanical angle).

2. In the reciprocal sinusoidal drive pushless motor, the rotor magnet shaft is attached with a sine wave as described above, so if the hole elements □ and the lumps are placed in the above-mentioned position g + , these holes can be The output voltage to the element block depends on the magnitude of the magnetic flux density and the fi flowing through the Hall element in the direction perpendicular to the magnetic flux.
It is given by the product of flow.

Therefore, as shown in Figure 1m7, the low-pass filter rA@O
If the output is passed through the Hall elements as a -ll1l wax flow, these Hall elements will produce the strength of the ffl field formed in the rotor magnet ◆ and the Hall weight -
-Hanging output with regional current can be obtained. Here, Hall Takako, H40f44 seki output eHA s 'H4 those 0I
RJIl
t IHs % II4, since this is a 60-hole element, if the magnetic flux faWL acting on the mass is the beak 11 t Bo of BM II, then aH, = Ko7 IH, m
BH.

= Log ksu# ・Bl) $11#=Ko-ni@
“b・i!＃・・・・・・・・・・・・・・・・・・
・(1) 6H4 = Ko11154″BH4 = Ko6 kmsl @ Bocase=: Ko,
k @B,, -cns2a-0---,----
-8-(2). Therefore, as can be seen from the above equations (1) and (2), the Hall elements are 5i12θ
and cos2# as factors.

If we add the outputs from Hall elements Toki and Ya, we get the above (1)
From the following equation and equation (2), 6H1+ BH4= K6"ke Blom (-
! $-)cm! j) = stripes・ni−4・・・・・・・・・
・・・・・・・・・・・・・・・(3) the above(
3) As can be seen from the equation, the voltage of the om bowl does not compensate for the ripple [g voltage].

However, this added voltage, that is, the DC voltage that is inversely proportional to the rotor QID rotation speed and does not include any ripple components, is operationally amplified! It is supplied to the non-inverting input of a4. As a result, the rotor tA4IO rotation moderation control is performed every n [times], and the same operation and effect as in the previously described embodiments can be achieved.

Although the present invention has been described above with reference to embodiments, the present invention is not limited to these embodiments, and various modifications can be made based on the technical idea of the present invention.

For example, in the embodiment described above, the multiplier (
However, the present invention is not limited to this, and it is also possible to use a square operation element constructed from an integrated circuit (IC). Further, the placement positions of the Hall elements h~ in the II2 embodiment are for the sake of example 1', and it is obvious that the placement positions are appropriately placed.

The present invention is to pass the drive range pressure supplied to the two-phase stator coil through a low-pass filter.
and the second square calculation means, and the driving current of the first and second Hall elements is determined based on the direct fIL voltage i obtained by adding the outputs of the square calculation means of 1IiI 1IiI and 2. It is designed to control. Therefore, according to the drive circuit of the two-rooted chord wave drive brushless motor of the present invention, by adding the outputs of the square calculation means, the relationship of su2θ+cm2g=1, that is, the configuration of the two-rooted chordal wave drive brushless motor, can be obtained by adding the outputs of the square calculation means. By making advantageous use of the above special conditions, it is possible to obtain a ripple-free DC voltage as a rotational speed control signal, so a frequency generator or a frequency-voltage converter with a double-wire configuration is used as in the past. It is possible to perform highly accurate rotational speed control without any problems. In addition, since it is not necessary to use a frequency generator and a frequency-voltage converter as a rotational speed detection means, the configuration of the drive circuit can be simplified, which is advantageous in terms of cost and space factor, and equipment using this circuit It is possible to reduce the thickness and thickness of the solder.

[Brief explanation of the drawing]

111g1Fi is a block diagram showing a rotational speed control system in a brushless motor drive circuit. [Figures 2 to alJ show the configuration of a two-string tIL driven brushless motor. Figure sm2 is a longitudinal sectional view of this brushless motor, Figure 6 is a plan view of the rotor magnet O, and Figure 4 is a diagram of the stator. The plan view, Fig. 5, and Fig. 6 show the GIO embodiment of the present invention. Fig. 5 is a circuit diagram of a brushless motor drive circuit, and Fig. 16 is a block diagram showing an example of a square calculation section. , FIG. 7 is a circuit diagram of a brushless motor drive circuit showing a second embodiment of the present invention. In addition, in the symbols used in the drawings, ga-...
・・・・・・・・・・・・ Low pass filter ---
...−'−−−−− Square operation part (to)...
・・・・・・・・・・・・ Multiplier n4. H2...
・Foil element for motor drive...
...... It is a Hall element as a square calculation means. Agent! bladder

Claims (1)

[Claims] Based on the outputs of the Hall elements 1 and 112, which are arranged at an angle α1 that is twice the electrical angle of T', a two-phase stator; In a drive circuit for a two-root sinusoidal drive brushless motor that supplies a sinusoidal ODC voltage proportional to the flux to these two-phase stator coils, the voltage is supplied to the two-phase stator coils. The drive voltage is supplied to the Jill and 2 square calculation means through a low-pass filter, and the +1!1 and #I
Direct IL11 obtained by adding the outputs of the 2 square calculation means
A drive circuit for a two-root sinusoidal wave drive brushless motor, characterized in that the drive currents of the first and second Hall elements G are controlled based on the L voltage. 2. The first square calculation means is composed of a Hall element arranged at a position different from the first Hall element by several times in electrical angle Kf), and the second square calculation means is , To in electrical angle for the Hall element of site Kirei 6
A strategy characterized in that it consists of a 1540 hole element that differs by n parity and is placed at a different position in the 15240 hole element with an IK @ angle of π.
The desired range is 1 $ 402 sine It-dynamic brushless motor drive circuit.