JPH11225026A - Wide-band amplifier circuit - Google Patents

Abstract

PROBLEM TO BE SOLVED: To output a large-amplitude wide-band signal without increasing power consumption by connecting the feedback impedance of an output signal to the low impedance terminal of an active element. SOLUTION: By connecting the feedback impedance 7 to the emitter of a transistor 9, the output signal can be fetched by a normal phase from the collector of the transistor 9 as a wide-band current signal. Thereby, in a low impedance terminal such as the emitter of the transistor 9, the increase of time constant by the effect of a variety of parasitic capacitance is suppressed. In addition, a signal inputted to the base of the transistor 9 from a terminal 2 to the base of the transistor 9 is subtracted from a fed-back wide-band current signal to be fetched by a reverse phase from the collector of the transistor 9. Thereby, by connecting the impedance 7 to an output point being high impedance, furthermore widening of a band become possible.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a wide-band amplifier circuit, and more particularly to a large-output low-power amplifier circuit suitable for a picture tube driving circuit requiring a large-amplitude wide-band signal output.

[0002]

2. Description of the Related Art In recent years, the frequency band of a picture tube driving circuit has been increasingly widened with the increase in resolution of a display device (display). Particularly, in the case of a computer display for CAD / CAM, etc.
A band of about MHz is required. Further, the voltage amplitude of the drive signal is required to be about 30 V for a monochrome picture tube and about 50 V for a color picture tube, and the amplitude has been further increased with the recent increase in the size of the display screen.

As a result, there has been a problem that the power consumption of the drive circuit is increased and the circuit components are increased in size and weight. In consideration of this problem, FIG. 2 shows a conventional capacitive load driving circuit such as a picture tube or a cathode ray tube described in Japanese Patent Publication No. 57-20724.

In the conventional capacitive load driving circuit shown in FIG. 2, a broadband signal applied from a signal source 1 to an input terminal 2 is amplified by dividing it into a low-frequency component and a high-frequency component. It is configured to be driven. The low-frequency component is generated by the transistor 2 having a feedback path including the input resistor 27, the feedback resistor 7, and the frequency characteristic compensating capacitor 28.
5, the signal is amplified while suppressing temperature drift and distortion.

[0005] Here, by suppressing the collector current of the transistor 4 constituting the bias constant current circuit,
Power consumption of the amplifier circuit can also be suppressed. The above high-frequency component is amplified by a series feedback amplifier comprising a transistor 26 to which a feedback resistor 31 and a peaking capacitor 32 are connected. At this time, the two frequency components described above are combined at the emitter of the transistor 3 having the common base configuration and sent to the output terminal 5.

[0006]

SUMMARY OF THE INVENTION The above prior arts include:
There is a problem that a wideband signal cannot be amplified to a sufficiently large signal amplitude. That is, when the high-frequency signal is amplified to a large amplitude by using the capacitive load driving circuit shown in FIG.
In many cases, the transistor 26 is cut off as a side effect of peaking with the use of, so that a sufficient output amplitude cannot be obtained. A more detailed explanation is added below.

When the input signal falls, it is necessary to discharge the peaking capacitor 32 so that the voltage waveform of the emitter of the transistor 26 follows the input signal. However, the maximum value of the discharge current of the peaking capacitor 32 is suppressed to the value of the bias current of the transistor 26. Therefore, in a state where the bias current of the transistor 26 is suppressed to suppress the power consumption of the circuit,
When the input signal falls during a very short transition time with a large amplitude, the peaking capacitor 32 cannot be completely discharged, and the transistor 26 is cut off.

Further, the prior art also has a problem that the characteristics of the amplifier circuit deteriorate due to the influence of the frequency characteristics of the feedback system. For example, the stability of the amplifier circuit may be impaired due to the influence of the phase delay occurring in the feedback network, and a sufficient frequency band may not be secured. Further, when the frequency band of the feedback network cannot be sufficiently secured, an excessive shoot may occur in the transient response of the amplifier circuit, or the frequency band of the amplifier circuit may not be sufficiently secured as described above.

Furthermore, due to the loading effect of the feedback network,
The large-amplitude wideband output capability of the amplifier circuit may be impaired. In FIG. 2 as well, due to the input resistor 27, the feedback resistor 7, the feedback circuit element of the frequency characteristic compensating capacitor 28, the parasitic capacitance and the parasitic inductance of the transistor 25,
The characteristic deterioration as described above occurs in the amplifier circuit. Further, although the frequency characteristic compensating capacitor 28 is used for improving the transient response characteristic of the amplifier circuit, there is a problem that the frequency band at the time of large amplitude output is narrowed due to a load effect on the amplifier circuit.

An object of the present invention is to provide a broadband amplifier circuit capable of outputting a large-amplitude wideband signal without increasing power consumption.

[0011]

In order to achieve the above object, the first means is to use a peaking capacitor in a wide band amplifier circuit as a normal output side of a push-pull circuit (in this case, it is used as an output side). However, it is conceivable that the connection is made for the gain setting, but this is separately filed (Japanese Patent Application No.
236696).

[0012] Next, as a second means for achieving the above object, in the broadband amplifier circuit of the present invention, the feedback network of the output signal is connected to the low impedance terminal of the active element to provide a feedback network. Is configured.
Further, as a third means, a feedback impedance is connected to an output signal detecting section exhibiting high impedance. Subsequently, as a fourth means, a current signal distribution circuit is connected to a drive element constituting the push-pull circuit. And the fifth
As a means, a part of the other signal path is connected to the AC ground terminal of the active element connected to the signal path.
Finally, as a sixth means, the peaking element and the output resistor are connected via a capacitor.

[0013]

In the first means, which has been separately filed, for reference, the peaking capacitor has the function of improving the frequency characteristics of the amplifier circuit. The push-pull circuit promotes charging and discharging of the peaking capacitor. With the above-described operation, the intended purpose is achieved.

In the above-mentioned second means according to the present invention,
The feedback impedance has an action of feeding back the output signal as a current signal. An active element having a low impedance terminal to which an impedance is connected has an effect of returning an output signal to an input portion of an amplifier circuit over a wide frequency range. The above object of the present invention is achieved by forming a feedback network by the above feedback impedance and the active elements.

In the third means, the output signal detecting section exhibiting high impedance has a function of guiding an output signal to a detection terminal. The feedback impedance reduces the impedance of the output signal detector and suppresses the time constant,
It has the effect of returning the output signal to the input of the amplifier circuit.
With the above-described operation, the above object of the present invention is achieved.

In the fourth means, the driving elements constituting the push-pull circuit have a function of outputting a large-amplitude wide-band signal without increasing power consumption by operating complementarily. The current signal distribution circuit drives the driving element by distributing the current signal over a wide frequency range from a DC component to a high-frequency component. With the above-described operation, the above object of the present invention is achieved.

In the fifth means, the active element connected to the signal path amplifies the signal. The other signal path has a function of canceling the parasitic impedance of the active element connected to the signal path by connecting a part of the signal path to the AC ground terminal. With the above-described operation, the above object of the present invention is achieved.

In the sixth means, the peaking element has a function of improving the frequency characteristics of the amplifier circuit.
The output resistor has a function of determining the gain of the amplifier circuit and a function as a damping element of the peaking element. The capacitor connected between the peaking element and the output resistor connects both at the frequency at which the damping is required. With the above-described operation, the above object of the present invention is achieved.

With the above operation, it is possible to provide a wide-band amplifier circuit capable of outputting a large-amplitude wide-band signal without increasing power consumption.

[0020]

FIG. 1 is a circuit diagram showing the basic concept of a broadband amplifier circuit according to the present invention. In FIG. 1, the process of signal amplification can be considered as follows.

That is, the voltage signal of the signal source 1 is converted into a current signal via the input impedance 8, and then flows into the input terminal 2 of the amplifier circuit. Since the current gain of the amplifier circuit composed of the elements after the transistor 9 is considered to be extremely large, the above-mentioned input current signal is again converted into a voltage signal amplified via the feedback impedance 7 and
To the capacitive load 6.

At this time, the output voltage signal is converted to a feedback current signal via a feedback impedance 7, subtracted from the input current signal in a transistor 9 having a grounded base configuration, and converted to an error voltage signal via an impedance 11. Is done. This error voltage signal is inverted and amplified by a transistor 12 having a common-emitter configuration, and applied to transistors 15 and 16 forming a single-ended push-pull circuit (hereinafter referred to as SEPP).

Thereafter, the above-described error voltage signal is supplied to a transistor 3 having a grounded base configuration that performs a complementary push-pull operation.
And 4 are amplified by the voltage to become an output signal. that time,
The impedances 8, 7 and 11, 13 and 14, which constitute the circuit, and 18 which is the input impedance of the grounded base circuit
It is needless to say that various series impedances composed of passive elements can be used for each of the series impedances 20 and 21.

For example, the feedback impedance 7 may be composed of a series combined impedance of a resistor and a coil in order to perform peaking in a high frequency range of the frequency characteristic of the amplifier circuit. Further, in order to improve the delay of the transient response of the amplifier circuit due to the influence of the thermal time constant of the transistor, the feedback impedance 7 may be constituted by a network including a parallel combined impedance of a resistor and a capacitor.

Next, among the respective means for realizing the present invention described above, those applied to the circuit shown in FIG. 1 will be described. The capacitor 21 forming the input impedance of the above-mentioned grounded base circuit can be regarded as a peaking capacitor. In the prior art, the capacitor 21
The blocking of the transistor 4 connected to the circuit prevents the output signal from having a large amplitude and a wide band.

However, in this circuit, the transistor 22 is used to make the grounded base circuit a push-pull configuration, thereby facilitating the charging and discharging of the peaking capacitor 21 despite the cutoff of the transistor 4. Voltage source 2
As a bias condition of the transistors 4 and 22 that can be set by the above, a class AB operation in which the transistor 4 is not interrupted when a low-frequency signal is input is preferable in terms of circuit operation.

However, the anode of the power supply 24 and the transistor 4
If a bias current path of the feedback impedance 7 flowing toward the emitter of the transistor 9 is provided by connecting the collector of the
Arbitrary settings such as class operation are possible. Also, the transistors 15 and 16 constituting the SEPP also have the function of accelerating the charging and discharging of the peaking capacitor 21, and the same applies to the bias conditions as those of the transistors 4 and 22.

Next, one terminal of the feedback impedance 7 is connected to the emitter of the transistor 9 which is a low impedance terminal whose signal voltage amplitude is suppressed, and transmits the feedback signal as a current signal as described above. Since the signal voltage amplitude is suppressed at the low impedance terminal as described above, the bypass of the signal current to the parasitic capacitance of this terminal and each element connected to the terminal is suppressed.

Therefore, by transmitting the feedback signal as a current signal, deterioration of the frequency characteristic of the feedback network due to the influence of the parasitic capacitance is suppressed, and a large output and wide band of the amplifier circuit can be achieved. Further, since the time constant is reduced at the low impedance terminal, the feedback impedance 7 can be set to a sufficiently high value, and the load effect on the amplifier circuit can be suppressed.

The other terminal of the feedback impedance 7 is connected to an output signal detecting section (output terminal 5) which is a connection point between the respective collectors of the transistors 3 and 4 and exhibits a high impedance. By connecting the feedback impedance 7 in parallel, the impedance of the output signal detecting section is reduced. As a result, it is possible to suppress the time constant of the output signal detection unit, expand the open-loop gain frequency band of the amplifier circuit, and improve the flatness of the closed-loop gain frequency characteristic.

The basic concept of the broadband amplifier circuit of the present invention has been described above with reference to FIG. Hereinafter, various embodiments using each means for realizing the above-described present invention will be described in detail. At this time, the same components as those shown in FIG. 1 are denoted by the same reference numerals.

First, an example of a circuit having the least number of constituent elements using the above-mentioned first means (the above-mentioned Japanese Patent Application No. 04-2366).
No. 96 (related to a separate application) is shown in FIG. 3 as a reference example. In FIG. 3, it is considered that the DC gain is determined by the ratio between the emitter resistance 31 and the output impedance 33, and the high-frequency gain is set by the ratio between the capacitance value of the peaking capacitor 32 and the capacitance value of the capacitive load 6. However, when the amplitude of the input signal applied from the signal source 1 to the input terminal 2 increases or the frequency increases, the charging and discharging of the peaking capacitor 32 is hindered by the cutoff of the transistor 16 as described above.

In particular, when the bias current of the transistor 16 is suppressed in order to reduce the power consumption of the amplifier circuit, the cutoff tendency of the transistor 16 is further promoted. In the above-described circuit example, the addition of the transistor 15 promotes the charging and discharging of the peaking capacitor 32, and enables a strong application of emitter peaking to achieve a wide output and wide band of the amplifier circuit.

In FIG. 3, the transistor 16 is set to a class AB bias in which a bias current flows when there is no signal, and the transistor 15 is set to a class C bias in which no current flows unless the signal amplitude or the like becomes larger than a certain level. However, a circuit for setting an arbitrary bias voltage or bias current can be provided between the bases of the transistors 15 and 16 as long as the charging and discharging of the peaking capacitor 32 can be promoted. Needless to say, the peaking capacitor 32 can be an arbitrary circuit network in which a series resistor is inserted to suppress and stabilize the peaking effect more than necessary.

Further, in order to further increase the output power and the bandwidth, a grounded base circuit is provided at the collector of the transistor 16 to form a cascode structure.
It goes without saying that a PP and an emitter follower circuit can be provided.

In FIG. 3, it will be apparent that the transistor can be replaced by a field effect transistor FET (MOS type or junction type). FIG. 47 shows a circuit diagram corresponding to a transistor of each polarity and a field-effect transistor FET.

Next, FIG. 4 shows, as a reference example, a circuit in which the transient response of the amplifier circuit is improved in symmetry using the first means described above. In FIG. 4, the peaking capacitor 3
SEP comprising transistors 35 and 36 with load 7
By driving P through the coupling capacitor 34,
A push-pull amplifier circuit is realized.

Therefore, a signal current can be output to the output terminal 5 from the collector of the transistor 35, so that not only the fall time but also the rise time of the output voltage can be reduced. In addition, the emitter resistances 39 to 4 of each transistor
2 has a function of suppressing the instability of SEPP caused by the capacitive load of the peaking capacitors 32 and 37 and a function of setting the bias current of each transistor using the voltages of the bias voltage circuits 23 and 38.

Accordingly, the emitter resistors 39 to 42 can be deleted by short-circuiting, or can be inserted in series at the base side of each transistor. Similarly, the bias voltage circuit 23
And 38 can be short-circuited and deleted.
It is also possible to set the bias by connecting the emitter of No. 5 to the anode of the power supply 24 via a resistor or the like. In addition, by securing the bias current of the transistor 35 and providing the negative feedback path as shown in FIG. 1 to stabilize the output voltage, the output impedance 33
The circuit scale and the load capacity can be reduced by eliminating the resistance.

Here, it goes without saying that, similarly to the reference example shown in FIG. 3, a cascode configuration can be adopted, or an SEPP or an emitter follower circuit can be provided in front of the output terminal 5. A similar effect can be obtained by connecting one terminal of the coupling capacitor 34 connected to the base of the transistor 16 to the emitter of the transistor 16.

Next, FIGS. 5, 6, and 7 show, as reference examples, circuits in which the number of circuit elements is reduced to realize the first means. FIG. 8 is a circuit diagram showing these basic reference examples as practical amplifier circuits.

In FIG. 8, the signal current flowing to the collector of the transistor 15 forming the SEPP is not directly discarded to the ground point, but the transistor 4 having the grounded base structure is used.
, And push-pull output of the amplifier circuit is achieved. With this configuration, it is possible to improve the symmetry of the transient response of the amplifier circuit without having to newly connect the transistor to the transistor 4 to form the SEPP.

In the circuit of FIG. 8, the input signal is
Since it is only necessary to drive a single SEPP, it is possible to reduce the characteristic degradation of the input signal due to the internal impedance of the signal source 1. Here, the bypass capacitor 50
Is used to reduce the driving impedance of the transistor 16, and the bias resistor 47 and the diodes 48 and 49 are used to set the bias of the transistors 15 and 16.

Therefore, it is needless to say that the above-mentioned network composed of the diodes 48 and 49 may use a larger number of diodes or short-circuit both ends to eliminate them. The transistor 3 has a grounded base configuration similarly to the transistor 4, and forms a cascode circuit together with the transistor 16. Bias resistors 51, 53 and 29 and temperature compensating diode 52 set the bias current of transistor 4, and capacitor 54 reduces the ground impedance.

An impedance 46 and a constant voltage circuit 45 used for flowing a signal current flowing through the collector of the transistor 15 to the emitter of the transistor 4 are used.
Can be replaced with various elements and circuits shown in FIG.

As the constant voltage circuit 45, a constant voltage circuit including a Zener diode 55 shown in FIG. 9A or a transistor 56 shown in FIG. 9B can be used as an alternative circuit. Further, the constant voltage circuit 45 can be replaced with only the bypass capacitor 60 shown in FIG. 3B or only with a single element such as a resistor or a battery. Similarly, the impedance 46 can be a constant current circuit 61 shown in FIG. 9C or a series combined impedance of the coil 63 and the impedance 62 shown in FIG. 9D. By using the impedance network as shown in FIG. 9D, the peaking effect at an appropriate frequency can be improved.

Next, FIG. 10 shows a basic circuit (skeleton) in the case where a wide-band amplifier circuit (reference example) constructed using the above-described first means is applied to a picture tube driving circuit, and its practical use is shown. The circuit is shown in FIG. In FIG. 11, the output signal amplified using the voltage buffer 68, the grounded base circuit, and the SEPP is applied to the picture tube 78 via the cathode current detection circuit.

In the amplifying process, since the voltage buffer 68 and the grounded base circuit, which can easily obtain good frequency characteristics by effectively utilizing the performance of the active element, are used, it is easy to reduce the cost of the amplifying circuit. Become. The circuit operation of this circuit example will be described in detail below. The input signal voltage is passed through a voltage buffer 68 composed of an emitter follower circuit or a low output impedance circuit such as SEPP, and a series combined impedance of the impedance 72 and the peaking capacitor 71 and the impedance 69 and the peaking capacitor 7.
0 is added to the parallel combined impedance.

Since the other terminals of these combined impedances are connected to the emitters of transistors 4 and 3 having a common base configuration, the above-mentioned signal voltage is converted into a current and the peaking coil 74 is connected in series. It flows into the output impedance 33 and is output as a voltage signal amplified in a wide band. At the time of amplification, even if the bias current is reduced to reduce the power and the cutoff of the transistors 3 and 4 is repeated frequently, the effect of the push-pull operation of the added transistors 73 and 22 causes
The charging and discharging of the peaking capacitors 70 and 71 are promoted.

The bias conditions for the transistors 22 and 4, 3 and 73 are as follows:
And the temperature compensating diodes 48 and 49 and 84 and 85. Also, capacitors 50 and 83, 86 and 5
4 is a bypass capacitor for reducing the impedance of the AC grounding point. Similarly, a transistor 7 is provided by a bias impedance 91 and emitter impedances 95 and 96 and temperature compensating diodes 90 and 92.
The bias conditions of 5 and 76 are set.

When used in a picture tube driving circuit, the emitter impedances 95 and 96 also serve as a protection element at the time of discharge in the picture tube 78. Transistor 77
The above-described cathode current detection circuit composed of the following detects the terminal current of the cathode 79 corresponding to the luminance in order to control the light emission luminance of the picture tube 78. The transistor 77 transmits the above output signal to the picture tube 78 as an emitter follower circuit, and at the same time, converts the cathode current flowing into the emitter into a voltage via the detection resistor 99 connected to the collector and outputs it to the detection output terminal 100.

The capacitor 97 is a bypass capacitor for compensating the asymmetry of the transient response of the emitter follower circuit including the transistor 77. The diode 98 is a protection element that guarantees the reverse breakdown voltage of the transistor 77. Further, the impedance 101 is inserted in series between the parasitic capacitance of the transistor 77 and the ground to prevent an increase in the load capacitance of the amplifier circuit. The coil 102 and the damping resistor 103 are elements for series peaking, and the impedance 104 is a protection circuit of the amplifier circuit against the above-mentioned discharge in the tube.

FIG. 12 shows a skeleton of another reference example in the case where the wideband amplifier circuit (reference example) constituted by using the above-mentioned first means is applied to a picture tube driving circuit. An example is shown in FIG. In FIG. 13, as shown in FIG. 12, the current mirror circuits CM1 and CM2 are used to supply the charging / discharging current flowing through the peaking capacitor to both of the components to the load side, so that the amplifier circuit Improves the symmetry of the transient response.

In FIG. 13, an input signal from the signal source 1 is applied to a transistor 109 forming an emitter follower circuit.
And the transistor 15 forming the SEPP through the line 110
And 16 are added. In this case, transistors 109 and 110 having opposite polarities are transistors 15 and 16
Transistors 15 and 16
The synthesis circuit with SEPP consisting of "Diamond circuit"
It is called and is often used.

The current component flowing through the transistor 15 in the charging / discharging current flowing through the peaking capacitor 32 is a current mirror circuit including transistors 113, 114 and 115 and a current mirror circuit on the anode side of the power supply 24 including transistors 120, 121 and 122. Through the circuit, S
It is supplied to the bases of transistors 75 and 76 constituting the EPP.

Of the charge / discharge currents described above, the transistor 16
Is supplied to the bases of the transistors 75 and 76 complementarily to the collector current of the transistor 122. The voltage at the output terminal 5 is stabilized by controlling the base voltage of the transistor 75 by negative feedback via the feedback impedance 7 and the input impedance 27.

By using the current mirror circuit as described above, the output transient response characteristic can be improved in a wide frequency band in which the collector current of the transistor 15 flows. At this time, the increase in power consumption due to the flow of the charge / discharge current also flows through the transistor 121 is caused by appropriately setting the ratios of the impedances 116 and 118 and 123 and 125 that determine the input / output current ratio of each current mirror circuit. Can be suppressed.

To reduce the power consumption of the transistor 120, a resistor 126 is connected to its collector. Further, a bypass capacitor 127 is added in parallel with the resistor 126 so that the base side of the transistor 120 is not adversely affected by the Miller effect. The transistors 3, 4, and 119 having the common base configuration function to form a cascode circuit with the preceding stage to suppress the Miller effect.

Then, the cathode current can be detected from the terminal 100 via the resistor 99 from the collector current of the transistor 76 biased to class AB by the diode 90. The capacitor 128 is a bypass capacitor similar to the aforementioned 127. A resistor 105 and a capacitor 106 are connected in parallel with the input impedance 27.
The frequency band of the amplifier circuit can be expanded by adding the series synthesis circuit of In FIG. 13, the base resistances 93 and 94, 107 and 108, 111 and 1 of each transistor are shown.
Reference numeral 12 denotes a stabilizing resistor that suppresses parasitic oscillation.

As described above, the reference example has been described in which the charging and discharging of the peaking capacitor is promoted by using the push-pull circuit to achieve a wider band. However, when each of the above-mentioned capacitors for peaking is applied to a high-frequency signal up to 100 MHz or the capacitance value is increased to be applied to a high-gain capacitive load driving circuit, the series resonance of the element itself is a problem. Becomes This is because signal waveforms are distorted due to sudden changes in frequency characteristics around the resonance frequency.

FIG. 14 shows a specific example of a capacitor suitable as a peaking capacitor used in the above reference example. By using the circuit shown in FIG. 14A, a plurality of small-capacity capacitors 131 to 13 having a high series resonance frequency can be obtained.
The parallel combined capacitance between terminals 129 and 130 obtained by connecting 3 in parallel can be used as the peaking capacitor.

The mounting bracket for the feedthrough capacitor 134 shown in FIG.
By short-circuiting 36 and 137 and connecting them to the terminal 130, they can be used as the above-mentioned peaking capacitor. Note that the feedthrough capacitor is a capacitor in which a lead wire is passed through a pipe and a capacity is provided between the lead wire and the pipe.

In general, a feedthrough capacitor has a feature that the series resonance frequency is extremely high due to the reduction in the number of leads, but the resonance frequency can be further increased by short-circuiting the leads as shown in the figure. Either the terminal on the lead terminal side or the terminal on the mounting bracket side may be used on the AC grounding point side.

Further, as shown in FIG. 14A, a parallel combined capacitor may be used.
As shown in (d), further higher frequency is possible. Also, replacing the feedthrough capacitor with a three-terminal capacitor,
Similarly to the feedthrough capacitor, the resonance frequency can be increased when a two-terminal circuit in which the conducting terminals are short-circuited is used as a peaking capacitor.

Next, in order to effectively operate as a peaking capacitor up to the vicinity of the series resonance frequency, FIG.
As shown in (c), the effect of resonance can be suppressed by inserting a series resistor 139. In order to effectively perform peaking up to a higher frequency, as shown in FIG. 14D, a capacitor 142 having a higher resonance frequency than the capacitor 140 is added in parallel.

Further, the circuit shown in FIGS. 14C and 14D or a capacitor is connected between one of the two conducting terminals of the feedthrough capacitor and the other terminal than the conducting two terminals. The same effect as described above can be obtained when the capacitance between the other of the two terminals and the terminal other than the conductive two terminals is used as a peaking capacitor.

FIG. 15 shows a specific example of the peaking capacitor in this case. FIG. 16 is also a circuit diagram showing another specific example of the peaking capacitor, so please refer to FIG. In FIG. 16, TEC indicates a three-terminal capacitor.

In view of the above, an embodiment of the present invention in which the output signal can be fed back as a current signal over a wide band by connecting the feedback impedance to the low impedance terminal of the active element using the second means described above. An example is shown in FIG.

In FIG. 17, by connecting the feedback impedance 7 to the emitter of the transistor 9, the output signal can be taken out from the collector of the transistor 9 in positive phase as a broadband current signal. This is because at a low impedance terminal such as the emitter of the transistor 9, an increase in the time constant due to the influence of various parasitic capacitances can be suppressed.

The signal input from the terminal 2 to the base of the transistor 9 is subtracted from the fed back broadband current signal and can be taken out of the collector of the transistor 9 in the opposite phase. The composite signal obtained from the collector of the transistor 9 is amplified by the inverting amplifier 143 and output from the terminal 5.

In particular, this embodiment is suitable when the output form of the inverting amplifier 143 is a dynamic load form comprising only a push-pull circuit using complementary active elements without using an output resistor. This is because, as will be described later, by connecting the feedback impedance 7 to the output point having a high impedance due to the dynamic load type,
This is because the band can be further widened.

Next, FIG. 18 shows an embodiment in which the above-mentioned second means shown in FIG. 17 is realized by using an inverting amplifier having a push-pull circuit. In FIG. 18, the inverting amplifier is constituted by a common-emitter circuit comprising transistors 16 and 35 whose bases are interconnected via a capacitor 34, and the output of which is formed by transistors 75 and 76.
It is output from terminal 5 via EPP.

At this time, the output is stabilized by the negative feedback via the feedback impedance 7. In FIG. 18, the connection point of the feedback impedance 7 for detecting the output voltage is provided at the collector of the transistor 35 to widen the band as described later. The point may be the emitter of the transistor 75, the terminal 5, or the like.

Further, a signal current enhancing impedance is newly added between the emitter of the transistor 9 and a point other than the connection point of the feedback impedance 7 for detecting the output voltage, such as an AC grounding point. Thus, the voltage gain of the entire circuit can be increased. The bypass capacitor 144 supplies a signal current without passing through the bias impedance 91 to strongly drive the bases of the transistors 75 and 76.

Next, FIG. 19 shows an embodiment in which a wider band can be realized by using the above-mentioned second means. FIG.
In, a current signal is input from the signal current source 145 via the terminal 2 to the low impedance terminal of the active element 9 to which the feedback impedance 7 is connected. By adopting the current input type, since the time constant is small in the low impedance terminal, the frequency band in the signal input path can be expanded.

Further, in FIG. 19, since the transistor 9 is used in a grounded base type, the influence of the Miller effect appearing at the input terminal 2 can be suppressed. Further, as shown in FIG. 19, in the signal source 146 using the signal current source 145, by considering the signal source impedance, or by inserting the input impedance 8 for voltage / current conversion in series, the signal voltage source 1 It is needless to say that the signal source 147 using the above can be applied. It goes without saying that any type of circuit can be applied to the inverting amplifier 143.

FIG. 20 shows a skeleton of an embodiment in which various peaking is applied to the embodiment shown in FIG. 19 to make it possible to further widen the band, and a practical circuit thereof is shown in FIG. 20, reference numeral 143 denotes an inverting amplifier, which comprises an inverting amplifier including the circuit shown in FIG.

In FIG. 21, similarly to the operation of the circuit shown in FIG. 1, after the input signal is converted into a current through the transistor 148 and the input impedance 8, the feedback impedance 7 is reduced by the negative feedback action of the subsequent amplifier. The voltage is inversely converted to an amplified voltage and output.

The various types of peaking shown will be described. The capacitor 149 and the resistor 150 enhance a high frequency component during the above-described current conversion, and the coil 152 is a parallel peaking element for suppressing band degradation caused by parasitic capacitance of the transistors 9 and 12 and the like. Similarly, capacitors 21, 138 and 159 are also peaking capacitors. The coils 166 and 168 and the damping resistors 167 and 169 are series peaking elements for suppressing band degradation caused by the parasitic capacitance of the transistors 75 and 76.

Next, various types of bias diodes will be described. The diode 153 is used for biasing the transistor 12 and, at the same time, has the effect of reducing the time constant by suppressing the resistance value of the resistor 11 by using the bypass capacitor 154 together, thereby achieving a wider band. The Zener diode 155 grounds the base of the transistor 9 in an AC manner by interaction with the bypass capacitor 157.
The diodes 160 to 162 are connected to the bypass capacitor 1
63 and transistors 15 and 16
Bias to class B.

Transistors 15 and 1 constituting SEPP
By supplying a sufficient bias current to the transistor 6, the switching speed of both transistors is increased, and the driving capability of the later-stage common-base transistors 3 and 4 is improved. By the action of diodes 84 and 85 and bias resistor 170, transistor 4 is biased to class AB and transistor 22 is biased to class C.

The grounded base transistor 22 promotes charging and discharging of the peaking capacitor 21 as described above, and enables strong peaking. Bypass capacitor 54
And 86 alternately ground the transistor. The diodes 90 and 92 and the bias resistor 91 bias the transistors 75 and 76 to class AB as described above.

Next, FIG. 22 shows a skeleton of an embodiment of the present invention using the above-mentioned third means, in which a feedback impedance is connected to an output signal detecting section showing a high impedance, and its practical use is shown. The circuit is shown in FIG. In FIG. 22, CA denotes an impedance conversion amplifier, which includes transistors 75 and 76, resistors 95 and 96 in FIG.

In FIG. 23, when the output signal appears and the feedback impedance 7 is connected to the interconnection point between the collectors of the transistors 16 and 35 exhibiting high impedance, the terminal 5 is connected to the terminal 5 via the SEPP composed of the transistors 75 and 76. Output impedance is reduced.

In the conventional amplifying circuit, in order to suppress the load effect of the feedback impedance, as shown by the broken line in FIG. It was common to connect. However, when an output point showing a high impedance is left as in the prior art, the frequency characteristic of the open loop gain of the amplifier circuit is affected by an extremely large time constant at that output point, and the solid line in FIG. As shown at 175, the gain in the low frequency range is excessively increased.

When the difference between the levels of the open loop gain is extremely large as described above, no matter how negative feedback is applied to flatten the gain, as shown by the broken line 176 in FIG. The increase in the low frequency range cannot be suppressed. However, as in the embodiment of the present invention, the frequency characteristic of the open-loop gain when a feedback impedance is connected to the output point showing high impedance can reduce the time constant at the output point appropriately. As shown by the solid line 177 in FIG. 24B, the gain in the low frequency range can be suppressed to the necessary minimum.

Therefore, by performing negative feedback to further flatten the gain, the broken line 178 in FIG.
As shown in (2), the frequency characteristic of the closed loop gain is flattened, and the bandwidth of the amplifier circuit can be widened.

In FIG. 23, transistor 7
Although the output impedance of the terminal 5 is reduced by using the SEPP composed of SEPPs 5 and 76, in the present invention, the S
It is needless to say that a buffer amplifier such as an emitter follower having a current amplifying function can be applied without using the EPP. Further, the above-mentioned output point, which showed a high impedance before connecting the feedback impedance, may be directly connected to the output terminal 5 without using the means corresponding to the buffer amplifier. In that case, the output impedance of the amplifier circuit is reduced by the action of the negative feedback.

As described above, the circuit example in which the feedback impedance is connected to the output signal detecting section exhibiting high impedance is as follows.
This is already shown in FIGS. 13, 18 and 21. FIG. 25 shows a skeleton of an embodiment of a positive-phase amplifier to which the present invention is applied and peaking is strengthened, and FIG. 26 shows a practical circuit thereof. In FIG. 25, CA is an impedance conversion amplifier, and 143 is an inverting amplifier.

In FIG. 26, the feedback impedance 7
, The series impedance is applied to the emitter of the transistor 16 via the gate, so that the input impedance of the amplifier circuit can be increased. The capacitor 21 has a function of limiting a frequency band for stabilizing negative feedback.

The DC gain of this embodiment is determined by the resistance ratio between the resistor 179 and the feedback impedance 7. Capacitor 3
7 and coils 166 and 168 are also used for peaking, similar to the elements described above.

Next, FIG. 27 shows a skeleton of an embodiment in which a current signal is transmitted from a DC region in a push-pull format by using a circuit configuration with a small number of elements, thereby enabling a wider band. The circuit is shown in FIG.

In FIG. 28, the signal voltage appearing at the input terminal 2 is applied from the DC region to the base of the transistor 16 and also to the base of the transistor 35 via the impedance 181.
The push-pull operation can be performed only by using the element.

In this case, it is considered that the current component of the input signal is shunted to the bases of the transistors 16 and 35 via the impedance network. Further, the high-frequency component of the signal voltage appearing at the input terminal 2 is added to the base of the transistor 35 through the bypass capacitor 34 while being emphasized more than the DC component.

The output transistors 16 and 35
Are not subject to amplitude limitations as in the case where the input signal is a voltage signal. Therefore, the gain frequency bandwidth product of the open loop gain of the circuit increases. As a result, the current signal from the signal current source 145 has a feedback impedance of 7
The voltage is converted to a wide band via the terminal and appears at the output terminal 5.
Although the capacitors 32 and 37 are peaking elements, it goes without saying that they can be omitted. Similarly, it goes without saying that the effect of the present invention can be obtained even if the bypass capacitor 34 is omitted.

Further, as shown in FIG. 19, the signal current source 145 can be replaced with a signal voltage source having an input impedance connected in series. FIGS. 29, 30, 31, 32, and 32 show a skeleton of a practical embodiment in which a current signal is efficiently transmitted in a push-pull form from a DC region to a high-frequency region, thereby enabling a wider band. 33 and their practical circuits are shown in FIG. In FIG. 33, reference numeral 183 denotes an integrated circuit.

In FIG. 34, after power supply 10 converts a voltage signal input to terminal 191 of relatively low voltage integrated circuit 183 into a current signal, grounded base transistor 184
To the amplifier circuit section having a high power supply voltage. Therefore, by interposing the transistor 184 between the high voltage portion and the high voltage portion, the semiconductor integrated circuit 183 and the like, which can easily realize the wide band characteristics, can be used without a fear of destruction due to an overvoltage.

In the amplifier circuit section, as in FIG.
The above current signal is converted into an output voltage signal via the feedback impedance 7. At this time, the transistors 185 and 18 are supplied so that the current signal is efficiently supplied to the feedback impedance 7 without being wasted as the base drive current of the output transistors 16 and 35 which increases at a high frequency.
6 is used.

The diodes 48 and 49 and the resistors 198 and 199 are used to set the bias of the SEPP, and the capacitor 50 is used to bypass the signal current and obtain a stable bias voltage. Also,
The output voltage of the SEPP composed of the transistors 185 and 186 is changed to impedances 180 and 187 and 182 and 18
9, the output transistor 16
And 35, respectively.

The bypass capacitors 188 and 190 enhance the base drive voltage at high frequencies. Resistors 195 and 1 inserted in series at the base of each transistor
Needless to say, 96 and 197, 112, 200, 93 and 94 are stabilizing resistors for preventing oscillation.

Next, an embodiment in which the “diamond circuit” shown in FIG. 13 can be applied to a wideband signal will be described with reference to FIG.
It is shown in FIG. The transistors 202 and 203 in FIG. 35 are emitter follower circuits for driving the SEPP composed of the transistors 75 and 76 at the subsequent stage, and also have the function of a bias setting circuit for the transistors 75 and 76.

However, in the conventional "diamond circuit", the sum of the base-collector parasitic capacitances of the transistors 109 and 110 constituting the preceding emitter follower circuit shown in FIG. The high input impedance originally required for an amplifier cannot be obtained.

In particular, in the case of a circuit having a relatively high output impedance such as a dynamic load type at the preceding stage of the "diamond circuit", it is often impossible to secure a sufficient frequency band due to a heavy load. .
In FIG. 35 showing the present embodiment, by connecting the respective collectors of the transistors 202 and 203 constituting the front-stage emitter follower circuit to the output of the rear-stage SEPP, a high input impedance originally required as a buffer amplifier is secured. ing.

That is, by applying a signal substantially equal to the signal inputted to the base to the collector of the transistor constituting the preceding emitter follower circuit, the current flowing through the base-collector parasitic capacitance is suppressed to reduce the input capacitance. Has been reduced. The embodiment shown in FIG. 35 is characterized by a bias voltage source 201 and an emitter resistor 9.
By the action of 5 and 96, the subsequent SEPP is converted to Class A or A
A sufficient bias current can be supplied to the constituent transistors 75 and 76 by biasing to class B, and a high-speed broadband can be achieved.

Conversely, the polarity of the bias voltage source 201 can be inverted to bias the subsequent SEPP into class C, thereby reducing the power consumption of the circuit. In order to improve the accuracy and stabilize the above-described bias setting, it is preferable to bias the transistors 202 and 203 by the constant current sources 204 and 205 as shown. However, it is needless to say that the above constant current sources 204 and 205 can be replaced with resistors or other impedances.

The transistors 75 and 76 are used for large-amplitude operation, electrostatic discharge, discharge in a picture tube of a load, and the like.
Needless to say, a protection diode can be added in parallel between the base and the emitter of each transistor so that a reverse voltage exceeding the breakdown voltage is not applied between the base and the emitter of the transistors 202 and 203.

FIG. 36 is a modification of the embodiment of FIG. Next, FIG. 37 shows an embodiment in which the “diamond circuit” of the present invention is applied to a buffer amplifier at the last stage of an amplifier circuit.

In FIG. 37 as well, the current signal input to terminal 2 is converted into an output voltage signal via feedback impedance 7 by the negative feedback operation of the circuit. In FIG. 37, the collectors of the transistors 202 and 203 constituting the emitter follower circuit of the former stage are connected to the SEP of the latter stage.
The output of P is connected to the emitters of transistors 76 and 75, respectively.

The feature of the embodiment shown in FIG. 37 is that the respective emitters of the transistors 202 and 203 are connected via a capacitor 206 so that the subsequent SEP
This means that the driving capability of the transistors 76 and 75 constituting P is improved. Both bases of transistors 76 and 75 are driven by transistors 203 and 202, respectively, when the output voltage signal rises and falls.

The stabilizing resistor 207 is connected to the capacitor 20.
6, the transistors 202 and 2 are connected in series.
Oscillation due to coupling of the 03 emitter is suppressed. Similarly, the base resistors 212 and 213 also suppress the oscillation of the transistors 202 and 203. Also, as described with reference to the embodiment shown in FIG.
1 is used to protect the transistors 202 and 203. Further, it goes without saying that the bias resistors 91 of the transistors 76 and 75 constituting the subsequent SEPP can be replaced with constant voltage elements or circuits such as diodes, or bypass capacitors can be added in parallel.

FIG. 38 is a circuit diagram showing a skeleton of the embodiment shown in FIG. 37, so please refer to FIG. Next, FIG. 39 shows an embodiment of the “diamond circuit” of the present invention capable of further broadening the bandwidth.

In FIG. 39, the bases of the transistors 202 and 203 constituting the preceding stage emitter follower circuit can be connected without using a bias voltage source. Therefore,
Since the number of elements connected to the input terminal of the “diamond circuit” can be reduced to the maximum, a high input impedance originally required as a buffer amplifier can be obtained.

In addition, the coil 214 and the damping resistor 2
The use of a single peaking circuit of 15 can further increase the bandwidth. In addition, a signal almost equal to the input is applied to the collectors of the transistors 202 and 203 constituting the emitter follower circuit via the bypass capacitor 220 and the transistor 221 and the bypass capacitor 217 and the transistor 218, thereby increasing the input impedance. I'm trying.

At this time, the bias impedance 216
And 219, respectively, to set the bias voltage between the base and collector of the transistors 202 and 203 by flowing the currents of the current sources 204 and 205, respectively.
02 and 203 are prevented, the parasitic capacitance itself is reduced, and the transient frequency is increased. The current sources 204 and 205 can be replaced by any element or circuit such as a resistor as long as the current source can flow a bias current.

Similarly, the bias impedance 216
And 219 can be replaced with any element or circuit such as a diode or a voltage source circuit as long as they can generate a bias voltage. Also, the transistor 7 constituting the subsequent SEPP
It is needless to say that the bias currents of the transistors 75 and 76 can be arbitrarily set by connecting the bases of the transistors 5 and 76 to the bases of the transistors 218 and 221 respectively.

FIG. 40 shows an embodiment of the "diamond circuit" of the present invention, which enables further high-speed broadband. In this embodiment, the emitters of the transistors constituting the emitter follower circuit of the preceding stage are connected to the SE of the latter stage.
The driving capability of the load is improved by connecting each of the transistors constituting the PP to the bases of elements having the same polarity.

The emitters of the transistors 202 and 203 constituting the emitter follower circuit in the preceding stage in FIG. 40 are connected to transistors 76 and 75 of the same polarity via coupling capacitors 222 and 223, respectively. Each of the base resistors 94 and 93 is a relatively low value because it is a stabilizing resistor as described above. The two cascaded sets of the same polarity transistors 202 and 7
In Nos. 6 and 203 and 75, the drive speed of the load can be maximized by increasing the emitter currents of the signal voltage in the forward direction when the signal voltage falls and when the signal voltage rises, respectively.

Here, the coupling between the emitters of the transistors 202 and 203 can be suppressed by interposing the DC transmission impedances 224 and 225 without impairing the driving capability of the subsequent stage. Also, as in the embodiment shown in FIG. 39, also in this embodiment, the number of elements connected to the input terminal can be reduced to the maximum, so that a high input impedance originally required as a buffer amplifier can be obtained.

It goes without saying that the impedances 216 and 226 and the impedances 219 and 227 are used for setting the bias current of the transistors 75 and 76 and the collector bias voltage of the transistors 203 and 202. Further, it goes without saying that the bypass capacitors 217 and 220 can be eliminated.

In FIG. 40, transistor 2
02 is removed from the emitter of the transistor 76 and connected to an AC ground such as a ground.
It is needless to say that the above-mentioned effect of increasing the speed can be obtained even if the collector of the transistor 03 is removed from the emitter of the transistor 75 and connected to an AC grounding point such as the anode of the power supply 24. FIG.
FIG. 2 is a circuit diagram showing such an embodiment. Also, FIG.
FIG. 39 is a circuit diagram showing a skeleton of the embodiment shown in FIG. 39.

Finally, an embodiment of the present invention using a series-parallel peaking circuit using a coil is shown in FIGS. 44 and 45, respectively. The feature of this embodiment is that it is possible to widen the band by using the existing output resistor via a capacitor to perform damping, which was conventionally performed by newly adding a resistor with power consumption. It is in the point which did.

FIG. 43 is a circuit diagram showing a conventional common-emitter amplifier circuit. The output frequency band of this common-emitter amplifier circuit is determined from the output-side resistance 33 and the capacitance of the transistor 16 including the load capacitance 6 on the collector side. It is limited by being inversely proportional to the output time constant. Therefore, a parallel peaking coil 74 that generates parallel resonance with the collector-side capacitance so as to expand the output frequency band,
Conventionally, it has been general to insert a series peaking coil 102 that generates series resonance as illustrated.

After the series peaking coil 102 is once disconnected from the circuit in the drawing, the collector of the transistor 16 is connected to the terminal of the coil 74 which is not connected to the output resistor 33, so that the collector of the transistor 16 It can also be inserted in series between the terminal 5. When the frequency characteristics of the amplifier circuit are to be flattened, damping by the output resistor 33 naturally acts on the resonance of the coil 74, so that only the inductance needs to be adjusted. 103 need to be added in parallel.

However, when the above-mentioned flattening of the frequency characteristics and the expansion of the band are compatible, it is necessary to reduce the resonance Q due to the influence of the resonance energy consumption in the resistor 103 and sufficiently expand the output frequency band. Can not. In the embodiment of the present invention shown in FIG. 44, a coil 74 for parallel peaking and a coil 1 for series peaking are connected to each other.
02, a coupling capacitor 228 is connected in parallel between the above-mentioned non-interconnected terminals.

The output signal current of the transistor 16 can be supplied to the existing output resistor 33 via the capacitor 228, and the output resistor 33 can be used for the above-described series resonance damping. It becomes possible. In addition, the coil 102 for series peaking is once removed from the circuit shown in FIG.
It is also possible to connect the collector of the transistor 16 to the terminal of the coil 74 that is not connected to the output resistor 33 and to insert the transistor 16 in series between the collector of the transistor 16 and the output terminal 5.

Also in this case, the mutually connected coils 74 for parallel peaking and the coils 102 for series peaking are connected.
By connecting the coupling capacitor 228 in parallel between the terminals that are not connected to each other, the same effect as described above can be obtained.

Further, in addition to the circuit configuration shown in FIG. 44, another series peaking coil can be inserted in series between the connection point between coils 74 and 102 and output terminal 5. In this case, it corresponds to dividing the series peaking coil, and the peaking can be optimized according to the ratio of the parasitic capacitance on the collector side of the transistor 16 to the load capacitance.

As shown in FIG. 45, the same effect can be obtained even if a common-base transistor 3 that inputs a signal to the emitter by grounding the base in an alternating current manner is inserted after transistor 16. Needless to say.

FIG. 46 is a circuit diagram showing an embodiment in which the periphery of the broadband amplifier circuit is shielded by a conductor plate LP in the embodiment of FIG. 27 to suppress unnecessary radiation from the broadband amplifier circuit. Please refer to.

Although the embodiment has been described using a transistor as an active element, it goes without saying that a semiconductor element such as an FET or an arbitrary active element such as a vacuum tube can be applied. It goes without saying that the polarities of each active element, voltage source and current source can also be inverted.

When a picture tube is assumed as a load, a monochrome picture tube, a projection type display, a monochromatic tube used for an oscilloscope, a color picture tube having a plurality of drive electrodes used for a color display, etc. Alternatively, any display element such as a plasma display panel or a liquid crystal display panel can be used.

As the driving electrodes, all kinds of electrodes to which signals such as cathodes, grids, anodes and the like are inputted can be considered. Further, the embodiments of the present invention can be applied not only to a picture tube but also to a general wideband signal amplifier circuit for driving an arbitrary load and to an arbitrary signal processing circuit for handling signals.

[0133]

As described above, according to the present invention,
A wide-band amplifier circuit capable of outputting a large-amplitude wide-band signal without increasing power consumption can be provided. Therefore, by using the present invention, a wide-band large-amplitude picture tube driving circuit with a bandwidth of about 50 MHz to 300 MHz and an output amplitude of about 30 V to 50 V applicable to a CAD / CAM computer display or the like can be reduced in size with reduced power consumption. It can be realized by a circuit configuration of a scale. Therefore, it is easy to cover and amplify the entire amplification circuit with a shield plate, and unnecessary radiation can be reduced.

[Brief description of the drawings]

FIG. 1 is a circuit diagram showing a basic concept of a broadband amplifier circuit of the present invention.

FIG. 2 is a circuit diagram showing a conventional capacitive load driving circuit.

FIG. 3 is a circuit diagram showing a reference example of the present invention.

FIG. 4 is a circuit diagram showing another reference example of the present invention.

FIG. 5 is a circuit diagram showing another basic reference example of the present invention.

FIG. 6 is a circuit diagram showing another basic reference example of the present invention.

FIG. 7 is a circuit diagram showing still another basic reference example of the present invention.

FIG. 8 is a circuit diagram showing a practical reference example of the present invention.

FIG. 9 is a circuit diagram showing various elements and circuits that can be used in a reference example of the present invention.

FIG. 10 is a circuit diagram showing a skeleton of still another reference example of the present invention.

FIG. 11 is a circuit diagram showing a practical reference example of the present invention. .

FIG. 12 is a circuit diagram showing a skeleton of another embodiment of the present invention.

FIG. 13 is a circuit diagram showing a practical reference example of the present invention.

FIG. 14 is a circuit diagram showing a specific example of a peaking capacitor used in a broadband amplifier circuit as a reference example of the present invention.

FIG. 15 is a circuit diagram showing a specific example of another peaking capacitor used in a broadband amplifier circuit as a reference example of the present invention.

FIG. 16 is a circuit diagram showing a specific example of another peaking capacitor used in a broadband amplifier circuit as a reference example of the present invention.

FIG. 17 is a circuit diagram showing one embodiment of the present invention.

FIG. 18 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 19 is a circuit diagram showing another embodiment of the present invention.

FIG. 20 is a circuit diagram showing a skeleton of another embodiment of the present invention.

FIG. 21 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 22 is a circuit diagram showing a skeleton of another embodiment of the present invention.

FIG. 23 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 24 is a characteristic diagram showing the effect of the example of the present invention.

FIG. 25 is a circuit diagram showing a skeleton of another embodiment of the present invention.

FIG. 26 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 27 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 28 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 29 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 30 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 31 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 32 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 33 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 34 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 35 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 36 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 37 is a circuit diagram showing a skeleton of a practical embodiment of the present invention.

FIG. 38 is a circuit diagram showing a skeleton of another embodiment of the present invention.

FIG. 39 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 40 is a circuit diagram showing a practical embodiment of the present invention.

FIG. 41 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 42 is a circuit diagram showing a skeleton of still another embodiment of the present invention.

FIG. 43 is a circuit diagram showing a conventional common-emitter amplifier circuit.

FIG. 44 is a circuit diagram showing an embodiment of the present invention.

FIG. 45 is a circuit diagram showing an embodiment of the present invention.

FIG. 46 is a circuit diagram showing another embodiment of the present invention.

FIG. 47 is a circuit diagram showing a circuit corresponding to a transistor of each polarity and an FET.

[Explanation of symbols]

DESCRIPTION OF SYMBOLS 1 ... Signal voltage source, 2 ... Input terminal, 3 ... Output transistor (NPN), 4 ... Output transistor (PNP), 5 ... Output terminal, 6 ... Load capacity, 7 ... Feedback impedance.

 ──────────────────────────────────────────────────続 き Continuing from the front page (72) Inventor Michitaka Osawa 292 Yoshida-cho, Totsuka-ku, Yokohama-shi, Kanagawa Prefecture, Ltd.

Claims (11)

[Claims] In an amplifier circuit including a sixth transistor, a base or a gate of the transistor is connected to the first transistor.
When the electrode, emitter or source is a second electrode and the collector or drain is a third electrode, the second side of the sixth transistor (9) having its first electrode connected to the input side (2) One terminal of the feedback impedance (7) is connected to the electrode, the other terminal of the feedback impedance (7) is connected to the output side (5), and also connected to the output side of the inverting amplifier (143); A broadband amplifier circuit (FIG. 17), characterized in that the input side of the inverting amplifier (143) is connected to the third electrode of the sixth transistor (9). 2. An amplifier circuit including a sixth transistor (9), wherein the base or gate of the transistor is connected to the first transistor (9).
When the electrode, emitter or source of the second transistor is a second electrode, and the collector or drain is a third electrode, the input side (2) is connected to the second electrode of the sixth transistor (9) and the feedback impedance ( 7), the other terminal of the feedback impedance (7) is connected to the output side (5), and the output terminal of the inverting amplifier (143) is connected to the inverting amplifier (1).
43) The third side of the sixth transistor (9) is connected to the input side of
19. A broadband amplifier circuit (FIG. 19), characterized by connecting the above electrodes. 3. The broadband amplifier circuit according to claim 2, wherein said inverting amplifier (143) is a broadband amplifier circuit described below, that is, an amplifier circuit including a push-pull circuit, which constitutes said push-pull circuit. A third and a fourth transistor (3, 73) in which the base or gate of the transistor is a first electrode, the emitter or source is a second electrode, and the collector or drain is a third electrode; ,
One terminal of a peaking capacitor (70) is connected to the input side (2), and the other terminal of the peaking capacitor (70) is connected to a second electrode of a third transistor (3). Peaking capacitor (70)
Is connected to a fourth transistor having a polarity opposite to that of the third transistor (3).
The third electrode of the third transistor (3) and the first electrode of the fourth transistor (73) are connected to each other, and the first electrode of the third transistor (3) is connected to the second electrode of the third transistor (73). The third electrode of the third transistor (3) is connected to the output side (5).
A broadband amplifier circuit (FIG. 20), characterized by comprising: 4. A feedback impedance (7) is connected between an input terminal and an output terminal of an inverting amplifier (143), and an output terminal of the inverting amplifier (143) is connected to an output terminal via an impedance conversion amplifier (CA). , And the input terminal of the inverting amplifier (143) is used as an input side. 5. An amplifier circuit including a seventh transistor, wherein the base or gate of the transistor is a first electrode, the emitter or source is a second electrode, and the collector or drain is a third electrode. Then, one terminal of the feedback impedance (7) is connected to the second electrode of the seventh transistor (16) having its first electrode connected to the input side (2), and the seventh transistor ( 16) The other terminal of the feedback impedance (7) is connected to the third electrode via an inverting amplifier (143), and the other terminal of the feedback impedance (7) is connected to the other terminal of the impedance conversion amplifier (CA). An input terminal is connected, and an output terminal of the impedance conversion amplifier (CA) is connected to an output side (5). 6. An amplifier circuit including an eighth transistor (16) and a ninth transistor (35), wherein the base or gate of the transistor is a first electrode, the emitter or source is a second electrode, and the collector is Alternatively, when the drain is the third electrode, the first electrode of the eighth transistor (16) is connected to the input side (2), and the ninth transistor (16) has a polarity opposite to that of the eighth transistor (16). The first electrode of the transistor (35) is connected, and one terminal of the feedback impedance (7) is also connected, so that the third electrode of the eighth transistor (16) and the ninth transistor (35) are connected. And the feedback impedance (7).
Of the eighth transistor (1).
6) connecting an interconnection point between the third electrode of the ninth transistor (35), the third electrode of the ninth transistor (35) and the other terminal of the feedback impedance (7) to the output side (5). Characteristic broadband amplifier circuit (FIG. 27). 7. An amplifier circuit including an eighth transistor (16) and a ninth transistor (35), wherein the base or gate of the transistor is a first electrode, the emitter or source is a second electrode, and the collector is Alternatively, when the drain is the third electrode, a first DC coupling circuit (1) including a resistor or the like is provided between the input side (2) and the first electrode of the eighth transistor (16).
89) and the input side (2)
And a first electrode of a ninth transistor (35) having the opposite polarity via a second DC coupling circuit (187) made of a resistor or the like, and a feedback impedance (7). ) Is connected to the input side (2), and the third electrode of the eighth transistor (16) and the third electrode of the ninth transistor (35) are connected to each other. The other terminal of the feedback impedance (7) is also connected, and the third electrode of the eighth transistor (16), the third electrode of the ninth transistor (35) and the other of the feedback impedance (7) are connected. 29. A broadband amplifier circuit (FIG. 29), characterized in that an interconnection point with the terminal of (1) is connected to the output side (5). 8. An amplifier circuit including an eighth transistor (16) and a ninth transistor (35), wherein the base or gate of the transistor is a first electrode, the emitter or source is a second electrode, and the collector is Alternatively, when the drain is the third electrode, a first DC coupling comprising a buffer amplifier (BA) and a resistor is provided between the input side (2) and the first electrode of the eighth transistor (16). A buffer amplifier connected between the input side (2) via a circuit (189) and a first electrode of a ninth transistor (35) having a polarity opposite to that of the eighth transistor (16); (BA) and the second consisting of resistance etc.
And one terminal of the feedback impedance (7) is connected to the input side (2), and the third electrode of the eighth transistor (16) is connected to the ninth transistor of the ninth transistor (16). And the third terminal of the feedback impedance (7) is connected to the third electrode of the transistor (35).
And the third electrode of the ninth transistor (35).
30. A broadband amplifier circuit (FIG. 30), characterized in that an interconnection point between the electrode of (1) and the other terminal of the feedback impedance (7) is connected to the output side (5). 9. The broadband amplifier circuit according to claim 8, wherein a signal current source (145) is connected to the input side (2) (FIG. 31). 10. The broadband amplifier circuit according to claim 9, wherein said signal current source (145) is connected to said input side (10) via a tenth transistor (184) having a structure in which a first electrode is grounded. A broadband amplifier circuit (FIG. 32), which is connected to 2). 11. The broadband amplifier circuit according to claim 10, wherein said signal current source is constituted by an integrated circuit (183).