JPH10262367A - Switching power device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a switching power device capable of supplying a stabilized voltage efficiently, even if the voltage of a battery is lower or higher than the voltage of a load. SOLUTION: Phase-inverted two triangular waves are generated from a first and second triangular wave generating circuits 8, 9. Pulse signals are generated by comparing a signal proportional to a voltage level from either a first switching circuit DC for lowering an input voltage or a second switching circuit UC for boositing an input voltage, with the two triangular waves. The first and the second switching circuits DC, UC are controlled using these pulse signals. In addition, a pulse generating circuit 10 for generating a pulse synchronized with the triangular wave generating circuit is provided, and duty restriction is imposed on the boosting switching circuit by the output of the pulse generating circuit 10.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a step-up / step-down switching power supply for use in an electronic device or the like using a battery as a power source and for obtaining an output voltage higher or lower than the battery voltage.

[0002]

2. Description of the Related Art In recent years, switching power supplies have been widely used in electronic equipment using a battery as a power source in order to operate with a small number of batteries and to extend the life of the battery. Hereinafter, an example of the above-described conventional switching power supply device will be described with reference to the drawings. In FIG. 8, which is a circuit diagram of a conventional switching power supply, a transistor Q51 is controlled to be turned on and off by a pulse input from a comparator 7 via a resistor R53. First, when the transistor Q51 is turned on, a current flows from the battery 1 to the transistor Q51 through the primary coil L51a of the flyback coil L51, and at this time, the electric charge accumulated in the smoothing capacitor C3 passes through the diode D51 and the resistor R51. The capacitor C51 is charged, and then Q
When the transistor 51 is turned off, the voltage on the collector side of the transistor Q51 rises at the other end of the secondary coil 51b due to the flyback of the flyback coil L51, and the voltage of C51 is further increased by the voltage of C51. The transistor Q52 is turned on, and the energy stored in the primary coil L51a of L51 while the transistor Q51 is turned on is stored in the capacitor C3 through the transistor Q52. Here, the diode D51 is a diode for preventing the charge of the capacitor C51 from flowing back to the capacitor C3 and effectively flowing the charge to the base of the transistor Q52. The capacitor C2 is for absorbing the ripple current flowing through the flyback coil L51. The capacitor C52 is for preventing the oscillation of the transistor Q52.

Next, the voltage of the capacitor C3, that is, the voltage applied to the load circuit 13 for operating the battery-powered electronic equipment is divided by a series circuit of a resistor R1, a variable resistor VR1, and a resistor R2. Is the difference voltage of the resistor R3
Is amplified by the operational amplifier 2 fed back by the capacitor C1. The purpose of the capacitor C1 is to increase the low-frequency gain to reduce the steady-state error, and to limit the high-frequency gain by the resistor R3 to prevent oscillation. Next, the output of the operational amplifier 2 is output from the comparator 7 to the triangular wave generation circuit 51.
Pulse width modulation (hereinafter referred to as PW
Abbreviated as M. ), And drives the transistor Q51 through the resistor R53.

Here, when the voltage of the battery 1 is lower than the load voltage across the capacitor C3, the transistor Q51 is PWM-driven with a duty corresponding to the voltage difference, and operates as a step-up switching power supply. Is higher than the load voltage across capacitor C3, the PWM duty is reduced, and capacitor C51
Is reduced, the base current of the transistor Q52 decreases, and the potential difference between the collector and the emitter of the transistor Q52 increases, thereby controlling the voltage. In addition, a switching power supply device is disclosed in
No. 1357 is also disclosed.

[0005]

However, in the conventional switching power supply as described above, when the voltage of the battery 1 is higher than the load voltage across the capacitor C3, the potential difference between the collector and the emitter of the transistor Q52 increases. As a result, the voltage is controlled, so that the efficiency is low. Further, in particular, there is a problem that the voltage from the operational amplifier 2 exceeds the voltage from the triangular wave generation circuit 51, the transistor Q51 continues to be turned on, and a large current flows through the coil L51a.

The present invention has been made to solve the above-mentioned conventional problems, and has a high efficiency switching power supply device regardless of whether the voltage of the battery 1 is lower or higher than the load voltage across the capacitor C3. It is an object of the present invention to provide a switching power supply device capable of preventing a large current from flowing through a coil.

[0007]

In order to solve the above-mentioned problems, a switching power supply according to a first aspect of the present invention comprises:
A boost switching circuit for boosting an input voltage;
A coil connected to the step-up switching circuit for storing and releasing energy; a capacitor for smoothing the output of the step-up switching element; an amplifier for comparing and amplifying a voltage of the capacitor with a reference voltage; A switching circuit that generates a slope and a rising slope, a triangular wave generating circuit that generates a triangular wave, and a comparator that compares the output of the amplifier with the triangular wave from the triangular wave generating device and drives the boost switching element. A switching power supply device having a pulse generation circuit for generating a pulse synchronized with the triangular wave generation circuit, wherein the output of the pulse generation circuit is configured to limit the duty of the step-up switching circuit.

A switching power supply according to a second aspect is characterized in that the pulse generation circuit is constituted by an edge detection circuit that detects an edge of a triangular wave and generates a pulse having a predetermined time width. A switching power supply device according to an aspect.

A switching power supply according to a third aspect is characterized in that the pulse generating circuit is constituted by a circuit that outputs a pulse synchronized with either a falling slope or a rising slope. It is a switching power supply device.

[0010]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Hereinafter, a switching power supply according to a first embodiment of the present invention will be described in detail with reference to the drawings. FIG. 1 is a block diagram of a switching power supply according to a first embodiment of the present invention, and FIG. 2 is a block diagram of a first triangular wave generating circuit 8 and a second triangular wave generating circuit 9.

In FIG. 1, the positive voltage of a battery 1 connected in parallel with an electrolytic capacitor C2 is connected to the drain of an N-channel MOS transistor Q1 as a first switching element, and its source is a diode D having an anode grounded.
1 and one end of a coil L1. The other end of the coil L1 is connected to a positive terminal of an electrolytic capacitor C3 connected in parallel to a load circuit 13 for operating a battery-powered electronic device. The positive terminal of the battery 1 is also connected to the positive terminal of the capacitor C3 via the coil L2 and the diode D2. From the connection point between the coil L2 and the anode of the diode D2, an N channel constituting a second switching element is formed. It is connected to the drain of MOS transistor Q2, and its source is grounded.

The transistor Q1, the coil L1, and the diode D1 are step-down switching power supplies (down converters).
The transistor Q2, the coil L2, and the diode D2 constitute a step-up switching power supply (upconverter) UC. As will be described later, when the transistor Q2 is off, a pulse signal S8 (FIG. 3 (g)) is sent to the transistor Q1, the step-down switching power supply DC is driven, and the current from the battery 1 is applied to the coil L1. It is stored, smoothed by the capacitor C3, and applied to the load circuit 13. The step-down switching power supply DC is driven when the voltage Vo of the battery 1 is lower than the voltage V applied to the load circuit 13.
It is when it is higher than L.

When the transistor Q1 is off,
The pulse signal S4 (FIG. 3 (c)) is sent to the transistor Q2, the step-up switching power supply UC is driven, the current from the battery 1 is accumulated in the coil L2, smoothed by the capacitor C3, and applied to the load circuit 13. Can be The boost switching power supply UC is driven when the voltage Vo of the battery 1 is
This is when the voltage is lower than the voltage VL applied to the load circuit 13.

A resistor R is connected in parallel with the electrolytic capacitor C3.
1. A series circuit of a variable resistor VR1 and a resistor R2 is connected, and a variable terminal of the variable resistor VR1 connects a series circuit of a capacitor C1 and a resistor R3 between an output terminal and a (−) input terminal; The (+) input terminal is connected to the (+) terminal of the reference voltage source 3. The output of operational amplifier 2 is 3
The first branch is connected to the (+) input terminal of the first comparator 6 which has input the output S1 of the first triangular wave generation circuit 8 to the (-) input terminal, and the second branch is the second triangular wave generation circuit. 9 is connected to the (+) input terminal of the second comparator 7 which has input to the (-) input terminal, and 3 is the output of the comparator 4 having the reference voltage source 5 connected to the (+) input terminal. −) Connected to input terminal. The output of the comparator 4 is input to the AND gate 11 together with the output of the first comparator 6, and the AND gate 1
1 is the transistor Q1 of the first switching element.
Connected to the gate. First triangular wave generation circuit 8
Has a pulse generation circuit 10 that outputs a pulse signal S6 in response to a trigger signal. The pulse signal S6 is input to an AND gate 12 together with the output of the second comparator 7, and
The output of the gate 12 is connected to the gate of the transistor Q2 of the second switching element.

The first triangular wave generating circuit 8 outputs a triangular wave S1 shown in FIG. The triangular wave S shown in FIG.
2 is output. The triangular waves S1 and S2 are vertically symmetrical waveforms at the voltage E2. Now, a case where the battery voltage Vo is higher than the load voltage VL will be described. First, when the load voltage VL rises and the voltage divided by the resistors R1, VR1, and R2 rises above the voltage of the reference voltage source 3, the output E5 (FIG. 3A) of the operational amplifier 2 falls. Therefore,
The voltage at the (+) input terminal of the comparator 6 also decreases,
Thus, the pulse width of the pulse signal S8 obtained by comparison with the triangular wave S1 becomes narrower and is output. When the pulse width of the pulse signal S8 is reduced, the period during which the transistor Q1 is turned on is shortened, the current supply from the battery 1 is reduced, and the load voltage VL is reduced. Next, the load voltage VL decreases, and R1, VR1, R2
Is lower than the voltage of the reference voltage source 3, the output E5 of the operational amplifier 2 (FIG. 3 (a)) becomes E2.
Higher in the lower range. Therefore, the voltage of the (+) input terminal of the comparator 6 also increases, and the comparator 6 outputs a triangular wave S1.
The pulse width of the pulse signal S8 obtained by comparison with the above is output with a larger width. By increasing the pulse width of the pulse signal S8, the period during which the transistor Q1 is turned on is lengthened, the supply of current from the battery 1 is increased, and the load voltage is increased. , The load voltage VL is maintained at a constant voltage. At this time, while E5 is added to the (+) input terminal of the comparator 7,
(-) The triangular wave S2 is applied to the input terminal, and since E5 <S2, the L level signal is output from the comparator 7, and the transistor Q2 is kept in the off state.

On the other hand, a case where the battery voltage Vo is lower than the load voltage VL will be described. First, when the load voltage VL decreases and the voltage divided by the resistors R1, VR1, and R2 drops below the voltage of the reference voltage source 3, the output E of the operational amplifier 2
4 (FIG. 3A) is higher. Therefore, the voltage of the (+) input terminal of the comparator 7 also increases, and the comparator 7 outputs the pulse signal S4 obtained by comparison with the triangular wave S2 with a wider pulse width. By increasing the pulse width of the pulse signal S4, the period during which the transistor Q2 is turned on is lengthened, the supply of current from the battery 1 is increased, and the load voltage VL is increased. next,
When the load voltage VL rises and the voltage divided by the resistors R1, VR1, and R2 rises above the voltage of the reference voltage source 3, the output E4 (FIG. 3A) of the operational amplifier 2 falls in a range higher than E2. . Therefore, the voltage of the (+) input terminal of the comparator 7 also decreases, and the comparator 7 outputs the pulse signal S4 obtained by comparison with the triangular wave S2 with a smaller pulse width. Since the pulse width of the pulse signal S4 is reduced, the period during which the transistor Q2 is turned on is shortened, the supply of current from the battery 1 is reduced, and the load voltage V
It acts to lower L, and the load voltage VL is kept at a constant voltage by such a negative feedback action. At this time, the comparator 4
The (−) input terminal has E4 added thereto, while the (+) input terminal has E2 applied from the reference voltage source 5 and E4> E2. Therefore, the L level signal is output from the comparator 4. Is output, and the transistor Q1 is kept off.

In FIG. 2, a current source 31 has a resistor R3
1 and R32 are connected in series to the ground, and a switch 35 composed of a transistor or the like is connected to the resistor 32 in parallel. The output of the rising edge detection circuit 38 for inputting the external synchronization clock Sc is input to AND gates 36 and 37, respectively. The connection point between the current source 31 and the resistor R31 is connected to the (-) terminal of the comparator 34, the output of the comparator 34 branches into three branches, one of which is the capacitor C31 of the serially connected current sources 32 and 33. The on / off of the current source 33 connected in parallel with the current source 33 is controlled, and the connection point of the current sources 32 and 33 is connected to the (+) input terminal of the comparator 34. The second output of the comparator 34 is an AND circuit 36
The switch 35 is controlled by the output of an AND gate 36, and the third output of the comparator 34 is connected to one input of an AND circuit 37 that generates a pulse signal S6 via a rise detection circuit 39. ing. From the connection point between the current sources 32 and 33, the first
The output S1 of the triangular wave generating circuit 8 of FIG.
34, the reference voltage source 42 is connected to the (+) input terminal, and the resistor R is connected to the (−) input terminal of the second triangular wave generation circuit 9.
33. The resistors R33 and R34 have the same value. The voltage value of the reference voltage source 42 is set to be substantially equal to (current value of the current source 31) × (R31 + R32). Rising edge detection circuit 39 and AN
The D gate 37 forms the pulse generation circuit 10.

Next, the operation of the first triangular wave generation circuit 8 and the second triangular wave generation circuit 9 will be described with reference to FIG. The rising edge detection circuit 38 is a circuit that normally generates an L level for a predetermined time when a rising edge of the external clock Sc is at H level. Similarly, the rising edge detection circuit 39 normally operates at the H level,
4 is a circuit that generates an L level for a certain period of time when a rising edge of the signal from 4 occurs.

The triangular wave S1 is generated by repeating forward charging and reverse charging of the capacitor C31. When the output of the comparator 34 is at L level, the current source 33 is off, and the current from the current source 32 causes the capacitor C3
1 is charged in the forward direction, and the voltage gradually increases. At this time, since the output of the AND gate 36 is at the L level, the switch 35 is off, and the (−) input terminal of the comparator 34 is (current value of the current source 31) × (R31 + R3
The voltage E2 of 2) is applied. The voltage of the capacitor C31 is input to the (+) input terminal of the comparator 34,
(-) The level of the input terminal (the current value of the current source 31)
When the voltage exceeds the voltage E2 of × (R31 + R32), the comparator 34
Becomes H level. Here, if there is no rising edge of the external clock Sc, since the output of the rising edge detection circuit 38 is at the H level, the output of the AND gate 36 is also at the H level, the switch 35 is turned on, and the (−) of the comparator 34 is turned off. ) Input terminal (current value of current source 31)
The voltage E1 of × (R31) is applied. Further, the output of the comparator 34 goes to the H level, and the current source 33 that generates a current value larger than the current value of the current source 32 is turned on, so that the capacitor C31 is charged in the reverse direction, and the voltage of the capacitor C31 gradually increases. Go down.

When the voltage drops below the voltage (E1) of (current value of current source 31) × (R31) which is the level of the (-) input terminal of comparator 34, the output of comparator 34 goes low and current source 33 Since the capacitor C31 is turned off, the capacitor C31 is charged in the forward direction again by the current from the current source 32. By repeating this operation, a triangular wave is generated, and the capacitor C
The same waveform as the terminal voltage change at 31 is output as the output S1 of the first triangular wave generation circuit 8 through the buffer 40.

The output of the buffer 40 is (current source 3
(Current value of 1) × (R31 + R32), the operational amplifier 4
1 and a waveform symmetrically inverted by R33 and R34 each having the same resistance value are output as the output S2 of the second triangular wave generation circuit 9.

When the comparator 34 changes from L level to H level, the rising edge detection circuit 39 generates a signal, and the pulse signal S 6 of the pulse generation circuit 10 is generated through the AND gate 37.

When the output of the comparator 34 is at the H level and the external synchronization clock Sc rises, an L level pulse is issued from the rising edge detection circuit 38 to turn off the switch 35 through the AND gate 36. , The (-) input terminal voltage of the comparator 34 rises, and the output of the comparator 34 is inverted to the L level, so that a triangular wave synchronized with the external synchronization clock Sc is obtained.

Next, the operation of the switching power supply device shown in FIG. 1 will be described with reference to the block diagram. First, when the voltage Vo of the battery 1 is higher than the load voltage VL across the capacitor C3 for smoothing the output of the first and second switching elements, the step-down switching power supply DC is driven and serves as a step-down switching power supply. Operate. In this operation, when the transistor Q1 is turned on, the battery 1
Current flows into the capacitor C3 through the transistor Q1 and the coil L1, and magnetic energy is accumulated in the coil 1. At this time, the current from the battery 1 is a diode D1
Does not flow to Next, when Q1 is turned off, the coil L
By releasing the energy stored in 1,
The current flows from the ground to the capacitor C3 through the diode D1 and the coil L1. Thereby, the capacitor C
The charge stored in 3, that is, the voltage between both ends is reduced. The voltage of the capacitor C3 is divided by the resistor R1, the resistor R2 and the variable resistor VR1, and the operational amplifier 2 in which the difference voltage between the divided voltage and the reference voltage source 3 is fed back by the resistor R3 and the capacitor C1. Amplified. Capacitor C
The purpose of 1 is to increase the low-frequency gain to reduce the steady-state error, and to prevent the high-frequency gain from being oscillated by being limited by the value of the resistor R3.

Next, the output E5 of the operational amplifier 2 is
Is compared with the triangular wave S1 output from the first triangular wave generation circuit 8 by the comparator 6, and the pulse signal S8
Is output. This pulse signal S8 is output from the AND gate 1
1 to drive the transistor Q1 by PWM. Here, the AND gate 11 is driven by a voltage boosted higher than the voltage of the battery 1, and when it is at the H level, a voltage high enough to turn on the transistor Q1 is supplied. As a result, the transistor Q1 has a duty ratio corresponding to the voltage difference between the voltage of the battery 1 and the voltage of the load circuit 13, and the transistor Q1
Driven to form a step-down switching power supply.

Next, the voltage Vo of the battery 1 is
When the load voltage VL across the terminals 3 is lower, when the transistor Q2 is turned on, a current flows from the battery 1 to the transistor Q2 through the coil L2, and magnetic energy is accumulated in the coil L2. At this time, the electric charge accumulated in the capacitor C3 is prevented from flowing backward by the diode D2, and is not discharged. Next, when the transistor Q2 is turned off, the drain voltage of the transistor Q2 rises due to the flyback of the coil L2, and the energy accumulated in the coil L2 while the transistor Q2 is on flows into the capacitor C3 through the diode D2.
The capacitor C3 is charged. The voltage of the capacitor C3 is divided by the resistor R1, the resistor R2 and the variable resistor VR1, and the voltage difference between the reference voltage source 3 and the differential voltage is amplified by the operational amplifier 2 fed back by the resistor R2 and the capacitor C1. Next, the output E4 of the operational amplifier 2 is compared by the comparator 7 with the triangular wave S2 output from the second triangular wave generation circuit 9,
The pulse signal S4 is output from the comparator 7. The pulse signal S4 is supplied to the transistor Q through the AND gate 12.
2 is driven.

Further, the AND gate 12 receives the pulse signal S6, which is generated by the pulse generation circuit 10 and has an L level in a section having a constant width, and forcibly turns off the transistor Q2 at the peak point of the triangular wave S2. As a result, the voltage E4 exceeds the voltage E3, so that the transistor Q2 is kept on and the duty is limited to prevent a large current from flowing to L2.

As described above, the voltage of the battery 1 and the load circuit 13
Transistor Q2 with a duty corresponding to the difference between
Are PWM-driven to form a step-up switching power supply. At this time, the output of the operational amplifier 2 is compared with the reference voltage source 5 by the comparator 4 and is higher than the reference voltage source 5, so that the comparator 4 outputs the L level and the output of the comparator 6 Stop at the AND gate 11 to turn off the transistor Q1.

FIG. 3 is a waveform diagram of each part of the apparatus. FIG.
In (a), S1 is the output waveform of the first triangular wave generation circuit 8, S2 is the output waveform of the second triangular wave generation circuit 9, and the broken lines in the waveforms S1 and S2 indicate the external synchronization clock S.
The waveform when c is not input, and the solid line is the waveform when the external synchronization clock Sc is input. FIG. 3B shows the waveform of the external synchronization clock Sc. E1 and E2 are threshold voltage levels for inverting the output of the first triangular wave generation circuit 8, E1 is a voltage value represented by (current value of current source 31) × (R31), and E2 is (current source value). 31 current value) ×
This is a voltage value represented by (R31 + R32). When an external clock is not input, a triangular wave is generated during this period.
The output of the second triangular wave generation circuit 9 generates the output waveform of the first triangular wave generation circuit 8 in S1 symmetrically with the voltage value of the reference voltage source 42 having substantially the same voltage value as the voltage of E2 as the axis of symmetry. When no external clock is input, a triangular wave is generated between the voltages E2 and E3. When the external clock Sc in FIG. 3B is input, the first triangular wave generation circuit 8 inverts the triangular wave on the level side of E1 at the rising edge to form a waveform like a solid line, and the second triangular wave Since the generation circuit 9 has a symmetrical waveform with the voltage E2 as the axis of symmetry, the waveform is also a solid line in FIG.

3 (c) and 3 (d) show waveforms during the operation of the step-up switching power supply. FIG. 3 (c) shows the output waveform of the comparator 7, and FIG. 3 (d) shows the output waveform of the comparator 6. It is. FIG.
(E) is an output waveform of the pulse generation circuit 10. The output level of the operational amplifier 2 is at the position E4 higher than the voltage value of E2, crosses the triangular wave of S2, and when the triangular wave S2 is lower than the level of E4, the output of the comparator 7 becomes H level. , And outputs the waveform of FIG. Since the triangular wave of S1 is always lower than the level of the voltage E4, the output of the comparator 6 is always at the H level as shown in FIG. Also, since the output of the rising edge detection circuit 39 and the output of the rising edge detection circuit 38 are input to the pulse generation circuit 10 through the AND gate 37, the output S6 of the AND gate 37 becomes as shown in FIG. Normally, the signal is at H level, and when either of the rising edge detection circuits 38 and 39 detects an edge, the signal becomes L level for a certain period of time. At this time, the output of the comparator 4 is compared with the reference voltage source 5 having the same voltage value as the voltage value of E2, and the L level is output, so the L level is input to the Q1 through the AND gate 11, and the Q1 is turned off. Figure 3
A signal obtained by ANDing (c) and (e) with the AND gate 12 is input to the transistor Q2, and the voltage of the battery 1 is boosted.

3 (f) and 3 (g) show waveforms when the step-down switching power supply operates, (f) shows the output waveform of the comparator 7, and (g) shows the output waveform of the comparator 6. Amplifier 2
Is at the position of E5 lower than the voltage value E2, and the triangular wave of S2 is always higher than the level of E5.
When the output of the comparator 7 is always at the L level as shown in FIG. 3 (f), the Q2 is turned off, the booster circuit is stopped, crosses the triangular wave of S1, and S1 is lower than the level of E5. Indicates that the output of the comparator 6 is at the H level,
(G), and the output of the comparator 4 becomes H level because the voltage of the reference voltage source 5 is higher, and
The gate 11 outputs the same signal as in FIG.
Since the gate 11 is driven by a voltage that is higher than the voltage of the battery 1, a high voltage is supplied to the transistor Q1 when it is at the H level, and the transistor Q1 is turned on during the H period, and the PWM is turned on.
Driven.

As described above, according to the present embodiment, the battery 1
The variable resistor VR is used for both the step-up operation in which the voltage of the battery 1 is lower than the load voltage and the step-down operation in which the voltage of the battery 1 is higher than the load voltage.
The output voltage can be freely and easily adjusted by changing 1 and, in any case, with high efficiency and
Amplifier 2 with filter characteristics fed back by R3 and C1
Is used as a step-up switching power supply and a step-down switching power supply, and operates in the range of two triangular wave levels. Therefore, a switching power supply that does not fluctuate in voltage when switching between the step-up switching power supply and the step-down switching power supply is used. It can be configured.

Next, a second embodiment of the present invention will be described. FIG. 4 is a circuit diagram of a switching power supply according to a second embodiment of the present invention. As shown in FIG. 4, one coil L21 is used for both a step-down switching power supply and a step-up switching power supply. That is, the coil L21 is disposed in place of the coil L1,
1 except that the transistor Q2 of the second switching element and the diode D2 are connected after that, and the comparator 4, the reference voltage source 5, and the AND gate 11 are not provided. The step-down switching power supply D
C is a transistor Q1, a diode D1, a coil L2
The boost switching power supply UC is composed of a transistor Q2, a diode D2, and a coil L21.

Now, a case where the battery voltage Vo is higher than the load voltage VL will be described. First, when the load voltage VL rises and the voltage divided by the resistors R1, VR1, and R2 rises above the voltage of the reference voltage source 3, the output E of the operational amplifier 2
5 (FIG. 3A) is lower. Accordingly, the voltage of the (+) input terminal of the comparator 6 also decreases, and the comparator 6 outputs a pulse signal S8 obtained by comparison with the triangular wave S1 with a smaller pulse width. When the pulse width of the pulse signal S8 is reduced, the period during which the transistor Q1 is turned on is shortened, the current supply from the battery 1 is reduced, and the load voltage VL is reduced. next,
When the load voltage VL decreases and the voltage divided by the resistors R1, VR1, and R2 drops below the voltage of the reference voltage source 3, the output E5 of the operational amplifier 2 (FIG. 3A) increases in a range lower than E2. . Accordingly, the voltage of the (+) input terminal of the comparator 6 also increases, and the comparator 6 outputs the pulse signal S8 obtained by comparison with the triangular wave S1 with a wider pulse width. By increasing the pulse width of the pulse signal S8, the period during which the transistor Q1 is turned on is lengthened, the supply of current from the battery 1 is increased, and the load voltage is increased. , The load voltage VL is maintained at a constant voltage. At this time, E5 is applied to the (+) input terminal of the comparator 7, while a triangular wave S2 is applied to the (-) input terminal, and E5 <S2
Therefore, an L level signal is output from the comparator 7, and the transistor Q2 is kept off.

On the other hand, a case where the battery voltage Vo is lower than the load voltage VL will be described. First, when the load voltage VL decreases and the voltage divided by the resistors R1, VR1, and R2 drops below the voltage of the reference voltage source 3, the output E of the operational amplifier 2
4 (FIG. 3 (a) is high. Therefore, the (+)
The voltage of the input terminal also increases, and the comparator 7 outputs a triangular wave S
2, the pulse width of the pulse signal S4 obtained from the comparison with the pulse signal S4 is increased. By increasing the pulse width of the pulse signal S4, the period during which the transistor Q2 is turned on becomes longer, and the supply of current from the battery 1 increases,
It acts to increase the load voltage VL. Next, when the load voltage VL rises and the voltage divided by the resistors R1, VR1 and R2 rises above the voltage of the reference voltage source 3, the output E4 of the operational amplifier 2 (FIG. 3A) is higher than E2. And lower. Therefore, the voltage of the (+) input terminal of the comparator 7 also decreases, and the comparator 7 outputs the pulse signal S4 obtained by comparison with the triangular wave S2 with a smaller pulse width. Since the pulse width of the pulse signal S4 is reduced, the period during which the transistor Q2 is turned on is shortened, the supply of current from the battery 1 is reduced, and the load voltage VL is reduced. By operation, the load voltage VL is maintained at a constant voltage. At this time, E4 is applied to the (+) input terminal of the comparator 6, while the triangular wave S1 is applied to the (-) input terminal, so that E4> E2
Therefore, an H level signal is output from the comparator 6, and the transistor Q1 is kept on.

That is, the feature of the second embodiment is that when the output level of the operational amplifier 2 is at the level E4 in FIG.
Since the output of the comparator 6 is at the H level (a voltage boosted higher than the voltage of the battery 1), the transistor Q1 is kept on and the current continues to flow through the coil L21 even while the transistor Q2 is being driven by PWM. ing. In the second embodiment, the efficiency is slightly reduced due to the internal resistance of the transistor Q1 even in the step-up power supply operation because the transistor Q1 is connected in series, but can be realized with a smaller number of parts than in the first embodiment. Also in this embodiment, the first triangular wave generating circuit 8 and the second triangular wave generating circuit 9 can employ the one shown in FIG.

Next, a third embodiment will be described.
FIG. 5 is a circuit diagram of a switching power supply device according to the third embodiment of the present invention. In FIG. 5, an N-channel MOS transistor Q3 is used instead of the diode D1 in FIG. 4, and an inverter 14 for driving the transistor Q3 is used. The drive signal of the transistor Q <b> 1 is input to the inverter 14. Therefore,
Transistors Q1 and Q3 perform operations that are mutually inverted. Further, in FIG. 5, an N-channel MOS transistor Q4 is used instead of the diode D2 in FIG. 4, and an inverter 15 for driving the transistor Q4 is used. Transistor Q2 is connected to inverter 15
Is input. Therefore, transistors Q2 and Q4 perform operations that are mutually inverted. Others
This is the same as the configuration in FIG.

Here, when the output level of the operational amplifier 2 is at the level E4 in FIG. 3, the output of the comparator 6 is at the H level (voltage boosted higher than the voltage of the battery 1). When Q1 is on, the drive signal is inverted by the inverter 14, so that Q3 is kept off. At this time, while Q2 is on and off and PWM-driven, Q4 is inverted and driven by inverter 15 and is off-on and PWM-driven to keep flowing current through L21.

The third embodiment is different from the second embodiment in that
Since the ON voltages of Q1 and Q2 are smaller than D1 and D2,
Efficiency is improved. In this embodiment, the driving of Q3 and Q4 is performed by simply adding an inverted signal to Q1 and Q2. However, in order to prevent Q1 and Q3 and Q2 and Q4 from being simultaneously turned on for a moment and flowing through current. May be provided with a timing circuit for simultaneously turning off.

Next, a fourth embodiment will be described.
FIG. 6 shows a fourth embodiment of the present invention, which is characterized in particular by a pulse generation circuit 10 ′ provided in the first triangular wave generation circuit 8. The pulse generation circuit 10 ′ includes an inverter 43, and an input thereof is connected to an output of the comparator 34. The pulse signal S6 '(FIG.
(H)) is output. In the above-described embodiment, the pulse generation circuit 10 has been described as an example of a so-called one-shot circuit in which an L level signal is generated for a predetermined time when an edge is detected. In this embodiment, the comparator 34 outputs an H level signal. 5 shows a circuit that outputs an L level during the period (while the output S1 of the first triangular wave generation circuit 8 is decreasing). Inverter 43
In the output waveform S6 ′, a signal of H level is generated during the rising period of the triangular wave S1, and a signal of L level is generated during the falling period. At this time, the signals S4 and S6 '
The ND signal is input to Q2, and the voltage of battery 1 is boosted. Since the falling period of the triangular wave S1 is sufficiently smaller than the rising period, the transistor Q2 is turned off during this falling period, and the step-up switching power supply UC is forcibly stopped.

Next, a fifth embodiment will be described.
FIG. 7 is a circuit diagram of a switching power supply device according to a fifth embodiment of the present invention. A starter circuit is added as compared with that of FIG. The starter circuit includes a drive power supply circuit DV and a start signal generation circuit ST. The driving power supply circuit DV includes a start switch 16, a holding switch 2
2. It is composed of a third triangular wave generation circuit 24, a control circuit 25, a coil L3, a transistor Q5, a diode D3, and a capacitor C4. The holding switch 22 is turned off when an L level signal is input and turned on when an H level signal is input. The start signal generation circuit ST includes a comparator 17 with hysteresis, a reference voltage source 18, resistors R4 and R5, a switch 19, an inverter 20, and an OR gate 21.
It consists of. The switch 19 connects the base of the transistor Q2 to the third triangular wave generation circuit 14 when the signal from the comparator 17 is at the L level, as shown by the solid line. The base is connected to the output of AND gate 12.

The operation of the starter circuit configured as described above will be described. When the start switch 16 is pressed, the third triangular wave generation circuit 24 starts oscillating, and the control circuit 25
Starts operating, and the switching operation of the transistor Q3 which repeats on / off is started. A boost operation is performed by the operation of the coil L3, the diode D3, and the capacitor C4, and a predetermined drive voltage Vc is generated in the capacitor C4. This drive voltage Vc is applied to a C-MOS gate (AND gate 11, switch 1) for driving MOS transistors Q1, Q2.
9, an OR gate 21, and an inverter 20) are supplied to these elements 11, 19, 21, and 20 as drive power.

When the switch 16 is depressed, the load voltage VL charged in the capacitor C3 is low.
This low load voltage VL is divided by resistors R4 and R5,
The reference voltage source 18 is compared with the comparator 17. When the load voltage VL is low, the comparator 17 outputs an L level signal. This L level signal is inverted by the inverter 20 and applied to the OR gate 21 to turn on the transistor Q1. At this time, an L level signal is also applied to the switch 19, and the switch 19 is set to the position shown by the solid line. Therefore, the switching signal from the third triangular wave generation circuit 24 repeatedly turns on / off the transistor Q2. The transistor Q2 starts PWM driving at the duty.

When the load voltage VL rises, the output of the comparator 17 becomes H level.
Switching to the D gate 12 side, the input of the OR gate 21 becomes L level, and the operation by the triangular wave signals from the first and second triangular wave generating circuits 8 and 9 is started as described above. Also, the H level signal from the comparator 17 keeps the switch 22 on and keeps the drive power supply circuit DV from stopping even when the start switch 16 is turned off.

According to this embodiment, since a MOS transistor requiring a high gate voltage can be used, a highly efficient switching power supply can be provided. That is, according to the present embodiment, the drive power supply circuit DV is activated first to generate a high gate voltage, and the step-down switching power supply DC and the step-up switching power supply UC M
Since the OS transistor can be operated, a highly efficient switching power supply device can be provided. Further, since the drive power supply circuit DV does not stop even when the start switch 16 is released, the step-down switching power supply DC and the step-up switching power supply UC can continue to operate.

As described above, according to each of the above-described embodiments, the amplifier as the filter amplifier is used as both the step-up switching power supply and the step-down switching power supply, and the output voltage of the filter amplifier is between two triangular waves. Automatically switches between step-up and step-down operation depending on where the battery voltage is, so even if the battery voltage is lower or higher than the load voltage, it is highly efficient and switches between step-up and step-down switching power supplies. In some cases, the operation is continuously switched without greatly changing the operating point of the filter amplifier, so that a switching power supply in which the output voltage does not fluctuate during the switching can be configured. Further, since the input voltage and the output voltage are not compared to switch between the step-up and step-down operations, the output voltage can be adjusted stably and easily.

In the description of the triangular wave generating circuit shown in FIG.
Although the voltage of the second triangular wave generating circuit 9 is synthesized by the output of the triangular wave generating circuit 8 described above, the voltage may be reversed or an external synchronous clock may be applied to the reverse of the example.

[0048]

As described above, according to the present invention, an amplifier having high efficiency and a filter characteristic even when the battery voltage Vo is lower or higher than the load voltage VL is used. Since it is also used as a switching power supply and operates in the range of two triangular wave levels, a switching power supply that does not fluctuate when switching between a step-up switching power supply and a step-down switching power supply can be configured. It has a high practical effect that can be performed continuously and easily by adjusting the vessel. In particular, even if the voltage from the operational amplifier 2 exceeds the voltage from the triangular wave generation circuit 9, the output of the pulse generation circuit is used to limit the duty of the boosting switching circuit. No large current flows through L21.

[Brief description of the drawings]

FIG. 1 is a block diagram of a switching power supply according to a first embodiment of the present invention.

FIG. 2 is a block diagram of a first triangular wave generation circuit 8 and a second triangular wave generation circuit 9 shown in FIG.

FIG. 3 is an output waveform diagram of each part of the device shown in FIGS. 1 and 2;

FIG. 4 is a block diagram of a switching power supply according to a second embodiment of the present invention.

FIG. 5 is a block diagram of a switching power supply according to a third embodiment of the present invention.

FIG. 6 is a block diagram of a switching power supply according to a fourth embodiment of the present invention.

FIG. 7 is a block diagram of a switching power supply according to a fifth embodiment of the present invention.

FIG. 8 is a block diagram of a conventional switching power supply device.

[Explanation of symbols]

 Reference Signs List 1 battery 2 operational amplifier 3,5 reference voltage source 4 comparator 6 first comparator 7 second comparator 8 first triangular wave generating circuit 9 second triangular wave generating circuit 10 pulse generating circuit 11,12 AND gate 13 Load circuit C1 Capacitor C2, C3 Electrolytic capacitor D1, D2 Diode L1, L2 Coil Q1, Q2 Transistor R1, R2, R3 Resistor VR1 Variable resistor

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[Procedure amendment]

[Submission date] April 30, 1998

[Procedure amendment 1]

[Document name to be amended] Statement

[Correction target item name] 0005

[Correction method] Change

[Correction contents]

[0005]

However, in the above-mentioned conventional switching power supply, when the voltage of the battery 1 is higher than the load voltage across the capacitor C3, the potential difference between the collector and the emitter of the transistor Q52 increases. As a result, the voltage is limited, so that the efficiency is low. Further, in particular, there is a problem that the voltage from the operational amplifier 2 exceeds the voltage from the triangular wave generation circuit 51, the transistor Q51 continues to be turned on, and a large current flows through the coil L51a. In addition, the conventional switching power supply as described above has a problem that when an external trigger is applied to a triangular wave, the maximum duty changes.
In particular, when used in the step-up / step-down switching power supply shown in the embodiment of the present invention, the duty becomes 100% depending on the external trigger frequency, and there is a problem that the duty is not useful. The present invention has been made in view of the above-described conventional problems, and has been made with an object to provide a switching power supply device in which a maximum duty is hardly changed by an external trigger frequency even when an external trigger is applied to a buck-boost switching power supply. is there.

Claims (3)

[Claims] A step-up switching circuit for stepping up an input voltage, a coil connected to the step-up switching circuit for storing and releasing energy, and a capacitor for smoothing an output of the step-up switching element.
An amplifier for amplifying the voltage of the capacitor by comparing it with a reference voltage; a switching circuit for generating a falling slope and a rising slope; a triangular wave generating circuit for generating a triangular wave; and an output of the amplifier and the triangular wave generating device. A comparator for driving the step-up switching element by comparing the triangular wave with a triangular wave, and a pulse generating circuit for generating a pulse synchronized with the triangular wave generating circuit. A switching power supply device configured to add restrictions. 2. The switching power supply device according to claim 1, wherein said pulse generation circuit comprises an edge detection circuit for detecting an edge of a triangular wave and generating a pulse having a predetermined time width. 3. The switching power supply device according to claim 1, wherein the pulse generation circuit includes a circuit that outputs a pulse synchronized with one of a falling slope and a rising slope.