JPH0670672B2 - Radar equipment - Google Patents
Radar equipmentInfo
- Publication number
- JPH0670672B2 JPH0670672B2 JP5876689A JP5876689A JPH0670672B2 JP H0670672 B2 JPH0670672 B2 JP H0670672B2 JP 5876689 A JP5876689 A JP 5876689A JP 5876689 A JP5876689 A JP 5876689A JP H0670672 B2 JPH0670672 B2 JP H0670672B2
- Authority
- JP
- Japan
- Prior art keywords
- coho
- signal
- stalo
- frequency
- output
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Landscapes
- Radar Systems Or Details Thereof (AREA)
Description
【発明の詳細な説明】 〔産業上の利用分野〕 この発明はバイスタテックあるいはマルチスタテックレ
ーダ等のレーダ装置に関し、特に受信局におけるクラッ
タ除去に関するものである。The present invention relates to a radar device such as a bistatic or multistatic radar, and more particularly to clutter removal in a receiving station.
第３図は従来の一般的なバイスタテックレーダの構成を
示すブロック図、第４図は送信局−受信局間の各種反射
波を説明するための図、第５図は受信局における受信波
のドプラ周波数軸上の説明図である。FIG. 3 is a block diagram showing the configuration of a conventional general Bistatec radar, FIG. 4 is a diagram for explaining various reflected waves between a transmitting station and a receiving station, and FIG. 5 is a receiving wave at the receiving station. 2 is an explanatory diagram on the Doppler frequency axis of FIG.
なお、これらの類似例としてはメリル・スコーニック著
「イントロダクション トゥ レーダシステム」（マグ
ローヒル インターナショナル ブックカンパニー,553
頁）（「Introduction To Radar System, by Merrill
Skolnik, Mcgraw Hill International Book Company,
p.553」）に示されるものがある。As a similar example to these, "Introduction to Radar System" by Merrill Sconic (Maglow Hill International Book Company, 553)
Page) ("Introduction To Radar System, by Merrill
Skolnik, Mcgraw Hill International Book Company,
p.553 ”).
第３図において１はバイスタティックレーダにおける送
信局であり、２は比較的低い周波数の信号を発生する第
１のコヒーレントオシレータ（COHO:Coherent Oscillat
or）、３は比較的高い周波数の信号を発生する第１のス
テーブルローカルオシレータ（STALO:Stable Local Osc
illator）、４は上記両者の信号を混合する第１のミキ
サ、５は送信信号を増幅する電力増幅器、６は送信波を
空間に放射する送信アンテナである。また、７はバイス
タティックレーダにおける受信局であり、８は目標等か
らの反射信号を受信する受信アンテナ、９は受信波を増
幅する前置増幅器、10は前置増幅器９で増幅された受信
波と送信局側からケーブル等で送られてくるSTALO信号
を混合し受信波の周波数をCOHO信号の周波数帯に変換す
る第２のミキサ、12は第２のミキサ10の出力を増幅する
IF（中間周波数）増幅器、13は送信局側からケーブル等
で送られてくるCOHO信号を基準として受信信号をビデオ
帯に変換する位相検波器、18はクラッタ等の不要信号を
除去し航空機等の移動目標の信号を取り出すMTI（Movin
g Target Indicator:移動目標表示）フィルタである。In FIG. 3, 1 is a transmitting station in the bistatic radar, and 2 is a first coherent oscillator (COHO: Coherent Oscillat) that generates a signal of a relatively low frequency.
or 3 is a first stable local oscillator (STALO) that generates a signal of a relatively high frequency.
illator), 4 is a first mixer for mixing both signals, 5 is a power amplifier for amplifying a transmission signal, and 6 is a transmission antenna for radiating a transmission wave into space. Further, 7 is a receiving station in the bistatic radar, 8 is a receiving antenna for receiving a reflected signal from a target or the like, 9 is a preamplifier for amplifying a received wave, and 10 is a received wave amplified by the preamplifier 9. And a STALO signal sent from the transmitting station via a cable or the like to mix the frequency of the received wave into the frequency band of the COHO signal, and the second mixer 12 amplifies the output of the second mixer 10.
IF (intermediate frequency) amplifier, 13 is a phase detector that converts the received signal to the video band based on the COHO signal sent from the transmitting station via a cable, etc. 18 is an unnecessary signal such as clutter that removes unnecessary signals such as aircraft MTI (Movin
g Target Indicator: A moving target display filter.
次の動作について説明する。第３図において、第１図の
ミキサ４にて得られた送信波は電力増幅器５、送信アン
テナ６を経て空間に放射される。The following operation will be described. In FIG. 3, the transmission wave obtained by the mixer 4 in FIG. 1 is radiated into space through the power amplifier 5 and the transmission antenna 6.
放射された送信波は第４図に示すごとく、航空機，クラ
ッチ等にて反射され、受信局に到達する。なお、説明を
簡単にするため第４図に示すごとく、送信局側のアンテ
ナ６は無指向性アンテナとし、受信局側のアンテナ８は
指向性アンテナとした。As shown in FIG. 4, the radiated transmitted wave is reflected by the aircraft, clutch, etc., and reaches the receiving station. For simplification of explanation, as shown in FIG. 4, the transmitting station side antenna 6 is an omnidirectional antenna, and the receiving station side antenna 8 is a directional antenna.
第３図において、受信局７に到達した上記受信信号はま
ず受信アンテナ８に入力され、前置増幅器９で増幅さ
れ、第２のミキサ10に入力される。第２のミキサ10には
送信局１よりケーブル等で導かれたSTALO信号が加えら
れている。よって受信信号はここでCOHO信号の周波数帯
に変換される。本信号はさらにIF増幅器12にて増幅さ
れ、位相検波器13に入力される。位相検波器13には送信
局１よりケーブル等で導かれたCOHO信号が加えられてお
り、受信信号はビデオ帯に変換される。In FIG. 3, the received signal reaching the receiving station 7 is first input to the receiving antenna 8, amplified by the preamplifier 9, and input to the second mixer 10. To the second mixer 10, the STALO signal guided by the cable from the transmitting station 1 is added. Therefore, the received signal is converted into the frequency band of the COHO signal here. This signal is further amplified by the IF amplifier 12 and input to the phase detector 13. A COHO signal guided by a cable or the like from the transmitting station 1 is added to the phase detector 13, and the received signal is converted into a video band.
第５図は各受信信号の位相検波器13出力におけるドプラ
周波数軸の様子を示す。図に示すごとくドプラ偏移の差
によりクラッタと航空器からの反射信号は周波数軸上に
て分離される。よって第５図に示すMTIフィルタ特性を
有するMTIフィルタ18により移動目標のみを取り出すこ
とができる。FIG. 5 shows the state of the Doppler frequency axis at the output of the phase detector 13 for each received signal. As shown in the figure, the reflected signals from the clutter and the aircraft are separated on the frequency axis due to the difference in the Doppler shift. Therefore, only the moving target can be extracted by the MTI filter 18 having the MTI filter characteristic shown in FIG.
従来のレーダ装置は以上のように構成されており、受信
局におけるSTALO及びCOHO信号は送信局側と同一のもの
を使用しているためケーブル又は他の手段にて両信号を
導く必要があった。The conventional radar device is configured as above, and since the STALO and COHO signals at the receiving station are the same as those at the transmitting station side, it was necessary to guide both signals with a cable or other means. .
この発明は上記のような問題点を解消するためになされ
たもので、STALO及びCOHO信号を送信局より導かれなく
とも所要の性能を有するレーダ装置を得ることを目的と
する。The present invention has been made to solve the above problems, and an object of the present invention is to obtain a radar device having the required performance even if the STALO and COHO signals are not guided by the transmitting station.
この発明に係るレーダ装置は、受信局側に送信局とは独
立したSTALO及びCOHOを設け、かつ両局間のSTALO及びCO
HOの周波数変動差を送信局から受信局への直接波受信時
のFFTフィルタの出力フィルタより検出し、その結果を
用いFFTフィルタの各出力を選択して、移動目標のみを
取り出すようにしたものである。The radar device according to the present invention is provided with STALO and COHO independent from the transmitting station on the receiving station side, and STALO and COHO between the two stations.
The difference in frequency fluctuation of HO is detected from the output filter of the FFT filter when the direct wave is received from the transmitting station to the receiving station, and each output of the FFT filter is selected using the result so that only the moving target is extracted. Is.
この発明においては、受信局側に送信局とは独立したST
ALO及びCOHOを設けるとともに、両局間のSTALO及びCOHO
信号の周波数変動差を等価的に補償するようにしたか
ら、STALO及びCOHO信号を送信局より導びかなくとも所
要の性能を有するレーダ装置を得ることができる。According to the present invention, the receiving station side has an ST independent from the transmitting station.
ALO and COHO are established, and STALO and COHO between both stations
Since the difference in the frequency variation of the signals is compensated equivalently, it is possible to obtain the radar device having the required performance without guiding the STALO and COHO signals from the transmitting station.
以下、この発明の一実施例を図について説明する。 An embodiment of the present invention will be described below with reference to the drawings.
第１図は本発明の一実施例によるレーダ装置の構成を示
すブロック図であり、図において、11及び14は送信局側
とは独立したSTALO信号及びCOHO信号を発生する第２のS
TALO及び第２のCOHOである。また、15はFFT（Fast Four
ier Transform:高速フーリエ変換）方式にて多数のフィ
ルタ配列を形成するFFTフィルタ、16はFFTフィルタ15の
出力とアンテナ方位角の情報より両局間のSTALO及びCOH
O信号の周波数偏移差を検出する周波数偏移検出器、17
は周波数偏移検出器16の結果に基づきFFTフィルタ15の
出力を選択する選択回路である。その他従来装置と同一
符号は同一又は相当部分である。また第２図はFFTフィ
ルタ15のフィルタ配列と受信信号のドプラ周波数軸上の
説明図である。FIG. 1 is a block diagram showing a configuration of a radar device according to an embodiment of the present invention. In the figure, 11 and 14 are second S for generating a STALO signal and a COHO signal independent of the transmitting station side.
They are TALO and the second COHO. In addition, 15 is FFT (Fast Four
FFT filter that forms a large number of filter arrays by ier Transform (fast Fourier transform) method, 16 is STALO and COH between both stations based on the output of the FFT filter 15 and the information of the antenna azimuth angle.
Frequency deviation detector for detecting frequency deviation difference of O signal, 17
Is a selection circuit that selects the output of the FFT filter 15 based on the result of the frequency shift detector 16. Other reference numerals that are the same as those of the conventional device are the same or corresponding parts. FIG. 2 is an explanatory diagram on the Doppler frequency axis of the received signal and the filter array of the FFT filter 15.
次に動作について説明する。各局のSTALO3,11及びCOHO
2,14は同一設計のものを用いるが、両者間には次に周波
数差が生じ、またこれらの差は一般的に時間と共に変動
する。Next, the operation will be described. STALO 3,11 and COHO of each station
Although 2 and 14 have the same design, a frequency difference occurs next between the two, and these differences generally fluctuate with time.
Δｓ＝s1−s1 s2；送信局のSTALO信号周波数s2 ；受信局のSTALO信号周波数ｓ ；両局間のSTALO信号周波数差 Δｃ＝c1−c2 c1；送信局のCOHO信号周波数c2 ；受信局のCOHO信号周波数ｃ ；両局間のCOHO信号周波数差 但し通常COHO信号の周波数はSTALO信号の周波数より１
桁以上低いためΔｃ＜＜Δｓである。Δ s = s1 − s1 s2 ; STALO signal frequency s2 of the transmitting station; STALO signal frequency s of the receiving station; STALO signal frequency difference between both stations Δ c = c1 − c2 c1 ; COHO signal frequency of the transmitting station c2 ; receiving station COHO signal frequency c ; COHO signal frequency difference between both stations However, the frequency of the COHO signal is usually 1 than the frequency of the STALO signal.
Since it is lower than the order of magnitude, Δ c << Δ s .
よって移送検波器13の出力信号の周波数はΔ（＝Δ
ｓ＋Δｃ）だけずれており，直接波又はクラッタ及び
航空機のドプラ周波数は第２図のごとくなる。Therefore, the frequency of the output signal of the transfer detector 13 is Δ (= Δ
s + Δ c ) and the direct wave or clutter and aircraft Doppler frequencies are as shown in FIG.
FFTフィルタ15のフィルタは第２図のごとく配列されて
おり、その出力は周波数偏移検出器16に加えられてお
り、受信アンテナ８が送信局方向を向いた時点（つまり
直接波の受信）でどのフィルタより信号が出力されたか
を検出する。つまり、該当するフィルタの周波数が上記
周波数偏移Δとなる。尚受信アンテナ８が送信局側を
向く時点はアンテナ方位角により知る事が出来る。The filters of the FFT filter 15 are arranged as shown in FIG. 2, the output of which is applied to the frequency deviation detector 16, and at the time when the receiving antenna 8 faces the transmitting station (that is, the reception of the direct wave). Detect which filter outputs the signal. That is, the frequency of the corresponding filter becomes the frequency deviation Δ. The time when the receiving antenna 8 faces the transmitting station can be known from the antenna azimuth angle.
以上にて、Δが判明した故、選択回路17にてFFTフィ
ルタ15の出力中、Δ付近のフィルタ出力を除いた信号
のみ取り出すこれにより、クラッタ等は除去され、移動
目標のみ取り出す事ができる。As described above, since Δ has been found, the output of the FFT filter 15 is extracted by the selection circuit 17, and only the signal excluding the filter output in the vicinity of Δ is extracted, whereby clutter and the like are removed, and only the moving target can be extracted.
但し、クラッタの周波数スペクトラムは直接波より拡が
っているため（従来の方式と同様）この分余分にΔ付
近のフィルタ出力を除去する必要がある。However, since the frequency spectrum of the clutter is wider than the direct wave (similar to the conventional method), it is necessary to additionally remove the filter output near Δ.
また、Δは時間と共に変化するため、受信アンテナ８
が送信局を向くたびに、つまりアンテナ１回転毎に上記
Δの検出を行う。Further, since Δ changes with time, the receiving antenna 8
Detects the above Δ each time it faces the transmitting station, that is, every time the antenna rotates once.
なお、上記実施例ではΔの判定に直接波を用いたが、
地上クラッタの方向はあらかじめ判明しているので地上
クラッタからの反射波を用いることも可能である。Although the direct wave was used to determine Δ in the above embodiment,
Since the direction of the ground clutter is known in advance, it is possible to use the reflected wave from the ground clutter.
また、上記実施例では、受信局を１個としたが、複数の
場合つまりマルチスタティックレーダにおいても本発明
を適用することが可能である。Further, in the above embodiment, the number of receiving stations is one, but the present invention can be applied to a plurality of receiving stations, that is, a multi-static radar.
以上のように、この発明によれば、受信局側に送信局と
は独立したSTALO及びCOHOを設けるとともに、両局間のS
TALO及びCOHO信号の周波数変動差を等価的に補償する構
成としたから、送信局から受信局へのSTALO及びCOHO信
号のケーブル等による接続を不要とすることができる効
果がある。As described above, according to the present invention, the receiving station side is provided with STALO and COHO independent of the transmitting station, and S
Since the configuration is such that the difference in frequency fluctuation between the TALO and COHO signals is equivalently compensated, there is an effect that the connection of the STALO and COHO signals from the transmitting station to the receiving station by a cable or the like is unnecessary.
第１図はこの発明の一実施例によるレーダ装置の構成を
示すブロック図、第２図は第１図の実施例における動作
の説明をするための図、第３図は従来のレーダ装置の構
成を示すブロック図、第４図はバイスタテックレーダの
説明図、第５図は従来のレーダ装置における動作を説明
するための図である。 １は受信局、２は第１のCOHO、３は第１のSTALO、４は
第１のミキサ、５は電力増幅器、６は送信アンテナ、７
は受信局、８は前置増幅器、９は第２のミキサ、10は第
２のSTALO、11はIF増幅器、12は位相検波器、13は位相
検波器、14は第２のCOHO、15はFFTフィルタ、16は周波
数偏移検出器、17は選択回路、18はMTIフィルタであ
る。 なお図中同一符号は同一又は相当部分を示す。FIG. 1 is a block diagram showing the structure of a radar device according to an embodiment of the present invention, FIG. 2 is a diagram for explaining the operation in the embodiment of FIG. 1, and FIG. 3 is a structure of a conventional radar device. FIG. 4 is a block diagram showing the above, FIG. 4 is an explanatory diagram of a bystatic radar, and FIG. 5 is a diagram for explaining the operation of a conventional radar device. 1 is a receiving station, 2 is a first COHO, 3 is a first STALO, 4 is a first mixer, 5 is a power amplifier, 6 is a transmitting antenna, 7
Is a receiving station, 8 is a preamplifier, 9 is a second mixer, 10 is a second STALO, 11 is an IF amplifier, 12 is a phase detector, 13 is a phase detector, 14 is a second COHO, and 15 is a FFT filter, 16 is a frequency shift detector, 17 is a selection circuit, and 18 is an MTI filter. The same reference numerals in the drawings indicate the same or corresponding parts.
Claims (1)
ステーブルローカルオシレータとを有し、上記第１のコ
ヒーレントオシレータが出力するCOHO信号と第１のステ
ーブルローカルオシレータが出力するSTALO信号とを混
合して送信する送信局と、 第２のコヒーレントオシレータ及び第２のステーブルロ
ーカルオシレータと、通過周波数帯域が少しずつずれた
複数のフィルタからなるドプラフィルタバンクと、アン
テナの方位角を受け特定方向の受信信号の上記FFT出力
より両局間のSTALO及びCOHO信号の周波数偏移を検出す
る周波数偏移検出器と、該周波数偏移検出器の出力に基
づいて上記ドプラフィルタバンクの出力を制御選択して
クラッタ除去を行なう選択回路とを有する、単数または
複数の受信局とから構成されることを特徴とするレーダ
装置。1. A first coherent oscillator and a first stable local oscillator, wherein a COHO signal output by the first coherent oscillator and a STALO signal output by the first stable local oscillator are mixed. Transmitting station, a second coherent oscillator and a second stable local oscillator, a Doppler filter bank consisting of a plurality of filters whose pass frequency bands are slightly shifted, and an azimuth angle of the antenna A frequency shift detector that detects the frequency shift of the STALO and COHO signals between the two stations from the FFT output of the received signal, and controls and selects the output of the Doppler filter bank based on the output of the frequency shift detector. Radar device comprising a single or a plurality of receiving stations having a selecting circuit for removing clutter by means of Place
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP5876689A JPH0670672B2 (en) | 1989-03-10 | 1989-03-10 | Radar equipment |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP5876689A JPH0670672B2 (en) | 1989-03-10 | 1989-03-10 | Radar equipment |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH02236480A JPH02236480A (en) | 1990-09-19 |
| JPH0670672B2 true JPH0670672B2 (en) | 1994-09-07 |
Family
ID=13093669
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP5876689A Expired - Fee Related JPH0670672B2 (en) | 1989-03-10 | 1989-03-10 | Radar equipment |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0670672B2 (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP4982966B2 (en) * | 2005-05-18 | 2012-07-25 | ブラザー工業株式会社 | Wireless tag detection system |
| JP6103951B2 (en) * | 2013-01-22 | 2017-03-29 | 三菱電機株式会社 | Radar apparatus and radar signal receiving method |
-
1989
- 1989-03-10 JP JP5876689A patent/JPH0670672B2/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| JPH02236480A (en) | 1990-09-19 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US4388622A (en) | Double sideband linear frequency modulation system for radar applications | |
| US7791530B2 (en) | Time duplex apparatus and method for radar sensor front-ends | |
| JP3498624B2 (en) | Radar equipment | |
| EP2584373B1 (en) | Radar device | |
| US4054879A (en) | Dual-frequency, remote ocean-wave spectrometer | |
| US7821443B2 (en) | Dual mode radar methods and systems | |
| US5323162A (en) | Synthetic aperture radar system | |
| US4914441A (en) | Method of processing in a pulse doppler radar | |
| US4885590A (en) | Blind speed elimination for dual displaced phase center antenna radar processor mounted on a moving platform | |
| JPH0727021B2 (en) | Synthetic aperture radar device | |
| US3924236A (en) | Surveillance radar with synthetic array scan for improved angle determination | |
| EP0928427B1 (en) | Radar systems | |
| CN104777467B (en) | Object detection method based on frequency scan antenna | |
| Almorox-Gonzalez et al. | Portable high resolution LFM-CW radar sensor in millimeter-wave band | |
| US3018477A (en) | Electromagnetic detector devices | |
| US4338603A (en) | Self adaptive correlation radar | |
| JPH0670672B2 (en) | Radar equipment | |
| KR20060037777A (en) | Apparatus for removing leakage signal of fmcw radar | |
| US3212087A (en) | Range detection system | |
| JPS6119949B2 (en) | ||
| JP3500629B2 (en) | DBF radar device | |
| US3882500A (en) | System for the automatic tracking of a moving target | |
| JPH03218486A (en) | Pulse doppler radar equipment | |
| JPS61284685A (en) | Radar equipment | |
| JP3303862B2 (en) | Pulse compression radar device |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| LAPS | Cancellation because of no payment of annual fees |