JPH0661894A - Interference wave elimination device - Google Patents
Interference wave elimination deviceInfo
- Publication number
- JPH0661894A JPH0661894A JP21587892A JP21587892A JPH0661894A JP H0661894 A JPH0661894 A JP H0661894A JP 21587892 A JP21587892 A JP 21587892A JP 21587892 A JP21587892 A JP 21587892A JP H0661894 A JPH0661894 A JP H0661894A
- Authority
- JP
- Japan
- Prior art keywords
- output
- interference wave
- polarization
- antenna
- interference
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Landscapes
- Filters That Use Time-Delay Elements (AREA)
- Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
- Radio Transmission System (AREA)
Abstract
Description
【０００１】[0001]
【産業上の利用分野】本発明は干渉波除去装置に関し、
特に偏波ダイバーシティを用いるマルチパスフェージン
グ回線においてＤ／Ｕ（希望波対干渉波比）がマイナス
となるような強度な干渉波が存在した場合の広帯域干渉
波の除去およびフェージングによる波形歪の適応等化を
行なう干渉波除去装置に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an interference wave removing device,
In particular, in a multipath fading line that uses polarization diversity, if there is a strong interference wave such that the D / U (desired wave to interference wave ratio) becomes negative, removal of wideband interference wave and adaptation of waveform distortion due to fading, etc. The present invention relates to an interference wave removing device for converting a signal.
【０００２】[0002]
【従来の技術】従来、ＰＳＫやＱＡＭ変調波を用いたデ
ィジタルマイクロ波回線に対してＦＭ回線による干渉
や、隣接チャンネルからの干渉あるいは妨害波などが問
題となることがある。特にディジタル伝送速度が高速の
場合、ＦＭ干渉波は狭帯域干渉波と見なせるが、それ以
外の干渉波は広帯域の場合がある。また強度のマルチパ
スフェージング回線においてはダイバーシティ方式や適
応等化技術が不可欠で、見通し外通信のように伝搬距離
が大きな回線では整合フィルタ（ＭＦ）と判定帰還形等
化器（ＤＦＥ）を備える適応受信機が必要となる。また
見通し外通信方式での受信信号レベルは低い為、干渉波
レベルの方が高くなりやすい。このような強度の広帯域
干渉波を除去するにはダイバーシティブランチ（複数の
ダイバーシティ信号）間での干渉波どうしを逆相合成す
るパワー・インバージョン・アダプティブ・アレイ方式
がよく用いられている。この技術に関してはコンプトン
が“ザパワー・インバージョン・アダプティブ・アレ
イ：コンセプト アンド パフォーマンス”（アイ・イ
ー・イー トランズアクション オン エアロスペース
アンド エレクトロニク システムズ ヴォル エーイ
ーエス １５ ナンバー６ １９７９年１１月）として
発表している。2. Description of the Related Art Conventionally, an interference due to an FM line, an interference from an adjacent channel or an interfering wave may be a problem with respect to a digital microwave line using PSK or QAM modulated waves. Particularly when the digital transmission speed is high, the FM interference wave can be regarded as a narrow band interference wave, but other interference waves may be in a wide band. In addition, diversity systems and adaptive equalization techniques are indispensable for strong multipath fading lines, and for lines with a large propagation distance such as non-line-of-sight communication, equipped with a matched filter (MF) and decision feedback equalizer (DFE). A receiver is required. Further, since the received signal level in the non-line-of-sight communication method is low, the interference wave level tends to be higher. In order to remove the broadband interference wave having such an intensity, a power inversion adaptive array system is often used in which interference waves between diversity branches (a plurality of diversity signals) are combined in anti-phase. This technology was announced by Compton as "The Power Inversion Adaptive Array: Concept and Performance" (Aye E Transaction on Aerospace and Electronic Systems Vol AES 15 No. 6 November 1979). There is.
【０００３】図３にマルチパスフェージング環境下での
広帯域干渉波の除去についてパワー・インバージョン・
アダプティブ・アレイを用いた従来技術の受信機の構成
図を示す。この偏波ダイバーシティ方式の受信機は、図
示されない偏波ダイバーシティ信号を受けるアンテナ，
Ｖ（垂直）およびＨ（水平）偏波信号を受信する二つの
受信回路から、入力端１および２にそれぞれダイバーシ
ティ信号を入力し、出力端３から判定データを出力して
いる。この受信機において、１１２と１１３は乗算器、
１１６は加算器、１１７は減算器、１１８と１１９はＡ
ＧＣ増幅器、１１４と１１５は相関器、１１０と１１１
はＡＧＣ増幅器、１２０は切替器（ＳＷ）、３１１は等
化器である。FIG. 3 shows a power inversion method for removing a wideband interference wave in a multipath fading environment.
FIG. 1 shows a block diagram of a prior art receiver using an adaptive array. This polarization diversity receiver is an antenna that receives a polarization diversity signal (not shown),
From two receiving circuits that receive V (vertical) and H (horizontal) polarized signals, diversity signals are input to input terminals 1 and 2, respectively, and determination data is output from output terminal 3. In this receiver, 112 and 113 are multipliers,
116 is an adder, 117 is a subtractor, 118 and 119 are A
GC amplifiers, 114 and 115 are correlators, 110 and 111
Is an AGC amplifier, 120 is a switch (SW), and 311 is an equalizer.
【０００４】各ダイバーシティ信号（入力端１，２に入
力される中間周波数またはベースバンド信号である信号
Ａ，Ｂ）は、ＡＧＣ増幅器１１０と１１１によりフェー
ジングによるレベル変動が除かれた後、乗算器１１２と
１１３に通される。乗算器１１２と１１３では相関器１
１４および１１５からの複素タップ係数がそれぞれ乗じ
られる。これらのタップ係数は、ＡＧＣ増幅器１１０と
１１１出力とのダイバーシティ合成後のＡＧＣ増幅器１
１８出力との相関値である。これらの相関値は乗算器１
１２と１１３の入力信号に対する伝達係数の複素共約と
なっており、乗算器１１２と１１３の出力は、位相に関
して互いに同相に、振幅に関しては入力の２乗になる。
従って乗算器１１２出力と１１３出力を加算器１１６で
合成することにより最大比合成が行われる。干渉波が存
在しない時、切替器１２０はＡＧＣ増幅器１１８出力の
最大比合成ルートを選択出力し、等化器（ＥＱＬ）３１
１に受信信号を供給し、等化器３１１はマルチパスフェ
ージングによる波形歪を除去した判定データを出力端子
３に出力する。Each of the diversity signals (intermediate frequency or baseband signals A and B input to the input terminals 1 and 2) is subjected to fading-level level fluctuation removal by AGC amplifiers 110 and 111, and then a multiplier 112. And 113. In the multipliers 112 and 113, the correlator 1
The complex tap coefficients from 14 and 115 are multiplied respectively. These tap coefficients are used for the AGC amplifier 1 after diversity combination of the outputs of the AGC amplifiers 110 and 111.
It is a correlation value with 18 outputs. These correlation values are multiplied by the multiplier 1
The transfer coefficients of the input signals of 12 and 113 are the complex co-reduction, and the outputs of the multipliers 112 and 113 are in phase with each other and the square of the input with respect to amplitude.
Therefore, the maximum ratio combination is performed by combining the outputs of the multipliers 112 and 113 with the adder 116. When there is no interference wave, the switch 120 selects and outputs the maximum ratio combining route of the output of the AGC amplifier 118, and the equalizer (EQL) 31
The received signal is supplied to 1, and the equalizer 311 outputs the determination data from which the waveform distortion due to the multipath fading is removed to the output terminal 3.
【０００５】図３のダイバーシティ受信機に広帯域でＤ
／Ｕ比（干渉波と希望波の比）がマイナスとなるような
強力な干渉波が存在する場合、切替器１２０は減算器１
１７出力をＡＧＣ増幅器１１９を介して選択出力する。
この減算器１１７は乗算器１１２出力から乗算器１１３
出力を減じており、加算器１１６が位相について同相合
成を行うのに対し、減算器１１７は逆相合成を行うこと
で、干渉波の除去を行う。すなわち減算器１１７出力は
パワー・インバージョン・アダプティブ・アレイ出力と
等価である。The diversity receiver shown in FIG.
If there is a strong interference wave such that the / U ratio (the ratio between the interference wave and the desired wave) becomes negative, the switching device 120 operates as the subtractor 1
The 17 outputs are selectively output via the AGC amplifier 119.
This subtractor 117 converts the output of the multiplier 112 to the multiplier 113.
While the output is being reduced, the adder 116 performs in-phase synthesis on the phases, while the subtractor 117 performs anti-phase synthesis to remove interference waves. That is, the output of the subtractor 117 is equivalent to the output of the power inversion adaptive array.
【０００６】図４に図３の受信機における干渉除去の動
作説明図を示す。図４（ａ）と（ｄ）は、それぞれダイ
バーシティルート１，２（入力端１，２）の信号Ａ，Ｂ
を示している。ここで、各ルートの希望波をＳ１，Ｓ２
とし、干渉波Ｊ１，Ｊ２とする。Ｄ／Ｕがマイナスとな
るくらい干渉波が大きい時、干渉波どうし同相合成され
るように制御され、図４（ｂ）と（ｅ）に示すように、
乗算器１１２と１１３出力にて干渉波Ｊ１とＪ２とが振
幅および位相が等しくなる。この場合、図４（ｃ）は、
加算器１１６出力では干渉波Ｊ１とＪ２どうしの同相合
成を示している。一方、図４（ｆ）に示すように減算器
１１７では干渉波どうし逆相合成され、干渉波は除去さ
れ、希望信号波Ｓ１とＳ２のみ抽出されている。しかし
希望波Ｓ１とＳ２については最大比合成のみならず同相
合成すら行なわれないことになる。特に希望波Ｓと干渉
波Ｊとの位相関係により、希望信号波Ｓ１とＳ２が消え
ることがある。信号ＡとＢが図４（ｇ）と（ｊ）のよう
にＳとＪとの振幅位相関係が同じ場合、乗算器１１２と
１１３の出力は図４（ｈ）と（ｋ）のように一致する。
この時図４（ｉ）のように加算器１１６出力はＳもＪも
同相合成で、減算器１１７出力はＳもＪも逆相合成とな
る。すなわち干渉波Ｊ１とＪ２は除去されているが、希
望信号波Ｓ１もＳ２も消滅することになる。FIG. 4 shows an operation explanatory diagram of interference cancellation in the receiver of FIG. 4A and 4D show signals A and B of diversity routes 1 and 2 (input ends 1 and 2), respectively.
Is shown. Here, the desired wave of each route is S1, S2
And interference waves J1 and J2. When the interference waves are so great that D / U becomes negative, the interference waves are controlled so that they are combined in phase, and as shown in FIGS. 4 (b) and (e),
The interference waves J1 and J2 have the same amplitude and phase at the outputs of the multipliers 112 and 113. In this case, FIG.
The output of the adder 116 shows in-phase synthesis of the interference waves J1 and J2. On the other hand, as shown in FIG. 4 (f), in the subtractor 117, the interference waves are combined in anti-phase with each other, the interference waves are removed, and only the desired signal waves S1 and S2 are extracted. However, for the desired waves S1 and S2, not only the maximum ratio combining but also the in-phase combining is not performed. In particular, the desired signal waves S1 and S2 may disappear due to the phase relationship between the desired wave S and the interference wave J. When the signals A and B have the same amplitude-phase relationship between S and J as shown in FIGS. 4 (g) and 4 (j), the outputs of the multipliers 112 and 113 match as shown in FIGS. 4 (h) and 4 (k). To do.
At this time, as shown in FIG. 4 (i), the output of the adder 116 is in-phase synthesis for both S and J, and the output of the subtracter 117 is in-phase synthesis for both S and J. That is, although the interference waves J1 and J2 are removed, both the desired signal waves S1 and S2 disappear.
【０００７】[0007]
【発明が解決しようとする課題】上述した従来技術の偏
波ダイバーシティ受信機では、干渉波を除去しようとす
ると、希望波についてダイバーシティの最大比合成ある
いは同相合成が行なわれないため、マルチパスフェージ
ング回線での適応等化による最適受信と干渉波除去とが
両立せず、場合によっては希望信号を消失させてしまう
と言う問題点がある。In the above-mentioned conventional polarization diversity receiver, when trying to remove the interference wave, the maximum ratio combining or the in-phase combining of the desired waves is not performed, so that the multipath fading line is not used. There is a problem that optimal reception by adaptive equalization and interference wave cancellation are not compatible with each other, and in some cases the desired signal is lost.
【０００８】本発明の目的は、この問題点を解決するこ
とにあり、干渉除去に伴う希望波の消滅を防ぐことがで
き、ダイバーシティ効果を損なわないで強度広帯域干渉
波を除去し、マルチパス歪を効果的に除去することが可
能な干渉波除去装置を提供することにある。An object of the present invention is to solve this problem. It is possible to prevent the desired wave from disappearing due to the interference removal, remove the strong broadband interference wave without impairing the diversity effect, and eliminate the multipath distortion. Another object of the present invention is to provide an interference wave removing device that can effectively remove the noise.
【０００９】[0009]
【課題を解決するための手段】この発明による干渉波除
去装置は、同一送信データで変調された垂直および水平
偏波の無線周波数信号を送信アンテナから送信する送信
機と、前記垂直および水平偏波の無線周波数信号を受信
アンテナに受ける受信機とを備える偏波ダイバーシティ
方式の干渉波除去装置において、前記送信機が、前記垂
直および水平偏波無線周波数信号間に所定の遅延時間差
を持たせて送信する送信手段と、前記送信アンテナの偏
波面を回転制御する送信アンテナ偏波回転制御手段とを
備え、前記受信機が、受信した前記垂直および水平偏波
無線周波数信号をそれぞれＡＧＣ増幅するＡＧＣ増幅器
と、前記ＡＧＣ増幅器各各の出力と前記ＡＧＣ増幅器に
対応する相関信号とをそれぞれ乗算する乗算器と、前記
二つの乗算器の出力を同相合成する加算器と、前記二つ
の乗算器出力を逆相合成する減算器と、前記加算器の出
力をＡＧＣ増幅するＡＧＣ増幅手段と、前記ＡＧＣ増幅
器各各の出力と前記ＡＧＣ増幅手段の出力との相関をそ
れぞれとって前記相関信号を生じる相関器と、前記同相
合成出力と逆相合成出力とを切替る切替器と、前記切替
器の出力を適応受信する適応整合フィルタと、前記適応
整合フィルタの出力を判定帰還等化する判定帰還形等化
器と、前記受信アンテナの偏波面を回転制御する受信ア
ンテナ偏波回転制御手段とを備えている。An interference wave removing apparatus according to the present invention is a transmitter for transmitting vertically and horizontally polarized radio frequency signals modulated by the same transmission data from a transmitting antenna, and the vertically and horizontally polarized waves. In a polarization diversity type interference wave canceller comprising a receiver for receiving a radio frequency signal in a receiving antenna, the transmitter transmits with a predetermined delay time difference between the vertical and horizontal polarization radio frequency signals. And an AGC amplifier for amplifying the received vertical and horizontal polarization radio frequency signals by AGC, respectively, the transmission means and the transmission antenna polarization rotation control means for controlling rotation of the polarization plane of the transmission antenna. , A multiplier for multiplying each output of each of the AGC amplifiers and a correlation signal corresponding to the AGC amplifier, and an output of the two multipliers. Of in-phase synthesis, a subtractor of anti-phase synthesis of the outputs of the two multipliers, an AGC amplification means for AGC amplification of the output of the adder, an output of each of the AGC amplifiers and the AGC amplification means. A correlator that takes the correlation with the output to generate the correlation signal, a switch that switches between the in-phase combined output and the anti-phase combined output, an adaptive matched filter that adaptively receives the output of the switch, and the adaptive A decision feedback equalizer for performing decision feedback equalization on the output of the matched filter, and a reception antenna polarization rotation control means for controlling rotation of the polarization plane of the reception antenna are provided.
【００１０】[0010]
【作用】本発明の干渉波除去装置は、偏波ダイバーシテ
ィを行うマルチパスフェージング回線の送信側にてダイ
バーシティブランチ間に一定の遅延時間差を持たせて送
信し、受信側ではダイバーシティブランチ間での干渉波
が逆相となるようにダイバーシティ合成を行うことによ
り、強度な広帯域干渉波を除去し、ダイバーシティブラ
ンチ間の送信シンボル遅延時間差により干渉除去に伴う
希望波の消滅を防ぎ、整合フィルタ（ＭＦ）および判定
帰還形等化器（ＤＦＥ）を用いることにより、ダイバー
シティ効果を損なわないで強度広帯域干渉波とマルチパ
ス歪を除去する。The interference wave canceling apparatus of the present invention transmits with a certain delay time difference between diversity branches on the transmitting side of a multipath fading line which performs polarization diversity, and on the receiving side interference between diversity branches. By performing diversity combining so that the waves have opposite phases, strong wideband interference waves are removed, and the desired wave disappears due to interference removal due to the transmission symbol delay time difference between diversity branches, and a matched filter (MF) and By using a decision feedback equalizer (DFE), the strong broadband interference wave and multipath distortion are removed without impairing the diversity effect.
【００１１】[0011]
【実施例】次に本発明について図面を参照して説明す
る。図１は本発明の一実施例の構成図である。また、図
２は図１の実施例の動作説明図である。The present invention will be described below with reference to the drawings. FIG. 1 is a block diagram of an embodiment of the present invention. 2 is an operation explanatory diagram of the embodiment shown in FIG.
【００１２】図１に示す偏波ダイバーシティ方式の送信
機１１は、送信データを変調器（ＭＯＤ）１０１によっ
て中間周波数信号の送信データに周波数変換し、この送
信データを２分岐する。この送信データの一方は送信器
（ＴＸ）１０３により無線周波数信号に変換され、送信
アンテナ１０５のＶ偏波信号として送信される。中間周
波数信号の送信データの他方は、遅延素子１０２により
時間τだけ遅延された後、送信器（ＴＸ）１０４により
同一周波数の無線周波数信号に変換され、送信アンテナ
１０５によりＨ偏波信号として送信される。これらＶお
よびＨ偏波信号のペアが、偏波ダイバーシティのダイバ
ーシティブランチをなす。なお、この送信機１１は、後
述する送信アンテナ制御器１０６を備える。A polarization diversity transmitter 11 shown in FIG. 1 frequency-converts transmission data into transmission data of an intermediate frequency signal by a modulator (MOD) 101, and bifurcates the transmission data. One of the transmission data is converted into a radio frequency signal by the transmitter (TX) 103 and transmitted as a V polarization signal of the transmission antenna 105. The other transmission data of the intermediate frequency signal is delayed by time τ by the delay element 102, converted into a radio frequency signal of the same frequency by the transmitter (TX) 104, and transmitted as an H polarization signal by the transmission antenna 105. It These V and H polarization signal pairs form a diversity branch of polarization diversity. The transmitter 11 includes a transmission antenna controller 106 described later.
【００１３】図１の受信機１２は、受信アンテナ１０７
のＶ偏波受信面から上記Ｖ偏波信号を受け、受信アンテ
ナ１０７のＨ偏波受信面から上記Ｈ偏波信号を受ける。
これらＶおよびＨ偏波受信信号は、それぞれ受信回路
（ＲＸ）１０８および１０９により中間周波数信号（ま
たはベースバンド信号）に変換される。これらの中間周
波数信号は、図３の受信機の説明における入力端１およ
び２の信号Ａおよび信号Ｂと同じである。以下、ＡＧＣ
増幅器１１０，１１１，乗算器１１２，１１３，相関器
１１４，１１５，加算器１１６，減算器１１７，ＡＧＣ
増幅器１１８，１１９，切替器１２０は、図３の従来技
術の受信機で述べたパワー・インバージョン・アダプテ
ィブ・アレイを構成している。The receiver 12 of FIG. 1 has a receiving antenna 107.
The V polarized wave signal is received from the V polarized wave receiving surface and the H polarized wave signal is received from the H polarized wave receiving surface of the receiving antenna 107.
The V and H polarized wave reception signals are converted into intermediate frequency signals (or baseband signals) by reception circuits (RX) 108 and 109, respectively. These intermediate frequency signals are the same as signals A and B at inputs 1 and 2 in the receiver description of FIG. Below, AGC
Amplifiers 110, 111, multipliers 112, 113, correlators 114, 115, adders 116, subtractors 117, AGC
The amplifiers 118 and 119 and the switch 120 constitute the power inversion adaptive array described in the prior art receiver of FIG.
【００１４】ここで、加算器１１６出力がダイバーシテ
ィの最大比合成出力に、減算器１１７出力がパワー・イ
ンバージョン・アダプティブ・アレイ出力に対応してい
る。すなわち干渉波が無い時には加算器１１６がダイバ
ーシティ合成信号を供給し、強度の干渉波がある場合に
は減算器１１７は干渉波が除去された信号を出力する。
なお、この受信機１２は、図３で述べた等化器３１１を
適応整合フィルタ（ＡＭＦ）１２１と判定帰還形等化器
（ＤＦＥ）１２２に分割して示し、また、後述する切替
制御器（ＳＷ ＣＯＮＴ）１２３と受信アンテナ制御器
（ＲＸ ＡＮＴＣＯＮＴ）１２４とを備えている。Here, the output of the adder 116 corresponds to the maximum ratio combining output of diversity, and the output of the subtractor 117 corresponds to the output of the power inversion adaptive array. That is, the adder 116 supplies the diversity combined signal when there is no interference wave, and the subtracter 117 outputs the signal from which the interference wave is removed when there is a strong interference wave.
The receiver 12 is shown by dividing the equalizer 311 described in FIG. 3 into an adaptive matched filter (AMF) 121 and a decision feedback equalizer (DFE) 122, and a switching controller (described later) ( SW CONT) 123 and a reception antenna controller (RX ANT CONT) 124 are provided.
【００１５】図２は図１の実施例の動作を説明するため
の図である。図１と図２を合せ参照し、この実施例の動
作を説明する。図２において、２０７は受信電界レベル
の変動、２０８は乗算器１１２出力での希望波Ｓ１のシ
ンボル列、２０９は乗算器１１２出力での干渉波Ｊ１、
２１０は乗算器１１３出力での希望波Ｓ２のシンボル
列、２１１は乗算器１１３出力での干渉波Ｊ１、２１２
は減算器１１７出力での希望波シンボル列、２１３は判
定帰還形等化器１２２出力での希望波シンボル列を、そ
れぞれ示している。FIG. 2 is a diagram for explaining the operation of the embodiment shown in FIG. The operation of this embodiment will be described with reference to FIGS. In FIG. 2, 207 is a fluctuation of the received electric field level, 208 is a symbol sequence of the desired wave S1 at the output of the multiplier 112, 209 is an interference wave J1 at the output of the multiplier 112,
210 is a symbol sequence of the desired wave S2 at the output of the multiplier 113, 211 is an interference wave J1, 212 at the output of the multiplier 113.
Indicates a desired wave symbol sequence at the output of the subtractor 117, and 213 indicates a desired wave symbol sequence at the output of the decision feedback equalizer 122.
【００１６】受信アンテナ１０７のＶ偏波面にはＶ偏波
希望信号Ｓ１と干渉波源Ｊからの干渉波Ｊ１が受信さ
れ、Ｈ偏波面にはＨ偏波希望信号Ｓ２と干渉波源Ｊから
の干渉波Ｊ２とが受信される。干渉波レベルが強く、Ｄ
／Ｕ（希望波対干渉波レベル比）がマイナスの場合、従
来技術で述べたように乗算器１１２および１１３出力で
の干渉波は２０９および２１１に示すように同振幅同位
相に制御されている。従って減算器１１７により干渉波
どうしキャンセルしあい、干渉波が除去される。一方希
望波に関しては２０８および２１０に示すように受信シ
ンボル列が時間的にずれている。これは送信機１１にて
送信データの送信シンボル｛ａn ｝（ｎ＝…−２，−
１，０，１，２，…）に対してＶＨ偏波間でτだけ遅延
差を持たせているからである。ここでは遅延差τを５Ｔ
（Ｔはシンボル周期）に設定している。また受信電界レ
ベル２０７は伝搬路のフェージングによる変動を示して
いる。通常Ｖ偏波とＨ偏波の無線周波数信号は同一経路
を伝搬する。従って互いに無相関となる経路を利用する
空間ダイバーシティと異なり、偏波ダイバーシティブラ
ンチ間には多少相関がある。従って電界レベル２０７の
ような受信レベル変動はＶＨ両偏波に対して共通に影響
を及ぼす。電界レベル２０７において、斜線部は瞬断し
きい値以下となる領域であり、この部分は受信シンボル
列に対して瞬断を引き起こす。これに対応してシンボル
列２０８および２１０の斜線部で示した部分は信号が消
失した信号断となっている。The V polarization plane of the receiving antenna 107 receives the V polarization desired signal S1 and the interference wave J1 from the interference wave source J, and the H polarization plane receives the H polarization desired signal S2 and the interference wave from the interference wave source J. J2 and are received. The interference wave level is strong and D
When / U (desired wave to interference wave level ratio) is negative, the interference waves at the outputs of the multipliers 112 and 113 are controlled to have the same amplitude and the same phase as indicated by 209 and 211 as described in the prior art. . Therefore, the subtractor 117 cancels out the interference waves and removes the interference waves. On the other hand, regarding the desired wave, the received symbol sequences are temporally displaced as shown by 208 and 210. This is the transmission symbol {a n } (n = ... -2,-) of the transmission data at the transmitter 11.
This is because there is a delay difference of τ between the VH polarized waves with respect to 1, 0, 1, 2, ... Here, the delay difference τ is 5T
(T is a symbol period). Further, the received electric field level 207 shows a fluctuation due to fading of the propagation path. Normally, the V-polarized and H-polarized radio frequency signals propagate on the same path. Therefore, unlike spatial diversity, which uses paths that are uncorrelated with each other, there is some correlation between polarization diversity branches. Therefore, reception level fluctuations such as the electric field level 207 commonly affect both VH polarized waves. In the electric field level 207, the shaded area is an area below the instantaneous interruption threshold value, and this portion causes an instantaneous interruption to the received symbol sequence. Corresponding to this, the shaded portions of the symbol arrays 208 and 210 are signal loss where signals have disappeared.
【００１７】減算器１１７出力では干渉波が除去されて
いるが、２１２に示すように信号断を有した受信シンボ
ル列となっている。一方、シンボル列２１２は希望波２
０８と２１０との差信号であり、１個のシンボルにそれ
ぞれ遅延差のあるシンボル２個が重なりあっている。シ
ンボル列２１２の上段を希望するブランチであるとする
と下段は符号間干渉と等価である。すなわちシンボル列
２１２は２波伝搬モデルによりマルチパス歪を受けた受
信信号で、かつ斜線部で示される信号断を有したものと
なっている。このようなマルチパス歪を受けた受信信号
に対しては適応整合フィルタ１２１と判定帰還形等化器
１２２とで構成される適応受信機が効果的である。この
適応整合フィルタ（ＡＭＦ）１２１と判定帰還形等化器
（ＤＦＥ）１２２による適応受信に関しては、渡辺孝次
郎により電子通信学会、通信方式研究会１９７９年２月
（ＣＳ７８−２０３）に“マルチパス伝送路における適
応受信方式”として提案されており、対流圏散乱通信に
おいてすでに実用化されている。Although the interference wave is removed at the output of the subtractor 117, the received symbol string has a signal break as shown at 212. On the other hand, the symbol row 212 is the desired wave 2
The difference signal between 08 and 210, and two symbols each having a delay difference overlap one symbol. If the upper stage of the symbol sequence 212 is the desired branch, the lower stage is equivalent to intersymbol interference. That is, the symbol sequence 212 is a reception signal that has undergone multipath distortion according to the two-wave propagation model, and has a signal disconnection indicated by the hatched portion. An adaptive receiver including an adaptive matched filter 121 and a decision feedback equalizer 122 is effective for a received signal subjected to such multipath distortion. Regarding adaptive reception by the adaptive matched filter (AMF) 121 and the decision feedback equalizer (DFE) 122, Kojiro Watanabe, Institute of Electronics and Communication Engineers, Communication Method Study Group, February 1979 (CS78-203), "Multipath transmission. It has been put into practical use in tropospheric scatter communication.
【００１８】適応整合フィルタ２０５は、受信信号に対
するインパルス応答の時間反転複素共約を畳み込むこと
により、伝送系のインパルス応答を対称化し、受信信号
のＳＮ比を最大化する。すなわちシンボル列２１２下段
の符号間干渉としてのシンボル−ａ0 成分の大半は２１
２上段の希望シンボルａ0 に時間領域の最大比合成され
る。同様にシンボル列２１２上段でシンボルａ1 からａ
4 の信号断となっている部分にはシンボル列２１２下段
の符号間干渉成分のａ1 からａ4 が最大比合成される。
すなわちシンボル列２１２斜線の信号消失している部分
には下段から希望信号が供給され、信号断を復旧させる
効果がある。この整合フィルタリングの後、伝搬路のマ
ルチパスフェージングを含めた最終的なマルチパス歪が
判定帰還形等化器１２１により除去され、信号断がなく
送信データと同じシンボル列２１３を復調することが可
能となる。すなわち、ここでは偏波面を媒体として時間
ダイバーシティ効果が得られていると解釈できる。The adaptive matched filter 205 makes the impulse response of the transmission system symmetrical by convoluting the time-reversal complex co-sign of the impulse response to the received signal, and maximizes the SN ratio of the received signal. That is, most of the symbol-a 0 components as intersymbol interference in the lower part of the symbol sequence 212 are 21
The maximum ratio in the time domain is combined with the desired symbol a 0 in the upper second row. Similarly, in the upper part of the symbol array 212, the symbols a 1 to a
In the signal disconnection portion of 4 , the maximum ratios of the intersymbol interference components a 1 to a 4 in the lower stage of the symbol sequence 212 are combined.
That is, the desired signal is supplied from the lower stage to the portion where the signal disappears in the diagonal line of the symbol array 212, which has the effect of recovering the signal disconnection. After this matched filtering, the final multipath distortion including multipath fading in the propagation path is removed by the decision feedback equalizer 121, and the same symbol sequence 213 as the transmission data can be demodulated without signal interruption. Becomes That is, it can be construed here that the time diversity effect is obtained using the polarization plane as a medium.
【００１９】さらに図１を参照すると、判定帰還形等化
器１２２からの判定データ信号により切替制御器１２３
は干渉波の有無を判断し、干渉波が無い場合には加算器
１１６出力を選択するよう、干渉波が有る場合には減算
器１１７出力を選択するように切替器１２０を制御す
る。Still referring to FIG. 1, the switching controller 123 is controlled by the judgment data signal from the judgment feedback equalizer 122.
Determines the presence or absence of an interference wave, and controls the switching unit 120 to select the output of the adder 116 when there is no interference wave and to select the output of the subtractor 117 when there is an interference wave.
【００２０】なお、干渉波がＶ偏波あるいはＨ偏波のい
ずれかで励振され、両偏波ダイバーシティブランチの一
方にしか受信されない場合には、パワー・インバージョ
ン・アダプティブ・アレイを用いた干渉除去が不可能と
なる。このような場合には送信アンテナ制御器１０６お
よび受信アンテナ制御器１２４により送信アンテナ１０
５および受信アンテナ１０７の偏波面を同一の角度を保
つように回転させる。この操作により偏波間の送受の直
交性を保ちながら干渉波成分が両偏波間に受信できるよ
うになり、以上述べた干渉除去動作が継続できる。When the interference wave is excited by either the V polarization or the H polarization and is received by only one of the polarization branch of both polarizations, the interference cancellation using the power inversion adaptive array is performed. Is impossible. In such a case, the transmitting antenna controller 106 and the receiving antenna controller 124 control the transmitting antenna 10
5 and the polarization planes of the receiving antenna 107 are rotated so that the same angle is maintained. By this operation, the interference wave component can be received between both polarizations while maintaining the orthogonality of transmission and reception between the polarizations, and the above-described interference removal operation can be continued.
【００２１】[0021]
【発明の効果】以上説明したように本発明は、偏波ダイ
バーシティ受信において、ダイバーシティブランチ間で
遅延時間差を持たせて送信し、受信側にて偏波ダイバー
シティブランチ間でパワー・インバージョン・アダプテ
ィブ・アレイによる干渉除去を行い、干渉除去後の信号
を適応整合フィルタ（ＡＭＦ）および判定帰還形等化器
（ＤＦＥ）を用いた適応受信機に通すことにより、従来
の干渉波除去に伴う希望信号波の消滅という問題点を解
決し、ダイバーシティ効果を保存しながら強度な広帯域
干渉波とマルチパス歪の除去を可能とする効果がある。As described above, according to the present invention, in polarization diversity reception, transmission is performed with a delay time difference between diversity branches, and at the receiving side, power inversion adaptive transmission between polarization diversity branches is performed. By performing interference cancellation by an array and passing the signal after the interference cancellation through an adaptive receiver using an adaptive matched filter (AMF) and a decision feedback equalizer (DFE), a desired signal wave accompanying conventional interference wave cancellation is obtained. There is an effect that solves the problem of disappearance of, and can remove strong broadband interference wave and multipath distortion while preserving the diversity effect.
【図１】本発明の一実施例の構成図である。FIG. 1 is a configuration diagram of an embodiment of the present invention.
【図２】この実施例の動作説明図である。FIG. 2 is an operation explanatory diagram of this embodiment.
【図３】従来の干渉波除去装置の構成図である。FIG. 3 is a configuration diagram of a conventional interference wave removing device.
【図４】従来の干渉波除去装置の動作説明図である。FIG. 4 is an operation explanatory view of a conventional interference wave removing device.
１，２ 入力端 ３ 出力端 １１ 送信機 １２ 受信機 １０１ 変調器（ＭＯＤ） １０２ 遅延素子 １０３，１０４ 送信器（ＴＸ） １０５ 送信アンテナ １０６ 送信アンテナ制御器（ＴＸ ＡＮＴ ＣＯＮ
Ｔ） １０７ 受信アンテナ １０８，１０９ 受信回路（ＲＸ） １１０，１１１，１１８，１１９ ＡＧＣ増幅器 １１２，１１３ 乗算器 １１４，１１５ 相関器 １１６ 加算器 １１７ 減算器 １２０ 切替スイッチ（ＳＷ） １２１ 適応整合フィルタ（ＡＭＦ） １２２ 判定帰還形等化器（ＤＦＥ） １２３ 切替制御器（ＳＷ ＣＯＮＴ） １２４ 受信アンテナ制御器（ＲＸ ＡＮＴ ＣＯＮ
Ｔ） ３１１ 等化器（ＥＱＬ） ２０７ 受信電界レベル変動 ２０８ 乗算器１１２出力での希望波Ｓ１のシンボル
列 ２０９ 乗算器１１２出力での干渉波Ｊ１ ２１０ 乗算器１１３出力での希望波Ｓ２のシンボル
列 ２１１ 乗算器１１３出力での干渉波Ｊ１ ２１２ 減算器１１７出力での希望波シンボル列 ２１３ 判定帰還型等化器１２２出力での希望波シン
ボル列1, 2 input terminal 3 output terminal 11 transmitter 12 receiver 101 modulator (MOD) 102 delay element 103, 104 transmitter (TX) 105 transmission antenna 106 transmission antenna controller (TX ANT CON)
T) 107 receiving antennas 108, 109 receiving circuits (RX) 110, 111, 118, 119 AGC amplifiers 112, 113 multipliers 114, 115 correlators 116 adders 117 subtractors 120 changeover switches (SW) 121 adaptive matched filters (AMF) ) 122 decision feedback equalizer (DFE) 123 switching controller (SW CONT) 124 receiving antenna controller (RX ANT CON)
T) 311 Equalizer (EQL) 207 Received electric field level variation 208 Symbol string of desired wave S1 at output of multiplier 112 209 Interference wave J1 210 at output of multiplier 112 Symbol string of desired wave S2 at output of multiplier 113 211 Interference wave at output of multiplier 113 J1 212 Desired wave symbol sequence at output of subtractor 117 213 Desired wave symbol sequence at output of decision feedback equalizer 122
Claims (1)
水平偏波の無線周波数信号を送信アンテナから送信する
送信機と、前記垂直および水平偏波の無線周波数信号を
受信アンテナに受ける受信機とを備える偏波ダイバーシ
ティ方式の干渉波除去装置において、 前記送信機が、前記垂直および水平偏波無線周波数信号
間に所定の遅延時間差を持たせて送信する送信手段と、
前記送信アンテナの偏波面を回転制御する送信アンテナ
偏波回転制御手段とを備え、 前記受信機が、受信した前記垂直および水平偏波無線周
波数信号をそれぞれＡＧＣ増幅するＡＧＣ増幅器と、前
記ＡＧＣ増幅器各各の出力と前記ＡＧＣ増幅器に対応す
る相関信号とをそれぞれ乗算する乗算器と、前記二つの
乗算器の出力を同相合成する加算器と、前記二つの乗算
器出力を逆相合成する減算器と、前記加算器の出力をＡ
ＧＣ増幅するＡＧＣ増幅手段と、前記ＡＧＣ増幅器各各
の出力と前記ＡＧＣ増幅手段の出力との相関をそれぞれ
とって前記相関信号を生じる相関器と、前記同相合成出
力と逆相合成出力とを切替る切替器と、前記切替器の出
力を適応受信する適応整合フィルタと、前記適応整合フ
ィルタの出力を判定帰還等化する判定帰還形等化器と、
前記受信アンテナの偏波面を回転制御する受信アンテナ
偏波回転制御手段とを備えることを特徴とする干渉波除
去装置。1. A transmitter for transmitting vertically and horizontally polarized radio frequency signals modulated by the same transmission data from a transmitting antenna, and a receiver for receiving the vertically and horizontally polarized radio frequency signals at a receiving antenna. In a polarization diversity type interference wave removing device comprising, the transmitter, a transmitting means for transmitting with a predetermined delay time difference between the vertical and horizontal polarization radio frequency signals,
Transmission antenna polarization rotation control means for controlling rotation of the polarization plane of the transmission antenna, wherein the receiver performs AGC amplification on the received vertical and horizontal polarization radio frequency signals, respectively, and each of the AGC amplifiers. A multiplier for multiplying each output by the correlation signal corresponding to the AGC amplifier, an adder for in-phase combining the outputs of the two multipliers, and a subtracter for performing anti-phase combining of the outputs of the two multipliers. , The output of the adder is A
AGC amplifying means for performing GC amplification, a correlator that takes the correlation between each output of the AGC amplifier and the output of the AGC amplifying means, and switches the in-phase combined output and the anti-phase combined output. A switch, an adaptive matched filter that adaptively receives the output of the switch, a decision feedback equalizer that performs decision feedback equalization on the output of the adaptive matched filter,
An interference wave elimination device, comprising: a reception antenna polarization rotation control unit that controls rotation of a polarization plane of the reception antenna.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP21587892A JP2858508B2 (en) | 1992-08-13 | 1992-08-13 | Interference wave canceller |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP21587892A JP2858508B2 (en) | 1992-08-13 | 1992-08-13 | Interference wave canceller |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH0661894A true JPH0661894A (en) | 1994-03-04 |
| JP2858508B2 JP2858508B2 (en) | 1999-02-17 |
Family
ID=16679758
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP21587892A Expired - Fee Related JP2858508B2 (en) | 1992-08-13 | 1992-08-13 | Interference wave canceller |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2858508B2 (en) |
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| FR2732173A1 (en) * | 1995-03-22 | 1996-09-27 | Nec Corp | Radio communication system for dispersed spectrum signals |
| WO1997040588A1 (en) * | 1996-04-19 | 1997-10-30 | Ericsson Inc. | Method and apparatus for interference rejection with different beams, polarizations, and phase references |
| US5691727A (en) * | 1995-01-03 | 1997-11-25 | State Of Israel-Ministry Of Defense Armament Development Authority-Rafael | Adaptive polarization diversity system |
| US7031368B1 (en) | 1998-06-30 | 2006-04-18 | Nec Corporation | Adaptive transmitter/receiver |
| JP2009267816A (en) * | 2008-04-25 | 2009-11-12 | Nippon Telegr & Teleph Corp <Ntt> | Wireless receiving apparatus, interference removal method, wireless communication system and wireless communication method |
| JP2010021919A (en) * | 2008-07-14 | 2010-01-28 | Nec Corp | Mobile communication system, base station, and interference cancellation method |
| US8031756B2 (en) | 2007-05-24 | 2011-10-04 | Sony Corporation | Communication device, communication method, communication system and program |
| WO2011158727A1 (en) * | 2010-06-17 | 2011-12-22 | シャープ株式会社 | Wireless communication apparatus, reception method and program thereof |
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| JP2015039218A (en) * | 2014-10-09 | 2015-02-26 | 株式会社日立製作所 | Polarization angle division diversity radio transmitter, radio receiver, and radio communication system |
| US9407349B2 (en) | 2011-03-09 | 2016-08-02 | Hitachi, Ltd. | Polarization-angle-division diversity wireless transmitter, wireless receiver, and wireless communication system |
| JP2017502614A (en) * | 2014-01-10 | 2017-01-19 | クゥアルコム・インコーポレイテッドＱｕａｌｃｏｍｍ Ｉｎｃｏｒｐｏｒａｔｅｄ | Opportunistic active interference cancellation using RX diversity antenna |
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1992
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| US5691727A (en) * | 1995-01-03 | 1997-11-25 | State Of Israel-Ministry Of Defense Armament Development Authority-Rafael | Adaptive polarization diversity system |
| FR2732173A1 (en) * | 1995-03-22 | 1996-09-27 | Nec Corp | Radio communication system for dispersed spectrum signals |
| JPH08265236A (en) * | 1995-03-22 | 1996-10-11 | Nec Corp | Diversity transmission and reception method and transmitter-receiver |
| WO1997040588A1 (en) * | 1996-04-19 | 1997-10-30 | Ericsson Inc. | Method and apparatus for interference rejection with different beams, polarizations, and phase references |
| US7031368B1 (en) | 1998-06-30 | 2006-04-18 | Nec Corporation | Adaptive transmitter/receiver |
| US8031756B2 (en) | 2007-05-24 | 2011-10-04 | Sony Corporation | Communication device, communication method, communication system and program |
| JP2009267816A (en) * | 2008-04-25 | 2009-11-12 | Nippon Telegr & Teleph Corp <Ntt> | Wireless receiving apparatus, interference removal method, wireless communication system and wireless communication method |
| JP2010021919A (en) * | 2008-07-14 | 2010-01-28 | Nec Corp | Mobile communication system, base station, and interference cancellation method |
| JP4623327B2 (en) * | 2008-07-14 | 2011-02-02 | 日本電気株式会社 | Mobile communication system, base station, interference canceling method |
| WO2011158727A1 (en) * | 2010-06-17 | 2011-12-22 | シャープ株式会社 | Wireless communication apparatus, reception method and program thereof |
| US9407349B2 (en) | 2011-03-09 | 2016-08-02 | Hitachi, Ltd. | Polarization-angle-division diversity wireless transmitter, wireless receiver, and wireless communication system |
| US9722687B2 (en) | 2011-03-09 | 2017-08-01 | Hitachi, Ltd. | Polarization-angle-division diversity wireless transmitter, wireless receiver, and wireless communication system |
| WO2014128906A1 (en) * | 2013-02-22 | 2014-08-28 | 株式会社 日立製作所 | Radio communication system, transmitter, receiver, elevator control system, and substation facility monitori ng system |
| JP5914746B2 (en) * | 2013-02-22 | 2016-05-11 | 株式会社日立製作所 | Wireless communication system, transmitter, receiver, elevator control system, and substation monitoring system |
| US9450652B2 (en) | 2013-02-22 | 2016-09-20 | Hitachi, Ltd. | Radio communication system, transmitter, receiver, elevator control system, and substation facility monitoring system |
| JP2017502614A (en) * | 2014-01-10 | 2017-01-19 | クゥアルコム・インコーポレイテッドＱｕａｌｃｏｍｍ Ｉｎｃｏｒｐｏｒａｔｅｄ | Opportunistic active interference cancellation using RX diversity antenna |
| JP2015039218A (en) * | 2014-10-09 | 2015-02-26 | 株式会社日立製作所 | Polarization angle division diversity radio transmitter, radio receiver, and radio communication system |
| JP2020047996A (en) * | 2018-09-14 | 2020-03-26 | Ｎｅｃプラットフォームズ株式会社 | Radio communication device, program, and radio communication system |
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