JPH06342063A - Pulse compression radar - Google Patents

Abstract

PURPOSE:To enhance the distance resolution and the clutter removal performance of the radar by a method wherein a pulse signal is generated by superposing many sine waves whose amplitude is identical and whose mutual frequency interval is definite. CONSTITUTION:Many sine waves whose amplitude is identical and whose mutual frequency interval is definite are oscillated respectively from many oscillators 5 in a pulse compression and modulation means 1. The sine waves are composed and superposed by an adder 6, they are then amplitude-modulated in a gate 7, they are then output to a transmission means 2 as a pulse signal, and they are transmitted toward a target object 33. A reflected pulse signal is received by a reception means 3, and it is output to a separation means 8 in a pulse compression and demodulation means 4. In the separation means 8, it is separated into frequency components by many filters 12. The individual frequency components are orthogonal-phase-detected in parallel by many orthogonal phase detectors 13. In a correlation operation means 11, the correlation between the individual frequency components as orthogonal phase detection results obtained via a holding means 10 is operated by a first Fourier transform.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a time interval between a transmission timing of a pulse signal having a predetermined waveform and a reception timing based on a pulse compression signal obtained by compressing a pulse signal received as a reflection echo. By a pulse compression radar that measures the distance to a target.

[0002]

2. Description of the Related Art As a compression method in a conventional pulse compression radar, there are a chirp modulation pulse compression method and a binary phase modulation pulse compression method. First, in the chirp modulation pulse compression method, a sine wave signal from an oscillator that is linearly frequency-modulated with respect to time is used as a pulse signal.

In the binary phase modulation pulse compression system, the pulse is divided into a number of small pulses according to the compression ratio, and a normal (+) or inversion (-) phase is given to each one in an appropriate order. After transmitting and receiving, the signals are processed in exactly opposite phases and superposed to realize a predetermined compression ratio.

[0004]

However, it is difficult for a conventional pulse compression radar using such a pulse compression system to realize a high pulse compression ratio for a pulse having a narrow time width. Specifically, in any pulse compression method, for a pulse of 100 nsec,
There is a problem that it is impossible to obtain the performance of the compression ratio of 50.

The present invention was devised in view of the above problems, and is capable of performing pulse compression demodulation with a high pulse compression ratio for a pulse having a narrow time width, thereby achieving distance resolution and clutter removal performance. It is an object to provide an improved pulse compression radar.

[0006]

FIG. 1 is a block diagram of the principle of the present invention. In FIG. 1, reference numeral 20 denotes a pulse compression radar. The pulse compression radar 20 has a pulse signal transmission timing and a pulse compression signal. The distance to the target is measured by the time interval with the reception timing based on.

The pulse compression radar 20 comprises pulse compression modulation means 1, transmission means 2, reception means 3 and pulse compression demodulation means 4. The pulse compression modulation means 1 is for generating a pulse signal having a predetermined waveform, and when generating this pulse signal, it is obtained by superimposing a large number of sine waves having the same amplitude and a constant mutual frequency interval. It is configured so as to have a large number of oscillators 5, an adder 6, and a gate 7.

Here, each oscillator 5 oscillates a large number of sine waves having the same amplitude and a constant mutual frequency interval. The adder 6 synthesizes and superimposes the sine waves respectively oscillated from the many oscillators 5, and the gate 7 amplitude-modulates the signal from the adder 6 and transmits it as a pulse signal having a predetermined pulse width. It is output to the means 2.

The transmitting means 2 is for transmitting the pulse signal from the pulse compression modulating means 1 to the target object 33, and the receiving means 3 is for receiving the pulse signal reflected from the target object 33. . The pulse compression demodulation means 4 obtains a pulse compression signal by performing compression processing on the pulse signal received by the reception means 3. The separation means 8, the quadrature phase detection means 9, the holding means 10,
It is configured to have a correlation calculation means 11.

Here, the separating means 8 separates the pulse signal received by the receiving means 3 for each frequency component, and is composed of a large number of filters 12. These filters 12 perform a matched filter process on a pulse signal having a predetermined pulse width for each frequency component. The quadrature phase detection means 9 detects the frequency components of the pulse signal separated by the separation means 8 (filter 12) in parallel and is composed of a large number of quadrature phase detectors 13. These quadrature phase detectors 13 use the pulse compression modulation means 1 for each frequency component.
The quadrature phase detection is performed using the quadrature phase detection reference signal obtained based on each of the oscillators 5.

The holding means 10 holds the quadrature phase detection result obtained by the quadrature phase detection means 9. The correlation calculation means 11 performs a correlation calculation between frequency components on the quadrature detection result held by the holding means 10, and outputs the correlation calculation result as a pulse compression signal.
The correlation calculating means 11 is adapted to calculate the correlation between the frequency components of the quadrature phase detection result for the respective frequency components obtained through the holding means 10 by the fast Fourier transform.

[0012]

In the above-described pulse compression radar of the present invention, as shown in FIG. 1, the pulse compression modulation means 1 superimposes a large number of sine waves having the same amplitude and constant frequency intervals. , A pulse signal having a predetermined waveform is generated. That is, a large number of oscillators 5 provided in the pulse compression modulation means 1 oscillate a large number of sine waves having the same amplitude and a constant mutual frequency interval, and these sine waves are generated by the pulse compression modulation means. It is input to the adder 6 in 1 and synthesized and superposed by the adder 6, and then output to the gate 7.

The signal from the adder 6 sent to the gate 7 is amplitude-modulated in the gate 7 and then output to the transmitting means 2 as a pulse signal having a predetermined pulse width. This pulse signal is transmitted from the transmitting means 2 to the target. It is transmitted toward the object 33. After that, the pulse signal reflected from the target object 33 is received by the receiving means 3 and output to the pulse compression demodulating means 4. In the pulse compression demodulation means 4,
A pulse compression signal is obtained by performing compression processing on this pulse signal.

That is, the pulse signal from the receiving means 3 is first output to the separating means 8 of the pulse compression demodulating means 4.
In the separating means 8, a matched filter process is performed on the pulse signal having a predetermined pulse width for each frequency component by the multiple filters 12, and the received pulse signal is separated for each frequency component. Each frequency component of the pulse signal separated by the separating means 8 is quadrature detected in parallel by a large number of quadrature phase detectors 13 in the quadrature phase detecting means 9. That is, for each quadrature detector 13, for each frequency component, each oscillator 5 of the pulse compression modulator 1
The quadrature detection is performed by using the quadrature detection reference signal obtained based on the above.

Then, the quadrature phase detection results by the quadrature phase detection means 9 are held by the holding means 10, and the held quadrature phase detection results are further calculated by the correlation calculation means 11 between the respective frequency components. Are performed, and the correlation calculation results are output as a pulse compression signal. At this time, the correlation calculation means 11 calculates the correlation between the frequency components of the quadrature phase detection result for each frequency component obtained through the holding means 10 by fast Fourier transform.

Then, the distance to the target object 33 is measured by the time interval between the transmission timing of the pulse signal from the transmission means 2 and the reception timing based on the pulse compression signal obtained by the pulse compression demodulation means 4. It is.

[0017]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of the present invention will be described below with reference to the drawings. FIG. 2 is a block diagram showing an embodiment of the present invention.
In FIG. 2, 20 is a pulse compression radar, and this pulse compression radar 20 measures the distance to the target by the time interval between the transmission timing of the pulse signal and the reception timing based on the pulse compression signal.

Then, the pulse compression radar 20 of this embodiment
Is a pulse compression modulator 1A, a transmitter 2A, a receiver 3A,
Pulse compression demodulation unit 4A, display processing unit 14, display unit 15,
It comprises a stabilized local oscillator 17, a duplexer 18, and a transmitting / receiving antenna 19. Here, the stabilized local oscillator 17 outputs a signal of a predetermined frequency for each modulation / demodulation process to the transmission unit 2A and the reception unit 3A. The duplexer 18 is for preventing the transmission wave and the reception wave from interfering with each other, and the transmitting / receiving antenna 19 transmits the transmission wave to the target object 33, and
The reflected echo (received wave) from the target object 33 is received.

The pulse compression modulator 1A is for generating a pulse signal f (t) having a predetermined waveform shown in the following equation (1), and this pulse f (t) has the same amplitude and has the same amplitude as described later. , Is generated by superimposing a large number of sine waves having a constant mutual frequency interval.

[0020]

[Equation 1]

In the equation (1), | t | <τ / 2
, G (t) = A, | t | = τ / 2, G (t) =
When A / 2, | t |> τ / 2, G (t) = 0.
Further, t is time, f _c is sine wave frequency, Δf is sine wave frequency interval, Φ _k is sine wave phase, A is sine wave amplitude, m is sine wave number, i is imaginary unit, τ is pulse time. Width. However, the sine wave frequency interval Δf is equal to the reciprocal of the pulse width τ.

The pulse compression modulator 1A produces m (m is an arbitrary natural number) oscillators (OSCs) 5 and m distributors (Di) in order to generate the pulse signal f (t).
v) 23, an adder (Comb) 6, and a gate 7. Here, the m oscillators 5 are respectively
It oscillates a sine wave having the same amplitude and a constant mutual frequency interval. Each distributor 23 distributes the sine wave from each oscillator 5 to each of the adder 6 and the pulse compression demodulation unit 4A and outputs the sine wave. At that time, the sine wave j _k (t) is supplied to the adder 6. To output the pulse compression demodulation unit 4
To sine wave g _k (t).

These sine wave j _k (t) and sine wave g
_k (t) is an equation showing the output of the k-th (k is an integer between 1 and m) output of the distributor 23 of the m-system, and the sine wave j _k (t) is The k-th system has a frequency of f _c + kΔf and a phase of 2πΦ _k , and the sine wave g _k (t) is of the k-th system and has a frequency of f _c.
+ KΔf and the phase is 2π (Φ _k + Φ). Then, the sine wave j _k (t) can be expressed by the following expression (2), and the sine wave g _k (t) can be expressed by the following expression (3). It should be noted that Φ in the following formula (3) is an arbitrary phase change amount, and other symbols in the following formulas (2) and (3) are as described above.

J _k (t) = A exp [2πi {(f _c + kΔf) t + Φ _k }] (2) g _k (t) = exp [2πi {(f _c + kΔf) t + Φ _k + Φ}] (3) Adder Reference numeral 6 is for synthesizing and superimposing the sine waves oscillated from the respective oscillators 5, and the gate 7 amplitude-modulates the signal from the adder 6 under the control of the timing control unit 16 which will be described later. Is output as the pulse signal f (t) having the predetermined pulse width described above. The above is a description of each device constituting the pulse compression modulation unit 1A of the present embodiment.

The transmitter 2A performs processing for transmitting the pulse signal from the pulse compression modulator 1A to the target object 33. The transmitter 2A and the transmission power amplifier 22 operate the same. It is configured. The transmission frequency conversion unit 21 modulates the pulse signal from the pulse compression modulation unit 1A based on the frequency of the output from the stabilized local oscillator 17, and the transmission power amplification unit 22 outputs from the transmission frequency conversion unit 21. The modulated wave of the pulse signal is amplified. The transmission wave amplified by the transmission power amplifier 22 is transmitted from the transmitting / receiving antenna 19 to the target object 33 via the duplexer 18 described above.

The receiving section 3A performs a receiving process of the pulse signal (obtained via the transmitting / receiving antenna 19 and the duplexer 18) reflected from the target object 33, and the receiving low noise amplifying section 31 and The reception frequency conversion unit 32 is included. The reception low noise amplification unit 31 amplifies the reception wave, and the reception frequency conversion unit 32 transmits the reception wave from the reception low noise amplification unit 31 based on the frequency of the output from the stabilized local oscillator 17. This is to remove the wave and extract the pulse signal.

The pulse compression demodulation unit 4A obtains a pulse compression signal by performing compression processing on the pulse signal from the reception unit 3A.
A is a separation unit 8A, a quadrature detection unit 9A, and a holding unit 10.
A, a correlation calculation unit 11A, and a timing control unit 16 are included. Here, the separation unit 8A separates the pulse signal received by the reception unit 3A for each frequency component and outputs the pulse signal, and includes a distributor 80 and m filters 12. The distributor 80 distributes the received pulse signal from the receiving unit 3A into m pieces and outputs the m pieces to the m filters 12, respectively.

Each filter 12 [FL (1) to FL
(M)] is for extracting frequency components assigned in advance when a pulse signal is sent. Specifically, (m)] is specifically the k-th (k = 1 to m) th filter 12 [FL
(K)] performs matched filter processing on a pulse having a frequency f _c + kΔf and a pulse width τ. Then, the quadrature phase detector 9A detects the frequency components of the pulse signals separated by the separator 8A in parallel in quadrature phase detection, and m quadrature phase detectors corresponding to the filters 12 of the m system. It is composed of 13.

These quadrature phase detectors 13 have a pulse compression modulator 1A for the frequency components sent to them.
The quadrature phase detection is performed using the quadrature phase detection reference signal obtained based on each of the oscillators 5. The quadrature detection reference signal is the sine wave g _k (t) described above as the output of the distributor 23 of the pulse compression modulator 1A.

The holding unit 10A has a function of m of the quadrature phase detection unit 9A.
M pieces are provided corresponding to each quadrature detector 13 of the system, and each holds the quadrature detection result from the corresponding quadrature detector 13. Specifically, each holding unit 10A, under the control of the timing control unit 16, receives the signal h from the corresponding quadrature phase detector 13.
_It holds the value h _k (t _s ) of _k (t) at time t _s . The signal h _k (t) indicates the k-th signal in the m-system quadrature phase detector 13.

The correlation calculation unit 11A includes the timing control unit 1
According to the control of No. 6, for each quadrature detection result h _k (t _s ) held by the holding unit 10A, correlation calculation between frequency components is performed by fast Fourier transform,
These correlation calculation results are output as m-system pulse compression signals. Specifically, the correlation calculation shown in the following equation (4) is performed. In this equation (4),
s _p (t _s ) represents the signal output from the p-th system after the arithmetic processing, and the pulse-compressed signal was measured at time t _s + ([2p-m + 1] / [2mΔf]). Indicates the value. Note that p is an integer between 1 and m.

[0032]

[Equation 2]

For example, the quadrature detection output is held at time t.
_{When S} = τ / 2, the output s _p (τ / 2) of the correlation calculator 11A is expressed by the following equation (5). And τ
Since 1 / Δf, the correlation calculation unit 11A performs the pulse compression process by the above equation so that the pulse compression ratio is set to m, which is the same number as the number of sine waves in the pulse compression modulation unit 1A. . In the equation (5), T (t) = A {1- (| t | / τ) when | t | ≦ τ, and T (t) = 0 when | t | ≧ τ.

[0034]

[Equation 3]

Further, the timing control section 16 includes gates 7,
Each holding unit 10A, correlation calculation unit 11A, display processing unit 14,
The operation processing timing of the display unit 15 is controlled. The above is a description of each device constituting the pulse compression demodulation unit 4A of the present embodiment. Then, the display processing unit 14 obtains the distance to the target object 33 based on the pulse compression signal obtained by the pulse compression demodulation unit 4A under the control of the timing control unit 16, and displays the result on the display unit 15. It is what makes me.

With the above-described configuration, as shown in FIG. 2, when the pulse signal is transmitted, the pulse compression modulator 1A has the same amplitude and a constant mutual frequency interval m.
A pulse signal f (t) having a predetermined waveform is generated by superimposing the sine waves. That is, the pulse compression modulator 1
From the m oscillators 5 provided in A, sine waves of m systems having the same amplitude and a constant mutual frequency interval are oscillated.

Each of these sine waves is distributed to the distributor 23.
Are divided into two sine waves j _k (t) and sine waves g _k (t), and m sine waves j _k (t) are combined in the adder 6 and superimposed, 7, the amplitude is modulated according to the control of the timing controller 16. As a result, the pulse f (t) having the predetermined pulse width shown in the equation (1) is obtained.
Is generated. After that, this pulse signal f
(T) is output to the transmitter 2A, where it is subjected to a transmission process and then transmitted to the target object 33.

Further, the following processing (pulse compression processing) is performed when the transmission pulse signal is received. That is, the pulse signal reflected and returned from the target object 33 is received by the receiving unit 3
After receiving the reception processing by A, the pulse compression demodulation unit 4A
Is output to. The pulse compression / demodulation unit 4A receiving the pulse signal from the receiving unit 3A subjects the signal to compression processing to obtain a pulse compression signal.

That is, the pulse signal f from the receiver 3A
(T) is first output to the separation unit 8A of the pulse compression demodulation unit 4A. Then, in the separation unit 8A, the pulse processing f
After (t) is divided into m pieces by the divider 80, for example, for the kth system, the kth filter 12
With [FL (k)], the matched filter processing is performed on the pulse having the frequency f _c + kΔf and the pulse width τ. By performing such a process for each system of 1 to m, the input pulse f (t) becomes the pulse compression modulator 1A.
Is decomposed into the m frequency components before synthesis.

The parts separated by m lines by the separating unit 8A
Each frequency component of the loose signal f (t) is detected by the quadrature phase detection unit 9
By A, the same system in the pulse compression modulator 1A
The sine wave g of the distributor 23 obtained from the sine wave of the oscillator 5_k
Quadrature phase detection is performed based on (t). And orthogonal
The quadrature phase detection result of the m system by the phase detection unit 9A is shown.
Signal h_k(T) is output to the holding unit 10A of the corresponding system.
To be done. The holding unit 10 of each system that receives such an output
At A, the predetermined time t_sSignal h at_kThe value h of (t)
_k(T _s) Is retained.

After that, the quadrature phase detection results h _k (t
_s ), the correlation calculation between each frequency component is
The fast Fourier transform as shown in FIG. As a result, the correlation calculation result s _p obtained for each of these m systems
(T _s ) is output as the pulse compression signal of each system. As a result, the waveform of the pulse compression signal for each m system as shown by the solid line portion in (c) of FIG. 3 is obtained.
In FIG. 3C, the amplitude of the pulse compression waveform for each system is weighted by the value indicated by the alternate long and short dash line in the figure, which is the absolute value of the pulse amplitude after pulse compression processing. 3 (a) shows the absolute value of the amplitude of the generated pulse signal f (t), and FIG. 3 (b) shows the absolute value of the pulse amplitude after the matched filter processing. It is a thing.

[0042] For example, the holding portion 10A is, when performed by quadrature phase detection output time tau / 2 retention of, each pulse compressed signal from the correlation calculation unit 11 at this time is s _p (τ /
2) and since τ = 1 / Δf, the compression ratio is the same number m as the frequency components of the pulse signal f (t), and the pulse time width is compressed to τ / m. If τ = 1
00nsec (n is an abbreviation for nano, nano = 1
^{0 -9), Δf = 10MHz,} m = 50 Datosuruto, pulse compression signal pulse width is the compression ratio 50 is compressed in 2nsec is obtained.

Further, in the holding section 10A, the value h of the signal h _k (t) sent in is transmitted at predetermined time intervals (1 / Δf).
_k a (t _s) continue to hold. Therefore, the correlation calculator 11
A will become possible to perform the correlation operation in accordance with the value h _k for each 1 / Δf (t _s), as shown in the FIG. 4 (c) ~ (g) , the pulse compression waveform of each 1 / mΔf Sample values will be obtained continuously. In addition, (c) to (g) of FIG.
Are t _s =-(τ / 2), t _s = 0, t, respectively.
_{s = τ / 2, t s} = τ, and the absolute value of the pulse amplitude after the pulse compression processing when held at t _s = (3/2) τ.

Further, the amplitude of the compressed pulse is attenuated to a maximum of 1/2 according to the delay time of the generated pulse signal f (t), but the pulse compression ratio remains unchanged and does not decrease. By outputting the pulse compression signal of each system as described above from the correlation calculation unit 11A to the display processing unit 14,
The information (information based on the distance to the target object 33) provided by the received pulse is displayed on the display unit 15.

At this time, the distance to the target object 33 is determined by the time interval t _u between the transmission timing of the pulse signal from the transmission unit 2A and the reception timing based on the pulse compression signal obtained by the pulse compression demodulation unit 4A. Although r _u is measured, the delay time t _u at that time has a relationship of r _u = ct _u / 2 with respect to the distance r _u , and therefore the time width 10
When a pulse compression ratio of 50 is obtained for a pulse of 0 nsec, the distance accuracy and distance resolution are about 0.3.
A performance of m (meter) is obtained. This is because range accuracy and range resolution are generally inversely proportional to the transmitted pulse width. In addition, c is the speed of light, and is approximately 3 × 10 ⁸ m / s.
ec.

Furthermore, the clutter removing performance of the radar is inversely proportional to the transmission power and the transmission pulse width if the environmental conditions are the same, so the clutter power is reduced to 1/50 of the clutter removing performance before pulse compression. Therefore, it is possible to obtain an improvement amount of about 17 db as compared with the conventional method. That is, according to the pulse compression radar of this embodiment, in the pulse compression radar including the pulse compression modulator 1A, the transmitter 2A, the receiver 3A, and the pulse compression demodulator 4A,
The pulse signal generated by the pulse compression modulator 1A is
The number of sine waves of the same number as the desired pulse compression ratio and the sine wave are generated by superimposing a large number of sine waves having the same amplitude and a constant mutual frequency interval. By setting the frequency interval Δf of the wave,
A desired pulse compression ratio can be obtained regardless of the length of the pulse time width. As a result, a high pulse compression ratio can be realized even for a pulse with a narrow time width, and the distance resolution, ranging accuracy, and clutter removal performance can be greatly improved.

[0047]

As described above in detail, according to the pulse compression radar of the present invention, the pulse compression modulation means for generating the pulse signal having the predetermined waveform and the pulse signal from the pulse compression modulation means are transmitted toward the target. The transmitting means, the receiving means for receiving the pulse signal reflected from the target, and the pulse compression demodulating means for obtaining the pulse compressed signal by performing the compression processing on the pulse signal received by the receiving means are transmitted. Transmission timing of the pulse signal from the means,
When measuring the distance to the target by the time interval with the reception timing based on the pulse compression signal obtained by the pulse compression demodulation means, the pulse signals generated by the pulse compression modulation means have the same amplitude and mutual frequency intervals. Since a large number of constant sine waves are superimposed and generated, and a predetermined compression process is applied to the reflected echo, a high pulse compression ratio can be realized for a pulse with a narrow time width,
Distance resolution, ranging accuracy, and clutter removal can be greatly improved.

[Brief description of drawings]

FIG. 1 is a principle block diagram of the present invention.

FIG. 2 is a block diagram showing an embodiment of the present invention.

FIG. 3 is a diagram showing an example of an m-system pulse compression waveform according to the present embodiment.

FIG. 4 is a diagram showing an example of pulse compression waveforms of 50 systems according to the present embodiment.

[Explanation of symbols]

 1 pulse compression modulator 1A pulse compression modulator 2 transmitter 2A transmitter 3 receiver 3A receiver 4 pulse compression demodulator 4A pulse compression demodulator 5 oscillator 6 adder 7 gate 8 separator 8A separator 9 quadrature detector 9A Quadrature detection section 10 Holding means 10A Holding section 11 Correlation calculation means 11A Correlation calculation section 12 Filter 13 Quadrature phase detector 14 Display processing section 15 Display section 16 Timing control section 17 Stabilized local oscillator 18 Duplexer 19 Transmission / reception antenna 20 pulse Compressed radar 21 Transmission frequency conversion unit 22 Transmission power amplification unit 23 Distributor 31 Reception low noise amplification unit 32 Reception frequency conversion unit 33 Target object 80 Distributor

Claims (6)

[Claims] 1. A pulse compression modulation unit (1) for generating a pulse signal of a predetermined waveform, a transmission unit (2) for transmitting the pulse signal from the pulse compression modulation unit (1) to a target, and the target. Receiving means (3) for receiving the pulse signal reflected from the pulse compression demodulating means (3) for obtaining a pulse compression signal by performing compression processing on the pulse signal received by the receiving means (3) ( 4), and to the target by the time interval between the transmission timing of the pulse signal from the transmission means (2) and the reception timing based on the pulse compression signal obtained by the pulse compression demodulation means (4). In the pulse compression radar for measuring the distance of, the pulse signal generated by the pulse compression modulation means (1) generates a large number of sine waves having the same amplitude and a constant mutual frequency interval. Characterized in that it is produced by tatami,
Pulse compression radar. 2. A plurality of oscillators (5) each of which the pulse compression modulation means (1) oscillates a plurality of sine waves having the same amplitude and a constant mutual frequency interval, and the plurality of oscillators (5). An adder (6) that synthesizes and superimposes the sine waves oscillated from each other, and amplitude-modulates the signal from the adder (6) and outputs to the transmitting means (2) as the pulse signal having a predetermined pulse width 2. The pulse compression radar according to claim 1, further comprising a gate (7) for 3. The pulse compression demodulation means (4) separates the pulse signal received by the receiving means (3) for each frequency component, and the separation means (8). A quadrature phase detection means (9) for quadrature phase detection of each frequency component of the generated pulse signal in parallel, a holding means (10) for holding a quadrature phase detection result by the quadrature phase detection means (9), The quadrature detection result held by the holding means (10) performs correlation calculation between frequency components, and the correlation calculation means (11) outputs the correlation calculation result as the pulse compression signal. The pulse compression radar according to claim 1, wherein the pulse compression radar is provided. 4. The separating means (8) comprises a number of filters (12) for performing a matched filtering process on a pulse signal having the predetermined pulse width for each frequency component. Pulse compression radar. 5. The quadrature phase detection means (9) uses, for each frequency component, a quadrature phase detection reference signal obtained based on each oscillator (7) of the pulse compression modulation means (1). Multiple quadrature phase detectors (13)
5. The method according to claim 3 or 4, wherein
The pulse compression radar according to 1. 6. The correlation calculation means (11) calculates the correlation between frequency components of the quadrature detection result for each frequency component obtained through the holding means (10) by fast Fourier transform. The pulse compression radar according to any one of claims 3 to 5, characterized in that.