JPH0465636B2 - - Google Patents
Info
- Publication number
- JPH0465636B2 JPH0465636B2 JP58166068A JP16606883A JPH0465636B2 JP H0465636 B2 JPH0465636 B2 JP H0465636B2 JP 58166068 A JP58166068 A JP 58166068A JP 16606883 A JP16606883 A JP 16606883A JP H0465636 B2 JPH0465636 B2 JP H0465636B2
- Authority
- JP
- Japan
- Prior art keywords
- winding
- output
- phase
- output voltage
- annular magnetic
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 238000004804 winding Methods 0.000 claims description 41
- 239000003990 capacitor Substances 0.000 claims description 7
- 238000010586 diagram Methods 0.000 description 16
- 230000004907 flux Effects 0.000 description 10
- 230000000694 effects Effects 0.000 description 5
- 230000010355 oscillation Effects 0.000 description 5
- 230000008878 coupling Effects 0.000 description 2
- 238000010168 coupling process Methods 0.000 description 2
- 238000005859 coupling reaction Methods 0.000 description 2
- 229920006395 saturated elastomer Polymers 0.000 description 2
- XEEYBQQBJWHFJM-UHFFFAOYSA-N Iron Chemical group [Fe] XEEYBQQBJWHFJM-UHFFFAOYSA-N 0.000 description 1
- 229910000859 α-Fe Inorganic materials 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/10—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using transformers
- H02M5/16—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using transformers for conversion of frequency
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Ac-Ac Conversion (AREA)
Description
【発明の詳細な説明】
〔産業上の利用分野〕
立体磁心、直交磁心あるいは平面回路における
２鉄心形で構成された変換器は、パラメトリツク
発振によつて位相差を有し、定電圧回路、逓倍
器、分周器として数多く利用されていることは周
知の事実である。[Detailed Description of the Invention] [Field of Industrial Application] A converter configured with a three-dimensional magnetic core, an orthogonal magnetic core, or a two-core type in a planar circuit has a phase difference due to parametric oscillation, and is used in a constant voltage circuit, It is a well-known fact that they are widely used as multipliers and frequency dividers.
本発明は、２鉄心形でパラメトリツク回路と鉄
共振回路を同時に併せ持つた変換器に係り、特に
制御巻線を有し、１次側の単相入力電圧を一定と
したとき、制御巻線に流す直流電流を変えること
によつて、位相差を保持したまま２次側の単相出
力電圧を自由に可変できる変換器に関する。 The present invention relates to a two-iron core type converter having both a parametric circuit and a ferro-resonant circuit at the same time. The present invention relates to a converter that can freely vary the single-phase output voltage on the secondary side while maintaining the phase difference by changing the DC current that flows.
本発明者らは磁気立体回路を用いた相数変換器
として、単相−二相、および単相−三相用で、能
動体素子を用いずに出力電圧を自由にい可変でき
る変換器を特願昭58−030399号、特願昭58−
094445号として既に提案した。
The present inventors have developed a converter for single-phase to two-phase and single-phase to three-phase converters that can freely vary the output voltage without using active elements as a phase number converter using a magnetic three-dimensional circuit. Patent Application No. 1983-030399, Patent Application No. 1983-
It has already been proposed as No. 094445.
本発明は単相交流を単相交流に周波数も変えて
変換することができ、かつ１次側の単相入力電圧
を一定としたとき、２次側の単相出力電圧を位相
差を保持したまた自由に可変できる変換器を提供
することを目的としたものである。
The present invention can convert single-phase AC to single-phase AC by changing the frequency, and when the single-phase input voltage on the primary side is constant, the single-phase output voltage on the secondary side can maintain the phase difference. Another purpose is to provide a converter that can be freely varied.
上記の目的を達成する本発明は第１、第２図示
のように２つの環状磁心Ａ，Ｂにぞれぞれ施こし
た同一巻数n1＝n1′の２つの巻線を直列に正接続
して単相入力電圧Vioが印加される入力側巻線Na
とし、同じく２つの環状磁心Ａ，Ｂにぞれぞれ施
こした同一巻数n2＝n2′の２つの巻線を直列に逆
接続して出力側巻線Nbとし、この出力側巻線bに
はコンデンサC1を並列に接続して該コンデンサ
C1の両端を出力端子とすると共に、更に２つの
環状磁心Ａ，Ｂに同一巻線n3＝n3′の２つの巻線
を直列に逆接続して直流制御電流idが流される制
御巻線Ndとして構成する。
The present invention, which achieves the above object, consists of two windings with the same number of turns n 1 = n 1 ' applied to two annular magnetic cores A and B, respectively, in series, as shown in the first and second figures. Input side winding N a connected to which single-phase input voltage V io is applied
Similarly, two windings with the same number of turns n 2 = n 2 ' applied to the two annular magnetic cores A and B are connected in reverse in series to form the output side winding N b , and this output side winding is Connect capacitor C 1 in parallel to line b .
Both ends of C 1 are used as output terminals, and two windings of the same winding n 3 = n 3 ' are connected in series and reversely to the two annular magnetic cores A and B, and a control winding is connected to which the DC control current id is passed. Configure as line N d .
以下図面によつて本発明の一実施例の構成を詳
細に説明する。
DESCRIPTION OF THE PREFERRED EMBODIMENTS The structure of an embodiment of the present invention will be explained in detail below with reference to the drawings.
第１図はその構成説明図、第２図はその回路
図、第３図は実施例で使用するＵ形磁心の形状寸
法を示す説明図である。 FIG. 1 is an explanatory diagram of its configuration, FIG. 2 is a circuit diagram thereof, and FIG. 3 is an explanatory diagram showing the shape and dimensions of the U-shaped magnetic core used in the embodiment.
Ｕ形磁心A1，A2，B1，B2は長さｌ＝107mm、
幅Ｗ＝20mm、高さｈ＝58mm、厚さｔ＝８mm、アー
ム間の距離ｆ＝92mmの積層鉄心で、フエライトコ
アでもよい。 U-shaped magnetic cores A 1 , A 2 , B 1 , B 2 have length l=107 mm,
It is a laminated iron core with width W = 20 mm, height h = 58 mm, thickness t = 8 mm, and distance between arms f = 92 mm, and a ferrite core may be used.
２つのＵ形磁心A1，A2の両端を互いに接合さ
せて１つの環状磁心Ａを形成する。同様にしても
う１つの環状磁心Ｂを形成する。環状磁心Ａ，Ｂ
は２つのＵ形磁心で形成しなくてよく、Ｏ形磁心
を用いることができる。 One annular magnetic core A is formed by joining both ends of the two U-shaped magnetic cores A 1 and A 2 to each other. Another annular magnetic core B is formed in the same manner. Annular magnetic core A, B
does not have to be formed by two U-shaped cores; an O-shaped core can be used.
この２つの環状磁心Ａ，Ｂにぞれぞれ直径0.5
mmのフオルマール線を用いた同一巻数n1＝n1′＝
250回の２つの巻線を施こし、これらを直列に正
接続して入力側巻線Naとし、これに単相入力電
源Eiを接続する。 These two annular magnetic cores A and B each have a diameter of 0.5
Same number of turns using mm formal wire n 1 = n 1 ′=
Two windings of 250 turns are made, and these are connected in series in a positive direction to form the input side winding N a , and a single-phase input power source E i is connected to this.
同じく２つの環状磁心Ａ，Ｂにそれぞれ直径
0.5mmのフオルマール線を用いた同一巻数n2＝
n2′＝250回の２つの巻線を施こし、これらを直列
に逆接続して出力側巻線Nbとし、この出力側巻
線NbにはコンデンサC1を並列に接続して該コン
デンサC1の両端を出力端子とする。 Similarly, each of the two annular magnetic cores A and B has a diameter
Same number of turns using 0.5mm formal wire n 2 =
Two windings with n 2 ′ = 250 turns are connected in reverse in series to form the output winding N b , and a capacitor C 1 is connected in parallel to this output winding N b to form the output winding N b . Both ends of capacitor C1 are output terminals.
更に２つの環状磁心Ａ，Ｂにそれぞれ直径0.5
mmのフオルマール線を用いた同一巻数n3＝n3′＝
270回の２つの巻線を施こし、これらを直列に逆
接続して制御巻線Ndとし、この制御巻線Ndに直
列に直流制御電源Edと可変抵抗Ｒの直列回路を
接続するる。 Furthermore, two annular magnetic cores A and B each have a diameter of 0.5
Same number of turns using mm formal wire n 3 = n 3 ′=
Two windings of 270 turns are made, and these are connected in reverse in series to form a control winding Nd , and a series circuit of a DC control power source Ed and a variable resistor R is connected in series to this control winding Nd . Ru.
次にこの作用を説明する。入力側巻線Naに単
相入力電源Eiによつて単相入力電圧Vioを印加し
交流電流を流すと、環状磁心Ａ，Ｂにぞれぞれ入
力側巻線Na、出力側巻線Nbによつて第１図の矢
印方向に磁束φa，φbが発生する。この磁束φa，
φbは磁気的に結合しないでそれぞれ独立磁路と
なつている。
Next, this effect will be explained. When a single-phase input voltage V io is applied to the input-side winding N a by a single-phase input power source E i and an alternating current flows, the input-side winding N a and the output-side winding N a are applied to the annular magnetic cores A and B, respectively. Magnetic fluxes φ a and φ b are generated by the winding N b in the direction of the arrow in FIG. This magnetic flux φ a ,
φ b are not magnetically coupled and form independent magnetic paths.
換言すれば通常の変圧器は１次、２次側共に変
圧器作用、すなわち誘導電圧が生じるわけである
が、これは１次、２次側の磁気的な結合でもつて
生じ、１次側、２次側の磁束は同相である。従つ
て、その電圧も当然、同相となるのであるが、本
発明の場合は出力側を逆接続してあるので、２次
側の変圧器誘導作用が打ち消し合うので磁気的な
結合を考えなくてもよいから１次側と２次側の磁
束φa，φbは90度の位相差を有しているために磁
路としては、独立と考えられる。 In other words, in a normal transformer, transformer action, that is, induced voltage occurs on both the primary and secondary sides, but this also occurs due to magnetic coupling between the primary and secondary sides, and the primary side, The magnetic flux on the secondary side is in phase. Therefore, the voltages are naturally in the same phase, but in the case of the present invention, the output side is reversely connected, so the induced effects of the transformer on the secondary side cancel each other out, so there is no need to consider magnetic coupling. Since the magnetic fluxes φ a and φ b on the primary side and the secondary side have a phase difference of 90 degrees, they are considered to be independent as magnetic paths.
しかし、使用している環状磁心は共有であるた
め、入力側磁束φaによつて出力側巻線Nbの磁気
抵抗が変調するために、それに伴なつて出力側イ
ンダクタンクも変調し、その結果、出力側巻線
NbとコンデンサC1によつてパラメトリツク発振
が生じ、単相入力電圧Vioに対し90度の位相差を
持つた出力電圧V2が確立する。この90度の位相
差を保持したまま出力電圧V2の値のみを加減さ
せるには独立している出力側の磁路、すなわち、
磁束φbを加減すればよく、そのためには、逆接
続した制御巻線Ndに直流制御電源Edにより直流
制御電流idを流し、この直流制御電流idを可変抵
抗Ｒによつて加減することによつて、環状磁心
Ａ，Ｂによれぞれ発生する磁束φdを変化させれ
ばよい。このようにすると、ある半周期では環状
磁心Ａの磁束は第１図の矢印で示すようにφbと
φdの差となつて未飽和となり環状磁心Ｂの磁束
はφbとφdの和となつて飽和する。また、次の半
周期ではこれと逆に環状磁心Ａが飽和し、環状磁
心Ｂが未飽和となり、以下半周期毎にこれを繰り
返しながら、磁束が制御されることにより、出力
電圧V2が制御されることになる。 However, since the annular magnetic core used is shared, the magnetic resistance of the output winding N b is modulated by the input magnetic flux φ a , and the output inductor tank is also modulated accordingly. As a result, the output side winding
Parametric oscillation is generated by Nb and capacitor C1 , and an output voltage V2 is established with a phase difference of 90 degrees with respect to the single-phase input voltage Vio . In order to adjust only the value of the output voltage V 2 while maintaining this 90 degree phase difference, an independent magnetic path on the output side, that is,
It is sufficient to adjust the magnetic flux φ b . To do this, a DC control current id is caused to flow through the reversely connected control winding N d by a DC control power source E d , and this DC control current id is adjusted by a variable resistor R. Therefore, the magnetic flux φ d generated by the annular magnetic cores A and B may be changed. In this way, in a certain half cycle, the magnetic flux of the annular magnetic core A becomes the difference between φ b and φ d , as shown by the arrow in Figure 1, and becomes unsaturated, and the magnetic flux of the annular magnetic core B becomes the sum of φ b and φ d . It becomes saturated. In addition, in the next half cycle, the annular magnetic core A becomes saturated and the annular magnetic core B becomes unsaturated, and as this is repeated every half cycle, the magnetic flux is controlled and the output voltage V 2 is controlled. will be done.
次に直流制御電流id対出力電圧V2の関係につ
いて述べる。 Next, the relationship between DC control current id and output voltage V2 will be described.
第１、第２図の入力側巻線Naの両端に単相入
力電圧Vioを印加し、出力側巻線Nbの両端にコン
デンサC1＝275μFを接続する。次に単相入力電圧
Vioを徐々に増加していくと、Vio＝34V付近でパ
ラメトリツク発振が生じ単相入力電圧Vioに対し
て90度の位相差を有した正弦波の出力電圧V2が
確立する。第４図及び第５図はそれぞれ入力電圧
Vioと出力電圧V2の波形図及びベクトル図であ
る。また、第６図は入力電圧Vio対出力電圧V2の
関係を示す特性線図である。この第６図からも判
るように本発明は、定電圧性を有した変換器であ
り、入力電圧が歪波形でも出力電圧波形は正弦波
（第４図参照）となり、更に過負荷に対する保護
や垂下特性を有している。そのために出力側を短
絡しても発振が停止するだけで回路には全々さし
つかえが無い等の優れた特徴を持つている。 A single-phase input voltage V io is applied to both ends of the input winding N a in FIGS. 1 and 2, and a capacitor C 1 =275 μF is connected to both ends of the output winding N b . Then single phase input voltage
As V io is gradually increased, parametric oscillation occurs near V io =34V, and a sinusoidal output voltage V 2 having a phase difference of 90 degrees with respect to the single-phase input voltage V io is established. Figures 4 and 5 are input voltages, respectively.
3 is a waveform diagram and a vector diagram of V io and output voltage V 2. FIG. Further, FIG. 6 is a characteristic diagram showing the relationship between the input voltage V io and the output voltage V 2 . As can be seen from Fig. 6, the present invention is a converter with constant voltage characteristics, and even if the input voltage is a distorted waveform, the output voltage waveform is a sine wave (see Fig. 4). It has drooping characteristics. Therefore, even if the output side is short-circuited, the oscillation will simply stop and there will be no problem with the circuit.
本発明は、これらの利点を生かした上で、環状
磁心Ａ，Ｂに制御巻線Ndを施こしたその両端に
直流制御電源Edと可変抵抗Ｒの直列回路を接続
し可変抵抗Ｒを徐々に変えながら直流制御電流id
を変化することにより、出力電圧V2を順次変動
させるものである。第７図はそのときの特性を示
したもので、Vio＝35V一定時における直流制御
電流id対出力電圧V2の関係である。第７図から
も明らかなようにidが0.4〜1.75Aまで変化した場
合、出力電圧V2は35V〜6Vまで変動していく様
子が理解できよう。第８図はVio＝35V一定、id
＝1.2Aにした場合の入力電圧波形対出力電圧波
形を示したものがあるが、位相差が90度を保持し
たまま出力電圧が変動していく状態が理解できよ
う。 The present invention makes use of these advantages, and the control windings Nd are provided on the annular magnetic cores A and B, and a series circuit of a DC control power source Ed and a variable resistor R is connected to both ends of the control windings Nd, and the variable resistor R is connected to both ends of the control windings Nd. DC control current while gradually changing ID
By changing the output voltage V 2 , the output voltage V 2 is sequentially varied. FIG. 7 shows the characteristics at that time, which is the relationship between the DC control current id and the output voltage V 2 when V io =35V constant. As is clear from FIG. 7, it can be seen that when id changes from 0.4 to 1.75A, the output voltage V2 changes from 35V to 6V. Figure 8 shows V io = 35V constant, id
There is a diagram showing the input voltage waveform vs. output voltage waveform when = 1.2A, and you can understand that the output voltage fluctuates while maintaining a 90 degree phase difference.
また、２倍周波数時の出力電圧も制御電流を駆
使することによつて変動が可能であることが実験
によつて確認できた。 Furthermore, it was confirmed through experiments that the output voltage at double frequency can also be varied by making full use of the control current.
以上の説明より明らかなように本発明によれば
次のような効果を奏する。
As is clear from the above description, the present invention provides the following effects.
出力電圧の位相差を保持したまた、自由に変
えることができる。入力側巻線と出力側巻線に
二相サーボ・モータを接続することによりその回
転ならびに回転制御できる。同一磁心を用いて
構成できるため、構造が安価である。能動体素
子は一切使用していな。過負荷保護や垂下特性
を有しているため、出力側を短絡しても発振が停
止するだけで回転には全く影響が無い。出力電
圧波形は良好である。 The phase difference of the output voltage is maintained and can also be changed freely. By connecting a two-phase servo motor to the input and output windings, the rotation and rotation can be controlled. The structure is inexpensive because it can be constructed using the same magnetic core. No active elements are used. Since it has overload protection and drooping characteristics, even if the output side is shorted, oscillation will simply stop and rotation will not be affected at all. The output voltage waveform is good.
第１図は本発明の一実施例の構成説明図、第２
図はその回路図、第３図は実施例で使用するＵ形
磁心の形状寸法を示す説明図、第４図及び第５図
はそれぞれ入力電圧と出力電圧の波形図及びベク
トル図、第６図は入力電圧対出力電圧の関係を示
す特性線図、第７図は入力電圧を一定としたとき
の直流制御電流対出力電圧の特性線図、第８図は
入力電圧及び直流制御電流を一定とした時の入力
電圧と出力電圧の波形図である。
Ａ，Ｂ……環状磁心、Na……入力側巻線、Nb
……出力側巻線、Nd……制御巻線、Ei……単相
入力電源、C1……コンデンサ、Ed……直流制御
電源、Ｒ……可変抵抗。
FIG. 1 is an explanatory diagram of the configuration of one embodiment of the present invention, and FIG.
The figure is the circuit diagram, Figure 3 is an explanatory diagram showing the shape and dimensions of the U-shaped magnetic core used in the example, Figures 4 and 5 are waveform diagrams and vector diagrams of the input voltage and output voltage, respectively, and Figure 6 is a characteristic diagram showing the relationship between input voltage and output voltage, Fig. 7 is a characteristic diagram of DC control current versus output voltage when the input voltage is constant, and Fig. 8 is a characteristic diagram showing the relationship between input voltage and DC control current. FIG. 3 is a waveform diagram of input voltage and output voltage when A, B...Annular magnetic core, N a ...Input side winding, N b
... Output winding, N d ... Control winding, E i ... Single-phase input power supply, C 1 ... Capacitor, E d ... DC control power supply, R ... Variable resistance.
Claims (1)
一巻数n1＝n1′の２つの巻線を直列に正接続して
単相入力電圧Vioが印加される入力側巻線Naと
し、同じく２つの環状磁心Ａ，Ｂにぞれぞれ施こ
した同一巻数n2＝n2′の２つの巻線を直列に逆接
続して出力側巻線Nbとし、この出力側巻線Nbに
はコンデンサC1を並列に接続して該コンデンサ
C1の両端を出力端子とすると共に、更に２つの
環状磁心Ａ，Ｂに同一巻線n3＝n3′の２つの巻線
を直列に逆接続して直流制御電流idが流される制
御巻線Ndとして構成した変換器。1 Input side winding to which a single-phase input voltage V io is applied by connecting two windings with the same number of turns n 1 = n 1 ' in series on two annular magnetic cores A and B, respectively. Let N a be the output side winding N b by connecting two windings with the same number of turns n 2 = n 2 ' on the two annular magnetic cores A and B in reverse in series. A capacitor C 1 is connected in parallel to the side winding N b .
Both ends of C 1 are used as output terminals, and two windings of the same winding n 3 = n 3 ' are connected in series and reversely to the two annular magnetic cores A and B, and a control winding is connected to which the DC control current id is passed. Transducer configured as line N d .
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58166068A JPS6059974A (en) | 1983-09-09 | 1983-09-09 | Converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58166068A JPS6059974A (en) | 1983-09-09 | 1983-09-09 | Converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS6059974A JPS6059974A (en) | 1985-04-06 |
| JPH0465636B2 true JPH0465636B2 (en) | 1992-10-20 |
Family
ID=15824378
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP58166068A Granted JPS6059974A (en) | 1983-09-09 | 1983-09-09 | Converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6059974A (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR101048659B1 (en) * | 2010-06-01 | 2011-07-14 | 이명환 | Auto voltage regulator for charge |
| WO2013039415A1 (en) * | 2011-09-02 | 2013-03-21 | ХОРЬЯКОВ, Владимир Владимирович | Resonant transducer |
| JP6102623B2 (en) * | 2013-08-08 | 2017-03-29 | 宇部興産株式会社 | Method for producing high purity aromatic compound |
-
1983
- 1983-09-09 JP JP58166068A patent/JPS6059974A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS6059974A (en) | 1985-04-06 |
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