JPH0435084B2 - - Google Patents
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- Publication number
- JPH0435084B2 JPH0435084B2 JP61185760A JP18576086A JPH0435084B2 JP H0435084 B2 JPH0435084 B2 JP H0435084B2 JP 61185760 A JP61185760 A JP 61185760A JP 18576086 A JP18576086 A JP 18576086A JP H0435084 B2 JPH0435084 B2 JP H0435084B2
- Authority
- JP
- Japan
- Prior art keywords
- distortion
- level
- signal
- input signal
- phase
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
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- 230000010363 phase shift Effects 0.000 claims abstract description 6
- 230000003321 amplification Effects 0.000 claims description 8
- 238000003199 nucleic acid amplification method Methods 0.000 claims description 8
- 230000002194 synthesizing effect Effects 0.000 abstract description 3
- 238000002955 isolation Methods 0.000 abstract description 2
- 238000010586 diagram Methods 0.000 description 7
- 230000000694 effects Effects 0.000 description 5
- 238000001228 spectrum Methods 0.000 description 3
- 230000002238 attenuated effect Effects 0.000 description 2
- 230000015572 biosynthetic process Effects 0.000 description 2
- 239000002131 composite material Substances 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 238000003786 synthesis reaction Methods 0.000 description 2
- 230000003247 decreasing effect Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
〔概要〕
歪補償器において、入力するマイクロ波のレベ
ルをサーキユレータで挟んだ歪レベル調整手段で
調整した後に分岐し、移相手段で移相したもの
と、歪発生増幅手段で増幅して歪を発生させたも
のとを合成して被補償増幅器で発生する歪と逆位
相、等振幅の補償用歪を発生する様にして調整工
数の削減を図つたものである。[Detailed Description of the Invention] [Summary] In a distortion compensator, the level of an input microwave is adjusted by a distortion level adjusting means sandwiched between circulators, and then branched and shifted by a phase shifting means, and a distortion generating amplification device. This is intended to reduce the number of adjustment steps by synthesizing the distortion generated by amplifying the distortion generated by the compensation amplifier to generate compensation distortion having an opposite phase and equal amplitude to the distortion generated by the compensated amplifier.
本発明は例えばマイクロ波帯で使用する歪補償
器の改良に関するものである。
The present invention relates to improvements in distortion compensators used in microwave bands, for example.
近年、マイクロ波を用いたデイジタル通信では
周波数の有効利用の為に例えば16値直交振幅変調
方式が実用化されたが、更に利用効率の向上の為
に256値などと多値化の傾向にある。 In recent years, in digital communications using microwaves, for example, 16-value orthogonal amplitude modulation has been put into practical use in order to make effective use of frequencies, but there is a trend toward multi-value modulation, such as 256 values, to further improve usage efficiency. .
この変調方式は搬送波の振幅と位相とを変調信
号に対応して変化させているので、これに使用す
る電力増幅器は振幅や位相の変化を歪なく増幅し
なければならないので、A級動作となり、しかも
最大出力レベルは標準出力レベルよりも例えば
10dB以上も高くしなければならないので消費電
力が大きくなる。 Since this modulation method changes the amplitude and phase of the carrier wave in accordance with the modulation signal, the power amplifier used for this method must amplify changes in amplitude and phase without distortion, so it operates in class A. Moreover, the maximum output level is higher than the standard output level, e.g.
Since it has to be increased by more than 10 dB, power consumption increases.
そこで、この消費電力を低下させる為に歪補償
器で発生させた補償用歪で電力増幅器で発生する
非直線歪を補償して、最大出力レベルの小さな電
力増幅器を使用する場合があるが、この時に調整
工数が少ないことが必要である。 Therefore, in order to reduce this power consumption, a power amplifier with a small maximum output level is sometimes used by compensating for the nonlinear distortion generated in the power amplifier with compensation distortion generated by a distortion compensator. Sometimes it is necessary to reduce the number of adjustment steps.
第3図は従来例のブロツク図、第4図は第3図
の動作説明図を示す。
FIG. 3 is a block diagram of a conventional example, and FIG. 4 is an explanatory diagram of the operation of FIG. 3.
尚、第4図中のa〜eは第3図中の同じ記号の
部分のスペクトラムを示す。以下、第4図を参照
しながら第3図の動作を説明する。 Note that a to e in FIG. 4 indicate spectra of portions with the same symbols in FIG. 3. The operation shown in FIG. 3 will be explained below with reference to FIG.
先ず、入力した周波数1,2のマイクロ波(第
4図a参照)はハイブリツド1で分岐された後、
第4図bに示す様に移相器2で位相が移相された
ものと、電力増幅器7と同じ増幅特性を持つ歪発
生増幅器4で増幅され、ハイブリツド5,6及び
ダイオードD1,D2で構成された可変減衰器8で
第4図cに示す様に減衰されたものとがハイブリ
ツド3で合成されて第4図dに示す様な信号が出
力する。 First, the input microwaves of frequencies 1 and 2 (see Figure 4 a) are split by hybrid 1, and then
As shown in FIG. 4b, the phase is shifted by the phase shifter 2, and is amplified by the distortion generating amplifier 4, which has the same amplification characteristics as the power amplifier 7 . The signal attenuated by the variable attenuator 8 constructed as shown in FIG. 4c is combined by the hybrid 3 to output a signal as shown in FIG. 4d.
この出力信号は電力増幅器7で増幅されるが、
この時に発生する第4図eに示す3次歪の成分
(f1−2f2)及び(2f2−f1)は補償用歪と逆位相、
等振幅になつているので打ち消されて歪のない1
及び2の波が出力される。尚、帯域内に落ちる歪
は3次歪によるものが多い。 This output signal is amplified by the power amplifier 7,
The third-order distortion components (f 1 −2f 2 ) and (2f 2 −f 1 ) shown in FIG. 4e that occur at this time are in opposite phase to the compensation distortion,
Since the amplitudes are equal, they are canceled and there is no distortion1
and 2 waves are output. Note that the distortion that falls within the band is often due to third-order distortion.
ここで、可変減衰器8は位相の温度特性が大き
いサーキユレータを用いると周囲温度が変化する
ことにより補償用歪の位相が変化して移相手段の
再調整が必要となるので、温度特性のより少ない
ハイブリツド5,6を使用してサーキユレータと
同じ効果を持たせているが、この部分の動作は下
記の様である。 Here, if the variable attenuator 8 uses a circulator with a large phase temperature characteristic, the phase of the compensation distortion will change due to a change in the ambient temperature, and the phase shifting means will need to be readjusted. The same effect as a circulator is achieved by using fewer hybrids 5 and 6, and the operation of this part is as follows.
先ず、この減衰器の中のダイオードD1,D2は
例えばピンダイオードで、このダイオードに印加
されるバイアス電圧が0の時は理想的にはインピ
ーダンスが無限大、V1の時は短絡されてここに
加えられるマイクロ波は全反射するので減衰量は
無限大(実際は20dB程度)となる。従つて、バ
イアス電圧を変化させればそれに対応して減衰量
は0から無限大まで変化する。 First, the diodes D 1 and D 2 in this attenuator are, for example, pin diodes, and ideally when the bias voltage applied to these diodes is 0, the impedance is infinite, and when it is V 1 , the impedance is short-circuited. Since the microwaves applied here are totally reflected, the amount of attenuation is infinite (actually about 20 dB). Therefore, if the bias voltage is changed, the amount of attenuation changes from 0 to infinity.
又、ハイブリツドの端子に加えられたマイク
ロ波は端子に同相、端子には−90度で表れる
とするとすると、2つのダイオードD1,D2で全
反射されたマイクロ波は端子→→は0度
で、端子→→は−90度で、端子→→
は−90度で、端子→→は−180度でそれぞ
れ戻つてくるので端子では逆相となり入力側に
表れないのでサーキユレータと同じ効果を持つ。 Also, assuming that the microwave applied to the terminal of the hybrid is in phase with the terminal and appears at -90 degrees at the terminal, the microwave totally reflected by the two diodes D 1 and D 2 will appear at 0 degrees at the terminal →→ So, the terminal →→ is -90 degrees, and the terminal →→
is -90 degrees, and the terminal →→ returns at -180 degrees, so the terminal has the opposite phase and does not appear on the input side, so it has the same effect as a circulator.
しかし、マイクロ波帯におけるダイオードは等
価的に抵抗分とリアクタンス分から構成されてい
るとみなされるので、バイアス電圧を変化させて
減衰量を変化するとリアクタンス分も変化して位
相が少し変化する。
However, a diode in the microwave band is equivalently considered to be composed of a resistance component and a reactance component, so when the bias voltage is changed to change the amount of attenuation, the reactance component also changes and the phase changes slightly.
そこで、第4図dに示す様なスペクトラムにす
る為に移相器2の移相量を再調整しなければなら
ないので調整工数が増えると云う問題点がある。 Therefore, the amount of phase shift of the phase shifter 2 must be readjusted in order to obtain a spectrum as shown in FIG. 4d, which poses a problem in that the number of adjustment steps increases.
上記の問題点は第1図に示す様に、入力信号を
分岐手段9で分岐し、分岐された一方を移相手段
10で移相した主信号成分と、分岐された他方を
歪発生増幅手段11で増幅して発生させた主信号
成分に補償歪みが付加されたものとを、合成手段
12で合成して、被補償増幅器で発生する歪と逆
移相、等振幅の補償用歪を入力信号に付加して出
力する歪補償器において、
入力信号のレベルを調整する歪レベル調整手段
14を該分岐手段9の前段に設け、該歪レベル調
整手段9により前記移相手段10と歪発生増幅手
段12とに入力する入力信号のレベルを同時に調
整することによつて、出力信号における主信号成
分と補償歪成分のレベル比を調整するようにした
本発明の歪補償器により解決される。
As shown in FIG. 1, the above problem is caused by splitting the input signal by a branching means 9, and converting one branched signal into a main signal component whose phase is shifted by a phase shifting means 10, and the other branched signal into a distortion generating amplification means. A synthesis means 12 synthesizes the main signal component amplified and generated in step 11 with compensation distortion added thereto, and inputs compensation distortion having an opposite phase shift and equal amplitude to the distortion generated in the compensated amplifier. In a distortion compensator that is added to and outputs a signal, a distortion level adjustment means 14 for adjusting the level of the input signal is provided before the branching means 9, and the distortion level adjustment means 9 connects the phase shift means 10 and distortion generation amplification. This problem is solved by the distortion compensator of the present invention, which adjusts the level ratio of the main signal component and the compensation distortion component in the output signal by simultaneously adjusting the level of the input signal input to the means 12.
本発明は入力信号のレベルを変化すると3次歪
成分が入力信号のレベル変化量の3倍変化するの
で、分岐手段9の前に設けた歪レベル調整手段1
4で合成手段12の出力側の3次歪成分のレベル
を制御することが可能となるが、分岐前の為にこ
の歪レベル調整手段のレベル調整による通過位相
変化と温度による特性変化とは分岐された両方の
部分に同じ様に影響を与える為、合成手段12の
出力側に対しては何ら影響を与えない。
In the present invention, when the level of the input signal is changed, the third-order distortion component changes by three times the amount of change in the level of the input signal, so the distortion level adjustment means 1 provided before the branching means 9
4 makes it possible to control the level of the third-order distortion component on the output side of the combining means 12, but since this is before branching, the passing phase change due to the level adjustment of the distortion level adjusting means and the characteristic change due to temperature are separated. Since it affects both parts in the same way, the output side of the combining means 12 is not affected at all.
そこで、この歪レベル調整手段14にサーキユ
レータを用いてアイソレーシヨンが良好な状態で
歪レベルを調整すると共に、歪発生増幅手段11
には半固定の減衰器を挿入して減衰量を可変しな
い様にして位相ずれの発生を防止して再調整をな
くし、調整工数の削減を図つた。 Therefore, a circulator is used in the distortion level adjustment means 14 to adjust the distortion level with good isolation, and the distortion generation amplification means 11
A semi-fixed attenuator was inserted to prevent the amount of attenuation from changing, thereby preventing the occurrence of phase shifts and eliminating the need for readjustment, thereby reducing the number of adjustment steps.
第2図は本発明の実施例のブロツク図を示す。 FIG. 2 shows a block diagram of an embodiment of the invention.
尚、全図を通じて同一符号は同一対象物で、サ
ーキユレータ141,142、可変減衰器143
と抵抗R5,R6は歪レベル調整手段14、ハイブ
リツド91と抵抗R7は分岐手段9、歪発生増幅
器111と半固定減衰器112は歪発生増幅手段
11、ハイブリツド121と抵抗R8は合成手段
12の構成部分を示す。 The same reference numerals throughout the drawings indicate the same objects, circulators 141, 142, variable attenuator 143.
and resistors R 5 and R 6 are distortion level adjusting means 14, hybrid 91 and resistor R 7 are branching means 9, distortion generating amplifier 111 and semi-fixed attenuator 112 are distortion generating amplifying means 11, hybrid 121 and resistor R 8 are composite The components of the means 12 are shown.
又、R5〜R10は終端抵抗である。以下、第4図
を参照して第2図により動作を説明する。 Moreover, R 5 to R 10 are terminating resistors. The operation will be described below with reference to FIG. 2 with reference to FIG. 4.
先ず、入力信号はサーキユレータ141、ピン
ダイオードを用いた可変減衰器143、サーキユ
レータ142を通つた後にハイブリツド91で分
岐され、移相器10で位相シフトしたものと、歪
発生増幅器111で増幅して補償用歪を発生し半
固定減衰器112を通つたものとがハイブリツド
121で合成される。 First, the input signal passes through a circulator 141, a variable attenuator 143 using a pin diode, and a circulator 142, and then is branched at a hybrid 91, phase-shifted by a phase shifter 10, and amplified by a distortion generating amplifier 111 for compensation. The hybrid 121 synthesizes the generated distortion and the one that has passed through the semi-fixed attenuator 112 .
そして、第4図dに示すスペクトラムを持つ合
成信号は利得調整用可変減衰器13を構成するサ
ーキユレータ131、可変減衰器133、サーキ
ユレータ132で所定のレベルに調整して被補償
増幅器(図示せず)に加えられる。 Then, the composite signal having the spectrum shown in FIG. 4d is adjusted to a predetermined level by the circulator 131, variable attenuator 133, and circulator 132 that constitute the variable attenuator 13 for gain adjustment, and then the synthesized signal is sent to the compensated amplifier (not shown). added to.
ここで、可変減衰器143は補償用の歪レベル
を調整するためのもので、減衰量を1dB少なくす
ると移相器10の出力、即ち主信号(f1及びf2の
信号成分を云う)は1dB高く、歪発生増幅器11
1の出力は主信号が1dB、3次歪成分は3dB高く
なるので、これをハイブリツド121で合成する
と主信号は1dB、3次歪成分は3dB高くなる。そ
こで、サーキユレータ131を通した後に可変減
衰器133で1dB減衰させると、主信号は0dB、
3次歪成分は+2dBとなり、歪成分のみが変化す
る。 Here, the variable attenuator 143 is for adjusting the distortion level for compensation, and when the attenuation amount is reduced by 1 dB, the output of the phase shifter 10, that is, the main signal (referring to the signal components of f 1 and f 2 ) 1dB higher, distortion generating amplifier 11
In the output of the hybrid 121, the main signal becomes 1 dB higher and the 3rd order distortion component becomes 3 dB higher, so when these are combined by the hybrid 121, the main signal becomes 1 dB higher and the 3rd order distortion component becomes 3 dB higher. Therefore, if the main signal is attenuated by 1 dB with the variable attenuator 133 after passing through the circulator 131, the main signal becomes 0 dB.
The third-order distortion component becomes +2 dB, and only the distortion component changes.
更に、可変減衰器の減衰量を1dB多くし、可変
減衰器133で減衰量を1dB少なくすると主信号
は変化せず、3次歪成分は−2dBとなり、可変減
衰器143の減衰量を調整することにより歪レベ
ルの調整ができる。 Furthermore, if the attenuation amount of the variable attenuator 133 is increased by 1 dB and the attenuation amount is decreased by 1 dB by the variable attenuator 133, the main signal remains unchanged, the third-order distortion component becomes -2 dB, and the attenuation amount of the variable attenuator 143 is adjusted. This allows the distortion level to be adjusted.
又、サーキユレータを分岐線路内に設けていな
い為に第4図dの特性は周囲温度が変化しても保
たれるので再調整の可能性が減り、調整工数が削
減される。 Furthermore, since the circulator is not provided in the branch line, the characteristics shown in FIG. 4d are maintained even if the ambient temperature changes, reducing the possibility of readjustment and reducing the number of adjustment steps.
以下詳細に説明した様に本発明によれば、調整
工数が削減されると云う効果がある。
As explained in detail below, the present invention has the effect of reducing the number of adjustment steps.
第1図は本発明の原理ブロツク図、第2図は本
発明の実施例のブロツク図、第3図は従来例のブ
ロツク図、第4図は第3図の動作説明図を示す。
図において、9は分岐手段、10は移相手段、
11は歪発生増幅手段、12は合成手段、13は
利得調整用可変減衰器、14は歪レベル調整手段
を示す。
FIG. 1 is a block diagram of the principle of the present invention, FIG. 2 is a block diagram of an embodiment of the present invention, FIG. 3 is a block diagram of a conventional example, and FIG. 4 is an explanatory diagram of the operation of FIG. 3. In the figure, 9 is a branching means, 10 is a phase shifting means,
Reference numeral 11 indicates a distortion generation amplification means, 12 a synthesis means, 13 a variable attenuator for gain adjustment, and 14 a distortion level adjustment means.
Claims (1)
一方を移相手段10で移相した主信号成分と、分
岐された他方を歪発生増幅手段11で増幅して発
生させた主信号成分に補償歪みが付加された信号
とを、合成手段12で合成して、被補償増幅器で
発生する歪と逆移相、等振幅の補償用歪を入力信
号に付加して出力する歪補償器において、 入力信号のレベルを調整する歪レベル調整手段
14を該分岐手段の前段に設け、該歪レベル調整
手段により前記移相手段10と前記歪発生増幅手
段11とに入力する入力信号のレベルを同時に調
整することによつて、出力信号における主信号成
分と補償歪成分のレベル比を調整するようにした
ことを特徴とする歪補償器。[Scope of Claims] 1. The input signal is split by the branching means 9, and one of the branched signals is phase-shifted by the phase shifting means 10, and the other branched signal is amplified and generated by the distortion generation and amplification means 11. The synthesizer 12 synthesizes the main signal component and the signal to which compensation distortion has been added, and outputs the input signal by adding compensating distortion of equal amplitude and inverse phase to the distortion generated in the compensated amplifier to the input signal. In the distortion compensator, a distortion level adjustment means 14 for adjusting the level of the input signal is provided at a stage before the branching means, and the input signal inputted to the phase shift means 10 and the distortion generation and amplification means 11 by the distortion level adjustment means is provided. A distortion compensator characterized in that the level ratio of a main signal component and a compensation distortion component in an output signal is adjusted by simultaneously adjusting signal levels.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP18576086A JPS6342207A (en) | 1986-08-07 | 1986-08-07 | Distortion compensator |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP18576086A JPS6342207A (en) | 1986-08-07 | 1986-08-07 | Distortion compensator |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS6342207A JPS6342207A (en) | 1988-02-23 |
JPH0435084B2 true JPH0435084B2 (en) | 1992-06-10 |
Family
ID=16176389
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP18576086A Granted JPS6342207A (en) | 1986-08-07 | 1986-08-07 | Distortion compensator |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS6342207A (en) |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP3545125B2 (en) * | 1996-03-08 | 2004-07-21 | 富士通株式会社 | Distortion compensation circuit |
GB2608839A (en) * | 2021-07-13 | 2023-01-18 | Walk It Ltd | Footwear accessory |
Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5936406A (en) * | 1982-08-23 | 1984-02-28 | Nec Corp | Distortion compensating circuit of predistortion system |
-
1986
- 1986-08-07 JP JP18576086A patent/JPS6342207A/en active Granted
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5936406A (en) * | 1982-08-23 | 1984-02-28 | Nec Corp | Distortion compensating circuit of predistortion system |
Also Published As
Publication number | Publication date |
---|---|
JPS6342207A (en) | 1988-02-23 |
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