JPH04113712A - Longitudinal dual mode surface acoustic wave filter - Google Patents

Abstract

PURPOSE:To obtain a pass band without undesired spurious output in the longitudinal dual mode SAW filter using an LiNbO3 piezoelectric substrate of 64 deg. rotation Y-cut X propagation by providing a coupling capacitor in parallel electrically with an interdigital electrode to a connection part between sections of an energy confined type resonator. CONSTITUTION:Two sections of energy confined type resonators are formed on an LiNbO3 piezoelectric substrate of 64 deg. rotation Y-cut X propagation. A coupling capacitor 30 is provided in parallel electrically with a connection part between an output interdigital electrode 23 of a 1st section and an input interdigital electrode 26 of a 2nd section. Thus, the longitudinal dual mode SAW filter employing the LiNbO3 piezoelectric substrate of 64 deg. rotation Y-cut X propagation having been difficult in a conventional filter in practical use is realized.

Description

DETAILED DESCRIPTION OF THE INVENTION [Industrial Field of Application] The present invention relates to a band-pass type, low-loss surface acoustic wave filter that utilizes vertical dual mode coupling.

[Prior Art] FIG. 6 shows a conventional vertical dual-mode SAW filter 1 constructed of an energy-trapped resonator that utilizes surface acoustic waves (SAW). This SAW filter 1 has two sets of comb-shaped electrodes 3 and 4 for excitation of surface waves on the surface of a piezoelectric substrate 2, and reflectors 5 and 6 are arranged on both sides thereof.

In such a configuration, as shown in FIG. 7, the energy of the surface wave excited between the reflector 5 and the reflector 6 is confined, and zero-order and first-order longitudinal resonance modes appear. The frequency difference between these two modes changes depending on the total logarithm of the comb-shaped electrodes 3 and 4, and by matching with the human impedance, the vertical type 2 A heavy mode SAW filter 1 is realized.

Furthermore, even higher-order resonance modes actually exist. For example, as shown in FIG. 8, in addition to two sets of comb-shaped electrodes 3 and 4 between reflectors 5 and 6, In some cases, another set of comb-shaped electrodes 7 is provided. In this case, it can be easily inferred that zero-order longitudinal resonance modes and second-order longitudinal resonance modes appear.

Note that in the configurations shown in FIGS. 6 to 8, the amount of suppression outside the passband is often insufficient,
Usually, a configuration as shown in FIG. 9 is adopted, in which two or more sections of the same type are cascaded in multiple stages, with one section being a SAW filter, ie, an energy-trapped resonator, having the above-described configuration.

The vertical dual mode SAW filter 1a shown in FIG. , further two sets of comb-shaped electrodes 8
and 9 and reflectors 10 and 11 are provided. These two sections of energy confinement type resonators are cascade-connected by connecting the comb-shaped electrode 4 and the comb-shaped electrode 8.

Problems to be Solved by the Invention C] In order to widen the passband of the vertical dual mode SAW filter having the configuration as described above,
It is desirable to use a piezoelectric substrate with a large electromechanical coupling coefficient, such as a LiNbO3 piezoelectric substrate with 64° rotation Y cut and X direction propagation.

However, for example, the vertical type 2 shown in FIG.
When the configuration is such as the heavy mode SAW filter 1a, in which two or more sections of energy-confined resonators are cascaded in multiple stages, the transmission characteristics are as shown in FIG. 10, at the zero-order longitudinal resonance point f. Unnecessary spurious fc appears on the high frequency side. This unnecessary spurious fc occurs similarly even when LiTaO3 with X-cut Y-direction propagation is used as a piezoelectric substrate, but in this case, the position of the unnecessary spurious fc is
Zero-order longitudinal resonance point f. Because it appears in the close vicinity of It is not. However, L iNb of 64° rotated Y-cut and X-direction propagation.

In the case of 3 piezoelectric substrates, it is difficult to keep the unnecessary spurious fc within the passband, and this is a practical problem for vertical dual mode SAW filters using LiNbO3 piezoelectric substrates with 64° rotation Y cut and X direction propagation. It became.

In addition, in FIG. 10, f indicates a longitudinal first-order resonance point.

Therefore, the object of this invention is to
The purpose of this invention is to make it possible to obtain a pass band free of unnecessary spurious components in a vertical dual mode SAW filter using a directional propagation LiNbO3 piezoelectric substrate.

[Means for Solving the Problems] This invention provides a 64° rotation Y-cut X-direction propagation LiNb
A multi-section energy-confined resonator is constructed by disposing at least two sets of comb-shaped electrodes in close proximity to each other on the O3 piezoelectric substrate, and by disposing reflectors on both sides of the comb-shaped electrodes. The present invention is directed to a vertical dual-mode SAW filter in which energy-confined resonators are cascaded in multiple stages, and in order to solve the above-mentioned technical problems, the connection between each section of the energy-confined resonators is provided. The device is characterized in that it includes a coupling capacitor that is electrically parallel to the comb-shaped electrode.

Preferably, the number of logarithms of the electrode fingers of the comb-shaped electrode and the magnitude of the coupling capacitance are set as follows. That is, the total number of electrode fingers of the comb-shaped electrodes in one section of the energy-trapped resonator is N1, the total capacitance of the comb-shaped electrodes connected by the connection part is Ct, and the size of the coupling capacitance is Cc. When N≦50 Cc/Ct≧0.5.

[Function] According to this invention, the L of 64° rotation Y cut X direction propagation
It has been experimentally confirmed that even when an iNbO3 piezoelectric substrate is used, by providing the above-mentioned coupling capacitance, unnecessary spurious waves can be brought closer to the resonance point of the zero-order longitudinal mode. Therefore, the vertical dual mode SAW according to the present invention
The filter can provide flat passband characteristics.

[Effects of the Invention] As described above, according to the present invention, a vertical dual mode SAW using a LiNbO3 piezoelectric substrate with a 64° rotation Y cut and X direction propagation, which has been considered difficult until now due to the generation of unnecessary spurious waves, can be realized. The filter can now be realized, and a wider band SAW filter can be provided compared to the conventional dual mode SAW filter.

Therefore, when the SAW filter according to the present invention is employed in, for example, communication equipment, it is possible to reduce the size of such equipment, and to widen the range of performance.

[Embodiment] FIG. 1 is a configuration diagram of a vertical dual mode SAW filter 20 according to a first embodiment of the present invention.

Referring to FIG. 1, a SAW filter 20 includes a LiNbO3 piezoelectric substrate 21 with a 64° rotation Y cut and x direction propagation. On this piezoelectric substrate 21, a two-section energy trapping resonator is constructed.

The energy-confined resonator of the first section comprises two pairs of closely spaced (comb-shaped electrodes 22 and 23) and reflectors 24 and 25 arranged on either side of these comb-shaped electrodes 22 and 23.

The energy-confined resonator of the second section comprises two sets of closely spaced comb-shaped electrodes 26 and 27 and reflectors 28 and 29 arranged on either side of these comb-shaped electrodes 26 and 27.

By connecting the comb-shaped electrode 23 in the first section and the comb-shaped electrode 26 in the second section, the energy trapping resonators in the first and second sections are connected in cascade.

A feature of this embodiment is that a coupling capacitor 30 is provided electrically in parallel at the connection between the output side comb-shaped electrode 23 in the first section and the input side comb-shaped electrode 26 in the second section. That's true. In this embodiment, the coupling capacitance 30 is composed of comb-shaped electrodes placed in a position that does not interfere with the surface waves excited by the comb-shaped electrodes 22, 23, 26, 27, but other than that, It may also be configured with an external additional capacitor.

The SAW filter 20 shown in FIG. 1 utilizes longitudinal zero-order and longitudinal first-order resonance modes, similar to the one shown in FIG. 7.

FIG. 2 is a configuration diagram of a vertical dual mode SAW filter 20a according to a second embodiment of the present invention.

Referring to FIG. 2, the SAW filter 20a includes a L i N b O3 piezoelectric substrate 21a of 640 rotations Y-cut and X-direction propagation, as in the case of the SAW filter 20 described above. On this piezoelectric substrate 21a, two
An energy-confined resonator of the section is constructed.

In order to make the comparison with the SAW filter 20 shown in FIG. 1 clear, the reference numbers used in FIG. 1 are attached to corresponding elements. Between the vessel 24 and the reflector 25, in addition to the comb-shaped electrodes 22 and 23, another set of comb-shaped electrodes 31 is arranged. In the energy-confined resonator of the second section, in addition to the comb-shaped electrodes 26 and 27, another set of comb-shaped electrodes 32 is arranged between the reflector 28 and the reflector 29. In this way, the first
Since the second energy-trapped resonator has a comb-shaped electrode divided into three parts, the zero-order longitudinal resonance mode and the second-order longitudinal resonance mode are used, as in the case shown in FIG. 8 described above.

Furthermore, in order to cascade-connect the energy trapping resonators in the first and second sections, the comb-shaped electrodes 23 and 31 in the first section are connected to the comb-shaped electrodes 26 and 32 in the second section.

Also, in this second embodiment, similarly to the first embodiment, the 8-force side comb-shaped electrodes 23 and 31 of the first section are
A coupling capacitor 30 is provided electrically in parallel at an electrode portion extending from the coupling portion of the input side comb-shaped electrodes 26 and 32 of the second section to the coupling portion of the input side comb-shaped electrodes 26 and 32.

In both the first and second embodiments described above,
Reflectors 24, 25, 28, 29 and associated comb electrodes 22
．． 23, 26, 27, 31.32, and the spacing between the comb-shaped electrodes 22, 23°26.27.31.32, respectively. 23. 2
6. 27. The Q of the resonator is improved by setting the electrode finger pitch to an integer multiple of 31.degree. It is well known that satisfying such conditions is desirable in designing a vertical dual mode SAW filter.

The feature of this invention is that, as mentioned above, coupling capacitance is added to the conventional vertical dual mode SAW filter. As a result, conventionally,
It is now possible to realize a vertical dual mode SAW filter using a 64° rotated Y-cut, X-direction propagation L i N b O3 piezoelectric substrate, which has been difficult to put into practical use due to spurious emissions.

Hereinafter, especially in relation to the second embodiment shown in FIG.
Preferred design conditions for the vertical double MAW filter according to the present invention will be explained.

First, the passband of the vertical dual mode SAW filter is 2
In the case of the second embodiment, it is determined by the difference between the frequency of the zero-order longitudinal resonance mode and the frequency of the second-order longitudinal resonance mode, as explained in the prior art. As I said. Moreover, this frequency difference is the total logarithm of the comb-shaped electrodes 22, 23, 31, and the comb-shaped electrodes 26, 26, . 2.7. It is a well-known fact that the upper limit of the fractional bandwidth is determined by the stopband width of the reflectors 24.25, 28.29. Here, in order to widen the stop band width, the electrode film thickness ratio h, which is the ratio of the electrode film thickness to the wavelength λ of the excited surface wave, is
Although it is desirable to increase /λ, it is known that increasing the thickness of the electrode for this purpose makes it difficult to process the electrode and also increases the loss caused by conversion to a bulk wave. Therefore, below, the film thickness of the electrode is
Experimental results regarding the second example will be explained in a case where the above-mentioned processing problems do not occur.

FIG. 3 shows a comb-shaped electrode 22, 23.31 or 26.27.32 in one section based on the second embodiment.
FIG. 3 is a diagram showing the variation of the fractional bandwidth depending on the size of the total logarithm N of the electrode fingers. Note that in this specification, the total logarithm N is 1/2 of the number of electrode fingers.

From the results shown in FIG. 3, it can be seen that LiNbO3 of 64° rotation Y cut and
Frequency fluctuation for 100℃ ambient temperature fluctuation 0.5
Considering 5%, the total number of logarithms N of the electrode fingers of the comb-shaped electrode is:
It can be determined that it is desirable to set it to 50 or less.

Next, the unnecessary spurious f as shown in FIG.
. In order to suppress this, the coupling capacitance 30 is added as described above, but if the size Cc of this coupling portion ji30 is appropriately set, a particularly remarkable effect is exhibited. Hereinafter, the results of an experiment conducted to determine an appropriate range for the size Cc of the coupling capacitance 30 in the second embodiment will be explained.

FIG. 4 shows the unnecessary spurious f when the magnitude Cc of the coupling capacitance 30 is varied with respect to the total capacitance Ct of the comb-shaped electrodes 23 and 31 and 26 and 32 connected by the connection portions in FIG. and the resonance point f of the longitudinal zero-order mode
. This shows the change in the frequency difference between the two, that is, (f-fo)/fo.

From the results shown in FIG. 10, the unnecessary spurious f0 is reduced to the resonance point f of the longitudinal O-th mode by increasing the coupling capacitance ratio Cc/Ct. It is confirmed that it approaches .

FIG. 5 shows a second
3 shows the frequency characteristics of the vertical dual mode SAW filter 20a according to the embodiment. Since the unnecessary spurious is coupled to the resonance point of the longitudinal O-order mode, it is confirmed that a flat band characteristic is obtained.

It is widely known that if the intersecting width of each comb-shaped electrode is given appropriately, it is possible to match the input/output impedance to the requirements. Therefore, such an intersecting width is not particularly limited in realizing the present invention.

Furthermore, from FIG. 3, if the lower limit of the total logarithm N of electrode fingers of a practical comb-shaped electrode is determined to be 10, then the coupling capacitance ratio Cc/
From FIG. 4, the magnitude of Ct is determined as follows: Cc/Ct≧0. It will be understood that it is sufficient to set it to 5.

Therefore, to summarize the above experimental results, the total logarithm N of the electrode fingers of the comb-shaped electrode and the coupling capacitance ratio Cc/'ct are:
By setting N and Cc so that N≦50 and Cc/Ct≧0.5, respectively, a vertical dual mode SAW filter with a fractional bandwidth of about 4% and no spurious can be realized. can do.

[Brief explanation of drawings]

FIG. 1 is a block diagram showing a vertical dual mode SAW filter 20 according to a first embodiment of the present invention. FIG. 2 is a block diagram showing a vertical dual mode SAW filter 20a according to a second embodiment of the present invention. FIG. 3 is a diagram showing the relationship between the total logarithm N of electrode fingers of a comb-shaped electrode and the fractional bandwidth, obtained by an experiment conducted based on the second example. FIG. 4 is a diagram showing the relationship between the coupling capacitance ratio Cc/Ct and the spurious frequency difference (fe-to)/lo obtained by an experiment conducted based on the second embodiment. FIG. 5 is a diagram showing the frequency characteristics of the vertical dual mode SAW filter 20a according to the second embodiment. FIG. 6 is a block diagram showing a conventional vertical dual mode SAW filter 1. As shown in FIG. FIG. 7 is a conceptual diagram showing two mode distributions of the SAW filter 1 shown in FIG. 6. FIG. 8 is a conceptual diagram showing two mode distributions in a modified example of the SAW filter 1 shown in FIG. 6. FIG. 9 is a configuration diagram showing a vertical dual mode SAW filter 1a as another conventional example. FIG. 10 is a diagram showing the frequency characteristics of the vertical dual mode SAW filter 1a shown in FIG. In the figure, 20.20a is a vertical dual mode SAW filter, 21.21a is a piezoelectric substrate, 22° 23.26, 2
7.31.32 is a comb-shaped electrode, 24.25, 28.29
is a reflector, and 30 is a coupling capacitor. (Bunsun comb-shaped Denyo, Hikimi Zuo father N

Claims (2)

[Claims] (1) 64° rotation Y cut X direction propagation LiNbO_3
At least two sets of comb-shaped electrodes are disposed close to each other on a piezoelectric substrate, and reflectors are disposed on both sides of the comb-shaped electrodes, thereby forming a multi-section energy-confining resonator. In a vertical dual-mode surface acoustic wave filter in which confined resonators are connected in cascade in multiple stages, a coupling capacitance electrically parallel to the comb-shaped electrode is provided at a connecting portion between each section of the energy confined resonator. A vertical dual mode surface acoustic wave filter comprising: (2) Let N be the total number of electrode fingers of the comb-shaped electrodes in one section of the energy-trapped resonator, Ct be the total capacitance due to the comb-shaped electrodes connected by the connection part, and Cc be the size of the coupling capacitance. The vertical dual mode surface acoustic wave filter according to claim 1, wherein: N≦50 and Cc/Ct≧0.5.