JPH0356073A - Power conversion circuit, ignition circuit starting and stopping means, switching circuit, arm pair, bridge circuit, power conversion circuit, and ignition circuit - Google Patents

Abstract

PURPOSE:To remove the saturation of a transforming means so as to miniaturize it by fixing the absolute value of AC voltage to be applied to the input side of the transforming means by constant voltage means. CONSTITUTION:For a power conversion circuit, transistors 2-3 form an arm pair between both terminals of a DC power source 1, and a reactor 4 and a capacitor 6 form a series resonance circuit, and further a load 7 becomes the component of the resonance circuit. And two diodes 8 are connected in reverse parallel between both terminals of a primary coil 5a, and form a constant voltage means form fixing the absolute value of the input voltage of a transformer 5 for driving. What is more, a switch 11 and a resistor 12 form a starting means. As a result, the saturation of the transformer 5 ceases to be affected by resonance voltage.

Description

DETAILED DESCRIPTION OF THE INVENTION A first aspect of the present invention relates to a series circuit of inductance means and capacitance means, normally-off voltage-driven switching means, and a plurality of inductance means for driving each of the switching means. A transformer magnetically coupled with −[
The present invention relates to a self-excited power conversion circuit using stages.

By applying this power conversion circuit, it is possible to construct ignition circuits for various purposes that can generate multiple sparks, especially ignition circuits for internal combustion engines and ignition circuits for rocket engines. The second invention is normally
A self-excited power conversion circuit that generates a driving signal from the main current of each off-type switching means, feeds it back positively to each switching means, and utilizes a series circuit of inductance means and capacitance means. Its startup and operation stop at 1F. The present invention relates to a starting/stopping means that can always be started smoothly even after repeated restarts, and can set the voltage of the capacitance means to a predetermined value each time it is restarted.

This technology is, for example, a self-excited DC-D using a resonant circuit.
It is useful in controlling the power voltage of the C converter circuit by starting and stopping it. It is also useful for ignition control in ignition circuits that apply self-excited inharter circuits that use oscillating circuits.

The third aspect of the present invention is to generate a drive signal from the main current of a normally-off type switching means, and to limit the positive feedback in a switching circuit that supplies a positive {iW to the switching means. 9. Relating to a switching circuit that can supply a reverse bias voltage to the switching means when the switch is kept turned off.In addition, this switching circuit can be used to configure an arm pair.

Furthermore, a bridge circuit can be constructed using two of these arm pairs. The fourth aspect of the present invention provides a power conversion circuit using a series circuit of an inductance means and a capacitance means, and four controllable switches connected in a full bridge, in which vibration of the capacitance means is suppressed regardless of the weight or weight of the load. A power conversion circuit that can stabilize the voltage is installed.

BACKGROUND ART The first to fourth aspects of the present invention will be explained below in parts (4). (1) - (1) As a prior art, a self-excited power conversion circuit using a bipolar transistor, a series resonant circuit, and a driving transformer is disclosed in Japanese Patent Publication No. 16861/1983. , M instead of bipolar transistor
A self-excited power conversion circuit using OS FET was published in Japanese Patent Application Publication No. 1986.
No. 3-59772. The basic circuit of the latter is shown in Figure 2. The latter name uses a saturable type for the drive transformer, but it doesn't have to be that way. The drive transformer 5 in the circuit shown in Figure 2 does not lie horizontally. If the transformer 5 is used in the unsaturated region, when the resonant current flowing through the transistor 2 or 3 is reversed and flows through one of the built-in diodes, both gate voltages are reversed due to the reversal of the output voltage of the transformer 5. 1 to transistors 2 and 3 are switched on and off.

Alternatively, the excitation current of the transformer 5 switches its on and off states. On the other hand, if the transformer 5 is used in saturation, the transistors 2 and 3 will be switched on and off at the point when the resonant current reaches saturation before it is reversed. In addition, load 7 beam actor 4 (
A type of inductance means. ) is connected in series with reactor 4 or capacitor 6 or 21 (
A type of capacitance. ) may be connected in parallel. By the way, if transistors 2 and 3 are replaced with bipolar transistors, this circuit will become
Although this is a modification of the circuit of No. 861, the operation of the drive transformer 5, etc. is not the same as that of the former. This difference occurs because the former circuit uses current-driven switching means, and this circuit uses voltage-driven switching means. The operation of this circuit is a little complicated.

In the second UA circuit, the resistor 45 and the gate-source capacitance of the transistor 2 form an integrating circuit, and this integrating circuit integrates the output voltage of the secondary coil 5b. If the re-gauge inductance of the transformer 5 is ignored, this output voltage will be the value obtained by multiplying the voltage of the exciting inductance of the primary coil 5a by its turns ratio.

As is well known, if the voltage of the coil is ■, its constant current is I, its inductance is L, and the time variable is T, then
v=L. -Since there is a relationship of dI/dT, the current I can be found by integrating the voltage ■.

Therefore, the output voltage waveform of the integrating circuit, ie, the gate-source voltage waveform of transistor 2, becomes almost the same as the current waveform of the excitation inductance, ie, the waveform of the main current of transistor 2 (or 3). The same applies to the transistor 3 and resistor 46 sides.

As a result, it is predicted that the phase of the main current and the on/off timing of transistors 2 and 3 will match exactly.
In reality, the on/off threshold voltages of transistors 2 and 3 are also involved, so the phase and timing will be slightly different. Also, in the differential equation, the inductance I is treated as a constant, but when the transformer 5 is saturated, the inductance L changes, so the relationship becomes complicated. By the way, when the capacitance of one gate-source capacitance is C, and the value of resistor 45 or 46 is R,
In order for both integrating circuits to integrate the sine wave of frequency f, the relationship CR >> 0.5 be. Unless the impedance of both integrating circuits is considerably larger than the impedance of the excitation inductance, the current of the excitation inductance will be different from the main current. In any case, sufficient driving voltage is applied to the transistors 2 and 46 for the large value resistors 45 and
3, it is necessary to input a large resonant voltage to both integrating circuits. As a result, energy consumption by the resistors 45 and 46 cannot be ignored.

Further, since the excitation inductance is included in the inductance component of the resonant circuit, when the load 7 is connected in parallel to the reactor 4, the vibration waveform becomes complicated. However, it is not possible to connect the load 7 in parallel to the series circuit of the reactor 4 and the primary coil 5a. This is because the current of the excitation inductance and the main current are different.

Further, since the inductance component of the resonant circuit becomes the phase of the inductance of the actor 4 and its excitation inductance, a resonance voltage corresponding to the inductance ratio is applied to the excitation inductance. Therefore, as the resonant voltage increases, the transformer 5 becomes more likely to be saturated. As a result, when using the transformer 5 in saturation, the on/off timing of the transistors 2 and 3 and their respective main currents (
(resonant current) is out of phase. In this case, the ratio of the energy returned from the resonant circuit to the DC power source 1 with respect to the energy given from the DC power source 1 to the load 7 becomes large, making it impossible to give full energy to the load 7.

Furthermore, since the resonant current flows almost unchanged through the excitation inductance, whether the transformer 5 is used in the unsaturated region or in the saturated state, it is necessary to design the transformer 56 to be large according to the magnitude of the current. be. For this reason, (g) it is desirable to prevent the excitation inductance from being incorporated as an inductance component of the resonant circuit a, and (8) the saturation of the transformer 5 will reduce the resonant voltage. (2nd problem) It is desired that the transformer C5 be made smaller regardless of the magnitude of its resonant current (3rd problem) There is a problem with this conventional power conversion circuit. Another problem is that the conversion efficiency is low due to energy loss in the resistors 45 and 46. (Fourth Problem) Therefore, the first aspect of the present invention aims to provide a power conversion circuit that eliminates these problems.

<2> Next, the background technology of the second wood power plant "Jl" will be described. Positive feedback means (for example, a transformer .), in a self-excited power conversion circuit in which the voltage across a series circuit in which an inductance means and a capacitance means are directly or equivalently connected in series is switched by a plurality of the switching means and one or more DC power sources, There are problems in the prior art, such as when restarting after stopping the operation, the restart cannot be performed depending on the residual voltage of the capacitance means in the series resonant circuit.For example, the turn-on at the beginning of the restart In the closed circuit formed by the switching means, the residual voltage and the power supply voltage cancel each other out, making it impossible to restart the switching means.Alternatively, even if the two voltages do not completely cancel each other out, the difference between the two voltages increases. This is the case when the vibration is insufficient and the vibration cannot be started, or the rise of the vibration is delayed.

On the contrary, it would be convenient if the residual voltage acted to help it restart. Also, when restarting,
Depending on the application, there are cases where it is necessary that the residual voltage always be at a predetermined voltage (for example, zero voltage or the power supply voltage). However, the conventional technology has a problem in that the residual voltage cannot be set to a predetermined voltage. For example, in the case of an ignition circuit for an internal combustion engine in which the series resonant circuit is composed of a series circuit of the primary coil of the ignition coil and a capacitor, when the series resonant circuit is repeatedly started and stopped, that is,
When repeating the ignition operation, it is necessary to set the residual voltage to a predetermined value. This means that the residual voltage determines the initial applied voltage for restarting the primary coil, and this applied voltage determines the initial voltage applied to the secondary coil. This is because the initial maximum output voltage of the ignition coil required to break down the insulation between the connected ignition discharge gaps is determined. In other words, this is because this maximum output voltage increases or decreases depending on the residual voltage. If this maximum output voltage does not exceed the constant dielectric breakdown voltage across the gap, no spark will occur and an ignition error will occur. Not only that, but if the spark does not short-circuit the secondary side, the ignition coil's two single-cage inductances and its capacitor will not perform normal resonant operation, making it difficult to start the ignition circuit. In some cases, the ignition will not work at all. Therefore, (±) It is desired that the a voltage of the capacitance means at the time of restart acts to help the restart, (1st problem) (3) The b voltage of the capacitance means at the time of restart. (Second problem) It is desirable that・The purpose is to provide a means of stopping.

(3) Describing the background art of the third aspect of the present invention Figure 3 shows an example of a switching circuit that generates a drive signal from the main current of a normally-off type switching means and positively feeds it back to the switching means. Transistor ■ can be forward biased or reverse biased depending on the direction of its main current. In order to stop the on/off operation of the switching circuit due to positive feedback and keep it off, the switch 11 can be turned on.

However, if voltage is applied between terminals t2 and t3,
Since there is a leakage current in transistor 1, transistor 1 is heated while it is not operating, and energy is wasted. This is particularly problematic when a bipolar transistor is used in place of transistor l, when the switching circuit is used in a high temperature environment, or when the applied voltage is high.

Therefore, when the on/off operation of the switching circuit due to positive feedback is stopped, it is desirable to supply a reverse bias voltage to the switching means as a solution for reducing the first ih-mainstream. (Problem) Also, IGBT (Insulat.ed Gat.e
[3ipolar 1"transistor), applying a reverse bias voltage improves reliability from the standpoint of noise resistance, so the same thing is desired when the on/off operation is stopped (problem). Therefore, it is an object of the third invention to provide a switching circuit that can supply a reverse bias: k pressure to the switching means when the on/off operation based on positive feedback is stopped. .

(4) The background technology of the fourth present invention will be described. As a conventional technology, this power conversion circuit uses four controllable switches connected in a full bridge and a series resonant circuit, and is capable of keeping the oscillating voltage constant regardless of the load. The inventor is JP-A-1-1
It is disclosed in Fig. 20 (a>, (b)) of No. 73917. Its basic circuit is shown in Fig. 4. Its operation is as follows. When the voltage of 6 becomes the same as the voltage of DC power supply l, diode 19, which had been off due to the reverse main voltage, turns on and capacitor 6 is clamped to DC power supply 1. Therefore, diode l9 and Transistors 47 and 2 act like flywheel diodes for reactor 4 and load 7, and the current in reactor 4 now flows through them, and the voltage across capacitor 6 is no longer -E.
Will not Increase. The same holds true during the ON period of transistors 3, 48, and 14. As a result, the absolute value of the voltage of the capacitor 6 is limited to the magnitude of the power supply voltage or less, so that the oscillating voltage becomes constant, and the oscillating voltage of the resonant concave path also becomes constant.

Note that the transistors 47 and 48 are the diode 9 and the transistor 14, or the transistor 15 and the diode 2.
This is necessary in order to prevent IE from interfering with the capacitor 6.

However, in order to keep it constant, the transistor groups connected by three dotted lines in the figure are controlled so that they turn on in tandem, but so that both transistor groups do not turn on at the same time. There must be.

For this reason, in addition to the transistors 47 and 48, a driving means that satisfies these requirements is required, so this circuit system has problems in that the number of parts is large and the circuit ellipse is complicated. (First problem) As an example of this circuit system, the 15th I2l
There is a concave road. Also, if the vibration period is shortened, the diodes 19 and 2
The turn-on delay of 0 can no longer be ignored, resulting in surge current and voltage. The mechanism of its occurrence is thought to be as follows. If the diode 19 or 20 turns on late, the voltage on the capacitor 6 will already be greater than its supply voltage. As a result, the voltage across the diode 19 or 20 changes rapidly when the diode is turned on, and an oscillating current flows to restore the voltage difference to the on-state voltage.

This oscillating current is caused by resonance due to inductance and capacitance in a closed circuit including the capacitor 6, diode 9, transistor 47, DC power supply L, and the diode built in transistor 15, or by the resonance caused by the capacitor 6, the diode built in transistor 14, and the DC power supply L. This occurs due to resonance due to inductance and capacitance in a closed circuit including the power supply 1, the transistor 48, and the diode 20.

Therefore, if the DC power supply 1 has a built-in output power supply capacitor and its output impedance is small, the oscillating current will become particularly large. As a result, the original resonant circuit is no longer able to resonate normally, the loss in the diodes 19, 20, etc. increases, and unnecessary radio noise is generated. Therefore, there is a problem in this circuit system that it is desired to reduce the occurrence of these surges (Second Problem) Therefore, the fourth invention provides four controllable switches connected in a bridge, In a power conversion circuit using a series circuit of an inductance means and a capacitance means, it is possible to stabilize the oscillating voltage of the capacitance means and reduce the occurrence of surges with a small number of parts and a simple circuit configuration.
The purpose is to provide a power conversion circuit that can perform DISCLOSURE OF THE INVENTION First of all, the first aspect of the present invention is to directly or equivalently connect a first inductance means, a capacitance means, and a primary side inductance means of a first transformer means magnetically coupled to a plurality of inductance means. a plurality of normally-off, voltage-driven switching means, each of which is driven by the output signal of the first transformer means to which the voltage across the series circuit connected in series is positively fed back; and one or more DC power sources. Self-excited type switched by: E
In a force conversion circuit, I
) 1f This is a power conversion circuit in which the absolute value of the input voltage of the first transformer is made constant.

The transformer may be a single transformer or may be a combination of a plurality of transformers.

As a result, the constant voltage means constantizes the absolute value of the AC voltage applied to the input side of the transformer, so its excitation inductance is separated from the inductance component of its resonant circuit (Effect No. 2). , the saturation of the transformer is not affected by the increase or decrease of its resonant current (second effect).Also, no matter how large the resonant current becomes,
Most of this is bypassed by the constant voltage means, and the absolute value of the AC voltage applied to the excitation inductance is kept constant, making it difficult for the transformer to saturate, making the transformer more compact. (Third effect)
．． Furthermore, unlike the prior art, the present invention does not require an integrating circuit that increases energy loss, so energy loss is reduced accordingly and conversion efficiency is improved (fourth effect). Next, the second invention provides positive 4mA means, inductance means, and capacitance means for generating each drive signal from the main current of each switching means and positively feeding back to each switching means, directly or equivalently. In a self-excited power conversion circuit in which the voltage across a series circuit connected in series is switched by a plurality of the switching means and one or more DC power supplies, the voltage across the series circuit is switched in accordance with a start/stop signal given from the outside. activating means for turning on one or more of the switching means forming a closed circuit providing a predetermined voltage;
operation stopping means for turning off one or more of the switching means; on-off detection means for detecting whether the one or more switching means is on or off; and the one or more of the on-off detection means or the one or more switching means. 9. The activation/stopping means is provided with a turn-off prevention means that prevents the operation stopping means from turning off the one or more switching means as long as it detects that the switching means of the switching means are turned on. As a result, the voltage of the capacitance means acts to help restart the self-excited power conversion circuit (first effect), and the voltage of the capacitance means at the time of restart can be set to a predetermined value. (Second effect). Its action is as follows.9 In the self-excited power converter circuit, the first switching means group (meaning the one or more switching means, including the singular). ) and the second switching means group (referring to the remaining one or more switching means, including the singular number) switch the first closed circuit (said closed circuit) and the second closed circuit during their operation. Form alternately.
When each of the first and second idle circuits is formed, the voltages at both ends take a predetermined value corresponding to each. Due to the action of the start/stop means of the present invention, the power conversion circuit always starts its operation by turning on the first switching means group, and starts its operation by turning off the second switching means group. Stop and listen. In other words, the timing of starting and stopping each operation is always the same. As a result, upon its restart, the voltage across said capacitance means is constant, and the voltage direction is such that it helps the resonant circuit to start oscillating by turning on the first group of switching means. A third aspect of the present invention provides a switching circuit in which the normally-off type first switching means is provided with positive feedback means for generating a drive signal from its main current and positively feeding it back to the first switching means. A first three-terminal switching means for switching is introduced, and when the first three-terminal switching means is brought into a first switching state, the driving signal is transmitted to the positive feedback means from the first three-terminal switching means. When the first three-terminal switching means is brought into the second switching state by positive feedback to the first switching means via the terminal switching means, a reverse bias voltage is applied to the DC power supply to the first three-terminal switching means. A switching circuit that supplies power to the first switching means through the first switching means. This allows the three-terminal switching means to determine whether the positive feedback means positively feeds back the drive signal to the first switching means or whether the DC power supply supplies its reverse bias voltage to the first switching means. Control whether or not. Therefore, when the on/off operation based on positive JiD is stopped, a reverse bias voltage is supplied to the first switching means.

(Effect) Then, in the fourth aspect of the present invention, the first pair of arms, the first non-controllable switch, the first and second controllable ITLII switches, and the second non-controllable switch are connected in series in this order. A second pair of connected arms is bridge-connected to a DC power source, and a two-way wire is connected between the connection point of the first non-controllable switch and the controllable switch and the connection point of the second controllable switch and the non-controllable switch. a third non-controllable switch in the opposite direction to the two non-controllable switches;
a fourth non-controllable switch is connected in series, a capacitance means is connected between the connection point of the third and fourth non-controllable switches and a midpoint terminal of the first pair of arms, and the third non-controllable switch is connected in series. , the connection point of the fourth non-controllable switch and the second
An inductance means or
It is a series circuit of a load and an inductance means, or a power conversion circuit that connects one or the other. As a result, by simply connecting four non-controllable switches to a conventional ordinary bridge-type resonant power conversion circuit, the L1
You can accomplish your goal. Therefore, since the driving means is not complicated, the oscillating voltage of the capacitance means can be made constant with a small number of parts and a simple circuit configuration (first effect). Since the non-controllable switch works to suppress the surge that is likely to occur due to the turn-on delay of the third or fourth non-controllable switch, the occurrence of the surge can be reduced. (Second effect) The effect is as follows. When the magnitude of the voltage across the capacitance means becomes equal to the magnitude of its power supply voltage due to the action of the first and second pair of arms, either the first or second controllable switch and the third or fourth Either of the non-controllable switches acts like a flywheel diode for the inductance means. As a result, the oscillating voltage of the capacitance means becomes constant, and +if either arm of the first pair of arms and either of the third or fourth non-controllable switches short-circuit the capacitance means. is prevented by either the first or second non-controllable switch. Then, in a closed circuit including the capacitance means, the DC power source, and the third or fourth non-controllable switch, the first or second non-controllable switch connects the third or fourth non-controllable switch. Since it is included in direct communication with the controllable switch, the first or second non-controllable switch prevents resonance in its respective closed circuit. As a result, the occurrence of a surge due to the turn-on delay of the third or fourth non-controllable switch is suppressed.

BEST MODE FOR CARRYING OUT THE INVENTION In order to explain each of the first to fourth aspects of the present invention in more detail, the same will be described below with reference to the accompanying drawings. The circuit diagrams of the 35 embodiments are shown in Fig. 1<a> to Fig. 1(d) and Fig. 5 to Fig. 36. In the embodiment shown in FIG. 1(a), transistors 2 and 3 form an arm pair between both power supply terminals of DC power supply l, and reactor 4 and capacitor 6 form a series resonant circuit. 7 is the load. If the load 7 includes an inductance component or a capacitance component, two diodes 8, which are also components of the resonant circuit, are connected in antiparallel between both terminals of the primary coil 5a, and a driving transformer is connected. The above-mentioned constant voltage means is formed to make the absolute value of the input voltage of the device 5 constant. The output voltage of the secondary coil 5b is fed back positively to the gate of transistor 2, giving it a positive gate voltage when transistor 2 should be on, and giving it a negative gate voltage when transistor 2 should be off. This is given. The same applies to the transistor 3 and secondary coil 5C side. The four Zener diodes 9 and two resistors lO are connected just in case, but they can be omitted. If the current of the load 7 is small, the two diodes 8 may be omitted. This is because the two Zener diodes 9 connected in series in opposite directions serve as the constant voltage means described above. Switch 11 and resistor 12 are starting means for starting this power conversion circuit. Although one end of the resistor 12 is connected to the gate of the transistor 2, it may be connected to its source, or it may be connected to the gate of the transistor 3.

In addition, a resistor is connected to the drain of transistor 3 for startup assistance.
Sources may be connected in parallel. The operation of this circuit will be described below. When the switch 11 is turned on, a positive voltage is applied to the gate of the transistor 2, and a negative gate voltage is applied to the gate of the transistor 3 through the transformer 5.

Therefore, when the transistor 2 begins to turn on and current begins to flow through the load 7, the primary coil 5a, etc., the output voltage of the transformer 5 is further fed back positively to each gate of the transistors 2 and 3. As a result, transistor 2 is completely turned on and transistor 3 is completely turned off. After that, the FR dynamic current of load 7 is reversed and transistor 2
When the current begins to flow through the built-in diode, the output voltage of the transformer 5 is also reversed, so the transistors 2 and 3 are switched between on and off states.

Furthermore, after that, when the oscillating current reverses and begins to flow through the diode built into transistor 3, the output voltage also reverses, so transistors 2 and 3 are switched between on and off states. From now on, the same thing is repeated and this circuit continues to oscillate9.In addition, in the case of this circuit, turn off the power and stop its operation. Also, in this circuit, two output voltages are generated from one transformer 5, but by using two transformers and connecting both primary coils in series, two output voltages are generated from both transformers. You can also take it out. Of course, in this case, a constant voltage means is required for each. It is also necessary to pay attention to each type of biased magnetism.

Furthermore, although the gates and sources of transistors 2 and 3 are directly connected to secondary coils 5b and 5c, respectively, in order to prevent a power supply short circuit due to a delay in turn-off of transistors 2 or 3, as shown in FIG. They may be connected through resistors, as in the embodiment shown in FIG. 15, or one diode may be connected in parallel to each resistor, as in the embodiment shown in FIG. 15, which will be described later. The embodiment shown in FIG. 1(b) is an ignition circuit using the circuit shown in FIG. 1(a), and the starting/stopping means (second
An embodiment of the present invention) is also utilized. The two cage inductances of the ignition coil 16 mainly play the role of the reactor 4. 17 is a discharge gap for ignition. l8 is a shield case, which is a countermeasure against radio noise. If possible, ground the shield gate 18 and
It is desirable to draw out the lead wire of the secondary coil 16a from this case via a feedthrough capacitor. Capacitors 6 and 21 are connected to respective power terminals of DC power supply 13, respectively. In this way, there may be two capacitors.

The diodes 19 and 20 limit the voltages of the capacitors 6 and 21 to a range from zero to the voltage of the DC power supply 13, and keep the peak value of the oscillating voltage constant. That is, transistor 1
When 4 or 15 turns off, capacitor 6
, 21 is approximately zero or the magnitude of the power supply voltage.

Therefore, immediately after the transistor 14 or 15 is turned on, a voltage almost equal to its power supply voltage is applied to the primary coil 16a, so that as long as the power supply voltage does not drop, this ignition circuit will always produce the same maximum output voltage. can do.

Its operation is as follows. When the voltage of the capacitor 2l is almost zero during the ON period of the transistor 4 and the voltage of the capacitor 6 almost reaches the power supply voltage, the diode 19, which had been off due to the reverse voltage, turns on.
Capacitor 6 is clamped to DC power supply l3.

As a result, since the diode 19 and the transistor 14 act like a flyboil diode for the primary coil 16a, the voltages across the capacitors 6 and 2 remain unchanged.

Similarly, during the ON period of the transistor 15, this and the diode 20 play a similar role for the primary coil 16a. However, for this purpose, the transformer 5 and the startup and
The stop means and the like ensure the on period of the transistors 14 and 15 appropriately and without waste.

The transistors 25 and 26 are responsible for starting this ignition circuit.
Configure the stopping means. An ignition signal (corresponding to the start/stop signal in this case) that controls the start and stop of this ignition circuit is input to the input terminal L}. The transistors 25, 26, the diode 23, etc. are used as the operation stopping means described in claim 23, the transistor 26, the resistor 22, etc. are used as the starting means described in the same description, and the transistor 26, the diode 29, the resistor 30, etc. are used as the activation means described in the same description. - The transistor 26 and the like correspond to the turn-off prevention means described in the same description as the off-detection means.9 The starting and stopping operations of this ignition circuit will be explained below.

This circuit operation begins when transistor 15 is turned on and stops when transistor 14 is turned off. This is to facilitate starting and stopping this circuit, and to ensure that a voltage equal to 41 ton is applied to the primary coil 16a immediately after the transistor 14 or l5 is turned on. , is. Furthermore, this is to prevent the transistor 14 or 15 from turning off while the oscillating current is flowing through the primary coil 16a. In other words, the purpose is zero current switching. Initially, when the ignition signal is low, transistor 25 is on and transistor 1 is on.
The current flowing through resistor 22 that attempts to flow toward the gate of 5 is bypassed. Three diodes 23 complete this bypass.

When the ignition signal rises, transistor 26 turns off transistor 25, giving a positive gate voltage to transistor 15, which turns off transistor 1.
4 is given a negative gate voltage via transformer 5. The subsequent operation is almost as described in the circuit description of Figure 1(a), and this ignition circuit oscillates and continuously generates sparks. This spark generation continues as long as the ignition signal is at a high level. Thereafter, when the ignition signal falls, if the gate voltage of transistor 15 is zero or negative, transistor 26 is turned off. The transistor 25 then turns on and, together with the Zener diode 9, prevents its gate voltage from becoming glass. Therefore, this circuit stops oscillating when transistor 14 turns off. However, when the ignition signal falls, if the gate voltage of transistor 15 is positive, the current in resistor 30 will keep transistor 26 on. Therefore, the transistor 25 is turned on until its gate voltage falls, that is, until the transistor 15 is turned off. After this, as mentioned above, the transistor 14
This ignition circuit stops operating when the ignition circuit turns off.

Furthermore, due to the action of the diodes 19 and 20, the primary coil 5
The oscillating current flowing through a and 16a hardly flows through the diode built into the transistor 14 or 15. Therefore, it is considered that the excitation current of the excitation (or mutual) inductance of the transformer 5 creates a trigger for switching the transistors 14 and 15 on and off. The excitation current, which has once increased due to the oscillating current, cannot keep up with the decrease in the oscillating current, and the ignition coil 16 prevents the entire excitation current from passing through, so the increased amount is transferred to the secondary coils 5b and 5C. It is thought that this causes the current to flow and inverts both gate voltages. Alternatively, diode 19 or 20
It is also considered that the current in the primary coil 16a is reversed by the voltage of the capacitor 6 or 21 charged to the on-voltage.

Also, transistors 14, 15, diodes 19, 20
If the voltage of capacitor 6 drops during operation stop f due to leakage current from capacitors 6, 21, etc., a high resistance may be connected in parallel to capacitor 21. The embodiment shown in FIG. 1(c) corresponds to the switching circuit (third aspect of the present invention) described in claim 26. The DC power supply l corresponds to the DC power supply described in the same paragraph, the transistor 2 corresponds to the first switching means described in the same paragraph, and the transformer 31 corresponds to the positive feedback means described in the same paragraph. The transistor 34, the diodes 32 and 33, and the resistor 35 constitute the first three-terminal switching device described in claim 30. The main current of the transistor 2 flows through the primary coil 31a. If switch 1l is off, secondary coil 3
The output voltage of 1b is applied between its gate and source via a transistor 34, a resistor 35, or a diode 32.

However, if the switch 11 is on, the DC power supply 1 supplies a reverse bias voltage to the transistor 2 via the diode 33 and the switch 11. (Effect) During that time, the transistor 34 is off and the current of the resistor 35 excites the secondary coil 31b. Then switch 1
1 is turned off, this excitation current becomes the trigger current for this switching circuit.

Therefore, this switching circuit also has the advantage that it does not require any separate trigger means. The embodiment shown in FIG. 1(d) corresponds to the power conversion circuit (fourth aspect of the present invention) according to claim 42. Diodes 40, 41
are the first and second non-controllable switches, and the transistor 36
, 37 correspond to the first and second controllable switches, transistors 38 and 39 connected in series correspond to the first arm pair, and diodes 19 and 20 correspond to the third and fourth non-controllable switches, respectively. Its effect is as follows. When the voltage of the capacitor 6 becomes the same as the voltage of the DC power supply 1 during the ON period of the transistors 36 and 3, the diode 19, which was previously off due to the reverse voltage, turns on. As a result, since the diode 19 and the transistor 36 act as a flywheel diode for the reactor 44, the voltage across the capacitor 6 no longer increases. The same applies to the transistors 37 and 38 and the diode 20fltl. In this way, the oscillating voltage of the capacitor 6 is made constant, and the oscillating voltage of the resonant circuit of the capacitor 6 and the reactor 44 is also made constant. The diode 40 also prevents the single diode and the transistor 38 from shorting the capacitor 6. Then, diode 41 connects transistor 39 and diode 2.
0 from shorting capacitor 6. Compared to the circuit of FIG. 4, transistors 47 and 48 are no longer needed, and diodes 40 and 41 are used instead.

Therefore, Tora. The driving means for two registers can be omitted. At the same time, these and other transistors 2
, 3, 14, and 15, so you don't have to worry about simultaneous conduction.
The oscillating voltage of the capacitor 6 can be made constant with a small number of parts and a simple circuit configuration. This kind of effect exists in the fourth invention, including this embodiment. (First effect) The first embodiment of the present invention using the conventional circuit shown in FIG. 4 will be described with reference to FIG. 15. On the other hand, an embodiment of the first invention using the fourth invention will be described with reference to FIG. 10.This circuit is a P.N channel type MOS.
- Since FETs are used, it is not possible to directly compare the two paths, but the first effect mentioned above can be seen. Then, even if the voltage of the capacitor 6 becomes higher than the voltage of the DC power supply 1 due to the turn-on delay of the diode 19 during the ON period of the transistors 36 and 39,
The resonance of the closed circuit including the capacitor 6, diodes 19 and 40, the DC power supply 1, and the diode 43 is controlled by the diode 4.
Similarly, even if the voltage of the capacitor 6 becomes larger than the voltage of the DC power supply l due to the turn-on delay of the diode 20 during the ON period of the transistors 37 and 38, the capacitor 6, the diode 42, and the DC power supply 1
The diode 41 prevents the resonance of the closed path including the diodes 41 and 20. As a result, the occurrence of surges due to the turn-on delay of diode 19 or 2o is reduced. (Second effect) The embodiment shown in FIG. 5 is an embodiment of the power conversion circuit of the first invention, and is a discharge lamp lighting circuit using the circuit shown in FIG. , 49 is a rectifier, 50 is a trigger diode, and 51 is a discharge lamp.
This invention uses a reactor 52 with two magnetically coupled coils. Regarding the direction of the magnetic coupling, the directions of the two back electromotive forces may be the same or opposite. The embodiment shown in FIG. 7 is a power conversion circuit in which transistors 2, 3, 14, and 15 are connected in a full bridge manner, and corresponds to the power conversion circuit according to claim 5 (first invention). Therefore, the transformer 353 has four secondary coils. Switch 11 etc. control starting and stopping of this circuit. When switch 11 is turned on, this circuit stops operating;
The embodiment of FIG. 8, in which this circuit is activated when the switch 11 is turned off, corresponds to the ignition circuit (first aspect of the invention) described in claim 22, and is one of the starting/stopping means described in claim 23. Examples are used. The ignition signal (corresponds to the start/stop signal in this case). > is input to terminal L4. This starting/stopping means includes transistors 54, 55, 26
etc., and is different from that of the circuit shown in Figure 1(b), but their basic operations are the same. The transistor 26, the resistor 56, etc. serve as the starting means in claim 23, and the transistors 55, 26, etc. serve as the operation stopping means in the same statement.
The transistor 54, transformer 5, etc. serve as the on/off detection means mentioned in the same description, and the transistor 54 etc. serve as the turn/off detection means mentioned in the same description.
Each corresponds to the off-assistance means.

However, this circuit starts operating when transistor 14 is turned on, and stops operating when transistor 15 is turned off. For this purpose, the transistor 54 etc.
The on/off state of the transistor 55 is detected via the transformer 5, and the transistor 55 is prevented from being turned on while the transistor 14 is on. This on/off detection method is performed by detecting the gate voltage of the transistor l4. Note that the two diodes 57 may be removed and the collector of the transistor 55 may be connected to the cathodes of the two Zener diodes 9 on the transistor 14 side as in the circuit shown in FIG. In this case, it is better to connect two diodes in anti-parallel connection as shown by the dotted line so that the collector current does not flow to the secondary coil 5b while the operation is stopped. Furthermore, even if there is a leakage current in the diode 19 while the operation is stopped, the leakage current will be transferred to the primary coils 58a, 5a, 2.
Since the current flows to ground through the next coil 5b, diode 57 and transistor 55, the capacitor 6 is not charged thereby. Furthermore, one end of the resistor 56 may be connected to the positive power terminal of the DC power supply 1 instead of the positive power terminal of the DC power supply 13. In that case, you will need to reduce the resistance value. In order to prevent current from flowing backward from the resistor 56 to the DC power supply 1, a diode may be connected between the two.

The embodiment shown in FIG. 9 uses P-channel type and N-channel type power MOS-PETs, and both gate voltages are common. Therefore, a transformer 31 having only one secondary coil can be used.

Switch 11 is a start switch, switch 5 is an operation stop switch, and resistor 60 is a start supplement. It is better to turn off switch 11 after startup. 11 load 7 is connected to reactor 4 via a transformer as in this circuit.
Even if it is equivalently connected in series with capacitor 6, it will not be horizontal.

The embodiment shown in FIG.
This is an example of the fourth invention). Two sets of P and N channel power MOS-FETs are connected in a full bridge. The diodes 6l and 62 may be present or absent. A resistor 60 is connected in parallel with a transistor 64 for activation. A resistor 60 may be connected between the source of the I-transistor 63 and ground. The embodiment shown in FIG. 11 is a DC-DC converter circuit using the circuit shown in FIG. The rectifier 66 and capacitor 67 are the power output section of this circuit.

The present inventor feeds back the output of the rectifier 65 to the power supply capacitor 69 in order to suppress the maximum absolute value of the voltage of the primary coil 68a to a predetermined value (for example, approximately the magnitude 9 of the input power supply voltage).

This circuit can be started and stopped by turning on and off the switch 11. For this purpose, a diode 71, a capacitor 72, resistors 73 and 74, and a tertiary coil 70d constitute a starting/stopping means. An example of the constants and parts used in this circuit is disclosed in Japanese Patent Application No. 2-1/1857. One use is shown in . The embodiment shown in FIG. 12 is a DC-DC converter circuit that applies the circuit shown in FIG. , is required if the Schmitt trigger circuit is not available. The number of turns of the secondary coil 68c is, for example, twice that of the secondary coil 68a. In other words, the inventor has suppressed the maximum absolute value of the voltage of the primary coil 6'8a to half the input power supply voltage.

The start/stop means formed by the switch 11, the diode 71, the capacitor 72, and the resistors 73 and 74 controls the first start and the last stop of this circuit. During the voltage control, the Schmitt trigger circuit repeatedly restarts and stops the circuit, keeping the output voltage constant. That is, when the output voltage reaches a predetermined value, the trigger circuit stops the oscillation operation of the inverter section of this circuit, and when it drops to another predetermined value, the trigger circuit starts the inverter section and starts oscillation. Let. The relationship between the two predetermined values is determined by the hysteresis characteristics of the Schmitt trigger circuit.

(Reference: Circuit shown in Fig. 20 of Japanese Patent Application Laid-Open No. 63-302217) The constants and examples of parts used in this circuit are given in Japanese Patent Application No. 2-14.
The embodiment shown in FIG. 3, which is disclosed in No. 857, corresponds to the power conversion circuit described in claim 11. In this circuit, a push-pull conversion circuit constituted by transistors 2 and 3 and a transformer 75 switches the voltage across a series circuit of a capacitor 6, a reactor 4, and a primary coil 5a. The present inventor connects the series circuit etc. in parallel to the secondary coil 75C, but these are connected to the primary coil 75a or 75b.
You can also connect them in parallel. Alternatively, they can be connected between both drains of transistors 2 and 3. In this embodiment, a push-pull conversion circuit was used to switch the voltage across the series circuit. As another method, a circuit using a half-bridge type conversion circuit or a full-bridge type conversion circuit <<Claim 12 or 1
The power conversion circuit described in 3) is also possible. The embodiment shown in FIG. 14 is a power conversion circuit using two DC power supplies 1 and 76 and two transistors 2 and 3, and claim 8
Or it corresponds to the power conversion circuit described in 9. transistor 2
The primary coil 77a and the primary coil 77a form two arms, and the primary coil 77I) and the transistor 3 form one arm. The embodiment shown in FIG. 15 is an embodiment of the power converter circuit of the first invention using the circuit shown in FIG. transistor 2
, 3, l4, 15, 47, and 48, one set of a resistor and a diode are connected in parallel. These are to lengthen each turn-on time while leaving each turn-off time unchanged to prevent short circuits. The embodiment shown in Figure 16 utilizes the circuit shown in Figure 1(d). The embodiment shown in FIG. 17, which is an ignition circuit, and which corresponds to the ignition circuit according to claim 43 or the power conversion circuit according to claim 42 is a modification of the circuit shown in FIG. 7, and is a power conversion circuit according to claim 6, etc. corresponds to The input side of the transformer 78 has two 1
It consists of secondary coils 78a and 78b. The transistor 2 and the primary coil 78a form one arm, and the transistor 14 and the primary coil 78,b form one arm. It may be connected to the drain side of transistor 3 or l5. One diode 8 may be connected to each primary coil as shown in the figure, or two antiparallel-connected diodes 8 may be connected in parallel to the primary coil 78a or 78b as shown by dotted lines.

The embodiment of FIG.
Corresponding to the power conversion circuit (first invention) according to claim 1 or 2, which is a one-cusp embodiment of the stopping means (second invention), this circuit is a modification of the circuit shown in FIG. 8. The circuit always starts when transistor 2 is turned on, and stops when transistor 3 turns off.

After the start/stop signal d2 instructs the operation to stop and the transistor 2 is turned off, the capacitor 6 vibrates slowly due to the action of the transformer 5, transistor 3, and its built-in diode, and the voltage converges to almost zero. do. On the contrary, the capacitor 21 converges to approximately the voltage of the DC power supply 13.

As a result, when the transistor 2 is turned on upon restart, the voltage across the capacitors 6 and 21 becomes a voltage that helps the restart.

If the two diodes shown by dotted lines in FIG. 18 are connected, the damped oscillation of the capacitor 6 as described above will not occur, and when the transistor 3 is turned off, its resonant current will no longer flow. Therefore, when restarting, the potential at the connection point between capacitors 6 and 21 becomes negative, making restart easier. If it is done when the current is zero, restarting and stopping the operation can also be done with zero current. This kind of effect exists in the second invention including this embodiment. The embodiment of FIG. 19 is based on the arm pair (third
This invention uses the switching circuit shown in Figure 1(c). There are three sets of two diodes 79 connected in antiparallel. These are used to obtain reverse bias voltage, secondary coil 5b,
In order to balance both output voltages of 5C, there is. The embodiment shown in FIG. 20 corresponds to the arm pair (third aspect of the invention) according to claim 36, which utilizes an embodiment of the switching circuit according to claim 31. Transistors 34, 8
0, 81, the diode 32, and the resistor 35 constitute the first three-sardine switching means according to claim 26. The embodiment shown in FIG. 21 corresponds to a switching circuit (third aspect of the present invention) described in claim 37 or 38.

The embodiment of FIG. 22 is a bridge circuit according to claim 41 (
9 which is a power conversion circuit using an embodiment of the third present invention) and an embodiment of the starting/stopping means (second present invention) according to claim 23 or 24. Each of the embodiments includes an arm pair (
This corresponds to the third aspect of the present invention).

The embodiment shown in FIG.
This corresponds to an arm pair according to claim 32 (third aspect of the present invention) using one embodiment of the switching circuit described above.

The embodiment shown in FIG.
This corresponds to the switching circuit described in the third aspect of the present invention.

The embodiment shown in FIG. 27 corresponds to the power conversion circuit (first invention) according to claim 5, 6 or 7, and the embodiment shown in FIG. 28 corresponds to the starting/stopping means according to claim 23 or 25. (Second
This is a power conversion circuit using an embodiment of the present invention). However, the value of the resistor 83 is very large, and the light emitting diode 84 does not emit light due to the current flowing through the resistor 83 alone. Only the charging current of the capacitor 82 causes the light emitting diode 84 to emit light. The current in resistor 85 helps turn transistor 2 off.

3, the embodiment of FIG. 29 is used in connection with the DC-DC converter circuit of FIG. 31. In both figures, the connection terminal c t.
In this example, 1 to ct3 have the same symbols connected to each other,
1 of 1,000 starting/stopping stages (second invention) according to claim 23
This corresponds to the ignition circuit (first invention) according to claim 22, which utilizes one embodiment of the arm pair (third invention) according to the embodiment and claim 36. Specifically, this ignition circuit is improved from the circuit shown in FIG. 1(b) by applying a reverse bias voltage to the gate of the transistor 15 in order to reduce the boiling current of the transistor 15 while the circuit is stopped. This is the ignition circuit. This modification is particularly effective when the circuit is operated in high temperature environments. Alternatively, it is effective in terms of noise resistance.

The ignition signal (corresponding to the start/stop I signal in this case) is input to the terminal L5. Capacitor 6 may be present or black. Transistors 34, 25, diodes 32, 33, resistor 35, etc. constitute a three-terminal switch. When this three-terminal switch is stopped, the DC power supply 1 is connected to the transistor L.
form a closed circuit that supplies gate reverse bias voltage to 5,
During its operation, the transformer 5 forms a closed circuit that inputs its output voltage to the transistor 15. These parts correspond to the switching circuit described in claim 26.

However, in the current path passing through the two Zener diodes 9, the diodes 33 and 57, and the transistor 25 on the lower side of the figure, in order to prevent these from shorting the DC power supply 1,
The sum of these ON voltages and Zener voltages must always be larger than the power supply voltage.

Activation of this circuit is performed as follows. During the ON period of the transistor 25, the current flowing through the DC power supply l, the secondary coil 5c, the resistor 35, the diode 57, and the transistor 25 excites the secondary coil 5C. Thereafter, transistor 25 is turned off and this excitation current passes through the three-terminal switch mentioned above and triggers transistor l5, which turns on completely due to the positive feedback action of transistor 15 and transformer 9. after that,
The transistor 86 and the like detect the on/off state of the transistor 15 by detecting the gate voltage of the transistor 15, and prevent the transistor 25 from turning on together with the transistor 26 and the like while the transistor 15 is on. In the DC-DC converter circuit shown in FIG. 31, transistors 93-96, transformer 107, etc. constitute an inverter circuit, and a Schmitt trigger circuit constituted by transistors 98-99, etc. stabilizes the DC output voltage. The outline of the operation of this inverter circuit is as follows. When the transformer 107 is saturated while the transistor 93 is on 1111, its magnetic permeability and its excitation inductance Le suddenly decrease as seen from the B-1-1 curve. On the other hand, compared to the degree of rapid decrease, the magnetic energy E
(=Le・i'/2> is not consumed rapidly and can be considered constant. According to the law of conservation of energy, in order to keep the energy constant, the transformer 107 itself reduces the current l of the primary coil 107a. However, the resistor 11 that detects the main current of the transistor 93
1, transistor 95, etc. act to turn off transistor 93 when its main current reaches a certain predetermined value, so that the current in primary coil 107a cannot flow through transistor 93 above that predetermined value.

Therefore, the transformer 107 acts to cause a current corresponding to the overheating amount to flow through the other primary coil 107b, etc. As a result, the voltage of the secondary coil 107b is reversed, and the diode built in the transistor 94 is turned on to function as a feedback diode. During this time, the drain voltage of transistor 94 decreases, transistor 93 is turned off, and transistor 94 is provided with a gate forward bias voltage.

Similarly, during the ON period of transistor 94, transistors 94, 96, etc. operate in a similar manner. In this way,
Transistors 93 and 94 are alternately turned on to perform inverter operation, and then rectify its AC output voltage. The DC output voltage rectified by O O is
A Schmitt trigger circuit centered around transistors 98 and 99 detects this and starts or stops the inverter circuit so that the voltage remains approximately constant. However, since this Schmitt trigger circuit cannot directly detect its DC output voltage, it uses a diode 1 to match its input voltage and its output voltage.
05, 106, resistors 121 to 123 and capacitor 12
7 on the same road.

The mechanism is as follows. The anode potential of the diode 105, that is, the connection terminal ct. 2, the cathode potential of the diode 106 is fixed to a constant potential by the diodes 105, 106, the resistor 123, and the capacitor 127. The relationship between the cathode potential of the diode 106, the base potential of the transistor 99, and the potential of the connection terminal ctl is just like the relationship between the fulcrum, the point of action, and the point of force in the "lever principle", and is approximately equal to the resistance ratio of the resistors 122 and 121. It is decided. Matching is performed in this way. The embodiment shown in FIG. 30 is also an improved ignition circuit in order to reduce the leakage current of the transistor l4 during stoppage of operation in the circuit shown in FIG. 8, and is used in combination with the DC-DC converter circuit shown in FIG. 31. In both figures, connection terminal cL1
~ct3, the same codes are connected. The ignition signal (corresponding to the start/stop signal in this case) is input to the terminal t6.

Transistor 9■ and the like constitute a constant voltage circuit.

The reason why the inventor introduced this into this embodiment is as follows.

Diode with built-in transistor l5, transistor 14
(!!If in the current path passing through the two Zener diodes 9, diodes 33, 57 and transistor 55, in order to prevent them from shorting the DC power supply 1, the voltage applied to these series circuits should be It may be made smaller than the sum of the ON voltage or Zener voltage.

Therefore, the inventor introduced into this embodiment a constant voltage circuit that outputs a voltage smaller than the total voltage. Incidentally, similarly to the circuit shown in FIG. 29, the transistor 34,
55, diodes 32, 33, 57 and resistor 35 etc. are 3
It forms a terminal switch. This 3-terminal switch is
While the operation is stopped, the DC power supply 1 forms a closed circuit that supplies gate reverse bias voltage to the transistor 14 via the constant voltage circuit, and during the operation, the transformer 5
4 is a closed circuit that inputs the output voltage. These parts correspond to the switching circuit described in claim 26.

Activation of this circuit is performed as follows. During the ON period of the transistor 55, the current flowing through the DC power supply 1, the diode built in the transistor 15, the secondary coil 5b, the resistor 35, the diode 57, the transistor 55, and the constant voltage circuit excites the secondary coil 5b. Thereafter, transistor 55 is turned off, and its excitation current is passed through the aforementioned three-terminal switch to transistor 1.
4, the transistor 14 is completely turned on by the positive 3m action of the transistor 14 and the transformer 5.
Turn on.

By the way, the present inventor uses a method in which the transistor 26 and the like detect the gate potential of the transistor 14 to detect whether the transistor 14 is on or off. When the transistor 14 is on, its gate potential is higher than or equal to the potential of the connection terminal ctl.

However, if the transistor l4 is off during the on/off operation of the transistors 14 and 15, the transistor 15 is on even though there is a slight time difference.

Therefore, the source potential of the transistor 14 is almost the same as the potential of the positive power terminal of the DC power supply 1. Moreover,
Since the transistor 14 is reverse biased, no matter how high the voltage of the capacitor 6 is, the gate position of the transistor 14 is close to the ground potential.

Therefore, if the values of the resistors 88 and 27 are appropriate, it is possible to detect whether the transistor l4 is on or off. However, it is also possible to connect one end of the resistor 88 to its source instead of its gate.

Also, the action of the resistor 87 is important. Below, examples of constants, parts used, etc. for both the circuits shown in Figures 30 and 31 are shown. Voltage of DC power supply 1... (+6) to +12 to (-1-16>volts Rated output voltage of DC-DC converter circuit...approximately +350 volts Transistors 14, 15...・Connect three 23K385 in parallel. (Directly connect all drains, all sources, and all gates.) 93, 94--IRF150 manufactured by Toshiba Corporation International Rectifier Co., Ltd. Ener Diode 9, 89, 102...RD11F101
......RD39F and above, manufactured by NEC Corporation...2SC2003 ...2SC3632 ...2SA1 1 54 ...2SA954 Diodes 8, 19, 20...1.2JG11 or 12
Jl-111 32, 33, 103-106...I Sl 588 or higher,
Manufactured by Toshiba Corporation 57...VO9G Rectifier 100...4 VO9G connected in a bridge.

Capacitor manufactured by Hitachi, Ltd. (unit: micro farad) 6...
...0.5 (Metallized film type) 92, 125...-470 126...0.01 127...1 124 -...2.2X5 ( (metallized film type) Resistance 24, 116...2 kilo ohm 27, 90,
108 (0.5 Watt), 1lO, 113-115
, 123 -... 1 kilo ohm 28, 87, 109... 4.7 kilo ohm 35... 1... 300 ohm 88... 100 kilo ohm 111 -... 0.05 ohm (10 watts) 112 ・-・200 ohm 117 ・1・2 ohm (adjustment required) 118, 12
0 122 - ・3.3 kilo ohm 119 ・・・7.5 kilo ohm 121 ・・Approx. 1.5 meg ohm (adjustment required) Ignition coil 16 ・・・ FL501AC (Remove the attached capacitor.

(manufactured by Toyodenso Co., Ltd.) Or, if the CM6120 (manufactured by Hitachi, Ltd.) is available, use a 4-terminal type and ground one end of the secondary coil, or use an additional ignition power source. gear nbu 17
It would be better to connect to

Transformer 5: Ferrite 1~・Core and bobbin...PQ2
6/25 Primary coil 5a manufactured by T'DK Co., Ltd. - Formal wire with a diameter of 0.4 mm - 2 PEW > 14 turns in L row 9 Secondary coils 5b, 5C...・Formal wire with a diameter of 0.3 mm, PPAV■l10- 160 turns 107: Ferrite core and bobbin...PQ3
Primary coils 107a, 107b manufactured by K Co., Ltd. 2/3 0'r D) --- Formal wire with a diameter of 0.4 mm, r' P. 10 turns of w with 4 trees in parallel, 10 secondary coils
7〈...Diameter O. 3mm formal wire, 369 turns of P rj W.

(see ゜゜) a) Ligoon intactance Make it as small as possible.

b〉Both transformers can be downsized. The embodiment shown in FIG. 32 is an ignition circuit having an electronic power distribution function for selecting at least one of the plurality of ignition coils 58
It is used in combination with the DC-DC converter circuit shown in the figure.

In both figures, connection terminal c. t. ] to ct3, the same symbols are connected. Ignition signal (start/stop + I2 in this case)
Equivalent to No. 6. ) is input to FA-J' t7.

The required number of combinations of the ignition coil 58, the transistors 130 to 132, and the switch 7-1-33'5 are connected together.All the ignition coils 58 are arranged in one shield gate 134 for convenience. A pair of transistors 1
30 and 131 form an AC switch. Transistor 132, switch 133, etc. forming a three-terminal switch control the AC switch. The set of ignition coils 58 whose switches 1, 3, and 3 are on will be affected.
It is also possible to use a triac for the AC switch mentioned above. By the way, the voltage of capacitor 6 is also applied to this circuit! There is a mechanism to limit the output voltage between 1 and zero and the above-mentioned output voltage of the C-DC converter circuit. About this, when the main voltage of the capacitor 6 becomes almost the same as its output voltage during the ON period of the transistors l4 and 129, the diode 19, which was previously off due to the reverse voltage, turns on, so ■The current of the next coil 58a is the transistor 1
29 and diode 9, the voltage of capacitor 6 remains unchanged.

In other words, the diode 19 and the transistor 129 act like a flywheel diode for the primary coil 58a.

On the other hand, when the voltage of the capacitor 6 becomes almost zero during the on period of the transistor 15, the diode 20 which was turned off due to the reverse voltage turns on, so that the current of the primary coil 58a becomes diode j: 2 0 begins to flow through the transistor 15, and the voltage of the capacitor 6 becomes ζ
It will remain at 1 and zero. Then, the mechanism of the starting and stopping means of this circuit is almost the same as that of the circuit shown in FIG. The 331st TA length embodiment has a power converter I circuit which limits the voltage of the capacitor 6 to between the voltage of the current power supply 13 and the voltage of the 11 current power supply 13.

Among the 12 ON recesses, the transistor 14 serves as a built-in diode and the transistor 129 acts like a fly-poil diode for the actuator 4. On the other hand, during the ON period of the transistors 15 and 136, the built-in diode of the transistor 29 and the transistor 136 play the same role for the reactor 4. The mechanism of the start/stop +h means of this circuit is basically the same as that of the same circuit in FIG. 32.

The embodiment shown in FIG. 34 is also a gravity conversion circuit in which the voltage of the capacitor 6 is limited between approximately zero and the voltage of the DC power supply 13, and its main circuit is basically the same as that shown in FIG. 32.

However, since the N-channel type transistor 15 and the P-channel type transistor 130 share the secondary coil 5C, it is possible to use the transformer 5 with a small number of coils.

The embodiment of the 35th UA is a lightning power conversion circuit constructed with pievora transistors, using an embodiment of the start-up, stop-and-start positive p-stage of the second invention and the circuit shown in FIG. 1(b).

The embodiment of FIG. 36 utilizes an embodiment of the start/stop 1L means of the second invention and the circuit of FIG.
After 9a, which is a power conversion circuit made up of transistors, we have shown an advanced example using a MOS FET as a normally-off, voltage-driven switching means, but the present invention is not limited to this, of course. Instead, FET. SI (electrostatic J4'4 type) transistor, S1 SIRISK, IGBT (Insulat-cd)
Gate nipotar Trans ist
．． or), or an F3IMOS composite element or the like may be used.

Reference material 1964, John Wiley and Sons Juice (
．． John Wiey & Sons,
Inc. ``Principles of Inverter Circuit'' published by )
Inverter Circuits〉”, translated book ・
1968, “Inverter Circuit 1: Latest Power Device Utilization Continuation Book” published by Coronasha Publishing, published by Ohmsha Publishing. Related technology Futsugi 14i Kaisho 5 2 1 0 4 6
3 No. 4 Same as above 54-3627 Same as above 5 7 1 6 8 0 6 No. 6 Same as above 59-5
No. 4772 Same as above No. 62-5019 (Japanese Patent Application No. 61-013938) Japanese Patent Application Publication No. 62-217017 Same as above No. 62-228815 PCT/JP 8 7/O O O 5 3 (W0
No. 87/04575) Japanese Patent Application Publication No. 6 3 3 0 2 2 1 7 Same as above 6
No. 3-294259 PCT/. J P8 7/0 0 5 9 5 Yuichi (W
No. 088/01804) }) CT/JP87/00612 (No. W088/01805) Japan Jitsugikai No. 163859, 1985 - Japanese Patent Publication No. 57-118438, same as above, No. 58-81332, No. 1-417416 Same as above No. 2-1609 Japanese Patent Application No. 1, 1999 No. 1995-299590 No. Japanese Patent Application No. 1-112845 Same as above No. 1-199326 No. 2-14857 as above

[Brief explanation of drawings]

FIG. 1(a) is a circuit diagram showing an embodiment of the power conversion circuit of the first invention, and FIG. 1(b) is a circuit diagram showing a one-cusp embodiment of the start/stop means of the second invention. FIG. 1(C) is a circuit diagram showing one embodiment of the ignition circuit of the first invention; FIG. 1(d) is a circuit diagram showing one embodiment of the switching circuit of the third invention; FIG. 2 is a circuit diagram showing an embodiment of the power conversion circuit of the present invention, FIG. 2 is a circuit diagram showing a conventional power conversion circuit, and FIG. 3 is a circuit diagram showing a conventional switching concave path. J, Fig. 4 is a circuit diagram showing a conventional power conversion circuit, Fig. 5 is a circuit diagram showing an embodiment of a discharge lamp lighting circuit using the power conversion circuit of the first invention, Figs. 7 is a circuit diagram showing a single-cusp embodiment of the power converter circuit of the first invention, and FIG. 8 is a circuit diagram showing a first embodiment using the single-cusp embodiment of the starting/stopping means of the second present invention. FIG. 9 is a circuit diagram showing one embodiment of the ignition circuit of the present invention; FIG. 9 is a circuit diagram showing one embodiment of the power conversion circuit of the first invention; FIGS. A circuit diagram showing one embodiment of the power conversion circuit of the fourth invention, FIG.
A circuit diagram showing one embodiment of the power conversion circuit of the first invention using one embodiment of the starting and stopping means of the present invention, Figures 1, 3, 14, and 15 are respectively from the first book. A circuit diagram showing one embodiment of the power conversion circuit of the invention, FIG. 16 is a circuit diagram showing one embodiment of the ignition circuit of the fourth invention, and FIG. 17 is a power conversion circuit of the first invention. 18th is a circuit diagram showing an embodiment of the power conversion circuit of the first invention using an embodiment of the activation/stopping means of the second invention; 19 and 20 respectively show a circuit B diagram showing one embodiment of the arm pair of the third invention, FIG. 21 shows a circuit port showing one embodiment of the switching circuit of the third invention, and FIG. 22 1 is a circuit showing an embodiment of the power conversion path of the first invention using an embodiment of the start/stop 1F means of the second invention and an embodiment of the blink IUI path of the third invention. Figures 23 to 25 are four-way diagrams showing one embodiment of the arm pair of the third invention, respectively; 2612 is a circuit diagram showing one embodiment of the switching circuit of the third invention; FIG. 27 is a circuit diagram showing an embodiment of the power conversion circuit of the first invention, and FIG. 28 is a circuit diagram showing a power conversion circuit using an embodiment of the start/stop +L means of the second invention. , 2917I, FIG. 30, and FIG. 32 respectively show an example of the start/stop t-stage of the second invention and the }th invention using a one-cusp embodiment of the arm pair of the third invention. FIG. 31 is a circuit diagram showing a part of a one-length embodiment of the power conversion circuit of FIG.
A circuit diagram showing a DC-DC converter circuit combined with each of the embodiments in the figures, Figures 33 and 34 respectively indicate the activation of the second invention.
This circuit shows a one-length embodiment of the E force conversion circuit of the first invention using a one-length embodiment of the fI; Fig. 351, /I, Fig. 36 is the 20th wooden branch nJ1
11 is a circuit diagram showing a power conversion circuit using a one-cusp embodiment of the starting f,'L11-means. (Explanation of symbols) ・1・・−reactor, 5−・・transformer
, 5a primary coil , 5E'1, 5(...
・Secondary coil 7...1 11 load, 10 Ignition coil 16a...Primary coil, 17 Ignition discharge lE gap, 18...Nolded case 31a...Primary coil, 3 lb...
Secondary coil, l19... Rectifier, 50
... tri-power diode, 51...discharge lamp
58 ignition coil, 5 8 a... primary coil 6
5, 66, 10o... Waterfall device 1 34... Shield case L 1-t7... Terminal c t. l~c t. ．． 3. Connection terminal 17 Applicant Toshiyasu Suzuki 18 Figure L Figure L (a) Figure 1 (b) Figure 1 (C) Atsushi 1 Figure (d) Figure 6 Figure 13 Figure 8 14 Figure 19 Figure 1; 10- 24 Figure 25 Figure 2'7 Figure 28 Figure 29 Figure 33 Figure 3 Toto Figure 35 Figure Atsushi 36 Figure

Claims (43)

[Claims] (1) A first inductance means, a capacitance means, and a first magnetically coupled inductance means.
The voltage across a series circuit in which the primary inductance means of the first transformer means are directly or equivalently connected in series is converted into a voltage at a plurality of normally-off circuits driven by the output signal of the first transformer means that is positively fed back. In a self-excited power conversion circuit that is switched by a driven switching means and one or more DC power sources, (2) An arm pair is formed between both power supply terminals of one DC power supply by the two switching means, and the series circuit is connected between one of the power supply terminals and a midpoint terminal of the arm pair. The power conversion circuit according to claim 1. (3) The power conversion circuit according to claim 2, wherein there are two primary inductance means, and each arm of the pair of arms includes one primary inductance means. (4) 2 magnetically coupled the first inductance means;
4. The power conversion circuit according to claim 2, wherein the power conversion circuit comprises two second inductance means, and one second inductance means is included in each arm of the arm pair. (5) Four arms each including one of the switching means are connected in a bridge between both power supply terminals of one of the DC power supplies, and the series circuit is connected between both midpoint terminals of the bridge connection circuit. The power conversion circuit according to claim 1. (6) There are two primary inductance means, and one primary inductance means is included in each of two arms that are not turned on at the same time among the four arms. 5. The power conversion circuit according to 5. (7) 2 magnetically coupled the first inductance means;
The power supply according to claim 5 or 6, characterized in that the power supply comprises two second inductance means, and one second inductance means is included in each of two arms that are not turned on at the same time among the four arms. conversion circuit. (8) The two DC power supplies are connected in series in the forward direction between both outer terminals of a pair of arms in which the two switching means are connected in series, and the series connection The power conversion circuit according to claim 1, characterized in that the circuits are connected. (9) The power conversion circuit according to claim 8, wherein there are two primary inductance means, and each arm of the pair of arms includes one primary inductance means. (10) The first inductance means is constituted by two second inductance means magnetically coupled, and each arm of the arm pair includes one second inductance means. 9. The power conversion circuit according to 8 or 9. (11) A push-pull type conversion circuit is constituted by one DC power supply, two switching means, and a second transformation means magnetically coupled with a plurality of inductance means, and both outputs of the second transformation means are configured. The power conversion circuit according to claim 1, wherein the series circuit is connected between terminals. (12) configuring a full bridge conversion circuit with one DC power supply, four switching means, and a second transformation means magnetically coupling a plurality of inductance means;
2. The power conversion circuit according to claim 1, wherein the series circuit is connected between both output terminals of the second transformer. (13) The second transformer means magnetically couples the one DC power supply, the two switching means, the two capacitance means, and the plurality of inductance means.
2. The power conversion circuit according to claim 1, wherein the power conversion circuit constitutes a bridge type conversion circuit, and the series circuit is connected between both output terminals of the second transformation means. (14) Claims 1 to 3, 5, 6, 8, and 9, characterized in that a load is connected in parallel to the first inductance means.
, 13. The power conversion circuit according to any one of , 11 to 13. (15) Claims 4 and 7, characterized in that a load is connected in parallel to at least one of the second inductance means.
Or the power conversion circuit according to 10. (16) The power conversion circuit according to any one of claims 1 to 15, characterized in that a load is connected in parallel to the capacitance means. (17) The series circuit is characterized in that the series circuit is a series circuit in which a load is directly or equivalently connected in series in addition to the first inductance means, the capacitance means, and the primary inductance means. 17. The power conversion circuit according to any one of 16 to 16. (18) The power conversion circuit according to any one of claims 1 to 17, wherein the constant voltage means is connected in parallel to the primary side of the first transformer means. (19) The power conversion circuit according to any one of claims 1 to 17, wherein the constant voltage means is connected in parallel to the secondary side of the first transformer means. (20) The power conversion circuit according to any one of claims 1 to 19, wherein the constant voltage means is constituted by two diodes connected in antiparallel. (21) The power conversion circuit according to any one of claims 1 to 19, characterized in that the constant voltage means is constituted by two Zener diodes connected in series in opposite directions. (22) The power conversion circuit according to any one of claims 1 to 21, wherein a primary coil of an ignition coil is used as the first inductance means. (23) Both ends of a series circuit in which a positive feedback means, an inductance means, and a capacitance means are directly or equivalently connected in series to generate each drive signal from the main current of each switching means and provide positive feedback to each switching means. In a self-excited power conversion circuit that switches voltage using a plurality of switching means and one or more DC power sources, the circuit is configured to provide a predetermined voltage across the series circuit in accordance with a start/stop signal given from the outside. activation means for turning on one or more of the switching means forming a circuit; operation stopping means for turning off the one or more switching means in accordance with the start/stop signal; and one or more of the switching means on/off detection means for detecting on/off of the switching means; and as long as the on/off detection means detects that the one or more switching means is on, the operation stopping means detects whether the one or more switching means is on. Or, a starting/stopping means characterized by being provided with a turn-off prevention means that prevents turning off a plurality of switching means. (24) The starting/stopping means according to claim 23, characterized in that the positive feedback means is a transformer means magnetically coupled with a plurality of inductance means. (25) The starting/stopping means according to claim 23, wherein the positive feedback means is a photoelectric conversion means that once converts electrical energy into optical energy and then converts it into electrical energy. (26) In a switching circuit in which a normally-off type first switching means is provided with a positive feedback means that generates a drive signal from its main current and positively feeds it back to the first switching means, the first switching means performs switching. When the first three-terminal switching means is brought into the first switching state, the driving signal is transmitted to the positive feedback means via the first three-terminal switching means. When positive feedback is applied to the first switching means to put the first three-terminal switching means into the second switching state, a reverse bias voltage is applied to the DC power supply through the first three-terminal switching means to the first switching means. A switching circuit characterized in that the switching circuit is supplied with a means. (27) The switching circuit according to claim 26, wherein the positive feedback means is a transformer means in which a plurality of inductance means are magnetically coupled. (28) The switching circuit according to claim 26, wherein the positive feedback means is a photoelectric conversion means that converts electrical energy into optical energy and then into electrical energy. (29) The first three-terminal switching means is connected to the control terminal side of the first switching means, and the DC power supply is connected to the main terminal side to which the drive signal is input between the first switching means and the control terminal. Claim 26, 2 characterized in that they are connected.
29. The switching circuit according to 7 or 28. (30) The first three-terminal switching means includes a bipolar first transistor in which the reverse bias voltage direction between the control terminal and the main terminal is the same as the reverse bias voltage direction between its base and emitter. , a resistor is connected between the collector and the base, a first non-controllable switch is connected in the opposite direction between the collector and the emitter, and a first constant voltage means is connected in parallel in the opposite direction to the emitter junction,
A three-terminal switching means having a second switching means connected to its base is used, and the collector, emitter, control terminal, and main terminal are connected in this order between both output terminals of the positive feedback means, and the DC power supply The main terminal, control terminal,
30. The switching circuit according to claim 29, wherein the first constant voltage means and the second switching means are connected in this order. (31) The switching circuit according to claim 30, wherein an emitter junction of a second transistor having a complementary relationship with the first transistor is used as the first constant voltage means, and the main terminal is connected between both the power supply terminals. , a control terminal, and the emitter and collector of the latter are connected in this order. (32) In the switching circuit according to any one of claims 29 to 31, the connection between the first switching means and the DC power supply is once disconnected, and both open ends thereof are connected by a third switching means, a second non-controllable switch is provided in parallel with the third switching means in the forward direction with respect to the DC power supply, and causing the positive feedback means to generate its drive signal from the main current of the third switching means; An arm pair characterized in that positive feedback is provided to the third switching means. (33) A second three-terminal switching means for switching the reverse bias voltages of the first and third switching means is made the same, and a second three-terminal switching means is also introduced on the third switching means side, and the second three-terminal switching means When the three-terminal switching means is placed in the first switching state, the positive feedback means causes the drive signal to be positively fed back to the third switching means via the second three-terminal switching means, and the second three-terminal switching means is switched to the second three-terminal switching state. 33. When the switching means is placed in the second switching state, the DC power source supplies a reverse bias voltage to the third switching means via the second three-terminal switching means. arm vs. (34) The second three-terminal switching means is a bipolar switching means in which the reverse bias voltage direction between the control terminal and the main terminal of the third switching means is the same as the reverse bias voltage direction between its base and emitter. There is a transistor No. 3, a resistor is connected between its collector and base,
A third non-controllable switch is connected in the opposite direction between the collector and emitter, a second constant voltage means is connected in parallel in the opposite direction to the emitter junction, and a fourth switching means is connected to the base of the third non-controllable switch. A terminal switching means is used to connect the collector, emitter, control terminal and main terminal of the third transistor of the third transistor between both output terminals for the third switching means of the positive feedback means. The main terminal, the control terminal, the second constant voltage means, and the fourth switching means of the third switching means are connected in this order between both power supply terminals of the DC power supply. 34. The arm pair according to claim 33. (35) In the arm pair according to claim 34, the second
As a constant voltage means, an emitter junction of a fourth transistor having a complementary relationship with the third transistor is used, and the main terminal, control terminal, and emitter and collector of the third switching means are connected between the two power supply terminals. A pair of arms characterized in that they are connected in this order. (36) The switching circuit according to any one of claims 26 to 31, wherein the first and third switching means are connected in series so that the third switching means is located on the opposite side of the main terminal, An arm pair characterized in that the positive feedback means generates a drive signal from the main current of the third switching means, and positive feedback is made to the third switching means. (37) The DC power supply is connected to the control terminal side of the first switching means, and the three-terminal switching means is connected to the main terminal side to which the drive signal is input between the first switching means and the control terminal. The switching circuit according to claim 26, 27 or 28, characterized in that: (38) The first three-terminal switching means includes a bipolar first transistor in which the reverse bias voltage direction between the control terminal and the main terminal and the reverse bias voltage direction between its base and emitter are different; A resistor is connected between the collector and the base, a first non-controllable switch is connected in the reverse direction between the collector and the emitter, a first constant voltage means is connected in parallel to the emitter junction in the reverse direction, and the base The control terminal, the main terminal, the emitter, and the collector are connected in this order between both output terminals of the positive feedback means using a three-terminal switching means in which a second switching means is connected to the The second
38. The switching circuit according to claim 37, wherein the switching means, the first constant voltage means, the main terminal, and the control terminal are connected in this order. (39) The switching circuit according to claim 38,
As the first constant voltage means, an emitter junction of a second transistor having a complementary relationship with the first transistor is used, and the collector, emitter, and
A switching circuit characterized in that a main terminal and a control terminal are connected in this order. (40) The switching circuit according to claim 37, 38 or 39, wherein a third switching means is connected in series to the first switching means, and the positive feedback means is driven by the main current of the third switching means. An arm pair characterized in that a signal is generated and fed back positively to the third switching means. (41) A bridge circuit in which the arm pair according to any one of claims 32 to 36 and 40 and the arm pair according to any one of claims 32 to 36 and 40 are connected in parallel. (42) a first pair of arms and a first non-controllable switch;
A second arm pair in which first and second controllable switches and second non-controllable switches are connected in series in this order is bridge-connected to a DC power supply, and the first non-controllable switch and the second controllable switch are connected in series. between the connection point and the connection point of the second controllable switch and the non-controllable switch;
A fourth non-controllable switch is connected in series, and a connection point between the third and fourth non-controllable switches and the first non-controllable switch are connected in series.
capacitance means is connected between the midpoint terminals of the pair of arms, and the connection point of the third and fourth non-controllable switches and the second
An inductance means or
A power conversion circuit characterized by a series circuit of a load and an inductance means, or a series circuit in which one or the other is connected. (43) The power conversion circuit according to claim 42, wherein a primary coil of an ignition coil is used for either one of the ignition coils.